CN102342008B - 用于功率转换器的控制器 - Google Patents
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- CN102342008B CN102342008B CN201080010436.9A CN201080010436A CN102342008B CN 102342008 B CN102342008 B CN 102342008B CN 201080010436 A CN201080010436 A CN 201080010436A CN 102342008 B CN102342008 B CN 102342008B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0083—Converters characterised by their input or output configuration
- H02M1/0085—Partially controlled bridges
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Rectifiers (AREA)
- Dc-Dc Converters (AREA)
Abstract
一种可与具有第一和第二同步整流器开关的桥式整流器一起运用的用于功率转换器的控制器及其操作方法。在一个实施例中,控制器包括放大器(510),该放大器被配置成实现用于第一同步整流器开关SR的接通延迟。控制器也包括放电开关Q3,该放电开关Q3具有分别耦合到第一同步整流器开关SR的栅极和源极端子的第一和第二切换端子并且配置成对第一同步整流器开关SR的栅极到源极电容进行放电以实现其关断。
Description
本申请要求于2009年1月19日提交的标题为“ControllerforaSynchronousRectifierSwitchandPowerConverterEmployingtheSame”的第61/145,657号美国临时申请的权益,该申请全文在此通过引用并入本文。
技术领域
本发明主要涉及功率电子设备,并且更具体而言,本发明涉及用于功率转换器的控制器及其操作方法。
背景技术
切换模式的功率转换器(也称为“功率转换器”或者“调控器”)是将输入电压波形转换成指定输出电压波形的功率供应或者功率处理电路。AC-DC功率转换器将交流(“ac”)输入电压转换成直流(“dc”)输出电压。与功率转换器关联的控制器通过控制其中运用的功率开关的导通时段来管理其操作。一般而言,控制器在反馈回路配置(也称为“控制回路”或者“闭合控制回路”)中耦合于功率转换器的输入与输出之间。
为了产生dc输出电压,功率转换器经常运用二极管以对ac电压进行整流。整流器件可能由于在二极管两端的前向电压降而在功率转换器中(尤其是在产生五伏或者更少的输出电压的功率转换器中)引入功率损耗分量。具有相对低的前向电压降的肖特基二极管经常运用于低电压功率转换器应用中以减少二极管前向电压降。然而,诸如肖特基二极管之类的无源整流器件通常不能实现少于约0.35伏(“V”)的前向电压降并且通常不能维系大于约60伏的反向电压,由此限制功率转换器的转换效率。
为了实现可接受的效率水平,功率转换器经常运用可以具有少于约0.1伏前向电压降的整流器件。为了提供功率损耗的这类减少,提供电阻性电压降的有源开关或者有源半导体开关(诸如金属氧化物半导体场效应晶体管(“MOSFET”))常用来取代二极管。然而,必须与ac电压(例如在向功率转换器的输入的两端产生的ac电压)的周期波形同步地将有源半导体开关周期性地驱动成导通和非导通模式或者状态。有源半导体开关可以由此避免无源整流器件中固有的较高前向电压降。
用有源半导体开关取代二极管而产生的设计问题在于需要为其提供如下驱动信号,该驱动信号与功率转换器的操作准确同步以控制有源半导体开关的导通和非导通模式或者状态,并且该驱动信号避免与包括二极管的其它半导体开关有导通重叠。在功率转换器中的取代二极管的有源半导体开关一般称为“同步整流器”或者“同步整流器开关”。
常规的ac到dc功率转换器运用桥式整流器以将ac正弦输入电压波形(诸如ac市电产生的输入电压波形)变换成整流的正弦波形。在桥式整流器之后,功率因子纠正(“PFC”)电路将整流的正弦波形转换成dc电压电平比正弦输入电压的峰电压更高的dc波形。桥式整流器通常由四个二极管构造而成。由于二极管的前向电压降,所以二极管产生大量功率损耗。
无桥升压PFC电路可以用来解决与二极管的前向电压降关联的功率损耗问题。因而减少二极管的导通损耗。然而,无桥升压PFC电路具有限制它在低成本、高容量电路中的应用的若干明显其余问题。在电路的ac侧上,电路引入的两个电感器的结构使输出电压相对于输入线电压浮动。因而,电路产生高等级的电磁干扰(“EMI”)噪声。升压电感器在ac侧上的位置使得难以感测ac线电压和电感器电流,并且该控制是比用于耦合到桥式整流器的简易升压PFC电路或者升压功率转换器的控制方案更复杂的过程。因而,无桥升压PFC电路的应用一直有限。
于2000年5月9日向Jansen授权的标题为“CircuitSimulatingaDiode”的第6,060,943号美国专利和于2002年10月22日向Jansen授权的标题为“CircuitSimulatingaDiode”的第6,469,564号美国专利涉及如下电路,该电路执行二极管的功能以在一个方向上导通电流而前向电压降为低,但是在另一方向上阻止电流以产生改进的整流功能,这两篇专利在此都通过引用结合于本文中。当在电路的指定正极端子的电压高于在指定负极端子的电压时,前向电流流动。当在这些指定端子的电压的极性反转时,电流中断。
然而,这些方法中的每种方法提供对同步整流器在诸多应用中的使用进行限制或者以别的方式对其不利的效率和/或成本限制。因而,在本领域中需要的是一种避免现有技术中的缺陷的可与功率转换器中的同步整流器一起运用的控制器和有关方法。
发明内容
主要通过本发明的有利实施例来解决或者避免这些和其它问题并且主要通过这些实施例来实现技术优点,这些实施例包括一种可与具有第一和第二同步整流器开关的桥式整流器一起运用的用于功率转换器的控制器及其操作方法。在一个实施例中,控制器包括放大器,该放大器被配置成启用用于第一同步整流器的接通延迟。控制器也包括放电开关,该放电开关具有分别与第一同步整流器开关的栅极和源极端子耦合的第一和第二切换端子,并且配置成对第一同步整流器开关的栅极到源极电容进行放电以启用其关断。
前文已经相当广义地概括本发明的特征和技术优点以便可以更好地理解下文对本发明的具体描述。下文将描述形成本发明权利要求主题的本发明附加特征和优点。本领域技术人员应当理解,可以容易利用公开的概念和具体实施例作为用于修改或者设计用于实现本发明相同目的的其它结构或者过程的基础。本领域技术人员也应当认识到,这样的等效构造并不脱离如在所附权利要求书中阐述的本发明精神实质和范围。
附图说明
为了更完整理解本发明,现在参照与以下附图结合的下文描述,其中:
图1图示了提供本发明原理应用环境的功率转换器的一个实施例的示意图,该功率转换器包括耦合到升压功率转换器的桥式整流器;
图2图示了根据本发明原理构造的功率转换器的一个实施例的示意图,该功率转换器包括桥式整流器中的两个同步整流器开关;
图3图示了用第一和第二同步整流器开关的重叠栅极驱动信号产生的波形的图形表示;
图4图示了用第一和第二同步整流器开关的栅极驱动信号产生的波形的图形表示;
图5图示了根据本发明原理构造的用于开关的控制器的一个实施例的示意图;
图6图示了根据本发明原理构造的功率转换器的一个实施例的示意图,该功率转换器包括由第一和第二同步整流器开关形成的桥式整流器;
图7图示了根据本发明原理的用第一和第二同步整流器开关的非重叠栅极驱动信号产生的波形的图形表示;
图8图示了如下图解,该图解示范了在参照图6介绍的第一与第二同步整流器开关之间的空载时间;并且
图9图示了根据本发明原理构造的用于第一和第二同步整流器开关的控制器的一个实施例的示意图。
在不同图中的对应标号和符号除非另有指明则一般指代对应部分并且可以在第一实例之后不重新加以描述以求简洁。绘制附图以图示示例实施例的相关方面。
具体实施方式
下文具体讨论本示例实施例的实现和运用。然而应当理解,本发明提供可以在广泛的各种具体背景中实施的许多可应用的发明概念。所讨论的具体实施例仅举例说明用于实现和运用本发明的具体方式而不限制本发明的范围。
将在具体背景(即一种用于开关(诸如具有其接通被延迟的同步整流器开关)的控制器及其操作方法)中参照示例实施例描述本发明。尽管将在功率转换器的环境中描述本发明的原理,但是可以从诸如功率放大器或者电机控制器之类的控制器中受益的任何应用也在本发明的广义范围内。此外,尽管将参照包括栅极、源极和漏极端子的场效应晶体管描述本发明的原理,但是该原理同样适用于具有控制和切换端子的任何类型的开关。
现在参照图1,图示了提供本发明原理应用环境的功率转换器(例如ac到dc功率转换器)的一个实施例的示意图,该功率转换器包括耦合到升压功率转换器120(也称为“升压功率链(boostpowertrain)”)的桥式整流器110。桥式整流器110包括多个桥式二极管D1、D2、D3、D4,这些二极管配置为四个二极管的桥式整流器,该桥式整流器耦合到ac输入电压源(称为“V1”)以产生作为用于升压功率转换器120的输入电压来工作的整流的波形。升压功率转换器120包括升压电感器L1和升压功率开关Q1。控制图1中图示为n沟道MOSFET的升压功率开关Q1以按照占空比D间歇导通以在升压电感器L1中产生按照互补占空比1-D向升压二极管D5间歇导通的电流。升压二极管D5对电感器电流进行整流以在输出滤波器电容器C1两端产生dc电压。电阻器RLOAD表示连接到ac到dc功率转换器的输出的负载。
图1中所示功率转换器中的主要功率损耗源是桥式二极管D1、D2、D3、D4的前向电压降。为了解决这一功率损耗问题,桥式二极管D1、D2、D3、D4可以由作为前向电压降比无源二极管明显更小的同步整流器或者同步整流器开关来工作的有源开关或者有源半导体开关取代。在使用有源开关形成同步整流器的设计中的一个问题在于在成对同步整流器之间的交叉导通,由此带来又一功率损耗问题。
现在参照图2,图示了根据本发明原理构造的功率转换器(例如ac-dc功率转换器)的一个实施例的示意图,该功率转换器包括在桥式整流器中的第一和第二同步整流器开关SR1、SR2。常规同步整流器布置不能用来取代桥式整流器中的二极管,因为常规同步整流器布置(例如参见Jansen的第6,469,564号美国专利)使用二极管和晶体管基极-发射极p-n结作为两个电压感测输入以确定用作同步整流器的有源开关何时启用导通。因而,常规同步整流器布置主要使用于运用单个二极管时,但是在耦合到另一有源开关时常规同步整流器布置受功率转换器效率下降所困扰。当使用常规同步整流器布置来取代桥式整流器中的两个或者更多二极管(如图1中所示顶部的两个二极管、底部的两个二极管或者上支路二极管和下支路二极管)时,在启用两个二极管以导通时的短暂时间段期间出现两个二极管之间的交叉导通。当***作为二极管的一个同步整流器开关接通而***作为***作为二极管的另一同步整流器开关关断时,同步整流器开关的二极管和基极发射极p-n结的不匹配以及二极管的反向恢复充电造成用于用作同步整流器开关的两个有源开关(例如MOSFET)的重叠控制端子信号(例如栅极驱动信号)或者至少未分离的栅极驱动信号。
现在参照图3,图示了使用第一和第二同步整流器开关SR1、SR2的重叠栅极驱动信号产生的波形的图解。第一和第二同步整流器开关SR1、SR2在串联布置中耦合,其中当两个同步整流器开关SR1、SR2同时启用导通时产生击穿电流。在图3的顶部中,图示了由于二极管交叉导通所致的针对50赫兹(“Hz”)输入ac电压而言的每10毫秒(“ms”)的输入电流尖峰310。在图3的中部和底部中,图示了启用第一和第二同步整流器开关SR1、SR2的导通而在它们的高栅极驱动电压电平之间无分开时段(也称为栅极驱动信号重叠320)的栅极驱动波形。因而,输入电压源在每半个线循环内短暂耦合到短路,这在来自输入电压源的电流中产生尖峰。这样的电路操作一般造成高等级的电磁干扰(“EMI”)并且增加桥式整流器的导通损耗。
现在参照图4,图示了使用第一和第二同步整流器开关SR1、SR2的栅极驱动信号产生的波形的图解。如图4中所示,示出了针对常规同步整流器设计的如下重叠时段,在该重叠时段期间,两个同步整流器开关SR1、SR2启用导通(第一同步整流器栅极驱动信号410和第二同步整流器栅极驱动信号420产生重叠430),由此在来自输入电压源的输入电流中产生尖峰。通过根据本发明的原理用第一和第二同步整流器开关SR1、SR2取代图1的桥式整流器的二极管D2、D4,可以大量减少其间交叉导通。
现在参照图5,图示了根据本发明原理构造的用于开关(例如同步整流器开关SR)的控制器的一个实施例的示意图。图5中所示桥式整流器包括对同步整流器开关SR的栅极到源极电容进行充电或者放电的元件。对栅极到源极电容进行充电和放电一般阻碍将用作同步整流器开关SR的有源开关(诸如MOSFET)的导通性快速启用或者禁用。将同步整流器开关SR的导通性快速禁用对于消除(或者基本上消除)其与功率转换器中的另一有源开关的交叉导通而言是重要的。
用于同步整流器开关SR的控制器包括具有根据多个串联耦合二极管D6、D15产生的阈值电压的放大器510。控制器还包括放电开关Q3(例如pnp晶体管),该开关具有耦合于同步整流器开关SR的源极与栅极端子之间的切换端子以及耦合到放大器510的输出的控制端子。放电开关Q3由发射极(称为“e”)、基极(称为“b”)和集电极(称为“c”)端子形成。同步整流器开关SR由源极(称为“s”)、栅极(称为“g”)和漏极(称为“d”)端子形成。放电开关Q3的发射极连接到同步整流器开关SR的栅极,而放电开关Q3的集电极连接到同步整流器开关SR的源极。因而,当同步整流器开关SR的体二极管D30反向偏置时,节点K的电压高于节点A的电压,并且放大器开关(例如npn晶体管)Q12由于电流从偏置电压源VCC经过电阻器R16流入它的基极中而接通。充电开关(例如晶体管)Q11关断而放电开关Q3接通。接通其发射极和集电极端子分别连接到同步整流器开关SR的栅极和源极端子的放电开关Q3使得同步整流器开关SR的栅极电荷被快速放电,由此启用同步整流器开关SR的快速关断。因此,耦合到同步整流器开关SR的端子的放电开关Q3被配置成响应于同步整流器开关SR的体二极管D30的反向偏置条件而实现其栅极到源极电容的快速放电。
当同步整流器功率开关SR的体二极管D30前向偏置,并且节点K的电压变为充分低于节点A的电压时,放大器开关Q12关断。二极管D6、D15提供比节点A电压更低的节点K电压阈值以关断放大器开关Q12,由此引入用于同步整流器开关SR的接通延迟。关断放大器开关Q12使电阻器R14能够向充电开关Q11的基极提供来自偏置电压源VCC的偏置电流,该充电开关由此接通。接通充电开关Q11提供了从偏置电压源VCC经过二极管D12到同步整流器开关SR的栅极的正偏置电压,从而将它启用导通。注意节点A的电压应当高于节点K的电压加上阈值电压Vthreshold以使同步整流器开关SR接通。通过使节点A的电压高于节点K的电压加上阈值电压Vthreshold来产生接通延迟。因此,耦合到同步整流器开关SR的端子的充电开关Q11被配置成响应于同步整流器开关SR的前向偏置条件在延迟之后对其栅极到源极电容进行充电。包括图5中所示其余电路元件(诸如电阻器R12、R15、R17)以提供用于控制器可靠操作的恰当电压和电流水平,从而施加针对具体器件的考虑(诸如用于恰当控制器操作的所需电压和电流水平)。
对于图5中所示控制器而言,节点A的电压VA等于节点M的电压VM减去放大器开关Q12的基极-发射极p-n结前向电压降。节点K的电压VK是节点M的电压VM减去串联耦合二极管D15、D6的p-n结前向电压降之和。电压Vthreshold是同步整流器开关SR的阈值电压。电压VbeQ12是放大器开关Q12的基极-发射极电压。电压VfD15是二极管D15的前向二极管电压。电压VfD6是二极管D6的前向二极管电压。
VA=VM-VbeQ12(1)
VK=VM-VfD15-VfD6(2)
VA=VK+Vthreshold(3)
Vthreshold=VfD15+VfD6-VbeQ12(4)
对比Jansen在第6,060,943号美国专利和第6,469,564号美国专利中描述的电路,这里介绍的用于同步整流器开关SR的控制器具有串联耦合二极管D6、D16生成的优选范围为一微秒(“μs”)至四毫秒(“ms”)的接通延迟。在Jansen描述的电路中,当节点A的电压高于节点K的电压时,电流从节点A流向节点K。然而在图5中,节点A的电压应当充分高于节点K的电压加上阈值电压Vthreshold以使同步整流器开关SR接通,因此生成接通延迟。
现在参照图6,图示了根据本发明原理构造的功率转换器的一个实施例的示意图,该功率转换器包括由第一和第二同步整流器开关SR1、SR2形成的桥式整流器。在图6中所示桥式整流器中,图1中所示桥式整流器的两个底部二极管由耦合到偏置电压源VCC的第一和第二同步整流器开关SR1、SR2和关联的控制器取代。耦合到偏置电压源VCC的第一和第二同步整流器开关SR1、SR2和关联的控制器各自被图示并且在上文中参照图5中所示同步整流器开关SR有所描述。第一和第二同步整流器开关SR1、SR2中的每个同步整流器开关的接通被延迟,但是通过相应栅极到源极电容的迅速放电来加速其关断。由此产生在第一和第二同步整流器开关SR1、SR2的栅极之间的空载时间,并且基本上消除交叉导通。因而,实质上衰减了图3中所示输入电流尖峰。
现在参照图7,图示了根据本发明原理的用第一和第二同步整流器开关SR1、SR2的非重叠栅极驱动信号产生的波形的图解。第一和第二同步整流器开关SR1、SR2在电路布置中耦合,其中如果两个同步整流器开关SR1、SR2同时启用导通则将产生击穿电流。在图7的顶部中,由于二极管交叉导通所致的输入电流尖峰不再可见(参见波形710)。在图7的中部和下部中,图示了栅极驱动波形而在它们的高电压状态之间无重叠(例如参见区域720)。因而,未向输入电压源呈现短暂周期短路,由此消除不必要的高等级电磁干扰并且减少桥式整流器的导通损耗。
现在参照图8,图示了如下图解,该图解示范在参照图6介绍的第一与第二同步整流器开关SR1、SR2之间的空载时间。该图解分别图示了用于第一和第二同步整流器开关SR1、SR2的栅极驱动信号的栅极驱动波形810、820,这些波形示范了第一同步整流器开关SR1的快速关断和第二同步整流器开关SR2的有延迟的接通。因此,在这里介绍的控制器中包括第二二极管(与二极管D6串联的二极管D15),该第二二极管检测在开关(例如第一同步整流器开关SR1)两端的前向电压降。在用于开关(例如第一同步整流器开关SR1)的控制器中包括放电开关Q3、二极管D12和电阻器R12、R15以对其栅极电荷快速放电,由此启用开关的快速关断。
现在参照图9,图示了根据本发明原理构造的用于第一和第二同步整流器开关SR1、SR2的控制器的一个实施例的示意图。控制器包括分别耦合到第一和第二同步整流器开关SR1、SR2的栅极端子的第一和第二锁开关Q24、Q25,从而提供用于防止第一和第二同步整流器开关SR1、SR2交叉导通的又一机制。第一和第二锁开关Q24、Q25形成用于第一和第二同步整流器开关SR1、SR2的互锁电路,其中锁开关之一(例如第一锁开关Q24)的切换端子耦合到另一锁开关(例如第二锁开关Q25)的控制端子。因而,第一锁开关Q24的栅极端子交叉耦合到第二锁开关Q25的漏极端子,而第二锁开关Q25的栅极端子交叉耦合到第一锁开关Q24的漏极端子。通过交叉耦合第一和第二锁开关Q24、Q25的栅极和漏极端子,在同一时间仅能接通一个(即仅一个可以维系它的漏极端子的有效正电压)。然而,交叉耦合第一和第二锁开关Q24、Q25的栅极和漏极端子仍然允许两个开关同时关断。图9中所示控制器的其余部分由参照图5图示和描述的类似部件形成。
因此,这里已经介绍用于开关的控制器。在一个实施例中,用于开关(例如同步整流器开关)的控制器包括如下放大器(例如耦合到偏置电压源),该放大器包括配置成为其产生输入偏移电压的多个串联耦合二极管和如下放电开关,该放电开关具有分别耦合到开关的栅极和源极端子的第一和第二切换端子以及耦合到放大器的输出的控制端子。放电开关被配置成对开关的栅极到源极电容进行放电。在有关实施例中,开关的栅极端子经过电阻器耦合到偏置电压源,和/或开关的栅极端子经过充电开关耦合到偏置电压源,其中充电开关的控制端子耦合到放大器的输出。放大器也可以包括如下放大器开关,该放大器开关具有耦合到放大器的输入并且经过多个串联耦合二极管耦合到开关的漏极端子的基极端子、耦合到开关的源极端子的发射极端子以及耦合到放大器的输出的集电极端子。多个串联耦合二极管产生的输入偏移电压被配置成引起用于开关的接通延迟(例如范围为一微秒至四毫秒)。当与多个开关一起运用时,控制器还可以包括如下互锁电路,该互锁电路包括分别与开关的栅极端子和另一开关的栅极端子耦合的第一锁开关和第二锁开关,其中第一锁开关的切换端子(例如漏极端子)耦合到第二锁开关的控制端子(例如栅极端子)。
在一个有关实施例中,这里已经介绍一种可与具有第一和第二同步整流器开关的桥式整流器一起运用的用于功率转换器的控制器及其操作方法。控制器包括放大器,该放大器包括放大器开关和配置成产生阈值电压的多个串联耦合二极管,以启用用于第一同步整流器开关的接通延迟。接通延迟基于在第一同步整流器的源极端子的电压,该电压比在第一同步整流器开关的漏极端子的电压高出阈值电压。此外,放大器开关被配置成当在源极端子的电压比在第一同步整流器开关的漏极端子的电压高出阈值电压并且第一同步整流器开关的体二极管前向偏置时被关断,由此使充电开关向第一同步整流器开关的栅极端子提供正偏置电压以使其导通。
控制器也包括放电开关,该放电开关具有分别耦合到第一同步整流器开关的栅极和源极端子的第一和第二切换端子以及耦合到放大器的输出的控制端子。放电开关被配置成对第一同步整流器开关的栅极到源极电容进行放电以启用其关断。放电开关被配置成在第一同步整流器开关的体二极管反向偏置时接通并且对第一同步整流器开关的栅极到源极电容进行放电。此外,放大器被配置成启用用于第一同步整流器开关的接通延迟,并且放电开关被配置成启用第一同步整流器开关的关断以基本上消除与第二同步整流器开关的交叉导通。此外,第一同步整流器开关的栅极端子经过充电开关耦合到偏置电压源,其中充电开关的控制端子耦合到放大器的输出,并且第一同步整流器开关的栅极端子经过电阻器耦合到偏置电压源。根据第一和第二同步整流器开关,互锁电路包括分别与第一和第二同步整流器开关的栅极端子耦合的第一锁开关和第二锁开关,其中第一锁开关的切换端子(例如漏极端子)耦合到第二锁开关的控制端子(例如栅极端子)。
本领域技术人员应当理解,仅出于示例目的而提出一种同步整流器功率开关及其有关操作方法的前述实施例。此外,各种功率转换器拓扑也在本发明的广义范围内。尽管已经在回扫功率转换器的环境中描述同步整流器功率开关,但是它也可以应用于其它***,诸如但不限于功率放大器和电机控制器。
为了更好地理解功率转换器,参见纽约州纽约市的VanNostrandReinhold公司的RudolphP.Severns和GordonBloom的“ModernDC-to-DCPowerSwitch-modePowerConverterCircuits”(1985)和Addison-Wesley的J.G.Kassakian、M.F.Schlecht和G.C.Verghese的“PrinciplesofPowerElectronics”(1991)。前述参考文献通过引用全文并入本文。
另外,虽然已经具体描述本发明及其优点,但是应当理解可以对其进行各种改变、替换和变更而不脱离如所附权利要求书限定的本发明精神实质和范围。例如,可以用不同方法实施并且用其它过程取代上文讨论的诸多过程或者其组合。
另外,本申请的范围并不限于在说明书中描述的过程、机器、制造产品、物质组成、装置、方法和步骤的具体实施例。如本领域普通技术人员将根据本发明的公开内容容易理解的那样,可以根据本发明利用执行与这里描述的对应实施例基本上相同的功能或者实现基本上相同的结果的、当前存在或者以后将开发的过程、机器、制造产品、物质组成、装置、方法或者步骤。因而,所附权利要求书旨在于在它们的范围内包括这样的过程、机器、制造产品、物质组成、装置、方法或者步骤。
Claims (20)
1.一种可与具有第一同步整流器开关和第二同步整流器开关的桥式整流器一起运用的控制器,包括:
放大器,被配置成使用多个串联耦合的二极管启用用于所述第一同步整流器开关的接通延迟;
放电开关,具有经由充电开关耦合到所述放大器的输出的控制端子以及分别耦合到所述第一同步整流器开关的栅极和源极端子的第一切换端子和第二切换端子并且配置成对所述第一同步整流器开关的栅极到源极电容进行放电以启用其关断;以及
互锁电路,具有分别耦合到所述第一同步整流器开关的所述栅极端子和所述第二同步整流器开关的栅极端子的第一锁开关和第二锁开关,其中所述第一锁开关的切换端子交叉耦合到所述第二锁开关的控制端子,所述第二锁开关的切换端子交叉耦合到所述第一锁开关的控制端子,并且所述第一锁开关并联至所述放电开关。
2.根据权利要求1所述的控制器,其中所述放大器被配置成产生阈值电压以启用用于所述第一同步整流器开关的所述接通延迟。
3.根据权利要求1所述的控制器,其中所述放大器被配置成根据所述多个串联耦合的二极管产生阈值电压以启用用于所述第一同步整流器开关的所述接通延迟。
4.根据权利要求1所述的控制器,其中所述接通延迟基于在所述源极端子的电压,所述电压比在所述第一同步整流器的漏极端子的电压高出阈值电压。
5.根据权利要求1所述的控制器,其中所述放大器包括放大器开关,所述放大器开关被配置成当在所述源极端子的电压比在所述第一同步整流器开关的漏极端子的电压高出阈值电压并且所述第一同步整流器开关的体二极管前向偏置时被关断,由此使所述充电开关向所述第一同步整流器开关的所述栅极端子提供正偏置电压以启用其导通。
6.根据权利要求1所述的控制器,还包括:
另一放大器,被配置成使用另一多个串联耦合的二极管启用用于所述第二同步整流器开关的接通延迟;以及
另一放电开关,具有经由另一充电开关耦合到所述另一放大器的输出的控制端子以及分别耦合到所述第二同步整流器开关的栅极和源极端子的第一切换端子和第二切换端子并且配置成对所述第二同步整流器开关的栅极到源极电容进行放电以启用其关断。
7.根据权利要求1所述的控制器,其中所述放电开关被配置成在所述第一同步整流器开关的体二极管反向偏置时接通并且对所述第一同步整流器开关的所述栅极到源极电容进行放电。
8.根据权利要求1所述的控制器,其中所述放大器被配置成启用用于所述第一同步整流器开关的所述接通延迟,并且所述放电开关被配置成启用所述第一同步整流器开关的所述关断以基本上消除与所述第二同步整流器开关的交叉导通。
9.根据权利要求1所述的控制器,其中所述充电开关被配置成提供从偏置电压源经由二极管到所述第一同步整流器开关的所述栅极端子的正向偏置电压以启用其导通。
10.根据权利要求1所述的控制器,其中所述放电开关是双极晶体管。
11.一种操作可与具有第一同步整流器开关和第二同步整流器开关的桥式整流器一起运用的控制器的方法,包括:
用放大器的多个串联耦合的二极管启用用于所述第一同步整流器开关的接通延迟;
用具有经由充电开关耦合到所述放大器的输出的控制端子以及分别耦合到所述第一同步整流器开关的栅极和源极端子的第一切换端子和第二切换端子的放电开关对所述第一同步整流器开关的栅极到源极电容进行放电以启用所述第一同步整流器开关的关断;以及
使用互锁电路减少所述第一同步整流器开关和所述第二同步整流器开关之间的交叉导通,所述互锁电路包括具有分别耦合到所述第一同步整流器开关的所述栅极端子和所述第二同步整流器开关的栅极端子的第一锁开关和第二锁开关,其中所述第一锁开关的切换端子交叉耦合到所述第二锁开关的控制端子,所述第二锁开关的切换端子交叉耦合到所述第一锁开关的控制端子,并且所述第一锁开关并联耦合至所述放电开关。
12.根据权利要求11所述的方法,其中所述启用包括根据所述多个串联耦合的二极管产生阈值电压。
13.根据权利要求11所述的方法,还包括当在所述源极端子的电压比在所述第一同步整流器开关的漏极端子的电压高出阈值电压并且所述第一同步整流器开关的体二极管前向偏置时关断所述放大器的放大器开关,由此使所述充电开关向所述第一同步整流器开关的所述栅极端子提供正偏置电压以启用其导通。
14.根据权利要求11所述的方法,其中放电包括在所述第一同步整流器开关的体二极管反向偏置时接通所述放电开关并且对所述第一同步整流器开关的所述栅极到源极电容进行放电。
15.一种功率转换器,包括:
桥式整流器,具有第一同步整流器开关和第二同步整流器开关;以及
控制器,包括:
放大器,配置成使用多个串联耦合的二极管启用用于所述第一同步整流器开关的接通延迟,
放电开关,具有经由充电开关耦合至所述放大器的输出的控制端子以及分别耦合到所述第一同步整流器开关的栅极和源极端子的第一切换端子和第二切换端子并且配置成对所述第一同步整流器开关的栅极到源极电容进行放电以启用其关断,以及
互锁电路,具有分别耦合到所述第一同步整流器开关的所述栅极端子和所述第二同步整流器开关的栅极端子的第一锁开关和第二锁开关,其中所述第一锁开关的切换端子交叉耦合到所述第二锁开关的控制端子,所述第二锁开关的切换端子交叉耦合到所述第一锁开关的控制端子,并且所述第一锁开关并联耦合至所述放电开关。
16.根据权利要求15所述的功率转换器,其中所述放大器被配置成根据所述多个串联耦合的二极管产生阈值电压以启用用于所述第一同步整流器开关的所述接通延迟。
17.根据权利要求15所述的功率转换器,其中所述放大器包括放大器开关,所述放大器开关被配置成当在所述源极端子的电压比在所述第一同步整流器的漏极端子的电压高出阈值电压并且所述第一同步整流器开关的体二极管前向偏置时关断,由此使所述充电开关向所述第一同步整流器开关的所述栅极端子提供正偏置电压以启用其导通。
18.根据权利要求15所述的功率转换器,其中所述放电开关被配置成在所述第一同步整流器开关的体二极管反向偏置时接通并且对所述第一同步整流器开关的所述栅极到源极电容进行放电。
19.根据权利要求15所述的功率转换器,其中所述放大器被配置成启用用于所述第一同步整流器开关的所述接通延迟,并且所述放电开关被配置成启用所述第一同步整流器开关的所述关断以基本上消除与所述第二同步整流器开关的交叉导通。
20.根据权利要求15所述的功率转换器,其中所述充电开关被配置成提供从偏置电压源经由二极管到所述第一同步整流器开关的所述栅极端子的正向偏置电压以启用其导通。
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Also Published As
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CN102342008A (zh) | 2012-02-01 |
US9088216B2 (en) | 2015-07-21 |
US20100188876A1 (en) | 2010-07-29 |
WO2010083514A1 (en) | 2010-07-22 |
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