US11451161B2 - Power switcher, power rectifier, and power converter including cascode-connected transistors - Google Patents

Power switcher, power rectifier, and power converter including cascode-connected transistors Download PDF

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US11451161B2
US11451161B2 US17/013,981 US202017013981A US11451161B2 US 11451161 B2 US11451161 B2 US 11451161B2 US 202017013981 A US202017013981 A US 202017013981A US 11451161 B2 US11451161 B2 US 11451161B2
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transistor
normally
voltage
electrode
power
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US20210126549A1 (en
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Yusuke Hayashi
Kazuto Takao
Kentaro IKEDA
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Toshiba Corp
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Toshiba Corp
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/337—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration
    • H02M3/3376—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration with automatic control of output voltage or current
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
    • H02M7/2195—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration the switches being synchronously commutated at the same frequency of the AC input voltage
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H03K17/687—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors
    • H03K17/6871—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors the output circuit comprising more than one controlled field-effect transistor
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
    • H02M1/007—Plural converter units in cascade
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
    • H02M1/0074—Plural converter units whose inputs are connected in series
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/285—Single converters with a plurality of output stages connected in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/06—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
    • H02M7/08—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode arranged for operation in parallel

Definitions

  • Embodiments of the present invention relate to a power switcher, a power rectifier, and a power converter.
  • a power converter that performs power conversion by applying an input voltage to a multi-cell circuit in which a plurality of cell circuits such as AC-DC converters and DC-DC converters is connected in series.
  • a slave controller that controls the output voltage and output electric current of a cell circuit for each cell circuit
  • a master controller that stabilizes the operation of all the cell circuits in the multi-cell circuit.
  • the master controller needs to control each cell circuit in cooperation with each slave controller, thus making the control more complicated.
  • the number of components increases and wiring is required to connect the master controller to all the cell circuits. This increases the number of wires, increases power consumption, and makes it difficult to reduce the size of the device.
  • the above-described cell circuit often includes a full-wave rectifier circuit, but when a diode is used in the full-wave rectifier circuit, power loss of the diode becomes a problem. Therefore, there has been proposed a synchronous rectifying circuit that suppresses power loss by connecting a transistor to a diode in parallel and passing the electric current through the transistor rather than through the diode.
  • FIG. 1 is a circuit diagram of a power switcher according to a first embodiment
  • FIG. 2 is a circuit diagram of a power switcher with a third transistor cascode-connected to the second transistor;
  • FIG. 3 is a circuit diagram of a power rectifier according to a second embodiment
  • FIG. 4 is a voltage/electric current waveform diagram when the power rectifier of FIG. 3 is actually operated
  • FIG. 5 is a circuit diagram of the power rectifier according to a third embodiment
  • FIG. 6 is a circuit diagram of a modification of the power rectifier of FIG. 5 ;
  • FIG. 7 is a block diagram illustrating a schematic configuration of a power converter including a power switcher 1 according to the fourth embodiment
  • FIG. 8 is a circuit diagram illustrating an example of the power converter of FIG. 7 ;
  • FIG. 9 is a waveform diagram of each part in the power converter of FIG. 7 .
  • a power switcher includes a first normally-off transistor that switches between interrupting and not interrupting a current path between first and second electrodes according to a drive voltage input to a first control electrode, a second normally-on transistor cascode-connected to the first transistor and including a second control electrode to which the second electrode of the first transistor is connected, a control voltage generator that generates a control voltage in accordance with a voltage between the first and second electrodes of the first transistor, and a drive voltage generator that generates a drive voltage equal to or lower than a withstand voltage of the first transistor in accordance with the control voltage.
  • Embodiments of a power switcher, a power rectifier, and a power converter will be described below with reference to the accompanying drawings.
  • the main constituent components of the power switcher, the power rectifier, and the power converter will be mainly described, but the power switcher, the power rectifier, and the power converter may include other constituent components or functions not illustrated or described.
  • FIG. 1 is a circuit diagram of the power switcher 1 according to a first embodiment.
  • the power switcher 1 of FIG. 1 includes a first normally-off transistor Q 1 , a normally-off second transistor Q 2 , a control voltage generator 2 , and a drive voltage generator 3 .
  • the first transistor Q 1 switches between interrupting and not interrupting the current path between first and second electrodes according to the drive voltage input to the first control electrode.
  • the first control electrode as a gate
  • the first electrode as a drain
  • the second electrode as a source
  • the first normally-off transistor Q 1 can be a normally-off transistor, such as a silicon power metal-oxide-semiconductor field effect transistor (MOSFET) or a silicon carbide bipolar junction transistor (BJT).
  • the first transistor Q 1 may contain a diode D 1 connected between the source and drain of the first transistor Q 1 due to its device structure. This diode D 1 may be external. The anode of the diode D 1 is connected to the source of the first transistor Q 1 , and the cathode is connected to the drain of the first transistor Q 1 .
  • MOSFET silicon power metal-oxide-semiconductor field effect transistor
  • BJT silicon carbide bipolar junction transistor
  • Normally-off means that no electric current passes between the drain and source of the first transistor Q 1 when the gate voltage of the first transistor Q 1 is set to, for example, 0 V and an off-command is given to the first transistor Q 1 . Therefore, the first transistor Q 1 does not consume power when the gate voltage is 0 V.
  • the second normally-on transistor Q 2 is cascode-connected to the first transistor Q 1 .
  • the second transistor Q 2 includes a second control electrode (e.g., gate) to which the second electrode (e.g., source) of the first transistor Q 1 is connected.
  • the second transistor Q 2 may include a diode D 2 connected between the source and drain of the second transistor Q 2 due to its device structure. The diode D 2 may be connected to the outside between the drain and the source of the second transistor Q 2 .
  • Normally-on means that the drain current Id passes through the second transistor Q 2 when 0 V is applied as the gate voltage, and the electric current stops when a negative voltage (e.g., ⁇ 15 V) is applied as the gate voltage.
  • the second transistor Q 2 may be any normally-on transistor, such as a junction field effect transistor (SiC-JFET).
  • the second transistor Q 2 has a higher withstand voltage than that of the first transistor Q 1 .
  • a voltage equal to or lower than the withstand voltage of the first transistor Q 1 is applied to the drain-source of the first transistor Q 1 , and the remaining voltage is applied to the drain-source of the second transistor Q 2 .
  • the withstand voltage of the power switcher 1 can be increased and a high voltage exceeding 100 V can be switched.
  • the withstand voltage of the first transistor Q 1 is, for example, about 20 V, but the withstand voltage of the second transistor Q 2 is, for example, about several hundred of V.
  • the withstand voltage of the first transistor Q 1 is, for example, between 10 V and 100 V, but the withstand voltage of the second transistor Q 2 is, for example, higher than 100 V and equal to or lower than 900 V.
  • the power switcher 1 of FIG. 1 is used to switch a high input voltage of several hundred of volts, most of the high input voltage is applied between the drain and source of the second transistor Q 2 , and high voltage switching can be performed without destroying the first transistor Q 1 .
  • the control voltage generator 2 generates a control voltage in accordance with the voltage between the first electrode (e.g., the drain) and the second electrode (e.g., the source) of the first transistor Q 1 .
  • the power switcher 1 of FIG. 1 enables the electric current to pass between the drain and source of the first transistor Q 1 rather than the diode D 1 when the first transistor Q 1 is on. Therefore, the control voltage generator 2 monitors the drain-source voltage of the first transistor Q 1 and generates a control voltage for controlling the gate of the first transistor Q 1 .
  • control voltage generator 2 sets the gate drive voltage of the first transistor Q 1 and the second transistor Q 2 so that, when the first transistor Q 1 is turned on, the electric current passes from the source to the drain through the first transistor Q 1 and from the source to the drain through the second transistor Q 2 , instead of the diode D 1 .
  • the drive voltage generator 3 generates a drive voltage equal to or lower than the withstand voltage of the first transistor Q 1 in accordance with the control voltage generated by the control voltage generator 2 , and applies the drive voltage to the gate of the first transistor Q 1 .
  • the power switcher 1 of FIG. 1 may include a voltage detector 4 and a polarity determination controller 5 .
  • the voltage detector 4 detects the drain-source voltage of the first transistor Q 1 .
  • the polarity determination controller 5 determines whether to instruct the drive voltage generator 3 to generate the drive voltage in accordance with the polarity of the voltage between the first electrode (e.g., the drain) and the second electrode (e.g., the source) of the first transistor Q 1 .
  • the drive voltage generator 3 applies the drive voltage to the gate of the first transistor Q 1 .
  • the reason for providing the polarity determination controller 5 is to turn on the first transistor Q 1 only when the AC input voltage Vin input to the power switcher 1 is, for example, the positive side voltage.
  • the control voltage generator 2 , the drive voltage generator 3 , the voltage detector 4 , and the polarity determination controller 5 can be built in a semiconductor IC 8 .
  • the control voltage generator 2 , the drive voltage generator 3 , the voltage detector 4 , and the polarity determination controller 5 all operate at a low voltage equal to or lower than the withstand voltage of the first transistor Q 1 , the power switcher 1 of FIG. 1 needs no high voltage for the switching operation, so that the circuit configuration can be simplified and the cost of parts can be suppressed.
  • the gate voltage of the second transistor Q 2 to which a high voltage may be applied, is automatically set once the source voltage of the first transistor Q 1 is determined, so that there is no need to control the second transistor Q 2 .
  • the second normally-on transistor Q 2 needs to be cascode-connected with other normally-on third transistors Q 3 a , Q 3 b , and the like.
  • the third transistors Q 3 a , Q 3 b , and the like may have n (n is an integer of 2 or more) transistors that are cascode-connected. As n increases, the withstand voltage of the power switcher 1 in FIG. 1 also increases.
  • FIG. 2 is a circuit diagram of the power switcher 1 in which the third transistors Q 3 a , Q 3 b , and the like are cascode-connected to the second transistor Q 2 .
  • the power switcher 1 of FIG. 2 includes the third transistors Q 3 a , Q 3 b , and the like that are cascode-connected to the second transistor Q 2 , and the third transistors Q 3 a , Q 3 b , and the like include n cascode-connected transistor groups.
  • a diode (third rectifying element) D 3 a is connected between the gates of the third transistors Q 3 a , Q 3 b , and the like and the source of the first transistor Q 1 .
  • diodes D 3 b are connected in the same direction between the gates of the transistors of the third transistors Q 3 a , Q 3 b , and the like.
  • the diodes D 3 a and D 3 b can be determined, so that there is no need to individually control the gate voltages of the second transistor Q 2 and the n transistors.
  • the withstand voltage of the power switcher 1 in FIG. 2 can be freely controlled. That is, if it is desired to further increase the withstand voltage, the number of cascode-connected transistors only has to be increased.
  • the power switcher 1 is configured by cascode-connecting the normally-off first transistor Q 1 having the low withstand voltage and the normally-on second transistor Q 2 having the high withstand voltage, so that the switching operation of the power switcher 1 can be performed at a low voltage, and the circuit configuration can be simplified. Further, the power switcher 1 according to the present embodiment has a high withstand voltage, although the first transistor Q 1 having the low withstand voltage is included. This is achieved by controlling the gate voltages of the transistors Q 1 and Q 2 to apply a voltage lower than the withstand voltage of the first transistor Q 1 to the drain-source of the first transistor Q 1 , while applying a high voltage between the drain and source of the second transistor Q 2 .
  • the third transistors Q 3 a , Q 3 b , and the like are cascode-connected to the second transistor Q 2 , while adjusting the number of cascode-connected transistors of the third transistors Q 3 a , Q 3 b , and the like, so that the withstand voltage of the power switcher 1 can be adjusted freely.
  • the second transistor Q 2 is a normally-on transistor and is cascode-connected to the first transistor Q 1 which is a normally-off transistor. Therefore, the electric current does not continuously pass through the power switcher 1 when the gate drive voltage is 0 V, and there is no need to continuously apply a negative gate drive voltage from the drive voltage generator 3 , so that power consumption during the turned-off period can be suppressed.
  • a second embodiment is provided by applying the power switcher 1 of the first embodiment to a power rectifier.
  • FIG. 3 is a circuit diagram of the power rectifier 6 according to the second embodiment.
  • a power rectifier 6 in FIG. 3 rectifies the AC input voltage Vin and outputs a half-wave rectified voltage.
  • the half-wave rectified voltage output from the power rectifier 6 is supplied to a load circuit 7 .
  • Any type of the load circuit 7 may be used.
  • the load circuit 7 may be a power converter such as a DC-DC converter.
  • the power rectifier 6 can be configured with a circuit similar to the power switcher 1 of FIG. 1 or 2 .
  • FIG. 3 illustrates an example in which the control voltage generator 2 , the drive voltage generator 3 , the voltage detector 4 , and the polarity determination controller 5 of FIG. 1 are configured by the semiconductor IC 8 , but at least a part of the IC 8 may be configured with another semiconductor IC 8 or with discrete components.
  • the power rectifier 6 of FIG. 3 is a synchronous rectifying circuit.
  • the gate voltage of the first transistor Q 1 is controlled to turn on the first transistor Q 1 , instead of passing the electric current to the diode D 1 connected in parallel with the drain-source of the first transistor Q 1 , so that the electric current can pass through the source-drain of the first transistor Q 1 .
  • the power rectifier 6 of FIG. 3 operates as a synchronous rectifying circuit by turning on or off the first transistor Q 1 to perform the rectifying action.
  • FIG. 4 is a voltage/current waveform diagram when the power rectifier 6 of FIG. 3 is actually operated.
  • a waveform w 1 is a waveform of an AC input voltage Vin
  • a waveform w 2 is a waveform of the drain-source voltage of the first transistor Q 1 (a source voltage with reference to the drain)
  • a waveform w 3 is the waveform of an enlarged view of the waveform w 2
  • a waveform w 4 is the waveform of the drain-source voltage of the second transistor Q 2 (a source voltage with reference to the drain)
  • a waveform w 5 illustrates the electric current passing from the AC power supply to the power rectifier 6 .
  • the AC input voltage Vin illustrated by the waveform w 1 is, for example, AC 100 V.
  • a voltage of about 20 V is applied between the drain and source of the first transistor Q 1 as illustrated by the waveforms w 2 and w 3 , and the remaining voltage is applied between the drain and source of the second transistor Q 2 as illustrated by the waveform w 4 .
  • the power rectifier 6 of FIG. 3 even when the AC input voltage Vin exceeding 100 V is applied, the power rectifier 6 of FIG. 3 applies only a low voltage of about 20 V to the drain-source of the first transistor Q 1 , and applying the remaining large voltage to the drain-source of the second transistor Q 2 , so that a large AC input voltage Vin can be synchronously rectified with a simple circuit configuration without destroying the first transistor Q 1 having the low withstand voltage.
  • the third embodiment implements a synchronous rectifying circuit that outputs a full-wave rectified voltage.
  • FIG. 5 is a circuit diagram of a power rectifier 6 a according to the third embodiment.
  • the power rectifier 6 a of FIG. 5 is configured by bridging-connection of first to fourth power switchers 11 to 14 having the configuration similar to the configuration of the power switcher 1 of FIG. 1 or 2 .
  • a first power switcher 11 switches between passing or not passing the electric current from a first input terminal IN 1 to a first output terminal OUT 1 .
  • a second power switcher 12 switches between passing or not passing the electric current from a second output terminal OUT 2 to a second input terminal IN 2 .
  • a third power switcher 13 switches between passing or not passing the electric current from the second input terminal IN 2 to the first output terminal OUT 1 .
  • a fourth power switcher 14 switches between passing or not passing the electric current from the second output terminal OUT 2 to the first input terminal IN 1 .
  • a full-wave rectified voltage is output between the first and second output terminals OUT 1 and OUT 2 .
  • the power rectifier 6 a in FIG. 5 is a synchronous rectifying circuit.
  • the first to fourth power switchers 11 to 14 individually turns on the first and second transistors Q 1 and Q 2 in accordance with the timing of passing the electric current in the forward direction.
  • the first to fourth power switchers 11 to 14 perform on/off control of the first and second transistors Q 1 and Q 2 in accordance with the phase of the AC input voltage Vin.
  • the first and second power switchers 11 and 12 are turned on to pass the electric current from the first input terminal IN 1 to the first output terminal OUT 1 through the first power switcher 11 . Further, the electric current flowing into the second output terminal OUT 2 passes through the second power switcher 12 to the second input terminal IN 2 .
  • the third and fourth power switchers 13 and 14 are turned on to pass the electric current from the second input terminal IN 2 to the first output terminal OUT 1 through the third power switcher 13 . Further, the electric current flowing into the second output terminal OUT 2 passes through the fourth power switcher 14 to the first input terminal IN 1 .
  • the first to fourth power switchers 11 to 14 can constitute the synchronous rectifying circuit to control on/off of the first and second transistors Q 1 and Q 2 in accordance with the phase of the AC input voltage Vin.
  • each of the first to fourth power switchers 11 to 14 includes the cascode-connected first transistor Q 1 having the low withstand voltage and second transistor Q 2 having the high withstand voltage, so that any voltage exceeding the withstand voltage cannot be applied to the drain-source of the first transistor Q 1 , and the voltage exceeding the withstand voltage of the first transistor Q 1 can be applied to the drain-source of the second transistor Q 2 , thus performing the full-wave rectification operation of a large AC input voltage Vin with low power loss.
  • a totem-pole type power rectifier 6 b as illustrated in FIG. 6 can be provided.
  • the power rectifier 6 b of FIG. 6 is achieved by substituting the second power switcher 12 of FIG. 5 with the fourth transistor Q 4 and the third power switcher 13 with the fifth transistor Q 5 .
  • the power rectifier 6 b of FIG. 6 is a simplified version of the power rectifier 6 a of FIG. 5 , and can be used for full-wave rectification of the AC input voltage Vin for only 50 Hz or 60 Hz components.
  • the diodes D 4 and D 5 may be connected in parallel with the drain-source of the fifth and sixth transistors Q 4 and Q 5 , respectively.
  • a fourth embodiment is implemented by applying the power switcher 1 described above to a power converter.
  • FIG. 7 is a block diagram illustrating a schematic configuration of a power converter 21 including the power switcher 1 according to the fourth embodiment
  • FIG. 8 is a circuit diagram illustrating an example of the power converter 21 of FIG. 7 .
  • the power converter 21 includes a multi-cell rectifier 22 and a step-up chopper 23 .
  • the multi-cell rectifier 22 includes first and second input terminals IN 1 and IN 2 , a plurality of AC-DC converters 24 , and first and second output terminals OUT 1 and OUT 2 .
  • the AC input voltage Vin is applied to the first and second input terminals IN 1 and IN 2 .
  • the plurality of AC-DC converters 24 are connected in series between the first and second input terminals IN 1 and IN 2 .
  • the AC-DC converters 24 each convert the divided input voltage, which is obtained by dividing the AC input voltage Vin, into the full-wave rectified voltage in an electrically insulating manner.
  • the full-wave rectified voltage converted by the plurality of AC-DC converters 24 is output from the first and second output terminals OUT 1 and OUT 2 .
  • the plurality of AC-DC converters 24 have the input side connected in series and the output side connected in parallel.
  • a large AC input voltage Vin such as a voltage exceeding 1,000 V, is applied between the first and second input terminals IN 1 and IN 2 .
  • the AC input voltage Vin applied between the first and second input terminals IN 1 and IN 2 is divided by the number of AC-DC converters 24 and applied to each AC-DC converter 24 .
  • the amplitude of the AC input voltage Vin applied to each AC-DC converter 24 can be suppressed to 100 V to several hundreds of V.
  • Each AC-DC converter 24 includes, for example, the power rectifier 6 a , which is similar to the power rectifier in FIG. 5 that performs the full-wave rectification, and a DC-DC converter 25 .
  • the DC-DC converter 25 includes a primary-side circuit 26 and a secondary-side circuit 27 that are electrically insulated from each other.
  • the primary-side circuit 26 includes capacitors C 1 and C 2 , cascode-connected sixth and seventh transistors Q 6 and Q 7 , an inductor L 1 , a primary-side winding 28 a of a transformer 28 , and a local controller 29 that performs switching control of the sixth and seventh transistors Q 6 and Q 7 .
  • the secondary-side circuit 27 includes a diode bridge circuit 30 having diodes D 8 to D 11 , a secondary-side winding 28 b of the transformer 28 , and a capacitor C 3 .
  • a diode D 6 is connected in parallel with the drain-source of the sixth transistor Q 6
  • a diode D 7 is connected in parallel with the drain-source of the seventh transistor Q 7 .
  • the internal configuration of the DC-DC converter 25 illustrated in FIG. 8 is merely an example, and various modifications can be applied.
  • the local controller 29 performs switching control of the sixth and seventh transistors Q 6 and Q 7 in the corresponding DC-DC converter 25 , regardless of the on/off timing of the sixth and seventh transistors Q 6 and Q 7 in other DC-DC converters 25 .
  • each DC-DC converter 25 is controlled by the corresponding local controller 29 , and a master controller that totally controls the plurality of DC-DC converters 25 is not provided. This is because, if each DC-DC converter 25 controls the sixth and seventh transistors Q 6 and Q 7 to be turned on/off at a constant duty ratio, the operation of balancing the input voltage and the output current for each DC-DC converter 25 is automatically performed without totally controlling the plurality of DC-DC converters 25 .
  • the master controller is provided to totally control the DC-DC converters 25 as in the conventional technique, such operation as changing the control of each local controller 29 and accordingly changing the control of the master controller again may be carried out repeatedly, so that the control may be complicated and the operation of each DC-DC converter 25 may be unstable.
  • Each local controller 29 in the present embodiment performs simple control by merely switching on and off the sixth and seventh transistors Q 6 and Q 7 at a fixed duty ratio, and no other controls such as changing the duty ratio to let the voltage and current to follow certain instruction values are not carried out. Accordingly, the input voltage and the output current of the series-connected DC-DC converters 25 are automatically balanced and, as a result, the operation of each DC-DC converter 25 is stabilized.
  • the windings 28 a and 28 b of the transformer 28 have the same number of turns, the voltage amplitude, frequency, and phase of the full-wave rectified voltage output from each DC-DC converter 25 and applied to the capacitor C 3 are identical to those of the full-wave rectified voltage applied to the capacitor C 1 .
  • the step-up chopper 23 is connected to the first and second output terminals OUT 1 and OUT 2 of the multi-cell rectifier 22 and performs an operation of converting a DC voltage level.
  • the step-up chopper 23 includes an inductor L 2 , an eighth transistor Q 8 , a diode D 12 , an electrolytic capacitor C 4 , a phase detector 31 , a first coefficient adjuster 32 , a differentiator 33 , and a second coefficient adjuster 34 , and a drive signal generator 35 .
  • a diode D 13 is connected in parallel with the drain-source of the eighth transistor Q 8 .
  • the step-up chopper 23 detects the phase of the input voltage by the phase detector 31 , and detects the zero point of the input voltage.
  • the first coefficient adjuster 32 generates a rectified waveform indicating how much electric current to be passed with respect to the zero point. A difference between the rectified waveform and the electric current that actually passes is detected by the differentiator 33 , and the second coefficient adjuster 34 performs proportional-integral control. Note that the internal configuration of the step-up chopper 23 illustrated in FIG. 8 is merely an example, and various modifications can be applied.
  • FIG. 9 is a waveform diagram of each part of the power converter 21 of FIG. 7 .
  • a waveform w 6 is the waveform of the AC input voltage Vin applied to the first and second input terminals IN 1 and IN 2 .
  • a waveform w 7 is a waveform of the voltage output from the first and second output terminals OUT 1 and OUT 2 in FIG. 7 .
  • a waveform w 8 is a waveform of the input voltage of each AC-DC converter 24 .
  • a waveform w 9 is a current waveform passing through the first output terminal OUT 1 .
  • the waveform w 10 is a waveform of the electric current passing through the first input terminal IN 1 .
  • the power converter 21 of FIG. 7 operates stably even when the local controller 29 only performs control.
  • the power converter 21 includes the plurality of AC-DC converters 24 whose connection stages can be freely changed. By increasing the number of connection stages, power conversion of a large AC input voltage Vin exceeding 1,000 V can be stably performed with a simple circuit configuration.
  • each AC-DC converter 24 includes the power rectifier 6 a having the power switcher 1 illustrated in, for example, FIG. 1 , and the DC-DC converter 25 . Since the power switcher 1 in the power rectifier 6 a is configured, as in FIG.
  • each DC-DC converter 25 is controlled by the corresponding local controller 29 , and the master controller that totally controls the plurality of DC-DC converters 25 is not required, so that the control of the AC-DC converter 24 can be simplified and the circuit size can be reduced.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Rectifiers (AREA)
  • Power Conversion In General (AREA)
  • Electronic Switches (AREA)
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