WO2017141559A1 - 半導体装置 - Google Patents
半導体装置 Download PDFInfo
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- WO2017141559A1 WO2017141559A1 PCT/JP2017/000049 JP2017000049W WO2017141559A1 WO 2017141559 A1 WO2017141559 A1 WO 2017141559A1 JP 2017000049 W JP2017000049 W JP 2017000049W WO 2017141559 A1 WO2017141559 A1 WO 2017141559A1
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- voltage
- switching element
- bootstrap capacitor
- switch
- side switching
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
- H03K17/10—Modifications for increasing the maximum permissible switched voltage
- H03K17/102—Modifications for increasing the maximum permissible switched voltage in field-effect transistor switches
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/538—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a push-pull configuration
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K2217/00—Indexing scheme related to electronic switching or gating, i.e. not by contact-making or -breaking covered by H03K17/00
- H03K2217/0081—Power supply means, e.g. to the switch driver
Definitions
- the present invention relates to a semiconductor device including a high-side driving circuit and a low-side driving circuit that complementarily drive a high-side switching element and a low-side switching element that are totem-pole connected.
- FIG. 11 shows a schematic configuration of a power converter including a high-side switching element XM1 and a low-side switching element XM2 that are totem-pole connected.
- This power converter alternately outputs the DC voltage HV and the ground potential to the load RL via the switching elements XM1 and XM2 that are complementarily turned on and off, thereby generating the AC power to be supplied to the load RL.
- the semiconductor device 1 that includes the high-side drive circuit 11 and the low-side drive circuit 12 and that turns on and off the switching elements XM1 and XM2 in a complementary manner is realized as, for example, an IPM (Intelligent Power Module).
- the semiconductor device 1 includes an interface circuit 13 that complementarily generates a high-side drive signal and a low-side drive signal in accordance with a control signal IN given from a controller 2 that is an external device.
- the high side drive circuit 11 turns on / off the high side switching element XM1 according to the high side drive signal
- the low side drive circuit 12 turns on / off the low side switching element XM2 according to the low side drive signal.
- the high side drive signal generated by the interface circuit 13 is given to the high side drive circuit 11 via the level shift circuit 14.
- the low-side drive circuit 12 and the interface circuit 13 operate by receiving a predetermined power supply voltage VCC using the ground potential GND as a reference potential.
- the high side drive circuit 11 uses the intermediate voltage VS generated at the series connection point of the switching elements XM1 and XM2 as a reference potential, and boosts the power supply voltage VCC by a bootstrap circuit including a bootstrap diode Dbs and a bootstrap capacitor Cbs ( Operates in response to the bootstrap power supply voltage VB.
- the bootstrap circuit charges the bootstrap capacitor Cbs with the power supply voltage VCC when the low-side switching element XM2 is turned on.
- the bootstrap circuit utilizes the fact that when the low-side switching element XM2 is in the off operation, the intermediate voltage VS, which is the low-voltage side terminal voltage of the bootstrap capacitor Cbs, increases with the on-operation of the high-side switching element XM1, A boosted (bootstrapped) power supply voltage VB is generated.
- the semiconductor device 1 configured as described above, for example, when the on time of the high side switching element XM1 is long, the charge charged in the bootstrap capacitor Cbs is greatly reduced, and the driving of the high side driving circuit 11 is performed. There is a risk that the power supply voltage VB necessary for the operation cannot be maintained.
- Patent Document 1 discloses that when the low-side switching element XM2 is turned off, a current is supplied from the floating power supply FV having a high-voltage side potential as a reference potential to the bootstrap capacitor Cbs. (See FIG. 1 of Patent Document 1).
- a floating power supply FV must be prepared, which causes problems such as the generation of additional costs and what to do with the floating power supply FV itself.
- Patent Document 2 discloses that the bootstrap capacitor Cbs is directly charged from a high-voltage DC voltage HV through a resistor R1 when the low-side switching element XM2 is on (see FIG. 1 of Patent Document 2). reference).
- the high-side switching element XM1 when the high-side switching element XM1 is on, the DC voltage HV and the intermediate voltage VS are substantially the same potential, and the resistor R1 serves as a load with respect to the power supply voltage VB.
- a problem arises in that the charge charged in Cbs is discharged.
- the intermediate voltage VS and the ground potential GND are substantially the same potential, so that the charging current of the bootstrap capacitor Cbs increases. Furthermore, the clamp current flowing through the Zener diode that defines the charging voltage of the bootstrap capacitor Cbs is also increased. As a result, there is a problem that power consumption in the bootstrap circuit increases and it is difficult to reduce the size of the semiconductor device 1.
- the first stage capacitor C1 is charged by the power supply voltage VCC via the switch elements Qn1 and Qn2, and then the charging voltage of the capacitor C1 is supplied via the switch elements Qp1 and Qp2.
- the switch elements Qn1, Qn2 and the switch elements Qp1, Qp2 are complementarily turned on / off under the control of the control circuit 15 independently of the on / off of the switching elements XM1, XM2.
- the power supply voltage VB is generated as the charging voltage of the second-stage capacitor C2. Therefore, even when the off time of the low side switching element XM2 is long, the power supply voltage VB necessary for driving the high side drive circuit 11 can be secured.
- the intermediate voltage VS becomes a high DC voltage HV or a ground potential GND in accordance with the switching operation of the switching elements XM1 and XM2.
- the power supply voltage VB is also high.
- the level shift circuit needs to be configured using a high breakdown voltage element. This complicates the configuration of the bootstrap circuit and inevitably increases the cost of parts associated with the use of a high breakdown voltage element.
- the present invention has been made in view of such circumstances, and its purpose is to provide a stable high-side drive circuit for turning on and off the high-side switching element even when the on-time of the high-side switching element is long.
- An object of the present invention is to provide an inexpensive and simple semiconductor device having a bootstrap circuit capable of supplying power.
- the semiconductor device basically includes a high-side driving circuit and a low-side driving circuit that complementarily turn on and off the high-side switching element and the low-side switching element that are totem-pole connected, and the low-side driving circuit via a diode.
- a bootstrap capacitor connected to a driving power source of the driving circuit and charged when the low-side switching element is turned on, and boosting the charging voltage when the low-side switching element is turned off and applying the boosted voltage to the high-side driving circuit;
- the semiconductor device has the above configuration in order to achieve the above-described object, Further, an auxiliary device provided in parallel to the bootstrap capacitor via a switch circuit and charged by an intermediate voltage generated at a connection point between the high side switching element and the low side switching element when the high side switching element is turned on.
- a control circuit that applies the charging voltage of the auxiliary bootstrap capacitor to the high-side drive circuit via the switch circuit when the charging voltage of the bootstrap capacitor is lower than a predetermined voltage when the high-side switching element is on. It is characterized by having.
- the semiconductor device generally includes an auxiliary bootstrap capacitor that is charged when the low-side switching element is turned off in parallel with the bootstrap capacitor that is charged when the low-side switching element is turned on.
- the voltage applied from the bootstrap capacitor to the high side driving circuit is compensated by using the charging voltage of the auxiliary bootstrap capacitor.
- the high-side drive circuit is configured to operate as a voltage operation reference voltage at the connection point.
- the Zener diode plays a role of defining a charging reference voltage of the auxiliary bootstrap capacitor charged by the intermediate voltage as a voltage of a driving power source of the low side driving circuit.
- the control circuit may determine that the charging voltage of the bootstrap capacitor has dropped below a predetermined voltage when the ON time of the high side switching element exceeds a preset time.
- the switch circuit connects the auxiliary bootstrap capacitor in parallel to the power line of the high side drive circuit when, for example, the charging voltage of the bootstrap capacitor drops below a predetermined voltage when the high side switching element is on.
- the third and fourth switches for applying the charging reference voltage to the auxiliary bootstrap capacitor when the high-side switching element is on and the first and second switches are off.
- a switch for example, bidirectional analog switches are used.
- control circuit is preferably provided so as to operate using an intermediate voltage generated at a series connection point between the high-side switching element and the low-side switching element, which are preferably connected totem pole, as an operation reference voltage.
- control circuit detects, for example, a drop in power supply voltage applied to the high side drive circuit and outputs a voltage drop detection signal, and the first to second based on the voltage drop detection signal.
- a control logic circuit for generating a switch signal for controlling on / off of each of the four switches.
- the first and second switches are provided so as to be turned on / off complementarily with the third and fourth switches.
- the first switch is realized as a first diode that conducts when the charging voltage of the auxiliary bootstrap capacitor exceeds the charging voltage of the bootstrap capacitor, and the third switch is configured as the auxiliary switch. It can also be realized as a second diode that conducts when the charging voltage of the bootstrap capacitor falls below the voltage defined by the zener diode.
- the present invention also provides a semiconductor device having the above-described configuration. Further, when the first and second switches are turned on, the fifth and sixth switches for disconnecting the bootstrap capacitor from the drive power supply of the low-side drive circuit, and the fifth and sixth switches are complementarily turned on. It is also possible to provide a seventh and eighth switch for applying the charging reference voltage to the auxiliary bootstrap capacitor. In this case, the fifth to eighth switches may be realized using bidirectional analog switches.
- the cathode of the Zener diode is connected to a connection point between the high-side switching element and the low-side switching element.
- the anode of the Zener diode defines a negative reference potential with respect to the intermediate voltage so that the anode-cathode voltage of the Zener diode becomes the charging reference voltage.
- the semiconductor device includes an auxiliary bootstrap capacitor that is charged when the high-side switching element is turned on in addition to the bootstrap capacitor that is charged when the low-side switching element is turned on as described above.
- the voltage applied from the bootstrap capacitor to the high-side drive circuit is compensated by using the charging voltage of the auxiliary bootstrap capacitor.
- the semiconductor device having the above configuration even when the on-time of the high-side switching element is long, the power supply voltage necessary for the operation can be stably supplied to the high-side drive circuit. Therefore, although it has a simple configuration, it has a great practical effect such as being able to guarantee a stable operation of the high side drive circuit without being related to the on / off conditions of the high side switching element.
- the high-side drive circuit operates using the voltage at the connection point as an operation reference voltage. Therefore, a bootstrap circuit can be constructed at low cost without using an expensive high-breakdown-voltage element as disclosed in Patent Document 3.
- the control circuit for controlling on / off of each of the first to fourth switches can be easily constructed as, for example, a control logic circuit. In this respect as well, the cost of the semiconductor device can be reduced. The effects such as the above are also exhibited.
- the auxiliary bootstrap capacitor can be charged independently of charging and discharging of the bootstrap capacitor. And the charging voltage of the bootstrap capacitor is lowered, and accordingly, when the charging voltage of the auxiliary bootstrap capacitor is applied to the high side driving circuit, the bootstrap capacitor can be recharged. Become. Accordingly, even when the on time of the high side switching element is long, the role of the bootstrap capacitor can be quickly recovered, and the power supply voltage can be stably supplied to the high side driving circuit.
- FIG. 1 is a schematic configuration diagram of a semiconductor device according to a first embodiment of the present invention.
- FIG. 2 is a diagram showing a configuration example of a control circuit in the semiconductor device shown in FIG. 1.
- FIG. 3 is a timing chart showing the operation of the control circuit shown in FIG. 2.
- FIG. 2 is a timing chart showing a bootstrap operation in the semiconductor device shown in FIG. 1.
- FIG. 6 illustrates a configuration example of a control circuit in the semiconductor device illustrated in FIG. 5.
- FIG. 7 is a timing chart showing the operation of the control circuit shown in FIG. 6.
- FIG. 6 is a timing chart showing a bootstrap operation in the semiconductor device shown in FIG. 5.
- FIG. 10 illustrates a configuration example of a control circuit in the semiconductor device illustrated in FIG. 9.
- 1 is a schematic configuration diagram of a conventional general semiconductor device including a high-side drive circuit and a low-side drive circuit that respectively drive a high-side switching element and a low-side switching element that are totem-pole connected.
- the figure which shows an example of the conventional semiconductor device comprised so that power might be stably supplied to a high side drive circuit irrespective of ON / OFF of a low side switching element.
- FIG. 1 is a diagram showing a schematic configuration of a semiconductor device 1 according to a first embodiment of the present invention.
- the semiconductor device 1 basically includes a high-side drive circuit 11 and a low-side drive circuit 12 that complementarily drive a high-side switching element XM1 and a low-side switching element XM2 that are totem-pole connected, and a bootstrap diode Dbs. And a bootstrap capacitor Cbs connected to the drive power supply of the low-side drive circuit 12 via
- the bootstrap capacitor Cbs has one end connected to the series connection point of the high side switching element XM1 and the low side switching element XM2, and the other end connected to the cathode of the bootstrap diode Dbs. Therefore, the bootstrap capacitor Cbs is charged to the power supply voltage VCC via the bootstrap diode Dbs with the ground potential GND as a reference potential when the low-side switching element XM2 is turned on.
- the voltage charged in the bootstrap capacitor Cbs is boosted to a potential based on the potential VS at the series connection point of the high-side switching element XM1 and the low-side switching element XM2 as the low-side switching element XM2 is turned off (bootstrap). Is done.
- the boosted charging voltage of the bootstrap capacitor Cbs is applied to the high side driving circuit 11 as the power supply voltage VB.
- the semiconductor device 1 according to the first embodiment is characterized in that an auxiliary bootstrap capacitor Cspl is provided in parallel with the bootstrap capacitor Cbs via a switch circuit including first to fourth switches SW1 to SW4. It is in.
- the first to fourth switches SW1 to SW4 are constituted by bidirectional analog switches (transmission gates).
- the first and second switches SW1 and SW2 are turned on / off in conjunction with each other under the control of the control circuit 15, and the third and fourth switches SW3 and SW4 are also controlled by the control circuit 15. In response to each other, they are turned on and off in conjunction with each other.
- one end of the auxiliary bootstrap capacitor Cspl is connected to the cathode of the bootstrap diode Dbs (the other end side of the bootstrap capacitor Cbs) via the first switch SW1, and the other end of the auxiliary bootstrap capacitor Cspl is
- the high-side switching element XM1 and the low-side switching element XM2 are connected to the series connection point (one end side of the bootstrap capacitor Cbs) via the second switch SW2.
- one end of the auxiliary bootstrap capacitor Cspl is connected to the series connection point (one end side of the bootstrap capacitor Cbs) of the high side switching element XM1 and the low side switching element XM2 via the third switch SW3.
- the other end of the capacitor Cspl is connected to the reference potential MVS via the fourth switch SW4.
- the reference potential MVS is connected to the ground potential GND through a constant current source ibias.
- a Zener diode ZD is interposed between one end of the bootstrap capacitor Cbs and the constant current source ibias. As will be described later, the voltage across the Zener diode ZD (particularly the breakdown voltage) becomes the charging reference voltage for charging the auxiliary bootstrap capacitor Cspl.
- the third and fourth switches SW3 and SW4 are turned on to charge the auxiliary bootstrap capacitor Cspl when the low-side switching element XM2 is off and the high-side switching element XM1 is on. Take on. At this time, a high DC voltage HV is applied to the cathode of the Zener diode ZD to cause breakdown, and the breakdown voltage is applied to the auxiliary bootstrap capacitor Cspl as a charging reference voltage. In the first and second switches SW1 and SW2, the low-side switching element XM2 is off, and the power supply voltage VB supplied from the bootstrap capacitor Cbs to the high-side drive circuit 11 controls the operation of the high-side drive circuit 11.
- Conduction (ON) control is performed when the voltage drops to a predetermined voltage in the vicinity of the guaranteed minimum voltage.
- the first and second switches SW1 and SW2 are turned on, the decrease in the power supply voltage VB is compensated by the discharge of the charging voltage from the auxiliary bootstrap capacitor Cspl, and the power supply voltage VB supplied to the high side drive circuit 11 is decreased. Is prevented.
- the third and fourth switches SW3 and SW4 are off.
- the control circuit 15 that controls the on / off of the first to fourth switches SW1 to SW4 is configured as shown in FIG. 2, for example.
- the control circuit 15 obtains the reference potential MVS from the anode of the Zener diode ZD.
- the reference potential MVS is (intermediate voltage VS ⁇ breakdown voltage of the Zener diode ZD) when the Zener diode ZD is broken, and becomes the ground potential GND when the Zener diode ZD is not broken.
- the breakdown voltage of the Zener diode ZD is set so that the Zener diode ZD breaks down when the high-side switching element XM1 is turned on and the low-side switching element XM2 is turned off.
- the high-side drive circuit 11 operates using the intermediate voltage VS as an operation reference potential.
- the control circuit 15 receives the signal CENB output from the high-side drive circuit 11 in conjunction with the on-drive of the high-side switching element XM1, and converts it into an on-signal CEN that sets the reference potential MVS of the control circuit 15 to the L level.
- An input circuit 15a is provided.
- the control circuit 15 also includes a voltage drop detector 16 that detects a drop in the power supply voltage VB with the intermediate voltage VS as a reference potential, that is, a drop in the voltage between (VB ⁇ VS).
- the voltage drop detector 16 outputs a voltage drop detection signal when the power supply voltage VB drops to a predetermined voltage near the lowest voltage that guarantees the operation of the high side drive circuit 11.
- the detection signal output from the voltage drop detector 16 when the power supply voltage VB is lowered is converted into a voltage drop signal UVEN that makes the reference potential MVS L level via the input circuit 15b.
- the control logic circuit 15c provided in the control circuit 15 operates using the reference potential MVS as an operation reference voltage and the intermediate voltage VS as a power supply voltage. Then, according to the ON signal CEN and the voltage drop signal UVEN, the control logic circuit 15c, for example, as shown in FIG. 3, switch signals S1C, S2C, and so on for ON / OFF control of the first to fourth switches SW1 to SW4, respectively. S3 and S4 are generated.
- control logic circuit 15c generates the switch signals S1C and S2C only when the power supply voltage VB (voltage between VB and VS) with the intermediate potential VS as a reference is lowered to a voltage that guarantees the operation of the high side drive circuit 11. .
- control logic circuit 15c outputs the switch signals S1C and S2C when the voltage between (VB-VS) decreases in accordance with the ON signal CEN and the voltage decrease signal UVEN when the high side switching element XM1 is ON. To do.
- the ON signal CEN is not necessarily required for the operation of the control logic circuit 15c. This is because during the period when the signal CENB is at the H level, the low-side switching element XM2 is basically turned on, the intermediate potential VS becomes the ground potential GND, and no power is supplied to the control logic circuit 15c. This is because it is meaningless to inform the control logic circuit 15c that the signal is at the H level. However, in order to determine the operation in the dead time in which both the high-side switching element XM1 and the low-side switching element XM2 are off, it is better to have the on signal CEN.
- the switch signals S1C and S2C generated by the control logic circuit 15c are negative logic signals for turning on the first and second switches SW1 and SW2 when they are at the L level. These switch signals S1C and S2C are converted into signals that are alternatively set to the power supply voltage VB or the intermediate voltage VS via the output circuits 15d and 15e, and are applied to the first and second switches SW1 and SW2, respectively.
- the switch signals S3 and S4 are positive logic signals for turning on the third and fourth switches SW3 and SW4 when they are at the H level. These switch signals S3 and S4 are applied to the third and fourth switches SW3 and SW4, respectively, as signals that are alternatively set to the intermediate voltage VS or the reference potential MVS.
- the first and second switches SW1, SW2 are turned on / off complementarily with the third and fourth switches SW3, SW4, and the power supply voltage VB and the intermediate voltage VS are The short circuit or the intermediate voltage VS and the reference potential MVS are not short-circuited.
- C1 is a smoothing capacitor that smoothes the voltage between (VS-MVS) clamped by the breakdown voltage of the Zener diode ZD and takes it into the control circuit 15.
- the smoothing capacitor C1 and the Zener diode ZD constitute a voltage regulator that stabilizes the reference voltage MVS of the control circuit 15.
- FIG. 4 is a timing chart showing a bootstrap operation in the semiconductor device 1 configured as described above. That is, FIG. 4 shows on / off forms of the first to fourth switches SW1 to SW4 associated with the operations of the high-side drive circuit 11 and the low-side drive circuit 12 that complementarily turn on / off the switching elements XM1 and XM2. The state of charging / discharging of the bootstrap capacitor Cbs and the auxiliary bootstrap capacitor Cspl is shown.
- the bootstrap capacitor Cbs is linked with the on / off of the low side switching element XM2, and is charged by the power supply voltage VCC when the low side switching element XM2 is on.
- the charging voltage (charge) of the bootstrap capacitor Cbs is discharged when the low side switching element XM2 is off and is supplied to the high side drive circuit 11.
- the power supply voltage VB supplied to the high-side drive circuit 11 by discharging the bootstrap capacitor Cbs boosts the power supply voltage VCC by the intermediate potential VS as the low-side switching element XM2 is turned off and the high-side switching element XM1 is turned on. (Bootstrap).
- the auxiliary bootstrap capacitor Cspl has a Zener diode when the high-side switching element XM1 is turned on and the intermediate voltage VS at the series connection point of the high-side switching element XM1 and the low-side switching element XM2 becomes a high voltage. It is charged by the voltage between (VS-MVS) clamped by the breakdown voltage of ZD, that is, the charging reference voltage.
- the voltage between (VS ⁇ MVS) clamped by the Zener diode ZD is a voltage corresponding to the power supply voltage VCC that drives the low-side drive circuit 12. That is, the auxiliary bootstrap capacitor Cspl receives and charges the intermediate voltage VS applied through the high-side switching element XM1 independently of the bootstrap capacitor Cbs charged by receiving the power supply voltage VCC.
- the remaining charge amount of the bootstrap capacitor Cbs becomes insufficient due to the discharge of the bootstrap capacitor Cbs serving as the supply source of the power supply voltage VB, and the power supply voltage VB applied to the high-side drive circuit 11 is reduced accordingly,
- the electric charge charged in the bootstrap capacitor Cspl is discharged.
- the discharge of the auxiliary bootstrap capacitor Cspl compensates for the decrease in the power supply voltage VB applied to the high side drive circuit 11 and maintains the power supply voltage VB necessary for the operation of the high side drive circuit 11.
- the power supply voltage VB necessary for the operation of the high side drive circuit 11 can be maintained without being restricted by the charging capacity of the bootstrap capacitor Cbs. It becomes.
- the shortage of the charging capacity of the bootstrap capacitor Cbs can be solved by the auxiliary bootstrap capacitor Cspl, even when the on time of the high side switching element XM1 is long, it can be easily and effectively dealt with.
- the capacity of the bootstrap capacitor Cbs can be increased.
- the bootstrap capacitor Cbs since the bootstrap capacitor Cbs is charged when the low-side switching element XM2 is turned on, the bootstrap capacitor Cbs may not be sufficiently charged.
- the auxiliary bootstrap capacitor Cspl is charged when the low-side switching element XM2 is off and the high-side switching element XM1 is on.
- the auxiliary bootstrap capacitor Cspl is charged independently of the charging / discharging of the bootstrap capacitor Cbs, and the auxiliary bootstrap capacitor Cspl is discharged only when the power supply voltage VB decreases to prevent the power supply voltage VB from decreasing. Therefore, even if the on-time of the low-side switching element XM2 is short, it is possible to sufficiently charge the charge necessary for stably supplying the power supply voltage VB to the bootstrap capacitor Cbs and / or the auxiliary bootstrap capacitor Cspl. It becomes. As a result, the power supply voltage VB can be stably generated even when the on / off times of the switching elements XM1 and XM2 change greatly, and the semiconductor device 1 can be stably operated.
- the voltage between (VS-MVS) is clamped by the Zener diode ZD, thereby limiting the charging voltage of the auxiliary bootstrap capacitor Cspl. Therefore, it is not necessary to use a high breakdown voltage element as in the circuit disclosed in Patent Document 3, and the control circuit 15 can be constructed easily and inexpensively. Further, the bidirectional analog switches used as the first to fourth switches SW1 to SW4 do not need to have a high breakdown voltage, so that the entire semiconductor device 1 can be constructed at low cost.
- FIG. 5 is a diagram showing a schematic configuration of a semiconductor device 1 according to the second embodiment of the present invention.
- the fifth to eighth switches SW5 to SW8 are added to the configuration of the semiconductor device 1 according to the first embodiment, and the bootstrap capacitor Cbs and the auxiliary bootstrap capacitor are added.
- Cspl is configured to be selectively connected between the cathode of the bootstrap diode Dbs and the series connection point of the switching elements XM1 and XM2, or between the series connection point of the switching elements XM1 and XM2 and the ground potential GND. It is characterized by.
- the fifth to eighth switches SW5 to SW8 are collectively turned on / off in conjunction with each other under the control of the control circuit 15. Further, the fifth to eighth switches SW5 to SW8 are constituted by bidirectional analog switches (transmission gates) or the like.
- one end of the bootstrap capacitor Cbs is connected to the cathode of the bootstrap diode Dbs via the fifth switch SW5, and the other end is connected to the high side switching element XM1 and the low side switching element via the sixth switch SW6. It is connected to the series connection point with XM2.
- one end of the bootstrap capacitor Cbs is connected to the series connection point of the high side switching element XM1 and the low side switching element XM2 via the seventh switch SW7, and the other end is connected to the reference potential via the eighth switch SW8.
- the reference potential MVS is connected to the ground potential GND through a constant current source ibias.
- These fifth to eighth switches SW5 to SW8 are ON / OFF controlled by the control circuit 15 in conjunction with the first to fourth switches SW1 to SW4 described above, so that the bootstrap capacitor Cbs and the auxiliary bootstrap are controlled.
- the capacitor Cspl plays a role of alternately charging and discharging.
- control circuit 15 for controlling on / off of the first to eighth switches SW1 to SW8 is configured as shown in FIG. 6, for example.
- the control circuit 15 includes a timer 17 in the control logic circuit 15c in place of the voltage drop detector 16 described above.
- the timer 17 counts the ON time of the high side switching element XM1, and plays a role of generating a voltage detection signal UVEN (not shown in FIG. 6) when the ON time exceeds a preset time in advance.
- the power supply voltage VB fed from the bootstrap capacitor Cbs to the high-side drive circuit 11 depends on the on-time of the high-side switching element XM1, and decreases as the discharge time of the bootstrap capacitor Cbs increases.
- the timer 17 generates the voltage detection signal UVEN by equivalently detecting the degree of decrease in the power supply voltage VB accompanying the discharge of the bootstrap capacitor Cbs as the length of the on time of the high side switching element XM1.
- the control logic circuit 15c switches, for example, as shown in FIG. 7, the switch signals S1C for turning on / off the first to fourth switches SW1 to SW4 described above.
- switch signals S5C, S6C, S7, and S8 for ON / OFF control of the fifth to eighth switches SW5 to SW8 are generated.
- switch signals S1C, S2C, S5C, and S6C generated by the control logic circuit 15c are at the L level, the first, second, fifth, and sixth switches SW1, SW2, SW5, and SW6 are turned on, respectively. Negative logic signal.
- These switch signals S1C, S2C, S5C, and S6C are converted into signals that are alternatively set to the power supply voltage VB or the intermediate voltage VS via the output circuits 15d, 15e, 15f, and 15g, and the first, second, Applied to the fifth and sixth switches SW1, SW2, SW5, SW6, respectively.
- the switch signals S3, S4, S7, and S8 are positive logic signals for turning on the third, fourth, seventh, and eighth switches SW3, SW4, SW7, and SW8 when they are at the H level.
- These switch signals S3, S4, S7, and S8 are the third, fourth, seventh, and eighth switches SW3, SW4, SW7, and SW8 as signals that are alternatively set to the intermediate voltage VS or the reference potential MVS. Respectively.
- FIG. 8 is a timing chart showing a bootstrap operation in the semiconductor device 1 configured as described above. That is, FIG. 8 shows on / off forms of the first to eighth switches SW1 to SW8 associated with the operations of the high-side drive circuit 11 and the low-side drive circuit 12 that complementarily turn on / off the switching elements XM1 and XM2. The state of charging / discharging of the bootstrap capacitor Cbs and the auxiliary bootstrap capacitor Cspl is shown.
- the bootstrap capacitor Cbs is linked with the on / off of the low side switching element XM2, and is charged by the power supply voltage VCC when the low side switching element XM2 is on. Is done.
- the charging voltage of the bootstrap capacitor Cbs is boosted (bootstrap) and supplied to the high side drive circuit 11 when the low side switching element XM2 is off and the high side switching element XM1 is on.
- the auxiliary bootstrap capacitor Cspl is charged by receiving the voltage between (VS-MVS) independently of the bootstrap capacitor Cbs charged by receiving the power supply voltage VCC, as in the case of the first embodiment. .
- the electric charge charged in the auxiliary bootstrap capacitor Cspl is discharged through the first and second switches SW1 and SW2 to obtain the power supply voltage VB. It is supplied to the high side drive circuit 11.
- the bootstrap capacitor Cbs is disconnected from the high-side drive circuit 11 by the fifth and sixth switches SW5 and SW6, and is also switched by the switching elements XM1 and XM2 via the seventh and eighth switches SW7 and SW8. Are connected to the series connection point and the reference potential MVS.
- the power supply voltage VB is applied from the auxiliary bootstrap capacitor Cspl to the high side drive circuit 11 instead of the bootstrap capacitor Cbs.
- the bootstrap capacitor Cbs is recharged in response to the voltage between (VS-MVS). Therefore, also in the semiconductor device 1 operating in this way, the power supply voltage VB is stably supplied to the high-side drive circuit 11 even when the on-time of the high-side switching element XM1 is long, similarly to the semiconductor device 1 described as the first embodiment. Can be supplied.
- the bootstrap capacitor Cbs since the bootstrap capacitor Cbs is charged when the auxiliary bootstrap capacitor Cspl is discharged, the bootstrap capacitor Cbs can be reliably charged even when the on-time of the low-side switching element XM2 is short.
- the timer 17 is restarted after the supply of the power supply voltage VB is started from the auxiliary bootstrap capacitor Cspl instead of the bootstrap capacitor Cbs.
- the power supply voltage VB is supplied from the bootstrap capacitor Cbs again instead of the auxiliary bootstrap capacitor Cspl.
- the supply of the power supply voltage VB from the bootstrap capacitor Cbs and the supply of the power supply voltage VB from the auxiliary bootstrap capacitor Cspl are continued alternately, the on-time of the high side switching element XM1 can be determined. But it is possible.
- the power supply can cope with the change in the ON / OFF time of the switching elements XM1 and XM2 more flexibly. There are effects that the voltage VB can be stably generated and the semiconductor device 1 can be stably operated.
- FIG. 9 shows a schematic configuration of the semiconductor device 1 according to the third embodiment of the present invention.
- the first and third switches SW1 and SW3 in the semiconductor device 1 according to the first embodiment described above are realized by using diodes D1 and D2. . That is, the anode of the diode D1 is connected to one end of the auxiliary bootstrap capacitor Cspl, and the cathode of the diode D1 is connected to the supply line of the power supply voltage VB of the high side drive circuit 11.
- the diode D1 When the second switch SW2 is turned on, the diode D1 is turned on / off using the potential difference between the power supply voltage VB and the voltage obtained by adding the charging voltage of the auxiliary bootstrap capacitor Cspl to the intermediate voltage VS, and the auxiliary bootstrap capacitor It is configured to control the discharge of Cspl.
- the anode of the diode D2 is connected to the series connection point of the switching elements XM1 and XM2, and the cathode of the diode D2 is connected to one end of the auxiliary bootstrap capacitor Cspl.
- the fourth switch SW4 is turned on, the diode D2 is turned on / off using the potential difference between the intermediate voltage VS and the voltage obtained by adding the charging voltage of the auxiliary bootstrap capacitor Cspl to the reference potential MVS of the control circuit 15, The auxiliary bootstrap capacitor Cspl is charged when the low-side switching element XM2 is off.
- the output circuit 15d can be omitted as shown in FIG. Therefore, according to the semiconductor device 1 according to the third embodiment, the configuration of the control circuit 15 can be simplified while acting in the same manner as the semiconductor device 1 according to the first embodiment described above. An effect is produced.
- this invention is not limited to each embodiment mentioned above.
- the capacitances of the bootstrap capacitor Cbs and the auxiliary bootstrap capacitor Cspl need only be set in consideration of the change width of the on / off times of the switching elements XM1 and XM2.
- the control logic circuit 15c can also be configured using, for example, various logic gate circuits.
- the present invention can be variously modified and implemented without departing from the scope of the invention.
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Abstract
Description
更にスイッチ回路を介して前記ブートストラップコンデンサに並列的に設けられて前記ハイサイドスイッチング素子のオン時に前記ハイサイドスイッチング素子および前記ローサイドスイッチング素子との接続点に生起される中間電圧により充電される補助ブートストラップコンデンサと、
前記接続点に接続されて該補助ブートストラップコンデンサの充電開始電圧を規定するツェナーダイオードと、
前記ハイサイドスイッチング素子のオン時における前記ブートストラップコンデンサの充電電圧が所定電圧よりも低下したときに前記スイッチ回路を介して前記補助ブートストラップコンデンサの充電電圧を前記ハイサイド駆動回路に印加する制御回路と
を備えたことを特徴としている。
更に前記第1および第2のスイッチの導通時に前記ブートストラップコンデンサを前記ローサイド駆動回路の駆動電源から切り離す第5および第6のスイッチ、並びに前記第5および第6のスイッチに対して相補的に導通して前記補助ブートストラップコンデンサに前記充電基準電圧を印加する第7および第8のスイッチを設けて構成することも可能である。この場合、前記第5~第8のスイッチについても双方向アナログスイッチを用いて実現すれば良い。
2 コントローラ
11 ハイサイド駆動回路
12 ローサイド駆動回路
13 インターフェース回路
14 レベルシフト回路
15 制御回路
15c 制御ロジック回路
16 電圧低下検出器
17 タイマー
XM1 ハイサイドスイッチング素子
XM2 ローサイドスイッチング素子
Dbs ブートストラップダイオード
Cbs ブートストラップコンデンサ
Cspl 補助ブートストラップコンデンサ
SW1,SW2~SW8 スイッチ
ZD ツェナーダイオード
ibias 定電流源
D1,D2 ダイオード(スイッチ)
Claims (11)
- トーテムポール接続されたハイサイドスイッチング素子およびローサイドスイッチング素子をそれぞれ相補的にオン・オフするハイサイド駆動回路およびローサイド駆動回路と、
ダイオードを介して前記ローサイド駆動回路の駆動電源に接続されて前記ローサイドスイッチング素子のオン時に充電され、その充電電圧を前記ローサイドスイッチング素子のオフ時に昇圧して前記ハイサイド駆動回路に印加するブートストラップコンデンサと、
スイッチ回路を介して前記ブートストラップコンデンサに並列的に設けられて前記ハイサイドスイッチング素子のオン時に前記ハイサイドスイッチング素子および前記ローサイドスイッチング素子との接続点に生起される中間電圧により充電される補助ブートストラップコンデンサと、
前記接続点に接続されて該補助ブートストラップコンデンサの充電基準電圧を規定するツェナーダイオードと、
前記ハイサイドスイッチング素子のオン時における前記ブートストラップコンデンサの充電電圧が所定電圧よりも低下したときに前記スイッチ回路を介して前記補助ブートストラップコンデンサの充電電圧を前記ハイサイド駆動回路に印加する制御回路と
を具備したことを特徴とする半導体装置。 - 前記ハイサイド駆動回路は、前記接続点の電圧を動作基準電圧として動作するものであって、
前記ツェナーダイオードは、前記中間電圧を受けて充電される前記補助ブートストラップコンデンサの充電基準電圧を前記ローサイド駆動回路の駆動電源の電圧に規定することを特徴とする請求項1に記載の半導体装置。 - 前記制御回路は、前記ハイサイドスイッチング素子のオン時間が予め設定した時間を上回るとき、前記ブートストラップコンデンサの充電電圧が所定電圧よりも低下したと判断することを特徴とする請求項1に記載の半導体装置。
- 前記スイッチ回路は、前記ハイサイドスイッチング素子のオン時で前記ブートストラップコンデンサの充電電圧が所定電圧よりも低下したときに前記補助ブートストラップコンデンサを前記ハイサイド駆動回路の電源ラインに接続する第1のスイッチおよび第2のスイッチと、前記ハイサイドスイッチング素子がオンで前記第1のスイッチおよび前記第2のスイッチがオフのときに前記補助ブートストラップコンデンサに前記充電基準電圧を印加する第3のスイッチおよび第4のスイッチとを備えたことを特徴とする請求項1に記載の半導体装置。
- 前記第1のスイッチ~前記第4のスイッチは、それぞれ双方向アナログスイッチからなることを特徴とする請求項4に記載の半導体装置。
- 前記制御回路は、トーテムポール接続された前記ハイサイドスイッチング素子と前記ローサイドスイッチング素子との接続点電圧を動作基準電圧として動作するものであって、
前記ハイサイド駆動回路に印加される電源電圧の低下を検出して電圧低下検出信号を出力する電圧低下検出器と、
前記電圧低下検出信号に基づいて前記第1のスイッチ~前記第4のスイッチをそれぞれオン・オフ制御するスイッチ信号を生成する制御ロジック回路とを備えて構成されることを特徴とする請求項4に記載の半導体装置。 - 前記第1のスイッチおよび前記第2のスイッチは、前記第3のスイッチおよび前記第4のスイッチと相補的にオン・オフすることを特徴とする請求項4に記載の半導体装置。
- 前記第1のスイッチは、前記補助ブートストラップコンデンサの充電電圧が前記ブートストラップコンデンサの充電電圧を上回ったときに導通する第1のダイオードからなり、前記第3のスイッチは、前記補助ブートストラップコンデンサの充電電圧が前記ツェナーダイオードにより規定される電圧を下回るときに導通する第2のダイオードからなることを特徴とする請求項4に記載の半導体装置。
- 請求項4に記載の半導体装置において、
更に前記第1および第2のスイッチの導通時に前記ブートストラップコンデンサを前記ローサイド駆動回路の駆動電源から切り離す第5および第6のスイッチ、
並びに前記第5および第6のスイッチに対し相補的に導通して前記ブートストラップコンデンサに前記充電基準電圧を印加する第7および第8のスイッチを備えることを特徴とする半導体装置。 - 前記第5のスイッチ~前記第8のスイッチは、双方向アナログスイッチからなることを特徴とする請求項9に記載の半導体装置。
- 前記ツェナーダイオードのカソードは前記ハイサイドスイッチング素子および前記ローサイドスイッチング素子との接続点に接続され、前記ツェナーダイオードのアノードは前記中間電圧に対する負側の基準電位を規定し、前記ツェナーダイオードのアノード・カソード間電圧が前記充電基準電圧であることを特徴とする請求項1~10のいずれかに記載の半導体装置。
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