WO2017012328A1 - 一种单级功率因数校正的移相全桥拓扑电路 - Google Patents

一种单级功率因数校正的移相全桥拓扑电路 Download PDF

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WO2017012328A1
WO2017012328A1 PCT/CN2016/072691 CN2016072691W WO2017012328A1 WO 2017012328 A1 WO2017012328 A1 WO 2017012328A1 CN 2016072691 W CN2016072691 W CN 2016072691W WO 2017012328 A1 WO2017012328 A1 WO 2017012328A1
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circuit
input
bridge arm
full
inductor
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PCT/CN2016/072691
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English (en)
French (fr)
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孙伟峰
张太之
苏畅
俞居正
钱钦送
陆生礼
时龙兴
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东南大学
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present invention relates to a full-bridge topology circuit for charging, and more particularly to a single-stage power factor correction (PFC) phase-shifted full-bridge topology circuit.
  • PFC power factor correction
  • the well-known charger topology is a two-stage structure.
  • the first stage is usually a boost converter that is used to implement power factor correction (PFC).
  • the second stage is typically a high efficiency isolated dc-dc converter that is used to electrically isolate and control the charging current.
  • full-bridge converters are the most common topology when the output power is in the range of 1-5 kW.
  • the cost and complexity of the overall circuit is greatly improved by the addition of an additional switching converter to the first stage. In addition to this, the efficiency of the entire circuit is also affected.
  • the resonant full-bridge converter can achieve high power factor and constant output voltage by using series-parallel resonance changes.
  • switching tubes require greater voltage stress and variable switching frequency. Control, which brings about problems such as magnetic components and complex filter design, limits its scope of application.
  • a buffer is generally added to the circuit. Such as input storage capacitors to eliminate overshoot and ringing, which in turn will reduce the conversion efficiency of the entire circuit.
  • the present invention proposes a single-stage power factor correction (PFC) phase-shifted full-bridge topology circuit, which reduces cost and circuit complexity, and simultaneously The function of the two-level topology is realized.
  • PFC power factor correction
  • a single-stage power factor correction phase-shifted full-bridge topology circuit including an input storage capacitor, an input rectifier circuit, a full bridge arm circuit, a DC blocking capacitor, a transformer, and an output rectification filter.
  • the circuit, the input storage capacitor is connected in parallel with the full bridge arm circuit, the DC blocking capacitor, the transformer, the output rectification filter circuit and the charged battery are connected in series, connected to the output end of the full bridge arm circuit, input to the storage circuit, the input rectifier circuit,
  • the common ground terminal of the full bridge arm circuit and the DC blocking circuit is connected to the input end ground, and the ground end of the output rectifying and filtering circuit is connected to the output end ground, and is characterized in that: an input inductor L and a freewheeling circuit are added, and the freewheeling circuit and the input inductor L are connected in parallel.
  • One end of the parallel connection one end is connected to the output end of the input rectifier circuit, the other end is connected to the full bridge arm circuit, and the lower switch tube of the lead bridge arm in the full bridge arm circuit is reused as a switch tube in the boost circuit to achieve rectification, Single stage with input inductor L Power factor correction;
  • One end of the input inductor L is connected to the output end of the input rectifier circuit, and the other end of the input inductor L is connected to the connection point of the upper and lower switch tubes of the front bridge arm in the full bridge arm circuit;
  • Freewheeling circuit comprising the freewheeling switch Q f and the freewheeling diode D f, the freewheeling switch L has one end connected to the drain of Q f input inductor, freewheeling switch tube connecting the source level Q f the freewheeling diode D f of the negative electrode The anode of the freewheeling diode D f is connected to the other end of the input inductor L.
  • the present invention realizes a two-stage circuit with a power factor correction function and a phase-shifted full-bridge topology structure by using a primary circuit, which greatly improves the power density of a full-bridge circuit with PFC function, and has a simple structure, low cost, and reliability. High sex.
  • the circuit operates at a constant switching frequency, the control mode is simple and easy, and the input current offset is small.
  • the working mode and process are similar to the standard phase-shifted full-bridge converter.
  • the zero-voltage turn-on of the switch can be realized, which reduces the loss of the circuit and improves the achievability of the circuit.
  • Figure 1 is a schematic diagram of the operation of the circuit of the present invention
  • Figure 2 is an operational waveform of the circuit of the present invention
  • Figure 4 is a graph showing the measured PF value and efficiency of the circuit of the present invention.
  • a single-stage power factor correction (PFC) phase-shifted full-bridge topology circuit of the present invention includes an input storage capacitor (C F ), an input rectifier circuit 2, a full bridge arm circuit 6, and a DC blocking capacitor (C b ). 7, transformer 8 and output rectification filter circuit 9, the above circuit is a known structure of single-stage power factor correction.
  • the input storage capacitor C F is connected in parallel with the full bridge arm circuit 6.
  • the DC blocking capacitor C b , the transformer 8 , the output rectifying and filtering circuit 9 and the charged battery Battery are sequentially connected in series, and are connected to the output end of the full bridge arm circuit 6 and input.
  • the common ground terminal of the storage capacitor C F , the input rectifier circuit 2 , the full bridge arm circuit 6 and the DC blocking capacitor C b is connected to the input terminal, and the ground terminal of the output rectifier filter circuit 9 is connected to the output terminal ground.
  • the present invention adds an input inductor (L) 3 and a freewheeling circuit 4, and the freewheeling circuit 4 and the input inductor L are connected in parallel.
  • the two ends of the parallel connection are respectively connected to the output end of the input rectifier circuit 2 and the bridge arm.
  • Circuit 6, and complex The lower switching transistor circuit 5 of the leading arm of the full bridge arm circuit 6 is used as a switching tube in the boost circuit to realize rectification, and the input inductor L is used together to realize single-stage power factor correction.
  • the positive terminal of the input storage capacitor C F is connected to the common end of the two upper tubes of the full bridge arm circuit 6 , and the negative end of the C F is connected to the input terminal common ground.
  • C F is applied to the input bus and is used in the circuit to reduce voltage overshoot and ringing on the input bus.
  • the input rectifier circuit 2 performs full-wave rectification of the AC input, including an AC input V I and a rectifier bridge composed of four diodes.
  • the AC input V I is connected between the two bridge arms of the rectifier bridge at both ends, and the output end of the rectifier bridge is connected to the input.
  • One end of the inductor L and the other end are connected to the input common ground.
  • the full bridge arm circuit 6 includes four switching tubes Q 1 , Q 2 , Q 3 , Q 4 , Q 1 and Q 2 constitute a leading bridge arm, and Q 3 and Q 4 constitute a lag bridge arm.
  • the lower switching tube Q 2 of the leading bridge arm is multiplexed to form a multiplexing circuit 5, which is rectified as a switching tube in the boost circuit, so that there is no need to add a boost circuit to implement the PFC in the circuit.
  • the multiplexing circuit 5, the full bridge arm circuit 6, the DC blocking capacitor 7, the transformer 8 and the output rectifying and filtering circuit 9 together constitute a standard full bridge converter.
  • the DC blocking capacitor (C b ) 7 is an electrolytic capacitor C b , the positive terminal is connected to the output of the full bridge arm 6 , and the negative terminal is connected to the input terminal of the transformer 8 , which isolates the DC output of the full bridge arm from the rear transformer to avoid The transformer is biased to cause the core to saturate.
  • the transformer 8 is composed of a power transformer T r and a transformer excitation inductance L m equivalently, L m and T r primary windings are connected in parallel, the primary side is connected to the output of the full bridge arm, the secondary winding leads three taps, and the output rectifier filter circuit is connected. 9, to achieve energy transfer and voltage conversion.
  • the output rectification filter circuit 9 includes two diodes D R1 and D R2 and a filter inductor L o and a capacitor C o .
  • the anodes of the two diodes D R1 and D R2 are respectively connected to the first and third taps of the transformer secondary winding. , and a cathode sequentially together with the filter inductor L o, the filter capacitor C o, B attery batteries to be charged in series, the last access intermediate tap of the secondary winding of the transformer.
  • the input inductor (L) 3 is connected to the switch transistor Q 2 , and the input inductor L is used as a freewheeling inductor in the boost circuit for realizing the PFC, and the single-stage PFC function is realized together with the switch transistor Q 2 .
  • One end of the L is connected to the output end of the input rectifying circuit 2, and the other end is connected to the connection point A of the upper and lower switching tubes of the front arm of the bridge arm circuit, that is, one end of the full bridge arm 6 is output.
  • Freewheeling circuit comprising the freewheeling 4 Q f power switch and freewheeling diode D f, L the inductance of the input end connected to the drain-wheeling power switch Q f freewheeling power MOSFET switch connected to the source level Q f the freewheeling diode D f of the negative electrode, a positive freewheeling diode D f is connected to the other end of the inductor L is input.
  • the freewheeling power switch Q f and the diode D f are connected in parallel on both sides of the input inductor L.
  • V CF is a constant value in the pseudo current continuous mode
  • the duty ratios of the switching tubes Q 4 and Q 2 are equal
  • the gate driving signals of the switching tubes Q 1 and Q 3 are complementary to Q 2 and Q 4 respectively, that is, when converting The upper tube on the bridge arm is opened and the lower tube is closed, and vice versa.
  • the charging current is controlled by the phase shift of the gate drive signal on the two bridge arms, and the phase shift difference between the two bridge arms is Although the positive and negative voltages of the primary side of the transformer are asymmetrical, the volt-second balance can still be achieved.
  • da is less than 0.5
  • the bridge arms of the switch tubes Q 1 and Q 2 are super forearms, and vice versa.
  • the input inductor current I L is decreased, and the capacitor C F is charged for a time interval of d b T. During this time interval, the switching transistors Q 2 and Q f are both turned off. Let Q 2 turn off and Q f turn on for d c T. During this time, the input inductor current is in freewheel mode and remains unchanged.
  • n is the turns ratio of the transformer
  • V o is the output voltage of the converter
  • L o is the output inductance
  • L r is the series resonant inductor value of the transformer.
  • V m is the leakage inductance voltage
  • I REF (t p ) represents the average value of the input current of the previous period
  • L is the input inductance value
  • the forward voltage V CF is applied to the series inductance of the resonant inductor and the refractive inductance of the output inductor on the primary side. Therefore, in this mode, the current flowing through the primary side of the transformer and the output inductor rises.
  • the primary current of the transformer is given by
  • V CF is the voltage value on the storage capacitor, and the positive voltage direction is as shown in Figure 1.
  • the current in the inductor is given by
  • Mode 2 ends when switch Q 2 is turned off.
  • the length of time of modal 1 and modal 2 is the time interval d a T.
  • the primary current of the transformer is given by
  • V L
  • V CF When V CF is greater than V m , the input inductor current begins to decrease.
  • the current in the inductor is given by
  • the inductance of the inductor on the primary inductance of the series inductance, the current flowing through the primary side of the transformer and the output inductor rises, the value is given by
  • the working mode and process of the present invention are similar to a standard phase-shifted full-bridge converter, and the zero-voltage turn-on of the switch tube can be realized. Therefore, the present invention has low loss during operation, high reliability, and is easy to implement in a circuit.
  • the phenomenon is that the flow velocity is too obvious in the upper and lower flow velocity of the water flow, and does not conform to the characteristics of the continuity of the natural water flow.
  • the fitted data has a steep change, the flow rate data can be improved by the fitting method based on the maximum flow velocity.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Rectifiers (AREA)

Abstract

一种单级功率因数校正的移相全桥拓扑电路，包括输入储能电容（1）、输入整流电路（2）、全桥臂电路（6）、隔直电容（7）、变压器（8）和输出整流滤波电路（9）。移相全桥拓扑电路增设输入电感（3）和包括续流开关管（Q f）和续流二极管（D f）构成的续流电路（4），续流电路和输入电感并联，并联后的一端连接输入整流电路的输出端，另一端连接全桥臂电路，并且复用全桥臂电路中超前桥臂的下开关管（Q 2）作为升压电路中的开关管实现整流，与输入电感共同实现单级功率因数校正。移相全桥拓扑电路将具有功率因数校正功能和移相全桥拓扑结构的两级电路用一级电路实现，提高了带有功率因数校正功能的全桥电路的功率密度，而且结构简单，成本低，可靠性高。

Description

一种单级功率因数校正的移相全桥拓扑电路 技术领域
本发明涉及充电用全桥拓扑电路，尤其涉及一种单级功率因数校正(PFC)的移相全桥拓扑电路。
背景技术
近年来，混合动力汽车的电机驱动和能量存储技术高速发展，与此同时，电池充电机也成为混合动力汽车发展的一项关键性需求。
广为人知的充电机拓扑电路是一种两级结构。第一级通常是一路boost变换器，被用来实现功率因数校正(PFC)。第二级通常是一个高效率的隔离dc-dc变换器，被用来实现电气隔离和控制充电电流。通常情况下，在输出功率在1-5kW范围内时，全桥变换器是最常用的拓扑结构。然而，在两级结构中，由于第一级加入了一路额外的开关变换器，使整个电路的成本和复杂程度都提高许多。除此之外，整个电路的效率也由此受到影响。
在现有的一些单级结构中，谐振全桥变换器利用串并联的谐振变化可以实现高的功率因数和恒定的输出电压，然而这类开关管需要更大的电压应力和可变的开关频率控制，带来了磁元件以及滤波器设计复杂等问题，限制了其适用范围。还有一些电流反馈型滤波器，通过开启一或两条桥臂上的开关管来实现输入电流的整流，为解决这类拓扑的电压超调与振铃问题，一般在电路中加入缓冲器(如输入储能电容)来消除超调和振铃，这又将会降低整个电路的转化效率。
发明内容
为了利用单级的拓扑结构实现PFC、电气隔离和充电电流控制，本发明提出了一种单级功率因数校正(PFC)的移相全桥拓扑电路，既降低了成本和电路的复杂程度，同时又实现了两级拓扑的功能。
实现上述目的，本发明采用如下技术方案：一种单级功率因数校正的移相全桥拓扑电路，包括输入储能电容、输入整流电路、全桥臂电路、隔直电容、变压器和输出整流滤波电路，输入储能电容与全桥臂电路并联，隔直电容、变压器、输出整流滤波电路及被充电的蓄电池依次串联，连接于全桥臂电路的输出端，输入储能电路、输入整流电路、全桥臂电路以及隔直电路的公共接地端连接输入端地，输出整流滤波电路的接地端连接输出端地，其特征在于：增设输入电感L和续流电路，续流电路和输入电感L并联，并联后的两端中，一端连接输入整流电路的输出端，另一端连接全桥臂电路，并且复用全桥臂电路中超前桥臂的下开关管作为boost电路中的开关管实现整流，与输入电感L共同实现单级 功率因数校正；其中：
输入电感L的一端连接输入整流电路的输出端，输入电感L的另一端连接全桥臂电路中超前桥臂上、下开关管的连接点；
续流电路包括续流开关管Qf和续流二极管Df，续流开关管Qf的漏极连接输入电感L的一端，续流管开关Qf的源级连接续流二极管Df的负极，续流二极管Df的正极连接输入电感L的另一端。
本发明具有如下优点：
1)本发明将具有功率因数校正功能和移相全桥拓扑结构的两级电路用一级电路实现，大大提高了带有PFC功能全桥电路的功率密度，而且其结构简单，成本低，可靠性高。
2)在实现功率因数校正的同时，可以保证***较大功率的输出(＞500W)。
3)复用了全桥变换器桥臂中的一只开关管实现功率因数校正，使电路拓扑简单，成本低，且效果和可靠性好。
4)电路工作在恒定的开关频率下，控制模式简单易行，同时输入电流失调较小。
5)工作模态和过程类似于标准的移相全桥变换器，开关管的零电压开启可以实现，降低了电路的损耗，提高了电路的可实现性。
6)由于加入了输入电感，使电路工作在“伪连续电流模式”，实现了输出电压可控。
附图说明
图1是本发明电路工作原理图；
图2是本发明电路的工作波形；
图3是本发明电路的输入电流电压实测波形；
图4是本发明电路的实测PF值与效率折线图。
具体实施方式
如图1，本发明一种单级功率因数校正(PFC)移相全桥拓扑电路包括输入储能电容(CF)1、输入整流电路2、全桥臂电路6、隔直电容(Cb)7、变压器8和输出整流滤波电路9，以上电路为单级功率因数校正的一种已知结构。输入储能电容CF与全桥臂电路6并联，隔直电容Cb、变压器8、输出整流滤波电路9及被充电的蓄电池Battery依次串联，连接于全桥臂电路6的输出端，输入储能电容CF、输入整流电路2、全桥臂电路6以及隔直电容Cb的公共接地端连接输入端地，输出整流滤波电路9的接地端连接输出端地。
在上述电路的基础上，本发明增设输入电感(L)3和续流电路4，续流电路4和输入电感L并联，并联后的两端分别连接输入整流电路2的输出端及桥式臂电路6，并且复 用全桥臂电路6中超前桥臂的下开关管电路5作为boost电路中的一个开关管实现整流，与输入电感L共同实现单级功率因数校正。
输入储能电容CF的正端连接全桥臂电路6两只上管的公共端，CF的负端连接输入端公共地。CF加在输入母线上，在电路中用于减小输入母线上的电压过冲和振铃。
输入整流电路2将交流输入进行全波整流，包括交流输入VI和四只二极管构成的整流桥，交流输入VI两端接入整流桥的两支桥臂中间，整流桥的输出端连接输入电感L的一端，另一端接入输入端公共地。
全桥臂电路6包括四个开关管Q1、Q2、Q3、Q4，Q1和Q2构成超前桥臂，Q3和Q4构成滞后桥臂。同时将超前桥臂的下开关管Q2进行复用，构成复用电路5，作为boost电路中的开关管实现整流，这样电路中就无需增加一个boost电路来实现PFC。复用电路5、全桥臂电路6、隔直电容7、变压器8和输出整流滤波电路9共同组成了一个标准的全桥变换器。
隔直电容(Cb)7为一只电解电容Cb，正端接全桥臂6的输出，负端接变压器8输入端，它将全桥臂输出的直流量与后级变压器隔离，避免了变压器偏磁从而导致磁芯饱和。
变压器8由功率变压器Tr和变压器励磁电感感Lm等效组成，Lm和Tr原边绕组并联，原边接全桥臂的输出，副边绕组引出三个抽头，连接输出整流滤波电路9，实现能量的转移和电压的变换。
输出整流滤波电路9包括两个二极管DR1和DR2以及滤波电感Lo和电容Co，两只二极管DR1和DR2的阳极分别接变压器副边绕组引出的第一个、第三个抽头，阴极接在一起并依次与滤波电感Lo、滤波电容Co、待充电蓄电池Battery串联，最后接入变压器副边绕组的中间抽头。两个二极管DR1和DR2、滤波电感Lo和电容Co一同构成了全波整流电路，将变压器8输出的非直流正负电压整流成为直流电压，供给蓄电池Battery充电。
输入电感(L)3连接到开关管Q2，输入电感L作为用以实现PFC的boost电路中的续流电感，与开关管Q2共同实现了单级PFC的功能。L的一端连接输入整流电路2的输出端，另一端连接桥式臂电路中超前桥臂上、下开关管的连接点A，即全桥臂6的一端输出。
续流电路4包括续流功率开关管Qf和续流二极管Df，续流功率开关管Qf的漏极连接输入电感L的一端，续流功率管开关Qf的源级连接续流二极管Df的负极，续流二极管Df的正极连接输入电感L的另一端。续流功率开关管Qf和二极管Df并联在输入电感L的两侧。加入续流MOSFET(Qf)和续流二极管(Df)可以让boost和全桥变换这两个功率转换过程分离，消除了两级之间的互相限制。
为了简化分析，假设所有元件均为理想状态且忽略变压器的漏感。假设开关管Q2的驱动信号占空比为da，电感电流IL在时间间隔daT内上升。在伪电流连续模式的控制下，da恒定不变(典型开关频率100Hz)，电路的工作状态类似于移相全桥变换器。VCF在伪电流连续模式下为恒定值，开关管Q4与Q2的占空比相等，开关管Q1与Q3的栅极驱动信号分别于Q2与Q4互补，即当一个转换桥臂上的上管开启，下管关闭，反之亦然。充电电流由两支桥臂上开关管栅极驱动信号的相移来控制，设两支桥臂的相移差为
Figure PCTCN2016072691-appb-000001
尽管变压器原边的正负电压不对称，依旧可以实现伏秒平衡。当da小于0.5时，开关管Q1和Q2所在桥臂为超前臂，反之为滞后臂。设输入电感电流IL下降、电容CF充电的时间间隔为dbT，在此时间间隔内开关管Q2和Qf均为关断。设Q2关断、Qf开启的时间间隔为dcT，在这段时间内输入电感电流处于续流模式，保持不变。
结合图2，分析电路工作在以下模态。
模态1(t0＜t＜t1)：在t＝t0时，开关管Q2开启。在整个模态1过程中，开关管Q2和Q4都保持在开启状态。变压器原边电压VAB为零且变压器漏感电流下降，没有能量传递给储能电容CF，变压器原边电流由下式给出
Figure PCTCN2016072691-appb-000002
式中n为变压器的匝比，Vo为变换器输出电压，Lo为输出电感，Lr为变压器串联谐振电感值。
与此同时，由于开关管Q2处于开启状态，输入电压加在输入电感L的两端，流过电感L中的电流增大，电感中电流由下式给出
Figure PCTCN2016072691-appb-000003
式中Vm为漏感电压，IREF(tp)代表上个周期输入电流的平均值，L为输入电感值。
当开关管Q4关断、Q3开启时，模态1结束。这里的讨论忽略死区时间，开关管Q3的零电压开启是在死区时间里完成的。
模态2(t1＜t＜t2)：在t＝t1时，开关管Q3开启。在此模态过程中，能量从dc母线经由变压器传递给输出。正向电压VCF加在了谐振电感和输出电感在原边的折射电感所组成的串联电感上，因此，在此模态中，流经变压器原边和输出电感的电流上升。变压器原边电流由下式给出
Figure PCTCN2016072691-appb-000004
式中VCF为储能电容上的电压值，电压正方向如附图1所示。
电感中电流由下式给出
Figure PCTCN2016072691-appb-000005
当开关管Q2关断时，模态2结束。模态1和模态2的时间长度即为时间间隔daT。
模态3(t2＜t＜t3)：在t＝t2时，开关管Q2关断、Q1打开。由于开关管Q2关断，能量传输结束，原边电流经由开关管Q1和Q3续流。变压器原边电流由下式给出
Figure PCTCN2016072691-appb-000006
与此同时，储存在输入电感L中的能量给储能电容CF充电，输入电感L两端的电压
由下式给出
VL＝|Vmsinωt|-VCF     (6)
式中当VCF大于Vm时，输入电感电流开始减小。电感中电流由下式给出
Figure PCTCN2016072691-appb-000007
当开关管Qf打开时，模态3结束，此时电感L中的电流等于本周期的平均参考电流，即
IL(t3)＝IREF(t3)     (8)
模态4(t3＜t＜t4)：在t＝t3时，开关管Qf开启，变压器原边电流继续由开关管Q1和Q3续流，其值由下式给出
Figure PCTCN2016072691-appb-000008
由于开关管Qf开启，输入电感两端的电压近似为零，流经输入电感的电流不变，其值由下式给出
IL(t)＝IREF(t3)    (10)
当开关管Q4开启、Q3关断时，模态4结束。
模态5(t4＜t＜t5)：在t＝t4时，开关管Q4开启，能量又开始从dc母线经由变压器传递 给输出，正向电压VCF加在了谐振电感和输出电感在原边的折射电感所组成的串联电感上，流经变压器原边和输出电感的电流上升，其值由下式给出
Figure PCTCN2016072691-appb-000009
由于开关管Qf依旧处于打开状态，流经输入电感的电流保持不变，即
IL(t)＝IREF(t3)    (12)
当开关管Q2开启时，这个模式结束，同时又开始了下一个工作循环(t5＜t＜t10)。
通过对这几个模态的分析表明，采用本发明，用于对输入电流整流的占空比da的选择不再受限，配合合理的驱动器以及变压器匝比的设计，调节输入电压时不会引起输入电流的失调。由于占空比da可以设定到接近0.5，变压器的匝比可以设计的更大，降低电流的环流损耗得以降低。通过实测图3可知，输入电流与输入电压的一致性好，PF值高，电路的功率因数校正效果好。通过实测图4可知，电路在全功率范围内的效率和PF值都比较高。此外本发明的工作模态和过程类似于标准的移相全桥变换器，开关管的零电压开启可以实现，因此本发明工作时损耗小，可靠性高，易于电路实现。
的现象是流速在水流上层和近底部的流速差距过于明显，不符合自然界水流连续性变化的特性，而经过拟合的数据虽然有陡峭变化，但基于其最大流速在拟合方法可以提高流速数据

Claims (1)

  1. 一种单级功率因数校正的移相全桥拓扑电路，包括输入储能电容、输入整流电路、全桥臂电路、隔直电容、变压器和输出整流滤波电路，输入储能电容与全桥臂电路并联，隔直电容、变压器、输出整流滤波电路及被充电的蓄电池依次串联，连接于全桥臂电路的输出端，输入储能电路、输入整流电路、全桥臂电路以及隔直电路的公共接地端连接输入端地，输出整流滤波电路的接地端连接输出端地，其特征在于：增设输入电感L和续流电路，续流电路和输入电感L并联，并联后的两端中，一端连接输入整流电路的输出端，另一端连接全桥臂电路，并且复用全桥臂电路中超前桥臂的下开关管作为boost电路中的开关管实现整流，与输入电感L共同实现单级功率因数校正；其中：
    输入电感L的一端连接输入整流电路的输出端，输入电感L的另一端连接全桥臂电路中超前桥臂上、下开关管的连接点；
    续流电路包括续流开关管Qf和续流二极管Df，续流开关管Qf的漏极连接输入电感L的一端，续流管开关Qf的源级连接续流二极管Df的负极，续流二极管Df的正极连接输入电感L的另一端。
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