US5537015A - Semiconductor circuit for a DC motor - Google Patents

Semiconductor circuit for a DC motor Download PDF

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Publication number
US5537015A
US5537015A US08/305,145 US30514594A US5537015A US 5537015 A US5537015 A US 5537015A US 30514594 A US30514594 A US 30514594A US 5537015 A US5537015 A US 5537015A
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Prior art keywords
voltage
motor
collectorless
rectifier
circuit
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Expired - Fee Related
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US08/305,145
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English (en)
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Arno Karwath
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Ebm Papst St Georgen GmbH and Co KG
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Papst Motoren GmbH and Co KG
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Assigned to PAPST-MOTOREN GMBH & CO. KG reassignment PAPST-MOTOREN GMBH & CO. KG ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: KARWATH, ARNO
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P29/00—Arrangements for regulating or controlling electric motors, appropriate for both AC and DC motors
    • H02P29/02—Providing protection against overload without automatic interruption of supply
    • H02P29/024—Detecting a fault condition, e.g. short circuit, locked rotor, open circuit or loss of load
    • H02P29/026—Detecting a fault condition, e.g. short circuit, locked rotor, open circuit or loss of load the fault being a power fluctuation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
    • H02H7/00—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions
    • H02H7/08—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for dynamo-electric motors
    • H02H7/0833—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for dynamo-electric motors for electric motors with control arrangements
    • H02H7/0838—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for dynamo-electric motors for electric motors with control arrangements with H-bridge circuit
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
    • H02P6/08—Arrangements for controlling the speed or torque of a single motor
    • H02P6/085—Arrangements for controlling the speed or torque of a single motor in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
    • H02P6/34—Modelling or simulation for control purposes
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P2201/00—Indexing scheme relating to controlling arrangements characterised by the converter used
    • H02P2201/07—DC-DC step-up or step-down converter inserted between the power supply and the inverter supplying the motor, e.g. to control voltage source fluctuations, to vary the motor speed

Definitions

  • the present invention relates generally to a collectorless dc motor commutated by a semiconductor circuit and, more particularly, to an improvement in such a semiconductor circuit.
  • dc motors are particularly well adapted, especially those operated in bridge circuits, since this permits a broad control range and simple control interventions. This is especially true of so-called two-pulse collectorless dc motors, as shown in U.S. Pat. No. 3,873,897, Mueller/Papst-Motoren, and German DE 23 46 380 C3.
  • motors are constructed in single-strand (single-phase) form, this results in a very simple circuit and a simple motor structure, since only a single stator winding must be included, and the motor can thus be made compact.
  • the present invention can also be used in multi-strand motors, e.g. for three-stranded (three-phase) motors which have three-pulse or six-pulse operating schemes.
  • both the number of pulses and the number of phases must be specified.
  • one branch of the circuit employs pnp transistors, and the other branch employs npn transistors. While there are npn transistors whose voltage tolerance extends to 400 V, the highest voltage tolerance of pnp transistors is usually around 300 V, or maximally 350 V.
  • this is accomplished by an arrangement with a collectorless dc motor commutated by a semiconductor circuit, with a rectified-current intermediate circuit supplied via a rectifier from an AC current network, the intermediate circuit having an input to which is applied a fluctuating rectified current with predetermined maximum values, with a transistor located between the rectifier and the collectorless dc motor, the transistor being driven as a variable resistor, and with limiting means, for limiting the voltage at the control input of this transistor to a value smaller than the predetermined maximal value of the fluctuating rectified voltage and which control voltage falls within the voltage-tolerance range of the semiconductor driving circuit of the collectorless dc motor.
  • the use of the limiting means in combination with the transistor operated as a variable resistor, limits the voltage in the rectified-current intermediate circuit to an upper value, e.g. 270 V, so that standard commercial pnp- and npn-transistors can be used for the semiconductor driving circuit for commutation of the collectorless dc motor, and in this manner the semiconductor circuit is protected from overvoltage conditions.
  • an upper value e.g. 270 V
  • FIG. 1 is a diagram of the present invention, in which the commutating circuit, the rotary speed control, and the collectorless dc motor are only schematically illustrated;
  • FIG. 2 is a diagram of a rotary speed control circuit which can advantageously be used in the device of FIG. 1;
  • FIG. 3 is a diagram which explains the operation of FIG. 2, showing the voltage variations on capacitor 68, shown in FIG. 2;
  • FIG. 4 is a diagram of a so-called Hall integrated circuit (IC) with two anti-valent outputs, so arranged that a small current gap occurs in the region of commutation;
  • IC Hall integrated circuit
  • FIG. 5 is a diagram which explains the operation of the Hall IC of FIG. 4;
  • FIG. 6 illustrates a first variant of the circuit of FIG. 1
  • FIG. 7 illustrates a second variant of the circuit of FIG. 1.
  • FIG. 1 illustrates a preferred embodiment 10 of the invention. It has a standard bridge rectifier 11 for rectification of the network alternating voltage U N of, for example, 230 V, 50 Hertz. From this, there results, at the outputs + and - of rectifier 11, a pulsing dc voltage. This is fed via a transistor 12 to a rectified-current intermediate circuit across whose connecting lines 13 (+) and 14 (-), during operation, an intermediate circuit voltage U ZK is applied.
  • a symbolic separation line 20 is shown dashed; it intersects with connecting points A, B, and C. Reference will be made to this separation line 20 and points A, B, C in describing FIGS. 6 and 7 below.
  • a measuring resistor 17 serves for measurement of the current which flows to the single stator winding 18 of a collectorless dc motor 19, whose permanent-magnet rotor 22 is shown schematically at 22.
  • Motor 19 is preferably a two-pulse single-strand collectorless dc motor; these terms are defined in the aforementioned literature reference ASR Digest.
  • motor 19 has a rotor position sensor 23, whose preferred structure as a Hall IC is set forth in FIGS. 4 and 5.
  • the npn transistor 12 is connected as an emitter follower, i.e. its collector is at the output + of rectifier 11, and its emitter is at terminal 13 of rectified-current intermediate circuit 13, 14, while its base is connected to the cathode of a zener diode 25, whose anode is connected to the negative line 14, which in turn is connected to ground.
  • transistor 12 reproduces the voltage at the output of Zener diode 25 on the rectified-current intermediate circuit 13, 14, i.e. the voltage U ZK can not exceed this maximum value, for example 270 volts.
  • the voltage at Zener diode 25 can be reduced using a voltage divider, formed by a resistor 27 (between the Zener diode and the collector of transistor 12) and an NPN setting transistor 28, whose collector is connected with the base of transistor 12 and whose emitter is connected with line 14, while to its base is applied a signal Y frown a rotation speed controller 30, whose preferred structure is shown in FIG. 2.
  • a voltage divider formed by a resistor 27 (between the Zener diode and the collector of transistor 12) and an NPN setting transistor 28, whose collector is connected with the base of transistor 12 and whose emitter is connected with line 14, while to its base is applied a signal Y frown a rotation speed controller 30, whose preferred structure is shown in FIG. 2.
  • the voltage at Zener diode 25 can be reduced, which will also correspondingly reduce voltage U ZK . This permits, in a very simple manner, a quick-responding control of rotation speed.
  • the transistor 12 is preferably a Darlington transistor.
  • Resistor 27 is preferably so dimensioned that transistor 12 can never be fully turned on. A voltage drop across transistor 12 results, and in normal operation, this limits the voltage U ZK .
  • Zener diode 25 serves as supplemental security, since the current-amplification factors of the transistors 12 have great excursions or variations.
  • Capacitor 16 smooths the voltage U ZK and takes up or absorbs the free-running currents of the stator winding 18 during commutation or during current limitation, which improves the efficiency. Capacitor 16 becomes repeatedly charged only up to a voltage specified by transistor 12 and the voltage on its base. Depending upon its capacitance, there results a corresponding residual wariness or ripple of voltage U ZK . This capacitance should be chosen sufficiently large that the frequency of the ripple of U ZK does not carry over to influence the motor RPM.
  • a full bridge circuit 33 serves to control or regulate the stator winding 18.
  • This has the usual H-shape, in which the upper branch has two PNP transistors 34, 35 and the lower branch has two NPN transistors 36, 37.
  • the voltage tolerance of transistor 34, 35 is approximately 300 V.
  • Connected in antiparallel to each of transistors 34, 35 is a respective recovery diode 38, 39; these become effective upon commutation and during current limitation.
  • the commutation is controlled by rotary position sensor 23, whose output signals Q1, Q2 are fed to a commutating circuit 42, which correspondingly controls transistors 34 through 37, and assures short current pauses upon commutation, so that transistors 34 through 37 of bridge 33 are never all simultaneously conductive; such a short-circuit condition would immediately destroy transistors 34 through 37.
  • These current pauses are derived from rotary position sensor 23, whose output waveforms Q1 and Q2 are, as shown in FIG. 3, separated from each other by a gap a.
  • these current pauses are used also for rotation speed control.
  • current can flow through winding 18 via one of respective recovery diodes 38, 39 into capacitor 16, which provides energy recovery.
  • the motor current is limited by a current limitation subcircuit 44, which measures the current at measuring resistor 17 and blocks both upper bridge transistors 34, 35 when this current becomes too great. Alternately, circuit 44 can block both lower bridge transistors 36, 37, which under certain circumstances is more advantageous, since line 13 carries a potential of +270 V, while line 14 carries a potential of zero V.
  • a corresponding circuit for current limitation is described in detail in Papst-Motoren German Utility Model 92 04 811, the contents of which are incorporated by reference.
  • FIG. 4 illustrates a preferred form of rotary position sensor 23.
  • the output signals of its Hall element 46 are amplified by a respective associated transistor 47, 48.
  • Each transistor is connected via a respective collector resistor 49,50 and a common diode to the positive voltage terminal Vcc.
  • a tap Between each collector and its associated collector resistor 49, 50, is a tap which leads via a respective resistor 52, 53 to respective outputs Q1, Q2.
  • transistor 48 switches on at time 58 and switches off at time 59, these points being separated by switching hysteresis Hys. 2, as shown.
  • Signals Q1, Q2 therefore have between them the aforementioned gaps a, whose size is a function of the form of magnetization of rotor 22, but which are present in every case, as those skilled in the art will immediately recognize.
  • signals Q1 and Q2 of sensor 23 pass respectively through identical resistors 62 and 63 and are logically combined in commutation circuit 42. At the output of these resistors, there is thus the signal X (shown also in FIG. 1) which combines signals Q1 and Q2 like an OR operator and is only low during the gaps a. This low signal serves as a rotary speed signal. It immediately goes high whenever one of signals Q1 and Q2 is present.
  • This signal X is fed, as shown in FIG. 2, to the base of an NPN transistor 65, which is therefore blocked only during the gaps a (FIGS. 3 and 5).
  • an NPN transistor 66 connected to it, remains conductive and very quickly discharges a capacitor 68, which is connected in parallel to transistor 66 to ground.
  • capacitor 68 continuously receives charging current via a charging resistor 70 which is connected to a positive voltage line 71. After the end of each gap a, i.e. after the end of the discharge, the capacitor begins again to charge, and is fed charging current via resistor 70 until the next gap a occurs.
  • FIG. 3 is a graph of the voltage u on capacitor 68.
  • the time interval T (FIG. 3) is longer at low rotation speeds, and voltage u on capacitor 68 can therefore reach higher values at low rotation speeds than at high rotation speeds.
  • the peak voltage on capacitor 68 is thus a function of rotation speed, i.e. when rotation speed rises, the peak voltage is reduced.
  • This voltage is fed via a resistor 73 to the - input of an operational amplifier 74, which is connected as a differential amplifier and integrator. For this purpose, between its output 25 and its - input, there are connected, in parallel, a resistor 76 and a capacitor 77.
  • the "target value" signal 80 (FIGS. 1, 2, 6 & 7) for the rotation speed is a Pulse Width Modulation (PWM) signal which is fed to the input w of an optical coupler 82, which furnishes at its output a corresponding signal w'.
  • PWM Pulse Width Modulation
  • the information content of this signal is in its duty factor (see German Utility Model DE-Gm 92 04 811) and this information can control various functions of motor 19, as thoroughly described in the Utility Model.
  • Signal w' is integrated using a resistor 83 and a capacitor 84, and converted into a rectified voltage, whose height is dependent upon the duty factor. This rectified voltage is fed to the + input of operational amplifier 74.
  • Resistors 85, 86, and 87, shown in FIG. 2, serve for level matching for the input of operational amplifier 74.
  • the difference between the rotation rate target value signal (voltage on capacitor 84) and the rotation rate actual value signal (voltage on capacitor 68) is amplified in operational amplifier 74, and integrated by capacitor 77. Through the integration, there results, at output 75 of operational amplifier 74, a rectified voltage signal Y, which linearly controls, via resistor 90, the setting transistor 28 (FIG. 1). During the control process, the resistance of transistor 12 is correspondingly varied, to increase or decrease voltage U ZK correspondingly.
  • the rotation speed controller according to FIG. 2 is a P-controller; its amplification factor (P-component) is determined by the ratio of resistances 73 and 76.
  • FIG. 6 illustrates a first variant of the circuit of FIG. 1.
  • the only components newly represented are those which in FIG. 1 fall to the left of symbolic separating line 20.
  • the components to the right of separating line 20 are the same as those in FIG. 1.
  • the bipolar transistor 12 is replaced by a power MOSFET 112 (here an n-channel MOSFET), which is better adapted for the application than a bipolar power transistor (MOSFET is an acronym for Metal Oxide Semiconductor Field Effect Transistor).
  • MOSFET is an acronym for Metal Oxide Semiconductor Field Effect Transistor.
  • the drain D of MOSFET 112 is connected to the + output of rectifier 11; source S is connected to line 13, and gate G is connected to the collector of setting transistor 28.
  • This circuit operates fully analogously to that of FIG. 1, i.e., the voltage on source S follows the voltage on gate G just as, with the emitter circuit of FIG. 1, the voltage at the emitter of transistor 12 follows the voltage at its base. Assuming, e.g., that the voltage at gate G is 100 V, the voltage at source S will be about 95 V, namely the gate voltage less the gate-source voltage drop of about 4.5 V. By analogy to the "emitter circuit" one could call this circuit a "source circuit.” For one skilled in the art, it is clear that in principle these are the same circuit, even though there is a familiar designation for only one of the circuits.
  • the circuit of FIG. 6 provides a particularly good control characteristic. If an abrupt change of target value signal 80 at a high rotation speed suddenly presents a target value for a low rotation speed, the motor is braked by the circuit of FIG. 6. In this case, transistor 28 fully conducts, and the Zener diode 121 is driven in the forward direction, so that a braking current iB flows, as shown by the dashed line in FIG. 6. This current drains off toward ground the energy stored in capacitor 16 (FIG. 1), thereby braking motor 19, which is driven in this case in a generating mode and practically as a short circuit. When such a braking mode of operation is desired, Zener diode 121 and setting transistor 28 must be rated for a sufficiently high power level.
  • this braking-operation mode also occurs with the circuit of FIG. 1, since there the base-emitter path of transistor 12 operates in this case like a Zener diode, so that a braking current also flows there.
  • a braking-operation mode is not desired, in order to avoid higher costs for setting transistor 28, one can connect a diode 122 between MOSFET 112 and point A, as shown in FIG. 7.
  • the diode blocks the flow of the current i B shown in FIG. 6. If the circuit of the invention is used, e.g., for driving the motor 19 of a blower (not shown), a faster braking process is unnecessary, since the blower inherently goes slower when less energy is fed to it.
  • Diode 122 can be used, in the same fashion in the circuit of FIG. 1, in order to hinder the flow of a braking current.
  • Suitable components/values for the circuit of FIG. 7 are:
  • the end stage 33 does not absolutely have to be a full bridge.
  • a two-stranded or two-phase solution would also be possible, as shown in EP 0 467 085 A1, HANS & MOINI.
  • the voltage U ZK can be higher, so that the losses in transistor 12 or 112 become smaller.
  • the embodiments shown are preferred. Still other variations are possible.
  • a very important advantage of the present invention is the elimination of the need for a component to supply low voltage to motor 19. This avoids significant expense. However, there are increased costs for a higher insulation class for winding 18, and due to the use of power transistors with high voltage tolerance and due to the use of correspondingly powerful transistors 12 and 112. Overall, there is a substantial savings in cost--and in required size--as a result of the present invention.
  • the invention can be used in many applications, e.g. for fans, vacuum cleaners, scanners, pump, medical-technical devices, blowers for gas- and oil-burners, and others.
  • the invention has a very broad range of applications or uses, since it also makes possible simple rotational speed control and current limitation. It is particularly advantageous in connection with a single-stranded collectorless dc motor, since here the expense for the electronics, and for the insulation of winding 18, is particularly small.

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  • Power Engineering (AREA)
  • Control Of Motors That Do Not Use Commutators (AREA)
US08/305,145 1993-09-15 1994-09-13 Semiconductor circuit for a DC motor Expired - Fee Related US5537015A (en)

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DE9313948U 1993-09-15

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WO1997015111A2 (en) * 1995-10-17 1997-04-24 Fasco Industries, Inc. A brushless dc motor assembly
GB2317277A (en) * 1996-09-04 1998-03-18 Sunonwealth Electr Mach Ind Co Motor for heat dissipation fans
EP0930697A1 (de) * 1998-01-15 1999-07-21 Plaset S.p.A. System zur steuerung eines büstenlosen Elektromotors
US6111458A (en) * 1997-08-18 2000-08-29 Siemens Aktiengesellschaft Power amplifier and nuclear spin tomography apparatus employing same
US6169378B1 (en) 1996-06-07 2001-01-02 Papst Motoren Gmbh & Co. Kg Electronically commutated motor with galvanically separate user interface circuit
US20020193922A1 (en) * 2001-06-07 2002-12-19 Denso Corporation Abnormality detection apparatus of vehicle AC generator
US6501200B2 (en) * 2000-05-27 2002-12-31 Papst-Motoren Gmbh & Co. Kg Motor arrangement
US20030080709A1 (en) * 1998-08-14 2003-05-01 Jorg Hornberger Arrangement with an electric motor
US20030174456A1 (en) * 2002-02-01 2003-09-18 Minebea Co., Ltd. Pre-drive circuit for brushless DC single-phase motor
US20040036435A1 (en) * 2000-12-28 2004-02-26 Hansjorg Berroth Method for commutating an electronically commutated dc motor, and motor for carrying out said method
US20040160792A1 (en) * 2003-02-14 2004-08-19 Samsung Electronics Co., Ltd. Motor power supply
US6825625B1 (en) 1998-06-13 2004-11-30 Ebm-Papst St. Georgen Gmbh & Co. Kg Device with an electromotor
US20050046364A1 (en) * 2003-09-03 2005-03-03 Yi-Pin Lin Method and circuit for driving a DC motor
US20060072353A1 (en) * 2004-09-30 2006-04-06 Mhaskar Uday P System and method for power conversion
US20070200516A1 (en) * 2006-02-27 2007-08-30 Matsushita Electric Works, Ltd. Control drive circuit for electric power tool
US20090021201A1 (en) * 2007-07-18 2009-01-22 Ampson Technology, Inc. Constant-current and constant-voltage driving circuit of dcbl fan motor with low acoustic noise and controllable speed
US7714355B1 (en) * 2005-12-20 2010-05-11 National Semiconductor Corp Method of controlling the breakdown voltage of BSCRs and BJT clamps
US20140152201A1 (en) * 2011-07-26 2014-06-05 Moog Inc. Electric motor clamping system
EP3327922A1 (de) * 2016-11-29 2018-05-30 Honeywell Technologies Sarl Lüftersteuerkreis

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JP4349120B2 (ja) * 2003-12-19 2009-10-21 株式会社デンソー 伝達比可変操舵装置

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US6111458A (en) * 1997-08-18 2000-08-29 Siemens Aktiengesellschaft Power amplifier and nuclear spin tomography apparatus employing same
EP0930697A1 (de) * 1998-01-15 1999-07-21 Plaset S.p.A. System zur steuerung eines büstenlosen Elektromotors
WO1999037015A1 (en) * 1998-01-15 1999-07-22 Plaset S.P.A. A system for controlling a brushless electric motor
US6060848A (en) * 1998-01-15 2000-05-09 Plaset Spa System for controlling a brushless electric motor
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US20090021201A1 (en) * 2007-07-18 2009-01-22 Ampson Technology, Inc. Constant-current and constant-voltage driving circuit of dcbl fan motor with low acoustic noise and controllable speed
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EP0643473B1 (de) 1998-04-29
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