TWI767346B - Resonant switching power converter - Google Patents
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- TWI767346B TWI767346B TW109134456A TW109134456A TWI767346B TW I767346 B TWI767346 B TW I767346B TW 109134456 A TW109134456 A TW 109134456A TW 109134456 A TW109134456 A TW 109134456A TW I767346 B TWI767346 B TW I767346B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/083—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the ignition at the zero crossing of the voltage or the current
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
Description
本發明係有關於一種諧振切換式電源轉換器,特定而言係有關於一種利用偵測零電流而判斷切換時點之諧振切換式電源轉換器。The present invention relates to a resonant switching power converter, in particular, to a resonant switching power converter that uses detecting zero current to determine the switching time point.
圖1係顯示習知的電源轉換器。於充電操作中,開關Q1、Q3、Q5、Q8、Q9係導通,開關Q2、Q4、Q6、Q7、Q10係不導通,使得電容C1串聯電感L1於輸入電壓VIN及輸出電壓VOUT之間,且電容C2串聯電容C3及電感L2於接地電位及輸出電壓VOUT之間。於放電操作中,開關Q2、Q4、Q6、Q7、Q10係導通,開關Q1、Q3、Q5、Q8、Q9係不導通,使得電感L1串聯電容C1、電容C2於接地電位及輸出電壓VOUT之間,且電感L2串聯電容C3於接地電位及輸出電壓VOUT之間。此習知的電源轉換器之電容需要耐較高的額定電壓,例如電容C1的直流偏壓是輸出電壓的3倍Vc1=3VOUT、電容C2的直流偏壓是輸出電壓的2倍Vc2=2VOUT、電容C3的直流偏壓與輸出電壓相當Vc3=VOUT,因為電容之直流偏壓相對較高,故此習知電源轉換器需要使用具有較大體積的電容。此外,電容的電容值通常會隨著直流偏壓的上升而降低,當輸入電壓的範圍是在36V及76V之間時,電容C1的直流偏壓範圍會是在27V及57V之間,由於直流偏壓的變化範圍較廣,故此習知電源轉換器之電容值變化相當大,其諧振頻率也會隨著電容的變化而改變。如此會造成較大的切換電源損耗並且需要複雜的控制來改變電源轉換效率。再者,此習知電源轉換器之輸入電壓VIN與輸出電壓VOUT之電壓轉換比率僅可為4:1或2:1,並無法進行3:1的電壓轉換比率。圖2係顯示電容的電容值隨著直流偏壓而改變的實例。當直流偏壓增加至50V時電容值降低70%。FIG. 1 shows a conventional power converter. During the charging operation, the switches Q1, Q3, Q5, Q8, and Q9 are turned on, and the switches Q2, Q4, Q6, Q7, and Q10 are turned off, so that the capacitor C1 is connected in series with the inductor L1 between the input voltage VIN and the output voltage VOUT, and The capacitor C2 is connected in series with the capacitor C3 and the inductor L2 between the ground potential and the output voltage VOUT. During the discharge operation, the switches Q2, Q4, Q6, Q7, and Q10 are turned on, and the switches Q1, Q3, Q5, Q8, and Q9 are turned off, so that the inductor L1 is connected in series with the capacitor C1 and the capacitor C2 between the ground potential and the output voltage VOUT. , and the inductor L2 is connected in series with the capacitor C3 between the ground potential and the output voltage VOUT. The capacitor of the conventional power converter needs to withstand higher rated voltage, for example, the DC bias voltage of capacitor C1 is 3 times the output voltage Vc1=3VOUT, the DC bias voltage of capacitor C2 is 2 times the output voltage Vc2=2VOUT, The DC bias voltage of the capacitor C3 is equivalent to the output voltage Vc3=VOUT. Because the DC bias voltage of the capacitor is relatively high, the conventional power converter needs to use a capacitor with a larger volume. In addition, the capacitance value of the capacitor usually decreases as the DC bias voltage increases. When the input voltage range is between 36V and 76V, the DC bias voltage range of capacitor C1 will be between 27V and 57V. The variation range of the bias voltage is wide, so the capacitance value of the conventional power converter varies considerably, and the resonant frequency also varies with the variation of the capacitance. This causes large switching power losses and requires complex control to change the power conversion efficiency. Furthermore, the voltage conversion ratio of the input voltage VIN to the output voltage VOUT of the conventional power converter can only be 4:1 or 2:1, and the voltage conversion ratio of 3:1 cannot be achieved. FIG. 2 shows an example of the capacitance value of the capacitor changing with the DC bias. The capacitance value decreases by 70% when the DC bias is increased to 50V.
有鑑於此,本發明即針對上述先前技術之不足,提出一種創新的電源轉換器。In view of this, the present invention proposes an innovative power converter aiming at the above-mentioned deficiencies of the prior art.
於一觀點中,本發明提供一種諧振切換式電源轉換器,用以將一輸入電壓轉換為一輸出電壓,該諧振切換式電源轉換器包含:複數電容;複數開關,與該複數電容對應耦接;至少一充電電感,與該複數電容中之至少其中之一對應串聯;至少一放電電感,與該複數電容中之至少其中之一對應串聯;一控制器,用以產生一充電操作訊號與至少一放電操作訊號,以分別對應一充電程序與至少一放電程序,而操作對應之該複數開關,以切換所對應之該電容之電連接關係;以及至少一零電流偵測電路,用以於該充電程序時偵測流經該至少一充電電感之一充電諧振電流及/或於該至少一放電程序時偵測流經該至少一放電電感之至少一放電諧振電流,當該至少一零電流偵測電路偵測到該充電諧振電流及/或該至少一放電諧振電流為零時對應產生至少一零電流偵測訊號至該控制器;其中,該充電操作訊號與該至少一放電操作訊號,分別各自切換至一導通位準一段導通期間,且該複數段導通期間彼此不重疊,以使該充電程序與該至少一放電程序彼此不重疊;其中,在該充電程序中,該控制器藉由該充電操作訊號控制該複數開關的切換,使該複數電容與該至少一充電電感彼此串聯於該輸入電壓與該輸出電壓之間,以形成一充電路徑;其中,在該至少一放電程序中,該控制器藉由該至少一放電操作訊號控制該複數開關的切換,使每一該電容與對應之該放電電感串聯於該輸出電壓與一接地電位間,以同時形成或輪流形成複數放電路徑;其中,該控制器根據該至少一零電流偵測訊號,決定該充電程序與該至少一放電程序各自的起始時點與結束時點;其中,該充電程序與該至少一放電程序彼此重複地交錯排序,以將該輸入電壓轉換為該輸出電壓。In one aspect, the present invention provides a resonant switching power converter for converting an input voltage into an output voltage, the resonant switching power converter comprising: a complex capacitor; a complex switch, which is correspondingly coupled to the complex capacitor ; at least one charging inductance, correspondingly connected in series with at least one of the complex capacitors; at least one discharging inductance, correspondingly connected in series with at least one of the complex capacitors; a controller for generating a charging operation signal with at least one of the complex capacitors a discharge operation signal corresponding to a charging process and at least one discharging process respectively, and operating the corresponding switches to switch the electrical connection relationship of the corresponding capacitor; and at least one zero current detection circuit for the Detecting a charging resonant current flowing through the at least one charging inductor during the charging process and/or detecting at least one discharging resonant current flowing through the at least one discharging inductor during the at least one discharging process, when the at least one zero current is detected When the detection circuit detects that the charging resonant current and/or the at least one discharging resonant current is zero, at least one zero current detection signal is correspondingly generated to the controller; wherein the charging operation signal and the at least one discharging operation signal are respectively Each is switched to a conduction level for a conduction period, and the plurality of conduction periods do not overlap each other, so that the charging process and the at least one discharging process do not overlap each other; wherein, in the charging process, the controller uses the The charging operation signal controls the switching of the plurality of switches, so that the plurality of capacitors and the at least one charging inductor are connected in series between the input voltage and the output voltage to form a charging path; wherein, in the at least one discharging process, the The controller controls the switching of the plurality of switches through the at least one discharge operation signal, so that each of the capacitors and the corresponding discharge inductance are connected in series between the output voltage and a ground potential to form a plurality of discharge paths simultaneously or alternately; wherein , the controller determines the respective start time and end time of the charging process and the at least one discharging process according to the at least one zero-current detection signal; wherein, the charging process and the at least one discharging process are repeatedly and staggered in sequence, to convert the input voltage to the output voltage.
於一實施例中, 該控制器更根據該充電操作訊號及/或該至少一放電操作訊號,決定該充電程序與該至少一放電程序各自的起始時點與結束時點。In one embodiment, the controller further determines the respective start time and end time of the charging process and the at least one discharging process according to the charging operation signal and/or the at least one discharging operation signal.
於一實施例中,該至少一零電流偵測電路包含一電流感測電路,用以於該充電程序時感測該充電諧振電流或於該至少一放電程序時感測該至少一放電諧振電流,而產生一電流感測訊號;及一比較器,用以比較該電流感測訊號與一參考訊號,而產生該至少一零電流偵測訊號。In one embodiment, the at least one zero current detection circuit includes a current sensing circuit for sensing the charging resonant current during the charging process or sensing the at least one discharging resonant current during the at least one discharging process to generate a current sensing signal; and a comparator for comparing the current sensing signal with a reference signal to generate the at least one zero current sensing signal.
於一實施例中,該諧振切換式電源轉換器更包含複數開關驅動器,分別耦接於該控制器與對應之該開關之間,用以根據對應之該充電操作訊號或對應之該放電操作訊號,而分別控制該複數開關。In one embodiment, the resonant switching power converter further includes a plurality of switch drivers, which are respectively coupled between the controller and the corresponding switch, and are used for the corresponding charging operation signal or the corresponding discharging operation signal. , and control the complex switches respectively.
於一實施例中,該控制器包括:一邏輯電路,與該至少一零電流偵測電路耦接,用以根據該至少一零電流偵測訊號與該充電操作訊號及/或該至少一放電操作訊號,產生一充電判斷訊號與一放電判斷訊號;以及一決定電路,與該邏輯電路耦接,用以根據該充電判斷訊號與該放電判斷訊號,產生該充電操作訊號與該至少一放電操作訊號,以決定該充電程序與該至少一放電程序各自的起始時點與結束時點。In one embodiment, the controller includes: a logic circuit, coupled to the at least one zero current detection circuit, for the at least one zero current detection signal and the charging operation signal and/or the at least one discharging an operation signal for generating a charging judging signal and a discharging judging signal; and a decision circuit coupled to the logic circuit for generating the charging operating signal and the at least one discharging operation according to the charging judging signal and the discharging judging signal The signal is used to determine the respective start time point and end time point of the charging process and the at least one discharging process.
於一實施例中,該控制器更包含一延遲電路,耦接於該邏輯電路與該決定電路之間,用以延遲該充電程序及/或該至少一放電程序的起始時點一延遲時間。In one embodiment, the controller further includes a delay circuit, coupled between the logic circuit and the decision circuit, for delaying the charging process and/or the starting point of the at least one discharging process by a delay time.
於一實施例中,該充電判斷訊號用以決定該充電程序之起始時點與該至少一放電程序之結束時點。In one embodiment, the charging determination signal is used to determine a start time point of the charging process and an end time point of the at least one discharge process.
於一實施例中,該邏輯電路對該至少一零電流偵測訊號與該充電操作訊號之反相訊號執行及邏輯運算,而產生該充電判斷訊號。In one embodiment, the logic circuit performs and logic operation on the at least one zero-current detection signal and an inversion signal of the charging operation signal to generate the charging determination signal.
於一實施例中,該決定電路包括一第一閂鎖電路,用以根據該充電判斷訊號而設定該充電操作訊號,並根據該放電判斷訊號而切換該充電操作訊號之位準,且產生該充電操作訊號之反相訊號以輸入該邏輯電路。In one embodiment, the determination circuit includes a first latch circuit for setting the charging operation signal according to the charging determination signal, switching the level of the charging operation signal according to the discharging determination signal, and generating the charging operation signal. The inversion signal of the charging operation signal is input to the logic circuit.
於一實施例中,該放電判斷訊號用以決定該至少一放電程序之起始時點與該充電程序之結束時點。In one embodiment, the discharge determination signal is used to determine a start time point of the at least one discharge process and an end time point of the charging process.
於一實施例中,該邏輯電路對該至少一零電流偵測訊號與該至少一放電操作訊號之反相訊號執行及邏輯運算,而產生該放電判斷訊號。In one embodiment, the logic circuit performs and logical operation on the at least one zero-current detection signal and the inverted signal of the at least one discharge operation signal to generate the discharge determination signal.
於一實施例中,該決定電路包括一第二閂鎖電路,用以根據該放電判斷訊號而設定該至少一放電操作訊號,並根據該充電判斷訊號而切換該至少一放電操作訊號之位準,且產生該至少一放電操作訊號之反相訊號以輸入該邏輯電路。In one embodiment, the determination circuit includes a second latch circuit for setting the at least one discharge operation signal according to the discharge judgment signal, and switching the level of the at least one discharge operation signal according to the charge judgment signal , and the inversion signal of the at least one discharge operation signal is generated to be input to the logic circuit.
於一實施例中,該至少一充電電感為單一個充電電感,該至少一放電電感為單一個放電電感。In one embodiment, the at least one charging inductor is a single charging inductor, and the at least one discharging inductor is a single discharging inductor.
於一實施例中,該單一個充電電感之電感值相等於該單一個放電電感之電感值。In one embodiment, the inductance value of the single charging inductor is equal to the inductance value of the single discharging inductor.
於一實施例中,該至少一充電電感與該至少一放電電感為單一個相同電感。In one embodiment, the at least one charging inductor and the at least one discharging inductor are a single same inductor.
於一實施例中,該單一個相同電感為可變電感。In one embodiment, the single identical inductor is a variable inductor.
於一實施例中,該充電程序具有一充電諧振頻率,且該至少一放電程序具有一放電諧振頻率,且該充電諧振頻率與該放電諧振頻率相同。In one embodiment, the charging process has a charging resonant frequency, and the at least one discharging process has a discharging resonant frequency, and the charging resonant frequency is the same as the discharging resonant frequency.
於一實施例中,該充電程序具有一充電諧振頻率,且該至少一放電程序具有一放電諧振頻率,且該充電諧振頻率與該放電諧振頻率不同。In one embodiment, the charging process has a charging resonant frequency, and the at least one discharging process has a discharging resonant frequency, and the charging resonant frequency is different from the discharging resonant frequency.
於一實施例中,調整該參考訊號之位準,以調整該充電程序的持續時間,以達到柔性切換(soft switching)之零電壓切換。In one embodiment, the level of the reference signal is adjusted to adjust the duration of the charging process to achieve zero-voltage switching of soft switching.
於一實施例中,調整該參考訊號之位準,以調整該至少一放電程序的持續時間,以達到柔性切換(soft switching)之零電壓切換。In one embodiment, the level of the reference signal is adjusted to adjust the duration of the at least one discharge procedure to achieve zero-voltage switching of soft switching.
於一實施例中,該諧振切換式電源轉換器為雙向諧振切換式電源轉換器。In one embodiment, the resonant switching power converter is a bidirectional resonant switching power converter.
於一實施例中,該諧振切換式電源轉換器之該輸入電壓與該輸出電壓之電壓轉換比率為4:1、3:1或2:1。In one embodiment, the voltage conversion ratio of the input voltage to the output voltage of the resonant switching power converter is 4:1, 3:1 or 2:1.
於一實施例中,當該至少一零電流偵測電路偵測到該充電諧振電流為零之時點而產生該至少一零電流偵測訊號之時點後延遲一延遲時間,並於該延遲時間之結束時點切換該放電操作訊號以進行該至少一放電程序。In one embodiment, when the at least one zero-current detection circuit detects the time point when the charging resonant current is zero and generates the at least one zero-current detection signal, a delay time is delayed, and after the delay time At the end time point, the discharge operation signal is switched to perform the at least one discharge procedure.
於一實施例中,當該至少一零電流偵測電路偵測到該放電諧振電流為零之時點而產生該至少一零電流偵測訊號之時點後延遲一延遲時間,並於該延遲時間之結束時點切換該充電操作訊號以進行該充電程序。In one embodiment, when the at least one zero-current detection circuit detects the time point when the discharge resonant current is zero and generates the at least one zero-current detection signal, a delay time is delayed, and after the delay time At the end point, the charging operation signal is switched to perform the charging procedure.
本發明之一優點在於本發明可減少電感數量、可補償因直流偏壓或操作溫度而產生的元件變化,且可降低切換頻率以改善低負載時的效率。One advantage of the present invention is that the present invention can reduce the number of inductances, compensate for component variations due to DC bias or operating temperature, and reduce switching frequency to improve efficiency at low loads.
本發明之另一優點在於本發明可支援輸出電壓調節功能、可降低電壓應力且可使所有諧振電容具有相同的額定電流及額定電壓而能夠使用較小體積的電容。Another advantage of the present invention is that the present invention can support the output voltage regulation function, can reduce the voltage stress, and can make all the resonant capacitors have the same rated current and rated voltage, and can use smaller volume capacitors.
本發明之又一優點在於本發明可動態控制以達到具有零電流切換(ZCS)或零電壓切換(ZVS)的柔性切換、可具有較佳的動態負載暫態響應且可具有較佳的電流電壓平衡。Another advantage of the present invention is that the present invention can be dynamically controlled to achieve flexible switching with zero current switching (ZCS) or zero voltage switching (ZVS), better dynamic load transient response, and better current-voltage balance.
本發明之再一優點在於本發明可具有穩定的諧振頻率、可更具彈性地調變電壓轉換比率且可雙向操作。Another advantage of the present invention is that the present invention can have a stable resonant frequency, can modulate the voltage conversion ratio more flexibly, and can operate bidirectionally.
底下藉由具體實施例詳加說明,當更容易瞭解本發明之目的、技術內容、特點及其所達成之功效。The following describes in detail with specific embodiments, when it is easier to understand the purpose, technical content, characteristics and effects of the present invention.
本發明中的圖式均屬示意,主要意在表示各電路間之耦接關係,以及各訊號波形之間之關係,至於電路、訊號波形與頻率則並未依照比例繪製。The drawings in the present invention are schematic, mainly intended to represent the coupling relationship between the circuits and the relationship between the signal waveforms, and the circuits, signal waveforms and frequencies are not drawn to scale.
圖3A係根據本發明之一實施例顯示一諧振切換式電源轉換器30之電路示意圖。本實施例係多個電容共用一充電電感或一放電電感,藉此無論電容數量為多少,都只需要一個充電電感及一個放電電感,可進一步減少電感的數量。如圖3A所示,本發明之諧振切換式電源轉換器30包含電容C1、C2、C3、開關Q1、Q2、Q3、Q4、Q5、Q6、Q7、Q8、Q9、Q10、充電電感L1、放電電感L2、控制器301、至少一零電流偵測電路302以及開關驅動器303。開關Q1-Q3分別與對應之電容C1-C3串聯,而開關Q4與充電電感L1串聯。應注意者為,本發明之諧振切換式電源轉換器30中的電容數量並不限於本實施例的三個,亦可為二個或四個以上,本實施例所顯示之元件數量僅用以說明本發明並不用限制本發明。FIG. 3A is a schematic circuit diagram showing a resonant
如圖3A所示,開關Q5之一端耦接至開關Q1與電容C1之間的節點,開關Q6之一端耦接至開關Q2與電容C2之間的節點,而開關Q7之一端耦接至開關Q3與電容C3之間的節點。開關Q8之一端耦接至電容C1與開關Q2之間的節點,開關Q9之一端耦接至電容C2與開關Q3之間的節點,而開關Q10之一端耦接至電容C3與開關Q4之間的節點。如圖3A所示,開關Q5-Q7之另一端共同電連接至一節點後,串聯至放電電感L2。開關Q8-Q10之另一端係共同耦接至接地電位。充電電感L1及放電電感L2的另一端係共同耦接至輸出電壓Vout,開關Q1之另一端耦接至輸入電壓Vin。控制器301係用以產生充電操作訊號GA與放電操作訊號GB,以分別對應一充電程序與一放電程序,而操作對應之複數開關Q1-Q10,以切換所對應之電容C1-C3之電連接關係。零電流偵測電路302係耦接於控制器301與輸出電壓Vout之間,用以於充電程序時偵測充電電感L1與輸出電壓Vout之間的節點上的一充電諧振電流IL1或於放電程序時偵測放電電感L2與輸出電壓Vout之間的節點上的一放電諧振電流IL2。當零電流偵測電路302偵測到充電諧振電流IL1或放電諧振電流Il2為零時,產生一零電流偵測訊號ZCD至控制器301,以供控制器301產生充電操作訊號GA及放電操作訊號GB。As shown in FIG. 3A, one end of the switch Q5 is coupled to the node between the switch Q1 and the capacitor C1, one end of the switch Q6 is coupled to the node between the switch Q2 and the capacitor C2, and one end of the switch Q7 is coupled to the switch Q3 and capacitor C3. One end of the switch Q8 is coupled to the node between the capacitor C1 and the switch Q2, one end of the switch Q9 is coupled to the node between the capacitor C2 and the switch Q3, and one end of the switch Q10 is coupled to the node between the capacitor C3 and the switch Q4. node. As shown in FIG. 3A , after the other ends of the switches Q5-Q7 are electrically connected to a node in common, they are connected in series to the discharge inductor L2. The other ends of the switches Q8-Q10 are commonly coupled to the ground potential. The other ends of the charging inductor L1 and the discharging inductor L2 are commonly coupled to the output voltage Vout, and the other end of the switch Q1 is coupled to the input voltage Vin. The
於一實施例中,控制器301可根據零電流偵測訊號ZCD、充電操作訊號GA及/或放電操作訊號GB決定充電程序與放電程序各自的起始時點與結束時點。零電流偵測電路302可包含一電流感測電路3021,用以於充電程序時感測充電諧振電流IL1或於放電程序時感測放電諧振電流IL2。零電流偵測電路302可進一步包含比較器3022,用以將感測所得之充電諧振電流IL1或放電諧振電流IL2與一參考訊號Vref1比對,用以產生零電流偵測訊號ZCD。開關驅動器303係耦接於控制器301與複數開關Q1-Q10之間,用以根據充電操作訊號GA或放電操作訊號GB控制複數開關Q1-Q10。於本實施例及其他實施例中,當零電流偵測電路302偵測到充電諧振電流IL1為零之時點而產生零電流偵測訊號ZCD之時點後延遲一延遲時間,並於該延遲時間之結束時點將放電操作訊號GB切換為高位準訊號,以進行放電程序。於本實施例及其他實施例中,當零電流偵測電路302偵測到放電諧振電流IL2為零之時點而產生零電流偵測訊號ZCD之時點後延遲一延遲時間,並於該延遲時間之結束時點將充電操作訊號GA切換為高位準訊號,以進行充電程序。In one embodiment, the
開關Q1-Q10可根據控制器301所產生之充電操作訊號GA、放電操作訊號GB經由開關驅動器303的控制,切換所對應之電容C1-C3與充電電感L1及放電電感L2之電連接關係。於一實施例中,充電操作訊號GA與放電操作訊號GB,分別各自切換至一導通位準一段導通期間,上述複數段導通期間彼此不重疊。The switches Q1-Q10 can be controlled by the
在一充電程序中,根據充電操作訊號GA,開關Q1-Q4係為導通,開關Q5-Q10係為不導通,使得電容C1-C3彼此串聯後與充電電感L1串聯於輸入電壓Vin與輸出電壓Vout之間,以形成一充電路徑。在一放電程序中,根據放電操作訊號GB,開關Q5-Q10係導通,開關Q1-Q4係不導通,使電容C1、電容C2及電容C3彼此並聯後串聯放電電感L2,而形成複數放電路徑。In a charging process, according to the charging operation signal GA, the switches Q1-Q4 are turned on, and the switches Q5-Q10 are turned off, so that the capacitors C1-C3 are connected in series with each other and the charging inductor L1 is connected in series with the input voltage Vin and the output voltage Vout. between to form a charging path. In a discharge process, according to the discharge operation signal GB, the switches Q5-Q10 are turned on, and the switches Q1-Q4 are turned off, so that the capacitor C1, the capacitor C2 and the capacitor C3 are connected in parallel with each other and then the discharge inductor L2 is connected in series to form a complex discharge path.
應注意者為,上述充電程序與上述放電程序係於不同的時間段重複地交錯進行,而非同時進行。其中,充電程序與放電程序彼此重複地交錯排序,以將輸入電壓Vin轉換為輸出電壓Vout。於本實施例中,每個第一電容C1、C2、C3的直流偏壓均為Vo,故本實施例中的第一電容C1、C2、C3相對於先前技術,在相同的輸入電壓與輸出電壓的應用中,僅需要承受較低的額定電壓,故可使用較小體積的電容器。It should be noted that, the above-mentioned charging process and the above-mentioned discharging process are repeatedly performed in different time periods, but are not performed simultaneously. Wherein, the charging procedure and the discharging procedure are repeatedly and alternately sequenced, so as to convert the input voltage Vin into the output voltage Vout. In this embodiment, the DC bias voltage of each of the first capacitors C1, C2, and C3 is Vo, so the first capacitors C1, C2, and C3 in this embodiment have the same input voltage and output as the prior art. In voltage applications, only lower rated voltages are required, so smaller capacitors can be used.
於一實施例中,上述充電程序之充電諧振頻率與上述放電程序之放電諧振頻率相同。於一實施例中,上述充電程序之充電諧振頻率與上述放電程序之放電諧振頻率不同。於一實施例中,上述諧振切換式電源轉換器30可為雙向諧振切換式電源轉換器。所謂雙向諧振切換式電源轉換器,係指輸入端(提供輸入電壓Vin)與輸出端(提供輸出電壓Vout)的角色對調,意即在如圖3A所示的實施例中,諧振切換式電源轉換器30可將輸出電壓Vout轉換為輸入電壓Vin。於一實施例中,上述諧振切換式電源轉換器30之輸入電壓Vin與輸出電壓Vout之電壓轉換比率可為4:1、3:1或2:1。In one embodiment, the charging resonant frequency of the above-mentioned charging procedure is the same as the discharging resonant frequency of the above-mentioned discharging procedure. In one embodiment, the charging resonant frequency of the above-mentioned charging procedure is different from the discharging resonant frequency of the above-mentioned discharging procedure. In one embodiment, the resonant
於一實施例中,上述充電程序的持續時間(Ton1)係與上述充電程序之充電諧振頻率(fr1)相關。於一較佳實施例中,上述充電程序的持續時間(Ton1)係與充電程序之充電諧振電流之正半波相關,例如開關Q1-Q4之導通時點及不導通時點係大致上同步於充電程序之一充電諧振電流之正半波之起始時點及結束時點。於一實施例中,上述放電程序的持續時間(Ton2)係與上述放電程序之放電諧振頻率(fr2)相關。於一較佳實施例中,上述放電程序的持續時間(Ton2)係與放電程序之放電諧振電流之正半波相關,例如開關Q5-Q10之導通時點及不導通時點係大致上同步於放電程序之一放電諧振電流之正半波之起始時點及結束時點。In one embodiment, the duration of the charging process (Ton1) is related to the charging resonant frequency (fr1) of the charging process. In a preferred embodiment, the duration of the charging process (Ton1) is related to the positive half-wave of the charging resonant current during the charging process. For example, the on-time and off-time of the switches Q1-Q4 are substantially synchronized with the charging process. The start time and end time of the positive half-wave of a charging resonant current. In one embodiment, the duration of the discharge process (Ton2) is related to the discharge resonance frequency (fr2) of the discharge process. In a preferred embodiment, the duration of the discharge process (Ton2) is related to the positive half-wave of the discharge resonant current during the discharge process. For example, the on-time and off-time of the switches Q5-Q10 are substantially synchronized with the discharge process. The start time and end time of the positive half-wave of a discharge resonant current.
於上述充電程序之充電諧振頻率(fr1)等於上述放電程序之放電諧振頻率(fr2)的實施例中,當上述充電程序的持續時間(Ton1)等於上述放電程序的持續時間(Ton2)時,例如大致上等於百分之五十之工作週期時,藉此可於流經開關的電流皆在其正半波相對較低位準的時點切換,以達成柔性切換。在一種較佳的實施例中,可達到零電流切換(zero current switch, ZCS)。In the embodiment in which the charging resonant frequency (fr1) of the above-mentioned charging procedure is equal to the discharging resonant frequency (fr2) of the above-mentioned discharging procedure, when the duration (Ton1) of the above-mentioned charging procedure is equal to the duration (Ton2) of the above-mentioned discharging procedure, for example, When the duty cycle is approximately equal to 50%, the current flowing through the switch can be switched at a relatively low level of its positive half-wave, so as to achieve flexible switching. In a preferred embodiment, zero current switch (ZCS) can be achieved.
此外需說明的是:因電路零件的本身之寄生效應或是零件間相互的匹配不一定為理想,因此,雖然欲使充電程序的持續時間等於放電程序的持續時間(也就是於此實施例中充電程序的持續時間為百分之五十之工作週期),以達到柔性切換(soft switching)之零電流切換。但實際可能並無法準確地為百分之五十之工作週期,而僅是接近百分之五十之工作週期,亦即,根據本發明,可接受由於電路的不理想性而使充電程序的持續時間與百分之五十之工作週期間具有一定程度的誤差,此即前述之放電至「大致上」為百分之五十之工作週期之意,本文中其他提到「大致上」之處亦同。In addition, it should be noted that due to the parasitic effect of the circuit components or the mutual matching between components is not necessarily ideal, therefore, although the duration of the charging process is intended to be equal to the duration of the discharging process (that is, in this embodiment The duration of the charging procedure is fifty percent of the duty cycle) to achieve zero-current switching for soft switching. However, the actual duty cycle may not be exactly 50%, but only close to 50% duty cycle. That is, according to the present invention, it is acceptable to make the charging procedure unsatisfactory due to circuit imperfections. There is a certain degree of error between the duration and the 50% duty cycle, which means that the aforementioned discharge to "substantially" means the 50% duty cycle. The same is true everywhere.
於一實施例中,上述充電程序的持續時間小於特定比例之工作週期一段預設期間,例如小於百分之五十之工作週期一段預設期間;藉此提前不導通開關Q1-Q4後仍維持有微小的電流,流經充電電感L1,因此,即可將開關Q10中,儲存於其中之寄生電容的累積電荷透過開關Q4之寄生二極體帶走,而降低開關Q10的跨壓,以達到柔性切換。在一種較佳的實施例中,調整上述參考訊號之位準以調整預設期間,而達到零電壓切換(zero voltage switch,ZVS)。於一實施例中,相對地,上述放電程序的持續時間大於特定比例之工作週期一段預設期間,例如大於百分之五十之工作週期一段預設期間;藉此,延後不導通開關Q5-Q10後放電電感L2的負電流會通過開關Q5的寄生二極體而對開關Q1的寄生電容進行充電,而降低開關Q1的跨壓,以達到柔性切換。在一種較佳的實施例中,調整上述參考訊號之位準,以調整預設期間,而達到零電壓切換。In one embodiment, the duration of the charging process is less than a certain percentage of the duty cycle for a predetermined period, for example, less than 50% of the duty cycle for a predetermined period; thereby the switches Q1-Q4 are not turned on in advance and still remain There is a small current flowing through the charging inductor L1, so the accumulated charge of the parasitic capacitance stored in the switch Q10 can be taken away through the parasitic diode of the switch Q4, and the cross-voltage of the switch Q10 can be reduced to achieve Flexible switching. In a preferred embodiment, the level of the reference signal is adjusted to adjust the preset period to achieve zero voltage switch (ZVS). In one embodiment, relatively, the duration of the above-mentioned discharge process is longer than a certain proportion of the duty cycle for a predetermined period, for example, a predetermined period greater than 50% of the duty cycle; thereby, the switch Q5 is not turned on after a delay. - The negative current of the discharge inductor L2 after the Q10 will charge the parasitic capacitance of the switch Q1 through the parasitic diode of the switch Q5, thereby reducing the cross-voltage of the switch Q1, so as to achieve flexible switching. In a preferred embodiment, the level of the reference signal is adjusted to adjust the preset period to achieve zero-voltage switching.
圖3B係根據本發明之一實施例顯示一諧振切換式電源轉換器之電路示意圖。本實施例與圖3A之實施例的不同在於,本實施例之放電程序為複數。控制器301係用以產生充電操作訊號GA與複數放電操作訊號GB1、GB2與GB3,以分別對應一充電程序與三放電程序,而操作對應之複數開關Q1-Q10,以切換所對應之電容C1-C3之電連接關係。零電流偵測電路302係耦接於控制器301與輸出電壓Vout之間,用以於充電程序時偵測充電電感L1與輸出電壓Vout之間的節點上的一充電諧振電流IL1;或於每一個放電程序時,偵測放電電感L2與輸出電壓Vout之間的節點上的一放電諧振電流IL2。當零電流偵測電路302偵測到充電諧振電流IL1或放電諧振電流Il2為零時,產生一零電流偵測訊號ZCD至控制器301,以供控制器301產生充電操作訊號GA及放電操作訊號GB1、GB2與GB3。3B is a schematic circuit diagram showing a resonant switching power converter according to an embodiment of the present invention. The difference between this embodiment and the embodiment of FIG. 3A is that the discharge procedures of this embodiment are plural. The
於一實施例中,控制器301可根據零電流偵測訊號ZCD、充電操作訊號GA及/或放電操作訊號GB1、GB2與GB3決定充電程序與放電程序各自的起始時點與結束時點。零電流偵測電路302可包含一電流感測電路3021,用以於充電程序時感測充電諧振電流IL1或於放電程序時感測放電諧振電流IL2。零電流偵測電路302可進一步包含比較器3022,用以將感測所得之充電諧振電流IL1或放電諧振電流IL2與一參考訊號Vref1比對,用以產生零電流偵測訊號ZCD。開關驅動器303係耦接於控制器301與複數開關Q1-Q10之間,用以根據充電操作訊號GA或放電操作訊號GB控制複數開關Q1-Q10。In one embodiment, the
開關Q1-Q10可根據控制器301所產生之充電操作訊號GA、放電操作訊號GB1、GB2與GB3經由開關驅動器303的控制,切換所對應之電容C1-C3與充電電感L1及放電電感L2之電連接關係。於一實施例中,充電操作訊號GA與放電操作訊號GB1、GB2與GB3,分別各自切換至一導通位準一段導通期間,上述複數段導通期間彼此不重疊。The switches Q1-Q10 can be controlled by the
舉例而言,在一充電程序中,根據充電操作訊號GA,開關Q1-Q4係為導通,開關Q5-Q10係為不導通,使得電容C1-C3彼此串聯後與充電電感L1串聯於輸入電壓Vin與輸出電壓Vout之間,以形成一充電路徑。在第一放電程序中,根據放電操作訊號GB1,開關Q5與Q8係導通,開關Q1-Q4、Q6、Q7、Q9與Q10係不導通,使電容C1串聯放電電感L2,而形成第一放電路徑。在第二放電程序中,根據放電操作訊號GB2,開關Q6與Q9係導通,開關Q1-Q4、Q5、Q7、Q8與Q10係不導通,使電容C2串聯放電電感L2,而形成第二放電路徑。在第三放電程序中,根據放電操作訊號GB3,開關Q7與Q10係導通,開關Q1-Q4、Q5、Q6、Q8與Q9係不導通,使電容C3串聯放電電感L2,而形成第三放電路徑。For example, in a charging process, according to the charging operation signal GA, the switches Q1-Q4 are turned on, and the switches Q5-Q10 are turned off, so that the capacitors C1-C3 are connected in series with each other and the charging inductor L1 is connected in series with the input voltage Vin and the output voltage Vout to form a charging path. In the first discharge procedure, according to the discharge operation signal GB1, the switches Q5 and Q8 are turned on, and the switches Q1-Q4, Q6, Q7, Q9 and Q10 are turned off, so that the capacitor C1 is connected in series with the discharge inductance L2 to form a first discharge path . In the second discharge procedure, according to the discharge operation signal GB2, the switches Q6 and Q9 are turned on, and the switches Q1-Q4, Q5, Q7, Q8 and Q10 are turned off, so that the capacitor C2 is connected in series with the discharge inductance L2 to form a second discharge path . In the third discharge procedure, according to the discharge operation signal GB3, the switches Q7 and Q10 are turned on, and the switches Q1-Q4, Q5, Q6, Q8 and Q9 are turned off, so that the capacitor C3 discharges the inductor L2 in series to form a third discharge path .
應注意者為,上述充電程序與上述第一放電程序、第二放電程序與第三放電程序係於不同的時間段重複地交錯進行,而非同時進行。其中,充電程序與上述三個放電程序彼此重複地交錯排序,以將輸入電壓Vin轉換為輸出電壓Vout,亦即,一個充電程序結束後,接著第一放電程序、第二放電程序、第三放電程序輪流執行,再接著執行充電程序,以此類推。It should be noted that, the above-mentioned charging procedure, the above-mentioned first discharging procedure, the second discharging procedure and the third discharging procedure are repeatedly performed in different time periods, but are not performed simultaneously. Wherein, the charging procedure and the above-mentioned three discharging procedures are repeatedly and interleaved with each other to convert the input voltage Vin into the output voltage Vout, that is, after one charging procedure is completed, the first discharging procedure, the second discharging procedure and the third discharging procedure are followed The procedures are executed in turn, followed by the charging procedure, and so on.
請參考圖4,其係根據本發明之另一實施例顯示一諧振切換式電源轉換器40之電路示意圖。圖4中之電容C1-C3、充電電感L1、放電電感L2、開關Q1-Q10、零電流偵測電路402、電流感測電路4021、比較器4022、開關驅動器403的配置與圖3A類似,故不贅述。本實施例與圖3A之實施例的不同在於本實施例之控制器401可包含邏輯電路4011、決定電路4012以及延遲電路4013,決定電路4012可包含第一閂鎖電路4012a及第二閂鎖電路4012b。Please refer to FIG. 4 , which is a schematic circuit diagram of a resonant
於一實施例中,延遲電路4013為可選擇性的。邏輯電路4011可與零電流偵測電路402耦接,用以根據零電流偵測訊號與充電操作訊號GA及/或放電操作訊號GB,產生一充電判斷訊號與一放電判斷訊號。於一實施例中,充電判斷訊號可用以決定充電程序之起始時點與放電程序之結束時點。邏輯電路4011例如但不限於對零電流偵測訊號與充電操作訊號GA之反相訊號執行及邏輯運算,而產生充電判斷訊號。於一實施例中,放電判斷訊號可用以決定放電程序之起始時點與充電程序之結束時點。邏輯電路4011例如但不限於對零電流偵測訊號與放電操作訊號GB之反相訊號執行及邏輯運算,而產生放電判斷訊號。決定電路4012可與邏輯電路4011耦接,用以根據充電判斷訊號與放電判斷訊號,產生充電操作訊號GA與放電操作訊號GB,以決定充電程序與放電程序各自的起始時點與結束時點。延遲電路4013係耦接於邏輯電路4011與決定電路4012之間,用以延遲充電程序及/或放電程序的起始時點一延遲時間,藉此可降低切換頻率並調整輸入電壓Vin與輸出電壓Vout的比例。In one embodiment, the
舉例而言,於充電程序中,充電操作訊號GA為高位準,且邏輯電路4011於零電流偵測電路402的零電流偵測訊號ZCD切換為高位準時,邏輯電路4011根據此時高位準的充電操作訊號GA與高位準的零電流偵測訊號ZCD,而產生高位準的放電判斷訊號,以輸出至決定電路4012,決定電路4012遂產生高位準的放電操作訊號GB,以輸出至開關驅動器403,使得開關Q5-Q10導通。另一方面,邏輯電路4011根據充電程序中,充電操作訊號GA之低位準的反相訊號,產生低位準的充電判斷訊號。決定電路4012根據前述高位準的放電判斷訊號與低位準的充電判斷訊號,而將充電操作訊號GA切換為低位準,使得開關Q1-Q4不導通,而結束充電程序。For example, in the charging process, the charging operation signal GA is at a high level, and when the
另一方面,於放電程序中,放電操作訊號GB為高位準,且邏輯電路4011從零電流偵測電路402接收零電流偵測訊號ZCD切換為高位準時,邏輯電路4011根據此時高位準的放電操作訊號GB與高位準的零電流偵測訊號ZCD,而產生高位準的充電判斷訊號,以輸出至決定電路4012,決定電路4012遂產生高位準的充電操作訊號GA,以輸出至開關驅動器403,使得開關Q1-Q4導通。另一方面,邏輯電路4011根據放電程序中,放電操作訊號GB之低位準的反相訊號,產生低位準的放電判斷訊號。決定電路4012根據前述高位準的充電判斷訊號與低位準的放電判斷訊號,而將放電操作訊號GB切換為低位準,使得開關Q5-Q10不導通,而結束放電程序。On the other hand, in the discharge process, the discharge operation signal GB is at a high level, and the
第一閂鎖電路4012a可用以根據充電判斷訊號而設定充電操作訊號GA,並根據放電判斷訊號而切換充電操作訊號GA之位準,且產生充電操作訊號GA之反相訊號以輸入邏輯電路4011,例如當第一閂鎖電路4012a接收到高位準的充電判斷訊號時,第一閂鎖電路4012a會設定充電操作訊號GA為高位準,並產生低位準的充電操作訊號GA之反相訊號,以輸入邏輯電路4011。另一方面,當第一閂鎖電路4012a接收到高位準的放電判斷訊號時,第一閂鎖電路4012a會將充電操作訊號GA之位準切換成低位準,並產生高位準的充電操作訊號之反相訊號,以輸入邏輯電路4011。The
第二閂鎖電路4012b可用以根據放電判斷訊號而設定放電操作訊號GB,並根據充電判斷訊號而切換放電操作訊號GB之位準,且產生放電操作訊號GB之反相訊號以輸入邏輯電路4011,例如當第二閂鎖電路4012b接收到高位準的放電判斷訊號時,第二閂鎖電路4012b會設定放電操作訊號GB為高位準,並產生低位準的放電操作訊號GB之反相訊號,以輸入邏輯電路4011。另一方面,當第二閂鎖電路4012b接收到高位準的充電判斷訊號時,第二閂鎖電路4012b會將放電操作訊號GB之位準切換成低位準,並產生高位準的放電操作訊號之反相訊號,以輸入邏輯電路4011。The second latch circuit 4012b can be used to set the discharge operation signal GB according to the discharge judgment signal, switch the level of the discharge operation signal GB according to the charge judgment signal, and generate an inversion signal of the discharge operation signal GB to be input to the
請參考圖5,其係根據本發明之又一實施例顯示一諧振切換式電源轉換器50之較具體的電路示意圖。圖5中之電容C1-C3、充電電感L1、放電電感L2、開關Q1-Q10、零電流偵測電路502、電流感測電路5021、比較器5022、開關驅動器503的配置與圖3A類似,故不贅述。本實施例與圖3A之實施例的不同在於,本實施例之控制器501可包含邏輯電路5011、決定電路5012以及延遲電路5013。其中,決定電路5012可包含第一閂鎖電路5012a及第二閂鎖電路5012b。其中,延遲電路5013可包含延遲單元5013a及延遲單元5013b。Please refer to FIG. 5 , which shows a more specific circuit schematic diagram of a resonant
在一種實施方式中,延遲電路5013為可選擇性的。於本實施例中,邏輯電路5011可包含第一及閘5011a、第二及閘5011b以及反閘5011c。其中,第一及閘5011a係耦接於比較器5022與第一閂鎖電路5012a之間;第二及閘5011b係耦接於比較器5022與第二閂鎖電路5012b之間;而反閘5011c係耦接於第一閂鎖電路5012a與第二及閘5011b之間。在決定電路5012中,第一閂鎖電路5012a係耦接於第一及閘5011a與對應之開關驅動器503之間,而第二閂鎖電路5012b係耦接於第二及閘5011b與對應之開關驅動器503之間。In one embodiment, the
以圖5所示之實施例,舉例說明根據本發明的一種操作方式。在充電程序開始時,第二閂鎖電路5012b之重置端R接收高位準的充電判斷訊號,而重置第二閂鎖電路5012b之輸出端Q,以使第二閂鎖電路5012b之輸出端Q,輸出低位準之放電操作訊號GB,以不導通開關Q5-Q10。且於充電程序時,第一閂鎖電路5012a之輸出端Q,輸出高位準之充電操作訊號GA,以導通開關Q1-Q4。此時,反閘5011c對第一閂鎖電路5012a之反相輸出端Ǭ所輸出之充電操作訊號GA之反相訊號(低位準)執行反邏輯運算,產生高位準的運算結果,以輸入第二及閘5011b。第二及閘5011b保持低位準的放電判斷訊號,直到零電流偵測電路502的零電流偵測訊號ZCD偵測到充電諧振電流IL1降低至零電流時,切換為高位準(示意充電程序結束),第二及閘5011b對反閘5011c所輸出高位準的運算結果,與高位準的零電流偵測訊號ZCD,執行及邏輯運算,而產生高位準的放電判斷訊號,以輸出至決定電路5012,使第二閂鎖電路5012b遂於其輸出端Q產生高位準的放電操作訊號GB,以輸出至開關驅動器503,使得開關Q5-Q10導通,而開始放電程序。此外,第一閂鎖電路5012a之重置端R接收高位準的放電判斷訊號,而重置第一閂鎖電路5012a之輸出端Q,使其輸出端Q產生低位準的充電操作訊號GA,以輸出至開關驅動器503,使得開關Q1-Q4不導通,而結束充電程序。The embodiment shown in FIG. 5 is used to illustrate an operation mode according to the present invention. At the beginning of the charging process, the reset terminal R of the
另一方面,在放電程序開始時,第一閂鎖電路5012a之重置端R接收高位準的放電判斷訊號,而重置第一閂鎖電路5012a之輸出端Q,以使第一閂鎖電路5012a之輸出端Q,輸出低位準之充電操作訊號GA,以不導通開關Q1-Q4。且於放電程序時,第二閂鎖電路5012b之輸出端Q,輸出高位準之放電操作訊號GB,以導通開關Q5-Q10。此時,第一閂鎖電路5012a之反相輸出端Ǭ所輸出之充電操作訊號GA之反相訊號(高位準)輸入第一及閘5011a。第一及閘5011a保持低位準的充電判斷訊號,直到零電流偵測電路502的零電流偵測訊號ZCD偵測到放電諧振電流IL2降低至零電流時,切換為高位準(示意放電程序結束),第一及閘5011a對高位準的反相輸出端Ǭ所輸出之充電操作訊號GA之反相訊號,與高位準的零電流偵測訊號ZCD,執行及邏輯運算,而產生高位準的充電判斷訊號,以輸出至決定電路5012,使第一閂鎖電路5012a遂於其輸出端Q產生高位準的充電操作訊號GA,以輸出至開關驅動器503,使得開關Q1-Q4導通,而開始充電程序。此外,第二閂鎖電路5012b之重置端R接收高位準的充電判斷訊號,而重置第二閂鎖電路5012b之輸出端Q,使其輸出端Q產生低位準的放電操作訊號GB,以輸出至開關驅動器503,使得開關Q5-Q10不導通,而結束放電程序。On the other hand, when the discharge process starts, the reset terminal R of the
其中,延遲單元5013a係耦接於第一及閘5011a與第一閂鎖電路5012a之設置端S之間,用以使複數開關Q1-Q4之導通時點延遲一延遲時間,於延遲時間中所有對應的開關Q1-Q4均為不導通以延遲充電程序的起始時點一延遲時間。延遲單元5013b係耦接於第二及閘5011b與第二閂鎖電路5012b之設置端S之間,用以使複數開關Q5-Q10之導通時點延遲一延遲時間,於延遲時間中所有對應的開關Q5-Q10均為不導通以延遲放電程序的起始時點一延遲時間。The
於一實施例中,L1的電感值可等於L2的電感值。於一實施例中,值得注意的是,L1的電感值等於L2的電感值的一個特例是,充電電感L1與放電電感L2可共用同一個電感,分別於不同時間作用為充電電感、放電電感。In one embodiment, the inductance value of L1 may be equal to the inductance value of L2. In one embodiment, it is worth noting that a special case where the inductance value of L1 is equal to the inductance value of L2 is that the charging inductor L1 and the discharging inductor L2 can share the same inductor and function as the charging inductor and the discharging inductor at different times.
因此,請參照圖6,其為根據本發明之再一實施例顯示一諧振切換式電源轉換器60之電路示意圖。圖6中之控制器601、零電流偵測電路602、電流感測電路6021、比較器6022、開關驅動器603的配置與圖3A類似,故不贅述。本實施例與圖3A的不同在於本實施例的充電電感與放電電感可為同一個電感L3,如此之設置可更進一步地減少電感的數量。如圖6所示,本發明之諧振切換式電源轉換器60包含電容C1、C2、C3、開關Q1、Q2、Q3、Q4、Q5、Q6、Q7、Q8、Q9、Q10、電感L3。開關Q1-Q3分別與對應之電容C1-C3串聯,而開關Q4與電感L3串聯。應注意者為,本發明之諧振切換式電源轉換器中的電容數量並不限於本實施例的三個,亦可為二個或四個以上,本實施例所顯示之元件數量僅用以說明本發明並不用限制本發明。Therefore, please refer to FIG. 6 , which is a schematic circuit diagram showing a resonant
須說明的是,在本實施例中,充電電感與放電電感為單一個相同的電感L3,在放電程序中,藉由開關Q1-Q10的切換,使電容C1-C3彼此並聯後串聯單一個相同電感L3。所謂充電電感與放電電感為單一個相同的電感L3,係指在充電程序與放電程序中,充電諧振電流與放電諧振電流分別僅流經單一個電感L3,而未再流經其他電感元件。It should be noted that, in this embodiment, the charging inductance and the discharging inductance are a single identical inductance L3. During the discharging process, through the switching of the switches Q1-Q10, the capacitors C1-C3 are connected in parallel with each other and then connected in series with a single identical inductance L3. Inductor L3. The so-called charging inductance and discharging inductance are a single same inductance L3, which means that in the charging process and the discharging process, the charging resonant current and the discharging resonant current respectively only flow through a single inductance L3, and do not flow through other inductive elements.
如圖6所示,開關Q5之一端耦接至開關Q1與電容C1之間的節點,開關Q6之一端耦接至開關Q2與電容C2之間的節點,而開關Q7之一端耦接至開關Q3與電容C3之間的節點。開關Q8之一端耦接至電容C1與開關Q2之間的節點,開關Q9之一端耦接至電容C2與開關Q3之間的節點,而開關Q10之一端耦接至電容C3與開關Q4之間的節點。如圖6所示,開關Q5-Q7之另一端共同電連接至一節點後,耦接至開關Q4與電感L3之間的節點,開關Q8-Q10之另一端係共同耦接至接地電位。電感L3的另一端係耦接至輸出電壓Vout,開關Q1之另一端耦接至輸入電壓Vin。As shown in FIG. 6 , one end of the switch Q5 is coupled to the node between the switch Q1 and the capacitor C1, one end of the switch Q6 is coupled to the node between the switch Q2 and the capacitor C2, and one end of the switch Q7 is coupled to the switch Q3 and capacitor C3. One end of the switch Q8 is coupled to the node between the capacitor C1 and the switch Q2, one end of the switch Q9 is coupled to the node between the capacitor C2 and the switch Q3, and one end of the switch Q10 is coupled to the node between the capacitor C3 and the switch Q4. node. As shown in FIG. 6 , after the other ends of the switches Q5-Q7 are electrically connected to a node in common, they are coupled to the node between the switch Q4 and the inductor L3, and the other ends of the switches Q8-Q10 are commonly coupled to the ground potential. The other end of the inductor L3 is coupled to the output voltage Vout, and the other end of the switch Q1 is coupled to the input voltage Vin.
開關Q1-Q10可根據控制器601所產生之充電操作訊號GA及放電操作訊號GB經由開關驅動器603的控制,切換所對應之電容C1-C3與電感L3之電連接關係。在一充電程序中,根據充電操作訊號GA,開關Q1-Q4係為導通,開關Q5-Q10係為不導通,使得電容C1-C3彼此串聯後與電感L3串聯於輸入電壓Vin與輸出電壓Vout之間,以形成一充電路徑。在一放電程序中,根據放電操作訊號GB,開關Q5-Q10係導通,開關Q1-Q4係不導通,使電容C1、電容C2及電容C3彼此並聯後串聯電感L3,而形成複數放電路徑。應注意者為,上述充電程序與上述放電程序係於不同的時間段重複地交錯進行,而非同時進行。其中,充電程序與放電程序彼此重複地交錯排序,以將輸入電壓Vin轉換為輸出電壓Vout。於本實施例中,每個第一電容C1、C2、C3的直流偏壓均為Vo,故本實施例中的第一電容C1、C2、C3需要耐較低的額定電壓,故可使用較小體積的電容器。The switches Q1-Q10 can be controlled by the
在充電電感與放電電感設置為單一個相同的電感L1的本實施例中,可適當配置上述充電程序的持續時間(Ton1)及放電程序的持續時間(Ton2)的比例,可達到柔性切換之零電流切換。具體而言,於一實施例中,上述充電程序的持續時間例如大致上等於百分之二十五之工作週期;藉此,開關可於流經開關的電流在其正半波相對較低位準的時點切換,以達成柔性切換。在一種較佳的實施例中,可達到零電流切換(zero current switch, ZCS)。於一實施例中,上述充電程序的持續時間小於特定比例之工作週期一段預設期間,例如小於百分之二十五之工作週期一段預設期間;藉此提前不導通開關Q1-Q4後仍維持有微小的電流,流經充電電感L1,因此,即可將開關Q10中,儲存於其中之寄生電容的累積電荷通過開關Q4之寄生二極體帶走,而降低開關Q10的跨壓,以達到柔性切換。In the present embodiment where the charging inductance and the discharging inductance are set as a single same inductance L1, the ratio of the duration of the charging procedure (Ton1) and the duration of the discharging procedure (Ton2) can be appropriately configured to achieve zero flexible switching current switching. Specifically, in one embodiment, the duration of the above-mentioned charging process is approximately equal to, for example, 25% of the duty cycle; thereby, the switch can make the current flowing through the switch at a relatively low level of its positive half-wave. Switch at the right time to achieve flexible switching. In a preferred embodiment, zero current switch (ZCS) can be achieved. In one embodiment, the duration of the charging process is shorter than a certain percentage of the duty cycle for a predetermined period, for example, less than 25% of the duty cycle for a predetermined period; thus, the switches Q1-Q4 are not turned on in advance. A small current is maintained and flows through the charging inductor L1, so the accumulated charge of the parasitic capacitance stored in the switch Q10 can be taken away through the parasitic diode of the switch Q4, and the cross-voltage of the switch Q10 can be reduced to reduce the cross-voltage of the switch Q10. achieve flexible switching.
在一種較佳的實施例中,調整參考訊號之位準,以調整預設期間,而達到零電壓切換(zero voltage switch,ZVS)。於一實施例中,相對地,上述放電程序的持續時間大於特定比例之工作週期一段預設期間,例如大於百分之七十五之工作週期一段預設期間;藉此,延後不導通開關Q5-Q10後放電電感L2的負電流會通過開關Q5的寄生二極體而對開關Q1的寄生電容進行充電,而降低開關Q1的跨壓,以達到柔性切換。在一種較佳的實施例中,調整參考訊號之位準,以調整預設期間,而達到零電壓切換(zero voltage switch,ZVS)。In a preferred embodiment, the level of the reference signal is adjusted to adjust the preset period to achieve zero voltage switch (ZVS). In one embodiment, relatively, the duration of the above-mentioned discharge procedure is longer than a certain proportion of the duty cycle for a predetermined period, for example, greater than 75% of the duty cycle for a predetermined period; thereby, the switch is not turned on after a delay The negative current of the post-discharge inductor L2 of Q5-Q10 will charge the parasitic capacitance of the switch Q1 through the parasitic diode of the switch Q5, thereby reducing the cross-voltage of the switch Q1, so as to achieve flexible switching. In a preferred embodiment, the level of the reference signal is adjusted to adjust the preset period to achieve zero voltage switch (ZVS).
於一實施例中,上述諧振切換式電源轉換器60可為雙向諧振切換式電源轉換器。於一實施例中,上述諧振切換式電源轉換器60之輸入電壓Vin與輸出電壓Vout之電壓轉換比率可為4:1、3:1或2:1。於一實施例中,諧振切換式電源轉換器60之電壓轉換比率可彈性地加以調整,例如於充電程序與放電程序中,藉由選擇將開關Q7保持導通,並選擇將開關Q10及Q4保持不導通,則可將諧振切換式電源轉換器60之電壓轉換比率調整為3:1。同樣地,例如可選擇將開關Q6保持導通,並選擇將開關Q9、Q3、Q7、Q10及Q4保持不導通,則可將諧振切換式電源轉換器60之電壓轉換比率調整為2:1。In one embodiment, the resonant
請參照圖7,其係根據本發明之又一實施例顯示一諧振切換式電源轉換器之電路70示意圖。圖7中之控制器701、邏輯電路7011、決定電路7012、第一閂鎖電路7012a、第二閂鎖電路7012b、延遲電路7013、零電流偵測電路702、電流感測電路7021、比較器7022、開關驅動器703係類似於圖4,圖7中之電容C1-C3、開關Q1-10、電感L3係類似於圖6,故不贅述。本實施例主要是將圖4中之控制器架構應用到單一個電感的諧振切換式電源轉換器中。Please refer to FIG. 7 , which is a schematic diagram showing a
請參照圖8A,其係根據本發明之再一實施例顯示一諧振切換式電源轉換器之電路80示意圖。圖8A中之電容C1-C3、開關Q1-10、電感L3係類似於圖6,故不贅述。本實施例將圖5中之控制器架構應用到單一個電感的諧振切換式電源轉換器中。此外,本實施例之控制器801可包含邏輯電路8011、決定電路8012以及延遲電路8013。其中,決定電路8012可包含第一閂鎖電路8012a及第二閂鎖電路8012b。其中,延遲電路8013可包含延遲單元8013a及延遲單元8013b。Please refer to FIG. 8A , which is a schematic diagram showing a
在一種實施方式中,延遲電路8013為可選擇性的。於本實施例中,邏輯電路8011可包含第一及閘8011a、第二及閘8011b以及反閘8011c。其中,第一及閘8011a係耦接於比較器8022與第一閂鎖電路8012a之間;第二及閘8011b係耦接於比較器8022與第二閂鎖電路8012b之間;而反閘8011c係耦接於第二閂鎖電路8012b與第一及閘8011a之間。在決定電路8012中,第一閂鎖電路8012a係耦接於第一及閘8011a與對應之開關驅動器803之間,而第二閂鎖電路8012b係耦接於第二及閘8011b與對應之開關驅動器803之間。In one embodiment, the
以圖8A所示之實施例,舉例說明根據本發明的一種操作方式。在充電程序開始時,第二閂鎖電路8012b之重置端R接收高位準的充電判斷訊號,而重置第二閂鎖電路8012b之輸出端Q,以使第二閂鎖電路8012b之輸出端Q,輸出低位準之放電操作訊號GB,以不導通開關Q5-Q10。且於充電程序時,第一閂鎖電路8012a之輸出端Q,輸出高位準之充電操作訊號GA,以導通開關Q1-Q4。此時,第二閂鎖電路8012b之反相輸出端Ǭ所輸出之放電操作訊號GB之反相訊號(高位準)輸入第二及閘8011b。第二及閘8011b保持低位準的放電判斷訊號,直到零電流偵測電路802的零電流偵測訊號ZCD偵測到充電諧振電流IL1降低至零電流時,切換為高位準(示意充電程序結束),第二及閘8011b對高位準的反相輸出端Ǭ所輸出之放電操作訊號GB之反相訊號,與高位準的零電流偵測訊號ZCD,執行及邏輯運算,而產生高位準的放電判斷訊號,以輸出至決定電路8012,使第二閂鎖電路8012b遂於其輸出端Q產生高位準的放電操作訊號GB,以輸出至開關驅動器803,使得開關Q5-Q10導通,而開始放電程序。此外,第一閂鎖電路8012a之重置端R接收高位準的放電判斷訊號,而重置第一閂鎖電路8012a之輸出端Q,使其輸出端Q產生低位準的充電操作訊號GA,以輸出至開關驅動器803,使得開關Q1-Q4不導通,而結束充電程序。The embodiment shown in FIG. 8A is used to illustrate an operation mode according to the present invention. At the beginning of the charging process, the reset terminal R of the
另一方面,在放電程序開始時,第一閂鎖電路8012a之重置端R接收高位準的放電判斷訊號,而重置第一閂鎖電路8012a之輸出端Q,以使第一閂鎖電路8012a之輸出端Q,輸出低位準之充電操作訊號GA,以不導通開關Q1-Q4。且於放電程序時,第二閂鎖電路8012b之輸出端Q,輸出高位準之放電操作訊號GB,以導通開關Q5-Q10。此時,反閘8011c對第二閂鎖電路8012b之反相輸出端Ǭ所輸出之放電操作訊號GB之反相訊號(低位準)執行反邏輯運算,產生高位準的運算結果,以輸入第一及閘8011a。第一及閘8011a保持低位準的充電判斷訊號,直到零電流偵測電路802的零電流偵測訊號ZCD偵測到放電諧振電流IL2降低至零電流時,切換為高位準(示意放電程序結束),第一及閘8011a對反閘8011c所輸出高位準的運算結果,與高位準的零電流偵測訊號ZCD,執行及邏輯運算,而產生高位準的充電判斷訊號,以輸出至決定電路8012,使第一閂鎖電路8012a遂於其輸出端Q產生高位準的充電操作訊號GA,以輸出至開關驅動器803,使得開關Q1-Q4導通,而開始充電程序。此外,第二閂鎖電路8012b之重置端R接收高位準的充電判斷訊號,而重置第二閂鎖電路8012b之輸出端Q,使其輸出端Q產生低位準的放電操作訊號GB,以輸出至開關驅動器803,使得開關Q5-Q10不導通,而結束放電程序。On the other hand, when the discharge process starts, the reset terminal R of the
其中,延遲單元8013a係耦接於第一及閘8011a與第一閂鎖電路8012a之設置端S之間,用以使複數開關Q1-Q4之導通時點延遲一延遲時間,於延遲時間中所有對應的開關Q1-Q4均為不導通以延遲充電程序的起始時點一延遲時間。延遲單元8013b係耦接於第二及閘8011b與第二閂鎖電路8012b之設置端S之間,用以使複數開關Q5-Q10之導通時點延遲一延遲時間,於延遲時間中所有對應的開關Q5-Q10均為不導通以延遲放電程序的起始時點一延遲時間。The
圖8B顯示圖8A所示之諧振切換式電源轉換器中不包含延遲電路8013之下,相關訊號之訊號波形示意圖。充電諧振電流/放電諧振電流(又稱電感電流)IL3、輸入電流Iin、零電流偵測訊號ZCD、充電操作訊號GA以及放電操作訊號GB如圖8B所示。在本實施例中,充電程序的持續時間大致上為百分之二十五之工作週期,放電程序的持續時間大致上為百分之七十五之工作週期。應注意者為,於充電程序期間所感測到的電感電流IL3為充電諧振電流,於放電程序期間所感測到之電感電流IL3為放電諧振電流。如圖8B所示,舉例而言,每次零電流偵測訊號ZCD產生脈波訊號之時點,觸發充電操作訊號GA以及放電操作訊號GB切換位準,而決定充電程序與放電程序的起始時點與結束時點。FIG. 8B shows a schematic diagram of signal waveforms of related signals when the resonant switching power converter shown in FIG. 8A does not include the
請參照圖9,其為根據本發明之又一實施例顯示一諧振切換式電源轉換器90之電路示意圖。圖9中之控制器901、零電流偵測電路902、電流感測電路9021、比較器9022、開關驅動器903、電容C1-C3、開關Q1-Q10、充電電感L1及放電電感L2的配置與圖3A類似,故不贅述。本實施例主要是將放電程序分成複數個放電程序分別於不同時段輪流進行,故放電操作訊號G2係用於使開關Q5、Q8導通,並使開關Q1-Q4、Q6、Q7、Q9、Q10不導通,以於第一時段對電容C1進行放電,放電操作訊號G3係用於使開關Q6、Q9導通,並使開關Q1-Q5、Q7、Q8、Q10不導通,以於第二時段對電容C2進行放電,放電操作訊號G4係用於使開關Q7、Q10導通,並使開關Q1-Q6、Q8-Q9不導通,以於第三時段對電容C3進行放電,而充電操作訊號G1是用於使開關Q1-Q4導通,並使開關Q5-Q10不導通,以對電容C1-C3進行充電。應得以領會者為,於一實施例中,本實施例之控制器901亦可與圖4或圖5的控制器架構替換實施。Please refer to FIG. 9 , which is a schematic circuit diagram showing a resonant
再請參照圖10,其係根據本發明之再一實施例顯示一諧振切換式電源轉換器100之電路示意圖。圖10中之控制器1001、零電流偵測電路1002、電流感測電路10021、比較器10022、開關驅動器1003與圖3A類似,故不贅述。如圖10所示,本發明之諧振切換式電源轉換器100包含電容C1、C2、C3、開關Q1、Q2、Q3、Q4、Q5、Q6、Q7、Q8、Q9、Q10、電感L1、L2、L3。開關Q1-Q3分別與對應之電容C1-C3串聯,而電容C1-C3分別與對應之電感L1-L3串聯。應注意者為,本發明之諧振切換式電源轉換器中的電容數量並不限於本實施例的三個,亦可為二個或四個以上,且電感數量亦不限於本實施例的三個,亦可為二個或四個以上,本實施例所顯示之元件數量僅用以說明本發明並不用限制本發明。應得以領會者為,於一實施例中,本實施例之控制器1001亦可與圖4或圖5的控制器架構替換實施。Please refer to FIG. 10 again, which is a schematic circuit diagram of a resonant
如圖10所示,開關Q5之一端耦接至開關Q1與電容C1之間的節點,開關Q6之一端耦接至開關Q2與電容C2之間的節點,而開關Q7之一端耦接至開關Q3與電容C3之間的節點。開關Q8之一端耦接至電感L1與開關Q2之間的節點,開關Q9之一端耦接至電感L2與開關Q3之間的節點,而開關Q10之一端耦接至電感L3與開關Q4之間的節點。如圖10所示,開關Q5-Q7之另一端則共同耦接至輸出電壓Vout。開關Q8-Q10之另一端係共同耦接至接地電位。開關Q4耦接於電感L3與輸出電壓Vout之間,開關Q1之一端耦接至輸入電壓Vin。As shown in FIG. 10 , one end of switch Q5 is coupled to the node between switch Q1 and capacitor C1, one end of switch Q6 is coupled to the node between switch Q2 and capacitor C2, and one end of switch Q7 is coupled to switch Q3 and capacitor C3. One end of the switch Q8 is coupled to the node between the inductor L1 and the switch Q2, one end of the switch Q9 is coupled to the node between the inductor L2 and the switch Q3, and one end of the switch Q10 is coupled to the node between the inductor L3 and the switch Q4. node. As shown in FIG. 10 , the other ends of the switches Q5-Q7 are commonly coupled to the output voltage Vout. The other ends of the switches Q8-Q10 are commonly coupled to the ground potential. The switch Q4 is coupled between the inductor L3 and the output voltage Vout, and one end of the switch Q1 is coupled to the input voltage Vin.
開關Q1-Q10可根據控制器1001所產生之充電操作訊號GA及放電操作訊號GB經由開關驅動器1003的控制,切換所對應之電容C1-C3與電感L1-L3之電連接關係。在一充電程序中,開關Q1-Q4係為導通,開關Q5-Q10係為不導通,使得電容C1-C3與電感L1-L3彼此串聯於輸入電壓Vin與輸出電壓Vout之間,以形成一充電路徑。在一放電程序中,開關Q5-Q10係導通,開關Q1-Q4係不導通,使電容C1與對應之電感L1串聯於輸出電壓Vout與接地電位間,電容C2與對應之電感L2串聯於輸出電壓Vout與接地電位間,電容C3與對應之電感L3串聯於輸出電壓Vout與接地電位間,而形成複數放電路徑。應注意者為,上述充電程序與上述放電程序係於不同的時間段交錯進行,而非同時進行。其中,充電程序與放電程序彼此重複地交錯排序,以將輸入電壓Vin轉換為輸出電壓Vout。於本實施例中,每個電容C1、C2、C3的直流偏壓均為Vo,故本實施例中的電容C1、C2、C3需要耐較低的額定電壓,故可使用較小體積的電容器。The switches Q1-Q10 can be controlled by the
於一實施例中,上述充電程序的持續時間大致上為特定比例之工作週期(duty cycle),例如但不限於大致上為百分之五十之工作週期;藉此,開關可於流經開關的電流在其正半波相對較低位準的時點切換,以達成柔性切換。在一種較佳的實施例中,可達到零電流切換(zero current switch, ZCS)。In one embodiment, the duration of the above-mentioned charging process is approximately a certain proportion of the duty cycle, such as, but not limited to, approximately 50% duty cycle; The current is switched at a relatively low level of its positive half-wave to achieve flexible switching. In a preferred embodiment, zero current switch (ZCS) can be achieved.
於一實施例中,上述特定比例係與諧振頻率相關。於一實施例中,上述充電程序具有一充電諧振頻率,上述放電程序具有一放電諧振頻率。於一較佳實施例中,上述充電諧振頻率與上述放電諧振頻率相同。In one embodiment, the above-mentioned specific ratio is related to the resonance frequency. In one embodiment, the charging process has a charging resonant frequency, and the discharging process has a discharging resonant frequency. In a preferred embodiment, the charging resonant frequency is the same as the discharging resonant frequency.
圖11A係根據本發明之一實施例顯示一充電程序與放電程序之對應之操作訊號與對應之電感電流之訊號波形示意圖。請同時參閱圖3A,圖11A所示的實施例中,開關Q1~Q4之充電操作訊號GA於充電程序時為高位準,而開關Q5~Q10之放電操作訊號GB於放電程序時為高位準。於圖11A之實施例中,充電程序的持續時間大致上為百分之五十之工作週期;藉此,開關Q1可於流經開關的電流在其正半波相對較低位準的時點切換,也是在充電電感L1之充電電感電流IL1為零電流時切換,以達成柔性切換。在一種較佳的實施例中,可達到零電流切換。FIG. 11A is a schematic diagram showing signal waveforms of corresponding operation signals and corresponding inductor currents in a charging process and a discharging process according to an embodiment of the present invention. Please also refer to FIG. 3A. In the embodiment shown in FIG. 11A, the charging operation signal GA of the switches Q1-Q4 is at a high level during the charging process, and the discharging operation signal GB of the switches Q5-Q10 is at a high level during the discharging process. In the embodiment of FIG. 11A, the duration of the charging process is approximately 50% of the duty cycle; thus, the switch Q1 can be switched when the current flowing through the switch is at a relatively low level of its positive half-wave. , is also switched when the charging inductor current IL1 of the charging inductor L1 is zero current, so as to achieve flexible switching. In a preferred embodiment, zero current switching can be achieved.
圖11B及11C係根據本發明之另一實施例顯示一充電程序與放電程序之對應之操作訊號與對應之電感電流之訊號波形示意圖。請同時參閱圖3A,圖11B所示的實施例中,開關Q1~Q4之充電操作訊號GA於充電程序時為高位準,而開關Q5~Q10之放電操作訊號GB於放電程序時為高位準。於圖11B之實施例中,可調高參考訊號,以使充電程序的持續時間大致上為小於百分之五十之工作週期一段預設期間T1;藉此,提前不導通開關Q1-Q4後仍維持有微小的電流流經充電電感L1,因此,即可將開關Q10中,儲存於其中之寄生電容的累積電荷透過開關Q4之寄生二極體放電,而降低開關Q10的跨壓,以達到柔性切換。在一種較佳的實施例中,調整預設期間T1,而達到零電壓切換。請同時參閱圖3A,圖11C所示的實施例中,開關Q1~Q4之充電操作訊號GA於充電程序時為高位準,開關Q5~Q10之放電操作訊號GB於放電程序時為高位準。於圖11C之實施例中,可調低參考訊號,以使放電程序的持續時間大致上為大於百分之五十之工作週期一段預設期間T2+T3;藉此,延後不導通開關Q5-Q10後放電電感L2的負電流會通過開關Q5的寄生二極體而對開關Q1的寄生電容進行充電,而降低開關Q1的跨壓,以達到柔性切換。在一種較佳的實施例中,調整預設期間T2與T3,而達到零電壓切換。於一實施例中,應注意者為,圖11B及11C之實施例可一起實施或僅實施其中一者。11B and 11C are schematic diagrams showing signal waveforms of corresponding operation signals and corresponding inductor currents in a charging process and a discharging process according to another embodiment of the present invention. 3A, in the embodiment shown in FIG. 11B, the charging operation signal GA of the switches Q1-Q4 is at a high level during the charging process, and the discharging operation signal GB of the switches Q5-Q10 is at a high level during the discharging process. In the embodiment of FIG. 11B , the reference signal can be increased so that the duration of the charging process is substantially less than 50% of the duty cycle for a predetermined period T1; thus, the switches Q1-Q4 are turned off in advance. There is still a small current flowing through the charging inductor L1. Therefore, the accumulated charge of the parasitic capacitance stored in the switch Q10 can be discharged through the parasitic diode of the switch Q4, thereby reducing the cross-voltage of the switch Q10, so as to achieve Flexible switching. In a preferred embodiment, the preset period T1 is adjusted to achieve zero voltage switching. 3A, in the embodiment shown in FIG. 11C, the charging operation signal GA of the switches Q1-Q4 is at a high level during the charging process, and the discharging operation signal GB of the switches Q5-Q10 is at a high level during the discharging process. In the embodiment of FIG. 11C , the reference signal can be lowered so that the duration of the discharge process is substantially greater than 50% of the duty cycle for a predetermined period T2+T3; thereby, the non-conducting switch Q5 is delayed. - The negative current of the discharge inductor L2 after the Q10 will charge the parasitic capacitance of the switch Q1 through the parasitic diode of the switch Q5, thereby reducing the cross-voltage of the switch Q1, so as to achieve flexible switching. In a preferred embodiment, the preset periods T2 and T3 are adjusted to achieve zero voltage switching. In one embodiment, it should be noted that the embodiments of Figures 11B and 11C may be implemented together or only one of them.
本發明如上所述提供了一種諧振切換式電源轉換器,其藉由特殊的電路設計可減少電感數量、可掩蓋因直流偏壓或操作溫度而產生的元件變化、可降低切換頻率以改善低負載時的效率、可支援輸出電壓調節功能、可降低電壓應力、可使所有諧振電容具有相同的額定電流及額定電壓而能夠使用較小體積的電容、可動態控制以達到具有零電流切換(ZCS)或零電壓切換(ZVS)的柔性切換、可具有較佳的動態負載暫態響應、可具有較佳的電流電壓平衡、可具有穩定的諧振頻率、可更具彈性地調變電壓轉換比率且可雙向操作。The present invention provides a resonant switching power converter as described above, which can reduce the number of inductances by special circuit design, can mask the component changes due to DC bias or operating temperature, can reduce the switching frequency to improve low load high efficiency, can support output voltage regulation, can reduce voltage stress, can make all resonant capacitors have the same rated current and voltage to use smaller capacitors, can be dynamically controlled to achieve zero current switching (ZCS) or zero voltage switching (ZVS) flexible switching, can have better dynamic load transient response, can have better current-voltage balance, can have a stable resonant frequency, can more flexibly adjust the voltage conversion ratio and can Bidirectional operation.
需說明的是,前述實施例中提到的「高位準」與「低位準」僅為舉例,並非用以限制本發明之範疇,在其他實施例中,前述的「高位準」與「低位準」,在前述符合本發明相同的精神下,可依實際所採用的開關型態與邏輯基礎,而適應性地至少部分調整或交換。It should be noted that the "high level" and "low level" mentioned in the foregoing embodiments are only examples, and are not intended to limit the scope of the present invention. In other embodiments, the foregoing "high level" and "low level" ”, under the same spirit of the present invention as described above, it can be adaptively at least partially adjusted or exchanged according to the actual switch type and logic basis used.
以上已針對較佳實施例來說明本發明,唯以上所述者,僅係為使熟悉本技術者易於了解本發明的內容而已,並非用來限定本發明之最廣的權利範圍。所說明之各個實施例,並不限於單獨應用,亦可以組合應用,舉例而言,兩個或以上之實施例可以組合運用,而一實施例中之部分組成亦可用以取代另一實施例中對應之組成部件。此外,在本發明之相同精神下,熟悉本技術者可以思及各種等效變化以及各種組合,舉例而言,本發明所稱「根據某訊號進行處理或運算或產生某輸出結果」,不限於根據該訊號的本身,亦包含於必要時,將該訊號進行電壓電流轉換、電流電壓轉換、及/或比例轉換等,之後根據轉換後的訊號進行處理或運算產生某輸出結果。由此可知,在本發明之相同精神下,熟悉本技術者可以思及各種等效變化以及各種組合,其組合方式甚多,在此不一一列舉說明。因此,本發明的範圍應涵蓋上述及其他所有等效變化。The present invention has been described above with respect to the preferred embodiments, but the above descriptions are only intended to make the content of the present invention easy for those skilled in the art to understand, and are not intended to limit the broadest scope of rights of the present invention. The described embodiments are not limited to be used alone, but can also be used in combination. For example, two or more embodiments can be used in combination, and some components in one embodiment can also be used to replace those in another embodiment. corresponding components. In addition, under the same spirit of the present invention, those skilled in the art can think of various equivalent changes and various combinations. According to the signal itself, when necessary, the signal is subjected to voltage-to-current conversion, current-to-voltage conversion, and/or ratio conversion, etc., and then processed or calculated according to the converted signal to generate an output result. It can be seen from this that under the same spirit of the present invention, those skilled in the art can think of various equivalent changes and various combinations, and there are many combinations, which are not listed and described here. Accordingly, the scope of the present invention should cover the above and all other equivalent changes.
30、40、50、60、70、80、90、100:諧振切換式電源轉換器 301、401、501、601、701、801、901、1001:控制器 302、402、502、602、702、802、902、1002:零電流偵測電路 3021、4021、5021、6021、7021、8021、9021、10021:電流感測電路 3022、4022、5022、6022、7022、8022、9022、10022:比較器 303、403、503、603、703、803、903、1003:開關驅動器 4011、7011:邏輯電路 4012、7012:決定電路 4012a、5012a、7012a:第一閂鎖電路 4012b、5012b、7012b:第二閂鎖電路 4013、7013:延遲電路 5011a、8011a:第一及閘 5011b、8011b:第二及閘 5012、8012:反相器 5013、8013:延遲電路 8014a:第一閂鎖器 8014b:第二閂鎖器 C1~C3、C1(CR)、C2(CF)、C3(CR):電容 Co:輸出電容 G1、GA:充電操作訊號 G2、G3、G4、GB:放電操作訊號 Iin:輸入電流 IL1:充電電感電流(充電諧振電流) IL2:放電電感電流(放電諧振電流) IL3:電感電流(充電諧振電流/放電諧振電流) L1:充電電感 L2:放電電感 L1(LR)、L2(LR)、L3、Lb:電感 Q:輸出端 Ǭ:反向輸出端 Q1~Q10、Q1(S1A)、Q2(S2A)、Q3(S1B)、Q4(S2B)、Q5(S1A)、Q6(S2A)、Q7(S2A)、Q8(S1B)、Q9(S1B)、Q10(S2B)、Qb:開關 R:重置端 S:設定端 RL:負載電阻 T1、T2、T3:期間 Vc1:電容C1直流偏壓 Vc2:電容C2直流偏壓 Vc3:電容C3直流偏壓 Vin:輸入電壓 Vout:輸出電壓 Vref1:參考訊號 ZCD:零電流偵測訊號30, 40, 50, 60, 70, 80, 90, 100: Resonant switching power converters 301, 401, 501, 601, 701, 801, 901, 1001: Controller 302, 402, 502, 602, 702, 802, 902, 1002: zero current detection circuit 3021, 4021, 5021, 6021, 7021, 8021, 9021, 10021: Current Sensing Circuit 3022, 4022, 5022, 6022, 7022, 8022, 9022, 10022: Comparator 303, 403, 503, 603, 703, 803, 903, 1003: Switch Drivers 4011, 7011: Logic circuits 4012, 7012: decision circuit 4012a, 5012a, 7012a: first latch circuit 4012b, 5012b, 7012b: second latch circuit 4013, 7013: Delay circuit 5011a, 8011a: first and gate 5011b, 8011b: Second and gate 5012, 8012: Inverter 5013, 8013: Delay circuit 8014a: First Latch 8014b: Second Latch C1~C3, C1(CR), C2(CF), C3(CR): Capacitor Co: output capacitance G1, GA: charging operation signal G2, G3, G4, GB: Discharge operation signal Iin: input current IL1: Charging inductor current (charging resonance current) IL2: Discharge inductor current (discharge resonance current) IL3: Inductor current (charge resonant current/discharge resonant current) L1: charging inductance L2: Discharge inductance L1(LR), L2(LR), L3, Lb: Inductance Q: output terminal Ǭ: Reverse output terminal Q1~Q10, Q1(S1A), Q2(S2A), Q3(S1B), Q4(S2B), Q5(S1A), Q6(S2A), Q7(S2A), Q8(S1B), Q9(S1B), Q10 (S2B), Qb: switch R: reset terminal S: setting terminal RL: load resistance T1, T2, T3: Period Vc1: DC bias voltage of capacitor C1 Vc2: Capacitor C2 DC bias Vc3: Capacitor C3 DC bias Vin: input voltage Vout: output voltage Vref1: Reference signal ZCD: zero current detection signal
圖1係為習知的電源轉換器。FIG. 1 shows a conventional power converter.
圖2係顯示電容值隨著直流偏壓改變之示意圖。FIG. 2 is a schematic diagram showing the change of capacitance value with DC bias.
圖3A係根據本發明之一實施例顯示一諧振切換式電源轉換器之電路示意圖。3A is a schematic circuit diagram showing a resonant switching power converter according to an embodiment of the present invention.
圖3B係根據本發明之一實施例顯示一諧振切換式電源轉換器之電路示意圖。3B is a schematic circuit diagram showing a resonant switching power converter according to an embodiment of the present invention.
圖4係根據本發明之另一實施例顯示一諧振切換式電源轉換器之電路示意圖。FIG. 4 is a schematic circuit diagram showing a resonant switching power converter according to another embodiment of the present invention.
圖5係根據本發明之又一實施例顯示一諧振切換式電源轉換器之電路示意圖。FIG. 5 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention.
圖6係根據本發明之再一實施例顯示一諧振切換式電源轉換器之電路示意圖。FIG. 6 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention.
圖7係根據本發明之又一實施例顯示一諧振切換式電源轉換器之電路示意圖。FIG. 7 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention.
圖8A及8B係根據本發明之再一實施例顯示一諧振切換式電源轉換器之電路及相關訊號之訊號波形示意圖。8A and 8B are schematic diagrams showing signal waveforms of a circuit of a resonant switching power converter and related signals according to yet another embodiment of the present invention.
圖9係根據本發明之又一實施例顯示一諧振切換式電源轉換器之電路示意圖。FIG. 9 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention.
圖10係根據本發明之再一實施例顯示一諧振切換式電源轉換器之電路示意圖。10 is a schematic circuit diagram showing a resonant switching power converter according to yet another embodiment of the present invention.
圖11A、11B及11C係根據本發明之一實施例顯示一充電程序與放電程序之對應之操作訊號與對應之電感電流之訊號波形示意圖。11A , 11B and 11C are schematic diagrams showing signal waveforms of corresponding operation signals and corresponding inductor currents in a charging process and a discharging process according to an embodiment of the present invention.
30:諧振切換式電源轉換器30: Resonant switching power converters
301:控制器301: Controller
302:零電流偵測電路302: Zero current detection circuit
3021:電流感測電路3021: Current Sensing Circuit
3022:比較器3022: Comparator
303:開關驅動器303: Switch Driver
C1~C3:電容C1~C3: Capacitor
Co:輸出電容Co: output capacitance
GA:充電操作訊號GA: Charging operation signal
GB:放電操作訊號GB: Discharge operation signal
IL1:充電電感電流IL1: Charging inductor current
IL2:放電電感電流IL2: Discharge inductor current
L1:充電電感L1: charging inductance
L2:放電電感L2: Discharge inductance
Q1~Q10:開關Q1~Q10: switch
RL:負載電阻RL: load resistance
Vin:輸入電壓Vin: input voltage
Vout:輸出電壓Vout: output voltage
ZCD:零電流偵測訊號ZCD: zero current detection signal
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TWI560984B (en) * | 2015-04-16 | 2016-12-01 | Anpec Electronics Corp | Zero current detecting circuit and related synchronous switching power converter and method |
TW201709647A (en) * | 2015-08-20 | 2017-03-01 | Lunghwa Univ Of Science And Tech | Digital-controlled converter for low voltage and large current output employing zero voltage switching mechanism to reduce switching loss of power switch, surge and ringing artifacts |
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TWI560984B (en) * | 2015-04-16 | 2016-12-01 | Anpec Electronics Corp | Zero current detecting circuit and related synchronous switching power converter and method |
TW201709647A (en) * | 2015-08-20 | 2017-03-01 | Lunghwa Univ Of Science And Tech | Digital-controlled converter for low voltage and large current output employing zero voltage switching mechanism to reduce switching loss of power switch, surge and ringing artifacts |
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