TWI742852B - Resonant switching power converter - Google Patents

Resonant switching power converter Download PDF

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TWI742852B
TWI742852B TW109131753A TW109131753A TWI742852B TW I742852 B TWI742852 B TW I742852B TW 109131753 A TW109131753 A TW 109131753A TW 109131753 A TW109131753 A TW 109131753A TW I742852 B TWI742852 B TW I742852B
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charging
power converter
switching power
discharging
inductance
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TW109131753A
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Chinese (zh)
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TW202143613A (en
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劉國基
白忠龍
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立錡科技股份有限公司
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/007—Regulation of charging or discharging current or voltage
    • H02J7/00712—Regulation of charging or discharging current or voltage the cycle being controlled or terminated in response to electric parameters

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The present invention provides a resonant switching power converter including: a plurality of capacitors; a plurality of switches; at least one charging inductor; and at least one discharging inductor. In a charging process, the plural capacitors are electrically connected to the charging inductor in series between an input voltage and an output voltage by switching the corresponding switches to form a charging path, and a turn-on time point and a turn-off time point of the corresponding switches are synchronous with a start time point and an end time point of a positive half wave of a charging resonant current of the charging process. In a discharging process, each of the capacitors is electrically connected to the corresponding discharging inductor in series between the output voltage and a ground level by switching the corresponding switches to form a plurality of discharging paths, and the turn-on time point and the turn-off time point of the corresponding switches are synchronous with a start time point and an end time point of a positive half wave of a discharging resonant current of the discharging process.

Description

諧振切換式電源轉換器Resonant switching power converter

本發明係有關於一種諧振切換式電源轉換器，特定而言係有關於一種充電或放電持續時間與充電或放電諧振頻率相關之諧振切換式電源轉換器。The present invention relates to a resonant switching power converter, and in particular to a resonant switching power converter in which the charging or discharging duration is related to the resonant frequency of the charging or discharging.

圖1係顯示習知的電源轉換器。於充電操作中，開關Q1、Q3、Q5、Q8、Q9係導通，開關Q2、Q4、Q6、Q7、Q10係不導通，使得電容C1串聯電感L1於輸入電壓VIN及輸出電壓VOUT之間，且電容C2串聯電容C3及電感L2於接地電位及輸出電壓VOUT之間。於放電操作中，開關Q2、Q4、Q6、Q7、Q10係導通，開關Q1、Q3、Q5、Q8、Q9係不導通，使得電感L1串聯電容C1、電容C2於接地電位及輸出電壓VOUT之間，且電感L2串聯電容C3於接地電位及輸出電壓VOUT之間。此習知的電源轉換器之電容需要耐較高的額定電壓，例如電容C1的直流偏壓是輸出電壓的3倍Vc1=3VOUT、電容C2的直流偏壓是輸出電壓的2倍Vc2=2VOUT、電容C3的直流偏壓與輸出電壓相當Vc3=VOUT，因為電容之直流偏壓相對較高，故此習知電源轉換器需要使用具有較大體積的電容。此外，電容的容值通常會隨著直流偏壓的上升而降低，當輸入電壓的範圍是在36V及76V之間時，電容C1的直流偏壓範圍會是在27V及57V之間，由於直流偏壓的變化範圍較廣，故此習知電源轉換器之電容值變化相當大，其諧振頻率也會隨著電容的變化而改變。如此會造成較大的切換電源損耗並且需要複雜的控制來改變電源轉換效率。再者，此習知電源轉換器之輸入電壓VIN與輸出電壓VOUT之電壓轉換比率僅可為4:1或2:1，並無法進行3:1的電壓轉換比率。Figure 1 shows a conventional power converter. During the charging operation, the switches Q1, Q3, Q5, Q8, and Q9 are turned on, and the switches Q2, Q4, Q6, Q7, and Q10 are not turned on, so that the capacitor C1 is connected in series with the inductor L1 between the input voltage VIN and the output voltage VOUT, and The capacitor C2 is connected in series with the capacitor C3 and the inductor L2 between the ground potential and the output voltage VOUT. In the discharging operation, the switches Q2, Q4, Q6, Q7, Q10 are turned on, and the switches Q1, Q3, Q5, Q8, Q9 are not turned on, so that the inductor L1 is connected in series with the capacitor C1 and the capacitor C2 between the ground potential and the output voltage VOUT , And the inductor L2 is connected in series with the capacitor C3 between the ground potential and the output voltage VOUT. The capacitor of this conventional power converter needs to withstand a higher rated voltage. For example, the DC bias of the capacitor C1 is 3 times the output voltage Vc1=3VOUT, and the DC bias of the capacitor C2 is 2 times the output voltage Vc2=2VOUT, The DC bias voltage of the capacitor C3 is equivalent to the output voltage Vc3=VOUT. Because the DC bias voltage of the capacitor is relatively high, the conventional power converter needs to use a capacitor with a larger volume. In addition, the capacitance of the capacitor usually decreases with the increase of the DC bias voltage. When the input voltage range is between 36V and 76V, the DC bias voltage range of the capacitor C1 will be between 27V and 57V. The bias voltage has a wide variation range. Therefore, the capacitance value of the conventional power converter varies greatly, and its resonant frequency also changes with the variation of the capacitance. This will cause a large switching power loss and require complex control to change the power conversion efficiency. Furthermore, the voltage conversion ratio between the input voltage VIN and the output voltage VOUT of the conventional power converter can only be 4:1 or 2:1, and a 3:1 voltage conversion ratio cannot be performed.

有鑑於此，本發明即針對上述先前技術之不足，提出一種創新的電源轉換器。In view of this, the present invention provides an innovative power converter in view of the above-mentioned shortcomings of the prior art.

於一觀點中，本發明提供一種諧振切換式電源轉換器，用以將一輸入電壓轉換為一輸出電壓，該諧振切換式電源轉換器包含：複數電容；複數開關，與該複數電容對應耦接，分別根據對應之一操作訊號，以切換所對應之該電容之電連接關係；至少一充電電感，與該複數電容中之至少其中之一對應串聯；以及至少一放電電感，與該複數電容中之至少其中之一對應串聯；其中，在一充電程序中，藉由該複數開關的切換，使該複數電容與該至少一充電電感彼此串聯於該輸入電壓與該輸出電壓之間，以形成一充電路徑，且對應之該複數開關之導通時點及不導通時點係同步於該充電程序之一充電諧振電流之正半波之起始時點及結束時點；其中，在一放電程序中，藉由該複數開關的切換，使每一該電容與對應之該放電電感串聯於該輸出電壓與一接地電位間，而形成複數放電路徑，且對應之該複數開關之導通時點及不導通時點係同步於該放電程序之一放電諧振電流之正半波之起始時點及結束時點；其中，該充電程序與該放電程序彼此重複地交錯排序，以將該輸入電壓轉換為該輸出電壓。In one aspect, the present invention provides a resonant switching power converter for converting an input voltage into an output voltage. The resonant switching power converter includes: a complex capacitor; a complex switch correspondingly coupled to the complex capacitor , Respectively switch the electrical connection relationship of the corresponding capacitor according to a corresponding one of the operation signals; at least one charging inductor is connected in series with at least one of the plurality of capacitors; and at least one discharge inductor is connected with the plurality of capacitors At least one of them is connected in series; wherein, in a charging process, by switching of the plurality of switches, the plurality of capacitors and the at least one charging inductor are connected in series with each other between the input voltage and the output voltage to form a The charging path, and the corresponding turn-on and non-turn-on timings of the plurality of switches are synchronized with the start and end of the positive half-wave of the charging resonant current of one of the charging procedures; wherein, in a discharging procedure, the The switching of the plurality of switches makes each capacitor and the corresponding discharge inductance connect in series between the output voltage and a ground potential to form a plurality of discharge paths, and the corresponding turn-on and non-turn-on time points of the plurality of switches are synchronized with the The start time and end time of the positive half-wave of the discharge resonant current in one of the discharge procedures; wherein the charging procedure and the discharging procedure are alternately sequenced repeatedly to convert the input voltage into the output voltage.

於一實施例中，該至少一充電電感為單一個充電電感，該至少一放電電感為單一個放電電感，在該放電程序中，藉由該複數開關的切換，使該複數電容彼此並聯後串聯該單一個放電電感。In one embodiment, the at least one charging inductance is a single charging inductance, and the at least one discharging inductance is a single discharging inductance. In the discharging process, by switching the plurality of switches, the plurality of capacitors are connected in parallel with each other and then connected in series. The single discharge inductor.

於一實施例中，該單一個充電電感之電感值相等於該單一個放電電感之電感值。In one embodiment, the inductance value of the single charging inductor is equal to the inductance value of the single discharging inductor.

於一實施例中，該至少一充電電感與該至少一放電電感為單一個相同電感，在該放電程序中，藉由該複數開關的切換，使該複數電容彼此並聯後串聯該單一個相同電感。In one embodiment, the at least one charging inductance and the at least one discharging inductance are a single same inductance. In the discharging process, by switching the plurality of switches, the plurality of capacitors are connected in parallel with each other and then the single same inductance is connected in series. .

於一實施例中，該諧振切換式電源轉換器於該充電程序與該放電程序中，藉由保持導通該複數開關中特定之至少一者，並保持不導通該複數開關中特定之至少二者，而改變該輸入電壓與該輸出電壓之電壓轉換比率。In one embodiment, the resonant switching power converter maintains conductive at least one of the plurality of switches during the charging process and the discharging process, and keeps at least two specific ones of the plurality of switches turned off , And change the voltage conversion ratio of the input voltage to the output voltage.

於一實施例中，該諧振切換式電源轉換器更包含一前端轉換器，其中該前端轉換器具有一前端電感，用以輔助該充電電感。In one embodiment, the resonant switching power converter further includes a front-end converter, wherein the front-end converter has a front-end inductor to assist the charging inductor.

於一實施例中，該前端轉換器包含降壓轉換器、升壓轉換器、升降壓轉換器、反壓轉換器或升反壓轉換器。In one embodiment, the front-end converter includes a buck converter, a boost converter, a buck-boost converter, a back-voltage converter, or a boost-back converter.

於一實施例中，該充電程序具有一充電諧振頻率，且該放電程序具有一放電諧振頻率，且該充電諧振頻率與該放電諧振頻率相同。In one embodiment, the charging process has a charging resonance frequency, and the discharging process has a discharging resonance frequency, and the charging resonance frequency is the same as the discharging resonance frequency.

於一實施例中，該充電程序具有一充電諧振頻率，且該放電程序具有一放電諧振頻率，且該充電諧振頻率與該放電諧振頻率不同。In one embodiment, the charging process has a charging resonance frequency, and the discharging process has a discharging resonance frequency, and the charging resonance frequency is different from the discharging resonance frequency.

於一實施例中，該諧振切換式電源轉換器藉由調整該充電程序的持續時間，以達到柔性切換(soft switching)之零電壓切換。In one embodiment, the resonant switching power converter adjusts the duration of the charging process to achieve soft switching (zero voltage switching).

於一實施例中，該諧振切換式電源轉換器藉由調整該放電程序的持續時間，以達到柔性切換(soft switching)之零電壓切換。In one embodiment, the resonant switching power converter adjusts the duration of the discharge process to achieve soft switching (zero voltage switching).

於一實施例中，該諧振切換式電源轉換器為雙向諧振切換式電源轉換器。In one embodiment, the resonant switching power converter is a bidirectional resonant switching power converter.

於一實施例中，該諧振切換式電源轉換器之該輸入電壓與該輸出電壓之電壓轉換比率為4:1、3:1或2:1。In one embodiment, the voltage conversion ratio of the input voltage to the output voltage of the resonant switching power converter is 4:1, 3:1, or 2:1.

於一實施例中，該電源轉換器可更包含一控制器，其耦接至該複數開關，用以產生該操作訊號。In one embodiment, the power converter may further include a controller coupled to the plurality of switches for generating the operation signal.

本發明之一優點在於本發明可減少電感數量至僅需一個電感分別於不同時段作為充電電感及放電電感。One of the advantages of the present invention is that the present invention can reduce the number of inductances so that only one inductance is used as the charging inductance and the discharging inductance in different periods.

本發明之另一優點在於本發明可降低電壓應力、可使所有諧振電容具有相同的額定電流及額定電壓而使用較小體積的電容且可諧振操作以達到具有零電流切換(ZCS)或零電壓切換(ZVS)的柔性切換。Another advantage of the present invention is that the present invention can reduce the voltage stress, can make all the resonant capacitors have the same rated current and rated voltage, but use a smaller volume of capacitors and can operate at resonance to achieve zero current switching (ZCS) or zero voltage. Flexible switching of switching (ZVS).

本發明之又一優點在於本發明可更具彈性地調變電壓轉換比率、可結合諧振電感與前端轉換器且可雙向操作。Another advantage of the present invention is that the present invention can adjust the voltage conversion ratio more flexibly, can be combined with a resonant inductor and a front-end converter, and can be operated bidirectionally.

底下藉由具體實施例詳加說明，當更容易瞭解本發明之目的、技術內容、特點及其所達成之功效。Detailed descriptions are given below by specific embodiments, so that it will be easier to understand the purpose, technical content, features, and effects of the present invention.

本發明中的圖式均屬示意，主要意在表示各電路間之耦接關係，以及各訊號波形之間之關係，至於電路、訊號波形與頻率則並未依照比例繪製。The drawings in the present invention are all schematic, and are mainly intended to show the coupling relationship between the circuits and the relationship between the signal waveforms. As for the circuits, signal waveforms, and frequencies, they are not drawn to scale.

圖2A係根據本發明之一實施例顯示一諧振切換式電源轉換器之電路示意圖；圖2B顯示圖2A所示之諧振切換式電源轉換器中，相關訊號之訊號波形示意圖。本實施例係多個電容共用一充電電感或一放電電感，藉此無論電容數量為多少，都只需要一個充電電感及一個放電電感，可進一步減少電感的數量。如圖2A所示，本發明之諧振切換式電源轉換器20包含電容C1、C2、C3、開關Q1、Q2、Q3、Q4、Q5、Q6、Q7、Q8、Q9、Q10、充電電感L1、放電電感L2。開關Q1-Q3分別與對應之電容C1-C3串聯，而開關Q4與充電電感L1串聯。應注意者為，本發明之諧振切換式電源轉換器中的電容數量並不限於本實施例的三個，亦可為二個或四個以上，本實施例所顯示之元件數量僅用以說明本發明並不用限制本發明。2A is a schematic diagram showing a circuit of a resonant switching power converter according to an embodiment of the present invention; FIG. 2B is a schematic diagram showing signal waveforms of related signals in the resonant switching power converter shown in FIG. 2A. In this embodiment, multiple capacitors share one charging inductance or one discharging inductance, so that no matter how many capacitors there are, only one charging inductance and one discharging inductance are needed, which can further reduce the number of inductances. As shown in FIG. 2A, the resonant switching power converter 20 of the present invention includes capacitors C1, C2, C3, switches Q1, Q2, Q3, Q4, Q5, Q6, Q7, Q8, Q9, Q10, charging inductor L1, discharge Inductance L2. The switches Q1-Q3 are respectively connected in series with the corresponding capacitors C1-C3, and the switch Q4 is connected in series with the charging inductor L1. It should be noted that the number of capacitors in the resonant switching power converter of the present invention is not limited to three in this embodiment, and can be two or more than four. The number of components shown in this embodiment is only for illustration. The present invention does not limit the present invention.

如圖2A所示，開關Q5之一端耦接至開關Q1與電容C1之間的節點，開關Q6之一端耦接至開關Q2與電容C2之間的節點，而開關Q7之一端耦接至開關Q3與電容C3之間的節點。開關Q8之一端耦接至電容C1與開關Q2之間的節點，開關Q9之一端耦接至電容C2與開關Q3之間的節點，而開關Q10之一端耦接至電容C3與開關Q4之間的節點。如圖2A所示，開關Q5-Q7之另一端共同電連接至一節點後，串聯至放電電感L2。開關Q8-Q10之另一端係共同耦接至接地電位。充電電感L1及放電電感L2的另一端係共同耦接至輸出電壓Vout，開關Q1之另一端耦接至輸入電壓Vin。As shown in FIG. 2A, one end of the switch Q5 is coupled to the node between the switch Q1 and the capacitor C1, one end of the switch Q6 is coupled to the node between the switch Q2 and the capacitor C2, and one end of the switch Q7 is coupled to the switch Q3 The node between and capacitor C3. One end of the switch Q8 is coupled to the node between the capacitor C1 and the switch Q2, one end of the switch Q9 is coupled to the node between the capacitor C2 and the switch Q3, and one end of the switch Q10 is coupled to the node between the capacitor C3 and the switch Q4 node. As shown in FIG. 2A, after the other ends of the switches Q5-Q7 are electrically connected to a node, they are connected in series to the discharge inductor L2. The other ends of the switches Q8-Q10 are commonly coupled to the ground potential. The other ends of the charging inductor L1 and the discharging inductor L2 are commonly coupled to the output voltage Vout, and the other end of the switch Q1 is coupled to the input voltage Vin.

開關Q1-Q10可根據對應之操作訊號，切換所對應之電容C1-C3與充電電感L1及放電電感L2之電連接關係。在一充電程序中，開關Q1-Q4係為導通，開關Q5-Q10係為不導通，使得電容C1-C3彼此串聯後與充電電感L1串聯於輸入電壓Vin與輸出電壓Vout之間，以形成一充電路徑。在一放電程序中，開關Q5-Q10係導通，開關Q1-Q4係不導通，使電容C1、電容C2及電容C3彼此並聯後串聯放電電感L2，而形成複數放電路徑。應注意者為，上述充電程序與上述放電程序係於不同的時間段重複地交錯進行，而非同時進行。在一種較佳的實施例中，該充電程序的持續時間與該放電程序的持續時間彼此不重疊。其中，充電程序與放電程序彼此重複地交錯排序，以將輸入電壓Vin轉換為輸出電壓Vout。於本實施例中，每個第一電容C1、C2、C3的直流偏壓均為Vo，故本實施例中的第一電容C1、C2、C3相對於先前技術，在相同的輸入電壓與輸出電壓的應用中，僅需要承受較低的額定電壓，故可使用較小體積的電容器。The switches Q1-Q10 can switch the electrical connection relationship between the corresponding capacitors C1-C3 and the charging inductor L1 and the discharging inductor L2 according to the corresponding operation signal. In a charging procedure, the switches Q1-Q4 are turned on and the switches Q5-Q10 are not turned on, so that the capacitors C1-C3 are connected in series with the charging inductor L1 in series between the input voltage Vin and the output voltage Vout to form a Charging path. In a discharge process, the switches Q5-Q10 are turned on, and the switches Q1-Q4 are not turned on. The capacitor C1, the capacitor C2, and the capacitor C3 are connected in parallel to each other and the inductor L2 is discharged in series to form a plurality of discharge paths. It should be noted that the above-mentioned charging process and the above-mentioned discharging process are repeatedly and staggered at different time periods, rather than being performed at the same time. In a preferred embodiment, the duration of the charging process and the duration of the discharging process do not overlap with each other. Wherein, the charging process and the discharging process are alternately sequenced repeatedly to convert the input voltage Vin into the output voltage Vout. In this embodiment, the DC bias voltage of each of the first capacitors C1, C2, C3 is Vo. Therefore, the first capacitors C1, C2, C3 in this embodiment have the same input voltage and output voltage compared to the prior art. In the application of voltage, only a lower rated voltage is required, so a smaller volume capacitor can be used.

於一實施例中，上述充電程序之充電諧振頻率與上述放電程序之放電諧振頻率相同。於一實施例中，上述充電程序之充電諧振頻率與上述放電程序之放電諧振頻率不同。於一實施例中，上述諧振切換式電源轉換器20可為雙向諧振切換式電源轉換器。所謂雙向諧振切換式電源轉換器，係指輸入端(提供輸入電壓Vin)與輸出端(提供輸出電壓Vout)的角色對調，意即在如圖2A所示的實施例中，諧振切換式電源轉換器20可將輸出電壓Vout轉換為輸入電壓Vin。於一實施例中，上述諧振切換式電源轉換器20之輸入電壓Vin與輸出電壓Vout之電壓轉換比率可為4:1、3:1或2:1。In one embodiment, the resonant frequency of charging in the charging process is the same as the resonant frequency of discharging in the discharging process. In one embodiment, the resonant frequency of charging in the charging process is different from the resonant frequency of discharging in the discharging process. In one embodiment, the above-mentioned resonant switching power converter 20 may be a bidirectional resonant switching power converter. The so-called two-way resonant switching power converter means that the roles of the input terminal (providing the input voltage Vin) and the output terminal (providing the output voltage Vout) are reversed, which means that in the embodiment shown in FIG. 2A, the resonant switching power converter The device 20 can convert the output voltage Vout into an input voltage Vin. In one embodiment, the voltage conversion ratio of the input voltage Vin to the output voltage Vout of the resonant switching power converter 20 may be 4:1, 3:1, or 2:1.

於一實施例中，上述充電程序的持續時間(Ton1)係與上述充電程序之充電諧振頻率(fr1)相關。於一較佳實施例中，上述充電程序的持續時間(Ton1)係與充電程序之充電諧振電流之正半波相關，例如開關Q1-Q4之導通時點及不導通時點係大致上同步於充電程序之一充電諧振電流之正半波之起始時點及結束時點。於一實施例中，上述放電程序的持續時間(Ton2)係與上述放電程序之放電諧振頻率(fr2)相關。於一較佳實施例中，上述放電程序的持續時間(Ton2)係與放電程序之放電諧振電流之正半波相關，例如開關Q5-Q10之導通時點及不導通時點係大致上同步於放電程序之一放電諧振電流之正半波之起始時點及結束時點。In one embodiment, the duration of the charging process (Ton1) is related to the resonant frequency (fr1) of the charging process. In a preferred embodiment, the duration of the charging process (Ton1) is related to the positive half-wave of the charging resonant current of the charging process. For example, the conduction time and non-conduction time of the switches Q1-Q4 are substantially synchronized with the charging process. One of the starting and ending points of the positive half-wave of the resonant charging current. In one embodiment, the duration (Ton2) of the above-mentioned discharge process is related to the discharge resonance frequency (fr2) of the above-mentioned discharge process. In a preferred embodiment, the duration of the discharge process (Ton2) is related to the positive half-wave of the discharge resonant current of the discharge process. For example, the conduction time and non-conduction time point of the switches Q5-Q10 are substantially synchronized with the discharge process. One is the starting point and ending point of the positive half wave of the discharge resonant current.

於上述充電程序之充電諧振頻率(fr1)等於上述放電程序之放電諧振頻率(fr2)的實施例中，當上述充電程序的持續時間(Ton1)等於上述放電程序的持續時間(Ton2)時，例如大致上等於百分之五十之工作週期時，藉此可於流經開關的電流皆在其正半波相對較低位準的時點切換，以達成柔性切換。在一種較佳的實施例中，可達到零電流切換(zero current switch, ZCS)。In the embodiment in which the charging resonance frequency (fr1) of the charging procedure is equal to the discharging resonance frequency (fr2) of the discharging procedure, when the duration of the charging procedure (Ton1) is equal to the duration of the discharging procedure (Ton2), for example When the duty cycle is roughly equal to 50%, the current flowing through the switch can be switched at a relatively low level of the positive half-wave, so as to achieve flexible switching. In a preferred embodiment, zero current switch (ZCS) can be achieved.

此外需說明的是：因電路零件的本身之寄生效應或是零件間相互的匹配不一定為理想，因此，雖然欲使充電程序的持續時間等於放電程序的持續時間(也就是於此實施例中充電程序的持續時間為百分之五十之工作週期)，以達到柔性切換(soft switching)之零電流切換。但實際可能並無法準確地為百分之五十之工作週期，而僅是接近百分之五十之工作週期，亦即，根據本發明，可接受由於電路的不理想性而使充電程序的持續時間與百分之五十之工作週期間具有一定程度的誤差，此即前述之放電至「大致上」為百分之五十之工作週期之意，本文中其他提到「大致上」之處亦同。In addition, it should be noted that the parasitic effects of the circuit components or the matching between the components are not necessarily ideal. Therefore, although it is desired to make the duration of the charging procedure equal to the duration of the discharging procedure (that is, in this embodiment) The duration of the charging procedure is 50% of the duty cycle) to achieve zero current switching of soft switching. However, in reality, it may not be exactly 50% of the duty cycle, but only close to the 50% duty cycle. That is, according to the present invention, the charging process can be accepted due to the imperfectness of the circuit. There is a certain degree of error between the duration and 50% of the work cycle. This means that the aforementioned discharge to "approximately" means 50% of the work cycle. Other references to "approximately" in this article Same place.

於一實施例中，上述充電程序的持續時間小於特定比例之工作週期一段預設期間，例如小於百分之五十之工作週期一段預設期間；藉此提前不導通開關Q1-Q4後仍維持有微小的電流，流經充電電感L1，因此，即可將開關Q10中，儲存於其中之寄生電容的累積電荷透過開關Q4之寄生二極體帶走，而降低開關Q10的跨壓，以達到柔性切換。在一種較佳的實施例中，調整預設期間，而達到零電壓切換(zero voltage switch，ZVS)。於一實施例中，相對地，上述放電程序的持續時間大於特定比例之工作週期一段預設期間，例如大於百分之五十之工作週期一段預設期間；藉此，延後不導通開關Q5-Q10後放電電感L2的負電流會通過開關Q5的寄生二極體而對開關Q1的寄生電容進行充電，而降低開關Q1的跨壓，以達到柔性切換。在一種較佳的實施例中，調整預設期間，而達到零電壓切換。In one embodiment, the duration of the above-mentioned charging process is less than a specific ratio of the duty cycle for a predetermined period, for example, less than 50% of the duty cycle for a predetermined period; thereby, the switch Q1-Q4 is not turned on in advance. There is a tiny current flowing through the charging inductor L1. Therefore, the accumulated charge of the parasitic capacitance stored in the switch Q10 can be taken away through the parasitic diode of the switch Q4, and the cross voltage of the switch Q10 can be reduced to achieve Flexible switching. In a preferred embodiment, the preset period is adjusted to achieve zero voltage switch (ZVS). In one embodiment, relatively, the duration of the above-mentioned discharge process is greater than a specific proportion of the duty cycle for a predetermined period, for example, a duty cycle greater than 50% for a predetermined period; thereby, the non-conduction switch Q5 is delayed. -After Q10, the negative current of the discharge inductor L2 will charge the parasitic capacitance of the switch Q1 through the parasitic diode of the switch Q5, and reduce the cross voltage of the switch Q1 to achieve flexible switching. In a preferred embodiment, the preset period is adjusted to achieve zero voltage switching.

上述充電程序之充電諧振頻率(fr1)及上述放電程序之放電諧振頻率(fr2)如下式所示。

Figure 02_image001
(1)
Figure 02_image003
(2) 假設 C1= C2= C3= Cr，且如上所述欲使 fr1= fr2，則結合式(1)與(2)可得下式
Figure 02_image005
進而可導出L2與L1的電感值需符合下式
Figure 02_image007
(3) 亦即欲使 fr1= fr2時，L2與L1的電感值需設置符合式(3)的關係。 The charging resonance frequency (fr1) of the above charging process and the discharging resonance frequency (fr2) of the above discharging process are shown in the following equations.
Figure 02_image001
(1)
Figure 02_image003
(2) Assuming that C 1 = C 2 = C 3 = C r, and we want to make fr 1 = fr 2, as described above, the following equation can be obtained by combining equations (1) and (2)
Figure 02_image005
Then it can be derived that the inductance values of L2 and L1 must conform to the following formula
Figure 02_image007
(3) That is, when fr 1 = fr 2, the inductance values of L2 and L1 need to be set in accordance with the relationship of formula (3).

圖2B顯示圖2A所示之諧振切換式電源轉換器中，相關訊號之訊號波形示意圖。輸出電壓Vout、輸出電流Io、充電諧振電流IL1、放電諧振電流IL2、電容C1直流偏壓Vc1、電容C1電流Ic1、開關Q7電流IS7以及開關Q9電流IS9如圖2B所示。在本實施例中，充電諧振頻率與放電諧振頻率相等且充電程序的持續時間及放電程序的持續時間大致上為百分之五十之工作週期。FIG. 2B shows a schematic diagram of signal waveforms of related signals in the resonant switching power converter shown in FIG. 2A. The output voltage Vout, output current Io, charging resonant current IL1, discharging resonant current IL2, capacitor C1 DC bias voltage Vc1, capacitor C1 current Ic1, switch Q7 current IS7, and switch Q9 current IS9 are shown in FIG. 2B. In this embodiment, the resonant frequency of charging is equal to the resonant frequency of discharging, and the duration of the charging process and the duration of the discharging process are approximately 50% of the duty cycle.

於另一實施例中，當L1的電感值等於L2的電感值時，且假設 C1= C2= C3= Cr，式(1)及式(2)可改寫為如下所示:

Figure 02_image009
Figure 02_image011
由上式中可理解到，當L1的電感值等於L2的電感值時，充電諧振頻率與放電諧振頻率是不相等的，在此條件下，若欲達成零電流切換，則持續時間(Ton1)及持續時間(Ton2)需各自對應設置為充電諧振頻率(fr1)及充電諧振頻率(fr2)的半週期，如下式所示:
Figure 02_image013
Figure 02_image015
若欲達成零電流切換，綜合以上公式可知，持續時間(Ton1)及持續時間(Ton2)需符合下式的關係:
Figure 02_image017
(4) In another embodiment, when the inductance value of L1 is equal to the inductance value of L2, and assuming that C 1 = C 2 = C 3 = C r, equations (1) and (2) can be rewritten as follows:
Figure 02_image009
Figure 02_image011
It can be understood from the above formula that when the inductance value of L1 is equal to the inductance value of L2, the charging resonance frequency and the discharging resonance frequency are not equal. Under this condition, if you want to achieve zero current switching, the duration (Ton1) And the duration (Ton2) should be set to the half cycle of the charging resonance frequency (fr1) and the charging resonance frequency (fr2) respectively, as shown in the following formula:
Figure 02_image013
Figure 02_image015
If you want to achieve zero current switching, based on the above formula, it can be known that the duration (Ton1) and the duration (Ton2) must conform to the relationship of the following formula:
Figure 02_image017
(4)

亦即當L1的電感值等於L2的電感值時，放電程序之持續時間(Ton2)需設置為充電程序之持續時間(Ton1)的3倍，亦即，充電程序之持續時間(Ton1)大致上等於百分之二十五之工作週期，放電程序之持續時間(Ton2)大致上等於百分之七十五之工作週期，仍可達成前述之零電流切換。That is, when the inductance value of L1 is equal to the inductance value of L2, the duration of the discharging process (Ton2) needs to be set to 3 times the duration of the charging process (Ton1), that is, the duration of the charging process (Ton1) is roughly Equal to 25% of the duty cycle, the duration of the discharge process (Ton2) is roughly equal to 75% of the duty cycle, and the aforementioned zero current switching can still be achieved.

值得注意的是，L1的電感值等於L2的電感值的一個特例是，充電電感L1與放電電感L2可共用同一個電感，分別於不同時間作用為充電電感、放電電感。It is worth noting that a special case where the inductance value of L1 is equal to the inductance value of L2 is that the charging inductance L1 and the discharging inductance L2 can share the same inductance, and act as the charging inductance and the discharging inductance at different times.

因此，請參照圖3，其為根據本發明之另一實施例顯示一諧振切換式電源轉換器之電路示意圖。本實施例中，充電電感與放電電感可為同一個電感L1，如此之設置可更進一步地減少電感的數量。如圖3所示，本發明之諧振切換式電源轉換器30包含電容C1、C2、C3、開關Q1、Q2、Q3、Q4、Q5、Q6、Q7、Q8、Q9、Q10、電感L1。開關Q1-Q3分別與對應之電容C1-C3串聯，而開關Q4與電感L1串聯。應注意者為，本發明之諧振切換式電源轉換器中的電容數量並不限於本實施例的三個，亦可為二個或四個以上，本實施例所顯示之元件數量僅用以說明本發明並不用限制本發明。Therefore, please refer to FIG. 3, which is a circuit diagram of a resonant switching power converter according to another embodiment of the present invention. In this embodiment, the charging inductance and the discharging inductance can be the same inductance L1, and this configuration can further reduce the number of inductances. As shown in FIG. 3, the resonant switching power converter 30 of the present invention includes capacitors C1, C2, C3, switches Q1, Q2, Q3, Q4, Q5, Q6, Q7, Q8, Q9, Q10, and inductor L1. The switches Q1-Q3 are respectively connected in series with the corresponding capacitors C1-C3, and the switch Q4 is connected in series with the inductor L1. It should be noted that the number of capacitors in the resonant switching power converter of the present invention is not limited to three in this embodiment, and can be two or more than four. The number of components shown in this embodiment is only for illustration. The present invention does not limit the present invention.

須說明的是，在本實施例中，充電電感與放電電感為單一個相同的電感L1，在放電程序中，藉由開關Q1-Q10的切換，使電容C1-C3彼此並聯後串聯單一個相同電感L1。所謂充電電感與放電電感為單一個相同的電感L1，係指在充電程序與放電程序中，充電諧振電流IL1與放電諧振電流IL2分別僅流經單一個電感L1，而未再流經其他電感元件。It should be noted that in this embodiment, the charging inductance and the discharging inductance are the same inductance L1. In the discharging process, the capacitors C1-C3 are connected in parallel and connected in series by switching the switches Q1-Q10. Inductance L1. The so-called charging inductance and discharging inductance are the same inductance L1, which means that in the charging process and the discharging process, the charging resonant current IL1 and the discharging resonant current IL2 respectively only flow through a single inductor L1, and no other inductive components. .

如圖3所示，開關Q5之一端耦接至開關Q1與電容C1之間的節點，開關Q6之一端耦接至開關Q2與電容C2之間的節點，而開關Q7之一端耦接至開關Q3與電容C3之間的節點。開關Q8之一端耦接至電容C1與開關Q2之間的節點，開關Q9之一端耦接至電容C2與開關Q3之間的節點，而開關Q10之一端耦接至電容C3與開關Q4之間的節點。如圖3所示，開關Q5-Q7之另一端共同電連接至一節點後，耦接至開關Q4與電感L1之間的節點，開關Q8-Q10之另一端係共同耦接至接地電位。電感L1的另一端係耦接至輸出電壓Vout，開關Q1之另一端耦接至輸入電壓Vin。As shown in FIG. 3, one end of the switch Q5 is coupled to the node between the switch Q1 and the capacitor C1, one end of the switch Q6 is coupled to the node between the switch Q2 and the capacitor C2, and one end of the switch Q7 is coupled to the switch Q3 The node between and capacitor C3. One end of the switch Q8 is coupled to the node between the capacitor C1 and the switch Q2, one end of the switch Q9 is coupled to the node between the capacitor C2 and the switch Q3, and one end of the switch Q10 is coupled to the node between the capacitor C3 and the switch Q4 node. As shown in FIG. 3, after the other ends of the switches Q5-Q7 are commonly electrically connected to a node, they are coupled to the node between the switch Q4 and the inductor L1, and the other ends of the switches Q8-Q10 are commonly coupled to the ground potential. The other end of the inductor L1 is coupled to the output voltage Vout, and the other end of the switch Q1 is coupled to the input voltage Vin.

開關Q1-Q10可根據對應之操作訊號，切換所對應之電容C1-C3與電感L1之電連接關係。在一充電程序中，開關Q1-Q4係為導通，開關Q5-Q10係為不導通，使得電容C1-C3彼此串聯後與電感L1串聯於輸入電壓Vin與輸出電壓Vout之間，以形成一充電路徑。在一放電程序中，開關Q5-Q10係導通，開關Q1-Q4係不導通，使電容C1、電容C2及電容C3彼此並聯後串聯電感L1，而形成複數放電路徑。應注意者為，上述充電程序與上述放電程序係於不同的時間段重複地交錯進行，而非同時進行。於本實施例中，每個第一電容C1、C2、C3的直流偏壓均為Vo，故本實施例中的第一電容C1、C2、C3需要耐較低的額定電壓，故可使用較小體積的電容器。The switches Q1-Q10 can switch the electrical connection relationship between the corresponding capacitor C1-C3 and the inductor L1 according to the corresponding operation signal. In a charging process, the switches Q1-Q4 are turned on, and the switches Q5-Q10 are not turned on, so that the capacitors C1-C3 are connected in series with each other and then connected in series with the inductor L1 between the input voltage Vin and the output voltage Vout to form a charge path. In a discharge procedure, the switches Q5-Q10 are turned on, and the switches Q1-Q4 are not turned on. The capacitor C1, the capacitor C2, and the capacitor C3 are connected in parallel to each other and then the inductor L1 is connected in series to form a complex discharge path. It should be noted that the above-mentioned charging process and the above-mentioned discharging process are repeatedly and staggered at different time periods, rather than being performed at the same time. In this embodiment, the DC bias voltage of each of the first capacitors C1, C2, C3 is Vo. Therefore, the first capacitors C1, C2, C3 in this embodiment need to withstand lower rated voltages, so they can be used. Small size capacitor.

在充電電感與放電電感設置為單一個相同的電感L1的本實施例中，根據前述公式而適當配置上述充電程序的持續時間(Ton1)及放電程序的持續時間(Ton2)的比例，可達到柔性切換之零電流切換。具體而言，於一實施例中，上述充電程序的持續時間例如大致上等於百分之二十五之工作週期；藉此，開關可於流經開關的電流在其正半波相對較低位準的時點切換，以達成柔性切換。在一種較佳的實施例中，可達到零電流切換(zero current switch, ZCS)。於一實施例中，上述充電程序的持續時間小於特定比例之工作週期一段預設期間，例如小於百分之二十五之工作週期一段預設期間；藉此提前不導通開關Q1-Q4後仍維持有微小的電流，流經充電電感L1，因此，即可將開關Q10中，儲存於其中之寄生電容的累積電荷通過開關Q4之寄生二極體帶走，而降低開關Q10的跨壓，以達到柔性切換。在一種較佳的實施例中，調整預設期間，而達到零電壓切換(zero voltage switch，ZVS)。於一實施例中，相對地，上述放電程序的持續時間大於特定比例之工作週期一段預設期間，例如大於百分之七十五之工作週期一段預設期間；藉此，延後不導通開關Q5-Q10後放電電感L2的負電流會通過開關Q5的寄生二極體而對開關Q1的寄生電容進行充電，而降低開關Q1的跨壓，以達到柔性切換。在一種較佳的實施例中，調整預設期間，而達到零電壓切換(zero voltage switch，ZVS)。In this embodiment in which the charging inductance and the discharging inductance are set to a single same inductance L1, the ratio of the duration of the charging procedure (Ton1) and the duration of the discharging procedure (Ton2) can be appropriately configured according to the aforementioned formula to achieve flexibility. Zero current switching of switching. Specifically, in one embodiment, the duration of the above-mentioned charging procedure is, for example, approximately equal to 25% of the duty cycle; thereby, the switch can be used when the current flowing through the switch is relatively low in its positive half-wave. Switch on time to achieve flexible switching. In a preferred embodiment, zero current switch (ZCS) can be achieved. In one embodiment, the duration of the charging process is less than a specific ratio of the duty cycle for a predetermined period, for example, less than 25% of the duty cycle for a preset period; thereby, the switch Q1-Q4 is not turned on in advance. A small current is maintained and flows through the charging inductor L1. Therefore, the accumulated charge of the parasitic capacitance stored in the switch Q10 can be taken away through the parasitic diode of the switch Q4, and the cross voltage of the switch Q10 can be reduced. Achieve flexible switching. In a preferred embodiment, the preset period is adjusted to achieve zero voltage switch (ZVS). In one embodiment, relatively, the duration of the above-mentioned discharge process is greater than a specific proportion of the duty cycle for a predetermined period, for example, a duty cycle greater than 75% for a predetermined period; thereby, the non-conduction switch is delayed. After Q5-Q10, the negative current of the discharge inductor L2 will charge the parasitic capacitance of the switch Q1 through the parasitic diode of the switch Q5, and reduce the cross voltage of the switch Q1 to achieve flexible switching. In a preferred embodiment, the preset period is adjusted to achieve zero voltage switch (ZVS).

於一實施例中，上述諧振切換式電源轉換器30可為雙向諧振切換式電源轉換器。於一實施例中，上述諧振切換式電源轉換器30之輸入電壓Vin與輸出電壓Vout之電壓轉換比率可為4:1、3:1或2:1。於一實施例中，諧振切換式電源轉換器30之電壓轉換比率可彈性地加以調整，例如於充電程序與放電程序中，藉由選擇將開關Q7保持導通，並選擇將開關Q10及Q4保持不導通，則可將諧振切換式電源轉換器30之電壓轉換比率調整為3:1。同樣地，例如可選擇將開關Q6保持導通，並選擇將開關Q9、Q3、Q7、Q10及Q4保持不導通，則可將諧振切換式電源轉換器30之電壓轉換比率調整為2:1。In one embodiment, the above-mentioned resonant switching power converter 30 may be a bidirectional resonant switching power converter. In one embodiment, the voltage conversion ratio of the input voltage Vin to the output voltage Vout of the resonant switching power converter 30 may be 4:1, 3:1, or 2:1. In one embodiment, the voltage conversion ratio of the resonant switching power converter 30 can be flexibly adjusted. For example, in the charging process and the discharging process, the switch Q7 is selected to be kept on, and the switches Q10 and Q4 are selected to be kept off. Turning on, the voltage conversion ratio of the resonant switching power converter 30 can be adjusted to 3:1. Similarly, for example, the switch Q6 can be selected to be kept on, and the switches Q9, Q3, Q7, Q10, and Q4 can be selected to be kept non-conducting, then the voltage conversion ratio of the resonant switching power converter 30 can be adjusted to 2:1.

請參照圖4，其係根據本發明之又一實施例顯示一諧振切換式電源轉換器之電路示意圖。本實施例與圖3之實施例之不同在於本實施例附加了前端轉換器401，用以將輸入電壓Vin轉換為電壓V1，前端轉換器401耦接於輸入電壓Vin與電容C1之間，前端轉換器401包含前端電感Lb以及開關Q1，前端電感Lb與開關Q1串聯，前端電感Lb除了設置為前端轉換器401中的感性儲能元件，用以進行前端電源轉換之外，在前述的充電程序的持續時間(Ton1)中，前端電感Lb還串聯於電感L1而成為充電電感的一部份，開關Q1可用作為圖3之實施例中的開關Q1，其餘元件與圖3類似，故不贅述。於一實施例中，前端轉換器401包含如圖6A-6J所示之降壓轉換器、升壓轉換器、反壓轉換器、升降壓轉換器及升反壓轉換器。Please refer to FIG. 4, which is a schematic circuit diagram of a resonant switching power converter according to another embodiment of the present invention. The difference between this embodiment and the embodiment in FIG. 3 is that this embodiment adds a front-end converter 401 to convert the input voltage Vin into a voltage V1. The front-end converter 401 is coupled between the input voltage Vin and the capacitor C1. The converter 401 includes a front-end inductor Lb and a switch Q1. The front-end inductor Lb is connected in series with the switch Q1. The front-end inductor Lb is set as an inductive energy storage element in the front-end converter 401 for front-end power conversion. During the duration (Ton1), the front-end inductor Lb is also connected in series with the inductor L1 to become a part of the charging inductor. The switch Q1 can be used as the switch Q1 in the embodiment of FIG. 3, and the remaining components are similar to those in FIG. In one embodiment, the front-end converter 401 includes a buck converter, a boost converter, a back-voltage converter, a buck-boost converter, and a boost-back converter as shown in FIGS. 6A-6J.

圖5A係根據本發明之一實施例顯示一充電程序與放電程序之對應之操作訊號與對應之電感電流之訊號波形示意圖。請同時參閱圖2A，圖5A所示的實施例中，開關Q1~Q4之操作訊號G1~G4於充電程序時為高位準，而開關Q5~Q10之操作訊號G5~G10於放電程序時為高位準。於圖5A之實施例中，充電程序的持續時間大致上為百分之五十之工作週期；藉此，開關Q1可於流經開關的電流在其正半波相對較低位準的時點切換，也是在電感L1之電流為零電流時切換，以達成柔性切換。在一種較佳的實施例中，可達到零電流切換。FIG. 5A is a schematic diagram showing the corresponding operation signal of a charging process and a discharging process and the signal waveform of the corresponding inductor current according to an embodiment of the present invention. Please also refer to Figure 2A. In the embodiment shown in Figure 5A, the operating signals G1~G4 of the switches Q1~Q4 are high during the charging process, and the operating signals G5~G10 of the switches Q5~Q10 are high during the discharging process allow. In the embodiment of FIG. 5A, the duration of the charging process is approximately 50% of the duty cycle; thereby, the switch Q1 can be switched at a time when the current flowing through the switch is at a relatively low level of the positive half wave , It is also switched when the current of the inductor L1 is zero current to achieve flexible switching. In a preferred embodiment, zero current switching can be achieved.

圖5B及5C係根據本發明之另一實施例顯示一充電程序與放電程序之對應之操作訊號與對應之電感電流之訊號波形示意圖。請同時參閱圖2A，圖5B所示的實施例中，開關Q1~Q4之操作訊號G1~G4於充電程序時為高位準，而開關Q5~Q10之操作訊號G5~G10於放電程序時為高位準。於圖5B之實施例中，充電程序的持續時間大致上為小於百分之五十之工作週期一段預設期間T1；藉此，提前不導通開關Q1-Q4後仍維持有微小的電流流經充電電感L1，因此，即可將開關Q10中，儲存於其中之寄生電容的累積電荷透過開關Q4之寄生二極體放電，而降低開關Q10的跨壓，以達到柔性切換。在一種較佳的實施例中，調整預設期間T1，而達到零電壓切換。請同時參閱圖2A，圖5C所示的實施例中，開關Q1~Q4之操作訊號G1~G4於充電程序時為高位準，開關Q5~Q10之操作訊號G5~G10於放電程序時為高位準。於圖5C之實施例中，放電程序的持續時間大致上為大於百分之五十之工作週期一段預設期間T2+T3；藉此，延後不導通開關Q5-Q10後放電電感L2的負電流會通過開關Q5的寄生二極體而對開關Q1的寄生電容進行充電，而降低開關Q1的跨壓，以達到柔性切換。在一種較佳的實施例中，調整預設期間T2與T3，而達到零電壓切換。於一實施例中，應注意者為，圖5B及5C之實施例可一起實施或僅實施其中一者。此外，請參照圖5D，其係根據本發明之另一實施例顯示一充電程序與放電程序之對應之操作訊號與對應之電容電流之訊號波形示意圖。請同時參照圖2A，如圖5D所示，可調整充電程序的持續時間與放電程序的持續時間例如加入延遲時間Td，而更具彈性地調整輸入電壓Vin與輸出電壓Vout的比例。5B and 5C are schematic diagrams showing the corresponding operation signals of a charging process and a discharging process and the corresponding signal waveforms of the inductor current according to another embodiment of the present invention. Please also refer to Figure 2A. In the embodiment shown in Figure 5B, the operating signals G1~G4 of the switches Q1~Q4 are high during the charging process, and the operating signals G5~G10 of the switches Q5~Q10 are high during the discharging process allow. In the embodiment of FIG. 5B, the duration of the charging process is substantially less than 50% of the duty cycle for a predetermined period T1; thereby, even after the switches Q1-Q4 are not turned on in advance, a small current flows through The charging inductor L1, therefore, can discharge the accumulated charge of the parasitic capacitance stored in the switch Q10 through the parasitic diode of the switch Q4, thereby reducing the cross voltage of the switch Q10 to achieve flexible switching. In a preferred embodiment, the preset period T1 is adjusted to achieve zero voltage switching. Please also refer to Figure 2A. In the embodiment shown in Figure 5C, the operating signals G1~G4 of the switches Q1~Q4 are high during the charging process, and the operating signals G5~G10 of the switches Q5~Q10 are high during the discharging process. . In the embodiment of FIG. 5C, the duration of the discharge procedure is substantially greater than 50% of the duty cycle for a predetermined period T2+T3; thereby, the negative of the inductance L2 is discharged after the non-conducting switch Q5-Q10 is delayed. The current will charge the parasitic capacitance of the switch Q1 through the parasitic diode of the switch Q5, and reduce the cross voltage of the switch Q1 to achieve flexible switching. In a preferred embodiment, the preset periods T2 and T3 are adjusted to achieve zero voltage switching. In one embodiment, it should be noted that the embodiments of FIGS. 5B and 5C can be implemented together or only one of them can be implemented. In addition, please refer to FIG. 5D, which is a schematic diagram showing the corresponding operation signal of a charging process and a discharging process and the signal waveform of the corresponding capacitor current according to another embodiment of the present invention. Please also refer to FIG. 2A. As shown in FIG. 5D, the duration of the charging process and the duration of the discharging process can be adjusted, for example, a delay time Td is added, and the ratio of the input voltage Vin to the output voltage Vout can be adjusted more flexibly.

請參照圖7，其根據本發明之一實施例顯示一電源轉換器中之控制器之示意圖。如圖7所示，本發明之電源轉換器可包含一控制器701，其耦接至開關Q1-10，用以產生操作訊號G1-G4、G5-G10，以分別輸出至開關Q1-Q4、Q5-Q10，藉此分別切換開關Q1-Q4、Q5-Q10。Please refer to FIG. 7, which shows a schematic diagram of a controller in a power converter according to an embodiment of the present invention. As shown in FIG. 7, the power converter of the present invention may include a controller 701, which is coupled to the switch Q1-10 to generate operation signals G1-G4, G5-G10 to output to the switches Q1-Q4, Q5-Q10, thereby switching the switches Q1-Q4, Q5-Q10 respectively.

須說明的是，所謂開關之導通時點及不導通時點係同步於充電程序之充電諧振電流之正半波之起始時點及結束時點，係指開關之導通時點及不導通時點與充電諧振電流之正半波之起始時點及結束時點相同，或是間隔一段固定的期間；而開關之導通時點及不導通時點係同步於放電程序之放電諧振電流之正半波之起始時點及結束時點，係指開關之導通時點及不導通時點與放電諧振電流之正半波之起始時點及結束時點相同，或是間隔一段固定的期間。It should be noted that the so-called switch conduction time and non-conduction time point are synchronized with the start time and end time of the positive half wave of the charging resonant current of the charging process, and refer to the switch conduction time and non-conduction time point and the charging resonant current The start time and end time of the positive half-wave are the same, or there is a fixed interval; the conduction time and non-conduction time of the switch are synchronized with the start and end time of the positive half-wave of the discharge resonant current of the discharge sequence. It means that the switch's conduction time and non-conduction time are the same as the start time and end time of the positive half-wave of the discharge resonant current, or are separated by a fixed period.

本發明如上所述提供了一種諧振切換式電源轉換器，其藉由特殊的電路設計可減少電感數量至僅需一個電感分別於不同時段作為充電電感及放電電感、可降低電壓應力、可使所有諧振電容具有相同的額定電流及額定電壓而能夠使用較小體積的電容、可諧振操作以達到具有零電流切換(ZCS)或零電壓切換(ZVS)的柔性切換、可更具彈性地調變電壓轉換比率、可結合諧振電感與前端轉換器且可雙向操作。As described above, the present invention provides a resonant switching power converter, which can reduce the number of inductances through a special circuit design to only require one inductor to be used as a charging inductance and a discharging inductance at different periods of time, which can reduce voltage stress and make all The resonant capacitors have the same rated current and rated voltage, and can use smaller-volume capacitors, can operate at resonance to achieve flexible switching with zero current switching (ZCS) or zero voltage switching (ZVS), and can adjust the voltage more flexibly Conversion ratio, can be combined with resonant inductors and front-end converters, and can be operated in both directions.

以上已針對較佳實施例來說明本發明，唯以上所述者，僅係為使熟悉本技術者易於了解本發明的內容而已，並非用來限定本發明之最廣的權利範圍。所說明之各個實施例，並不限於單獨應用，亦可以組合應用，舉例而言，兩個或以上之實施例可以組合運用，而一實施例中之部分組成亦可用以取代另一實施例中對應之組成部件。此外，在本發明之相同精神下，熟悉本技術者可以思及各種等效變化以及各種組合，舉例而言，本發明所稱「根據某訊號進行處理或運算或產生某輸出結果」，不限於根據該訊號的本身，亦包含於必要時，將該訊號進行電壓電流轉換、電流電壓轉換、及／或比例轉換等，之後根據轉換後的訊號進行處理或運算產生某輸出結果。由此可知，在本發明之相同精神下，熟悉本技術者可以思及各種等效變化以及各種組合，其組合方式甚多，在此不一一列舉說明。因此，本發明的範圍應涵蓋上述及其他所有等效變化。The present invention has been described above with respect to preferred embodiments, but the above description is only for making it easier for those skilled in the art to understand the content of the present invention, and is not intended to limit the broadest scope of rights of the present invention. The illustrated embodiments are not limited to individual applications, but can also be combined. For example, two or more embodiments can be used in combination, and part of the composition in one embodiment can also be used to replace another embodiment. Corresponding components. In addition, under the same spirit of the present invention, those skilled in the art can think of various equivalent changes and various combinations. For example, the “processing or calculation based on a certain signal or generating a certain output result” in the present invention is not limited to According to the signal itself, it also includes performing voltage-current conversion, current-voltage conversion, and/or ratio conversion on the signal when necessary, and then process or calculate an output result according to the converted signal. It can be seen from this that under the same spirit of the present invention, those skilled in the art can think of various equivalent changes and various combinations, and there are many combinations of them, which will not be listed here. Therefore, the scope of the present invention should cover all the above and other equivalent changes.

20, 30, 40:諧振切換式電源轉換器 401:前端轉換器 701:控制器 C1~C3, C1(CR), C2(CF), C3(CR):電容 Co:輸出電容 G1~G10:操作訊號 Ic1:電容C1電流 IL1:充電諧振電流 IL2:放電諧振電流 Io:輸出電流 IS7:開關Q7電流 IS9:開關Q9電流 L1:充電電感 L2:放電電感 L1(LR), L2(LR), Lb:電感 Q1~Q10, Q1(S1A), Q2(S2A), Q3(S1B), Q4(S2B), Q5(S1A), Q6(S2A), Q7(S2A), Q8(S1B), Q9(S1B), Q10(S2B), Qb:開關 RL:負載電阻 T1, T2, T3:期間 Td:延遲時間 V1:電壓 Vc1:電容C1直流偏壓 Vc2:電容C2直流偏壓 Vc3:電容C3直流偏壓 Vin:輸入電壓 Vout:輸出電壓 20, 30, 40: resonant switching power converter 401: front-end converter 701: Controller C1~C3, C1(CR), C2(CF), C3(CR): capacitance Co: output capacitance G1~G10: Operation signal Ic1: Capacitor C1 current IL1: Charging resonance current IL2: Discharge resonance current Io: output current IS7: Switch Q7 current IS9: Switch Q9 current L1: Charging inductance L2: discharge inductance L1(LR), L2(LR), Lb: inductance Q1~Q10, Q1(S1A), Q2(S2A), Q3(S1B), Q4(S2B), Q5(S1A), Q6(S2A), Q7(S2A), Q8(S1B), Q9(S1B), Q10 (S2B), Qb: switch RL: load resistance T1, T2, T3: period Td: Delay time V1: Voltage Vc1: Capacitor C1 DC bias Vc2: Capacitor C2 DC bias Vc3: Capacitor C3 DC bias Vin: input voltage Vout: output voltage

圖1係為習知的電源轉換器。Figure 1 is a conventional power converter.

圖2A及2B係根據本發明之一實施例顯示一諧振切換式電源轉換器之電路與相關訊號之訊號波形示意圖。2A and 2B are schematic diagrams showing the circuit of a resonant switching power converter and the signal waveforms of related signals according to an embodiment of the present invention.

圖3係根據本發明之另一實施例顯示一諧振切換式電源轉換器之電路示意圖。FIG. 3 is a schematic diagram showing a circuit of a resonant switching power converter according to another embodiment of the present invention.

圖4係根據本發明之又一實施例顯示一諧振切換式電源轉換器之電路示意圖。FIG. 4 is a schematic diagram showing a circuit of a resonant switching power converter according to another embodiment of the present invention.

圖5A、5B及5C係根據本發明之一實施例顯示一充電程序與放電程序之對應之操作訊號與對應之電感電流之訊號波形示意圖。5A, 5B, and 5C are schematic diagrams showing the corresponding operation signals of a charging process and a discharging process and the corresponding signal waveforms of the inductor current according to an embodiment of the present invention.

圖5D係根據本發明之一實施例顯示一充電程序與放電程序之對應之操作訊號與對應之電容電流之訊號波形示意圖。FIG. 5D is a schematic diagram showing the corresponding operation signal of a charging process and a discharging process and the signal waveform of the corresponding capacitor current according to an embodiment of the present invention.

圖6A-6J顯示降壓轉換器、升壓轉換器、反壓轉換器、升降壓轉換器及升反壓轉換器。Figures 6A-6J show a buck converter, a boost converter, a back-voltage converter, a buck-boost converter, and a boost-back converter.

圖7係根據本發明之一實施例顯示一電源轉換器中之控制器之示意圖。FIG. 7 is a schematic diagram showing a controller in a power converter according to an embodiment of the present invention.

20:諧振切換式電源轉換器 20: Resonant switching power converter

C1~C3:電容 C1~C3: Capacitance

Co:輸出電容 Co: output capacitance

L1:充電電感 L1: Charging inductance

L2:放電電感 L2: discharge inductance

Q1~Q10:開關 Q1~Q10: switch

RL:負載電阻 RL: load resistance

Vin:輸入電壓 Vin: input voltage

Vout:輸出電壓 Vout: output voltage

Claims (14)

一種諧振切換式電源轉換器，用以將一輸入電壓轉換為一輸出電壓，該諧振切換式電源轉換器包含：複數電容；複數開關，與該複數電容對應耦接，分別根據對應之一操作訊號，以切換所對應之該電容之電連接關係；至少一充電電感，與該複數電容中之至少其中之一對應串聯；以及至少一放電電感，與該複數電容中之至少其中之一對應串聯；其中，在一充電程序中，藉由該複數開關的切換，使該複數電容與該至少一充電電感彼此串聯於該輸入電壓與該輸出電壓之間，以形成一充電路徑，且對應之該複數開關之導通時點及不導通時點係同步於該充電程序之一充電諧振電流之正半波之起始時點及結束時點；其中，在一放電程序中，藉由該複數開關的切換，使每一該電容與對應之該放電電感串聯於該輸出電壓與一接地電位間，而形成複數放電路徑，且對應之該複數開關之導通時點及不導通時點係同步於該放電程序之一放電諧振電流之正半波之起始時點及結束時點；其中，該充電程序與該放電程序彼此重複地交錯排序，以將該輸入電壓轉換為該輸出電壓；其中該至少一充電電感為單一個充電電感，該至少一放電電感為單一個放電電感，在該放電程序中，藉由該複數開關的切換，使該複數電容彼此並聯後串聯該單一個放電電感。 A resonant switching power converter for converting an input voltage into an output voltage. The resonant switching power converter includes: a complex capacitor; a complex switch, which is correspondingly coupled to the complex capacitor, and is respectively based on a corresponding operation signal , To switch the electrical connection relationship of the corresponding capacitor; at least one charging inductance in series with at least one of the plurality of capacitors; and at least one discharging inductance in series with at least one of the plurality of capacitors; Wherein, in a charging process, by switching the plurality of switches, the plurality of capacitors and the at least one charging inductor are connected in series with each other between the input voltage and the output voltage to form a charging path corresponding to the plurality of The conduction time and the non-conduction time of the switch are synchronized with the start time and end time of the positive half-wave of the resonant current of one of the charging processes; wherein, in a discharge process, the switching of the plurality of switches causes each The capacitor and the corresponding discharge inductance are connected in series between the output voltage and a ground potential to form a plurality of discharge paths, and the conduction time and non-conduction time point of the corresponding plurality of switches are synchronized with a discharge resonance current of the discharge process The start time and end time of the positive half-wave; wherein the charging procedure and the discharging procedure are alternately sequenced repeatedly to convert the input voltage to the output voltage; wherein the at least one charging inductor is a single charging inductor, the The at least one discharge inductance is a single discharge inductance. In the discharge process, the plurality of switches are switched to connect the plurality of capacitors in parallel with each other and then the single discharge inductance is connected in series. 如請求項1所述之諧振切換式電源轉換器，其中該單一個充電電感之電感值相等於該單一個放電電感之電感值。 The resonant switching power converter according to claim 1, wherein the inductance value of the single charging inductor is equal to the inductance value of the single discharging inductor. 如請求項1所述之諧振切換式電源轉換器，其中該至少一充電電感與該至少一放電電感為單一個相同電感，在該放電程序中，藉由該複數開關的切換，使該複數電容彼此並聯後串聯該單一個相同電感。 The resonant switching power converter according to claim 1, wherein the at least one charging inductance and the at least one discharging inductance are a single same inductance, and in the discharging process, the plurality of switches are switched to make the plurality of capacitors After connecting in parallel with each other, the single same inductance is connected in series. 如請求項1所述之諧振切換式電源轉換器，其中該諧振切換式電源轉換器於該充電程序與該放電程序中，藉由保持導通該複數開關中特定之至少一者，並保持不導通該複數開關中特定之至少二者，而改變該輸入電壓與該輸出電壓之電壓轉換比率。 The resonant switching power converter according to claim 1, wherein the resonant switching power converter keeps conducting at least one of the plurality of switches during the charging process and the discharging process, and keeps being non-conducting At least two of the plurality of switches are specified to change the voltage conversion ratio between the input voltage and the output voltage. 如請求項1、2或3所述之諧振切換式電源轉換器，更包含一前端轉換器，其中該前端轉換器具有一前端電感，用以輔助該充電電感。 The resonant switching power converter according to claim 1, 2 or 3 further includes a front-end converter, wherein the front-end converter has a front-end inductor to assist the charging inductor. 如請求項5所述之諧振切換式電源轉換器，其中該前端轉換器包含降壓轉換器、升壓轉換器、升降壓轉換器、反壓轉換器或升反壓轉換器。 The resonant switching power converter according to claim 5, wherein the front-end converter includes a buck converter, a boost converter, a buck-boost converter, a back-voltage converter, or a boost-back converter. 如請求項1所述之諧振切換式電源轉換器，其中該充電程序具有一充電諧振頻率，且該放電程序具有一放電諧振頻率，且該充電諧振頻率與該放電諧振頻率相同。 The resonant switching power converter according to claim 1, wherein the charging procedure has a charging resonance frequency, and the discharging procedure has a discharging resonance frequency, and the charging resonance frequency is the same as the discharging resonance frequency. 如請求項1、2或3所述之諧振切換式電源轉換器，其中該充電程序具有一充電諧振頻率，且該放電程序具有一放電諧振頻率，且該充電諧振頻率與該放電諧振頻率不同。 The resonant switching power converter according to claim 1, 2 or 3, wherein the charging procedure has a charging resonance frequency, and the discharging procedure has a discharging resonance frequency, and the charging resonance frequency is different from the discharging resonance frequency. 如請求項1、2或3所述之諧振切換式電源轉換器，其中藉由調整該充電程序的持續時間，以達到柔性切換(soft switching)之零電壓切換。 The resonant switching power converter according to claim 1, 2 or 3, wherein the duration of the charging process is adjusted to achieve soft switching (zero voltage switching). 如請求項1、2或3所述之諧振切換式電源轉換器，其中藉由調整該放電程序的持續時間，以達到柔性切換(soft switching)之零電壓切換。 The resonant switching power converter according to claim 1, 2 or 3, wherein the duration of the discharge process is adjusted to achieve soft switching (zero voltage switching). 如請求項1、2或3所述之諧振切換式電源轉換器，其中該諧振切換式電源轉換器為雙向諧振切換式電源轉換器。 The resonant switching power converter according to claim 1, 2 or 3, wherein the resonant switching power converter is a bidirectional resonant switching power converter. 如請求項1、2或3所述之諧振切換式電源轉換器，其中該諧振切換式電源轉換器之該輸入電壓與該輸出電壓之電壓轉換比率為4：1、3：1或2：1。 The resonant switching power converter according to claim 1, 2 or 3, wherein the voltage conversion ratio of the input voltage to the output voltage of the resonant switching power converter is 4:1, 3:1, or 2:1 . 如請求項1、2或3所述之諧振切換式電源轉換器，其中該充電程序的持續時間與該放電程序的持續時間彼此不重疊。 The resonant switching power converter according to claim 1, 2 or 3, wherein the duration of the charging procedure and the duration of the discharging procedure do not overlap with each other. 如請求項1所述之諧振切換式電源轉換器，更包含一控制器，其耦接至該複數開關，用以產生該操作訊號。 The resonant switching power converter according to claim 1 further includes a controller coupled to the plurality of switches for generating the operation signal.
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