TWI742914B - Two-stage power converter - Google Patents

Two-stage power converter Download PDF

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TWI742914B
TWI742914B TW109138675A TW109138675A TWI742914B TW I742914 B TWI742914 B TW I742914B TW 109138675 A TW109138675 A TW 109138675A TW 109138675 A TW109138675 A TW 109138675A TW I742914 B TWI742914 B TW I742914B
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charging
voltage
discharging
operation signal
inductor
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TW109138675A
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Chinese (zh)
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TW202147760A (en
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劉國基
楊大勇
白忠龍
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立錡科技股份有限公司
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
    • H02M3/07—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The present invention provides a two-stage power converter including: a resonant switched-capacitor converter (RSCC) configured to operably receive an inputted voltage and generate a first stage voltage; a voltage regulator configured to operably receive the first stage voltage and generate an output voltage; and a communication interface and control circuit configured to operably generate a charging operation signal, at least one discharging operation signal and a switching signal, wherein the charging operation signal and the at least one discharging operation signal are employed to control the RSCC to perform a charging process and at least one discharging process respectively, and the switching signal is utilized to control the voltage regulator, so as to synchronize a resonant frequency of the RSCC and a switching frequency of the voltage regulator; wherein the communication interface and control circuit adjusts a delay time after the at least one discharging process is finished, and starts the charging process at a time point when the delay time ends.

Description

兩級電源轉換器Two-stage power converter

本發明係有關於一種兩級電源轉換器，特定而言係有關於一種能夠同步切換頻率之兩級電源轉換器。The present invention relates to a two-stage power converter, and in particular to a two-stage power converter capable of switching frequencies synchronously.

圖1係顯示習知的電源轉換器。於充電操作中，開關Q1、Q3、Q5、Q8、Q9係導通，開關Q2、Q4、Q6、Q7、Q10係不導通，使得電容C1串聯電感L1於輸入電壓VIN及輸出電壓VOUT之間，且電容C2串聯電容C3及電感L2於接地電位及輸出電壓VOUT之間。於放電操作中，開關Q2、Q4、Q6、Q7、Q10係導通，開關Q1、Q3、Q5、Q8、Q9係不導通，使得電感L1串聯電容C1、電容C2於接地電位及輸出電壓VOUT之間，且電感L2串聯電容C3於接地電位及輸出電壓VOUT之間。此習知的電源轉換器之電容需要耐較高的額定電壓，例如電容C1的直流偏壓是輸出電壓的3倍Vc1=3VOUT、電容C2的直流偏壓是輸出電壓的2倍Vc2=2VOUT、電容C3的直流偏壓與輸出電壓相當Vc3=VOUT，因為電容之直流偏壓相對較高，故此習知電源轉換器需要使用具有較大體積的電容。此外，電容的電容值通常會隨著直流偏壓的上升而降低，當輸入電壓的範圍是在36V及76V之間時，電容C1的直流偏壓範圍會是在27V及57V之間，由於直流偏壓的變化範圍較廣，故此習知電源轉換器之電容值變化相當大，其諧振頻率也會隨著電容的變化而改變。如此會造成較大的切換電源損耗並且需要複雜的控制來改變電源轉換效率。再者，此習知電源轉換器之輸入電壓VIN與輸出電壓VOUT之電壓轉換比率僅可為4:1或2:1，並無法進行3:1的電壓轉換比率。Figure 1 shows a conventional power converter. During the charging operation, the switches Q1, Q3, Q5, Q8, and Q9 are turned on, and the switches Q2, Q4, Q6, Q7, and Q10 are not turned on, so that the capacitor C1 is connected in series with the inductor L1 between the input voltage VIN and the output voltage VOUT, and The capacitor C2 is connected in series with the capacitor C3 and the inductor L2 between the ground potential and the output voltage VOUT. In the discharging operation, the switches Q2, Q4, Q6, Q7, Q10 are turned on, and the switches Q1, Q3, Q5, Q8, Q9 are not turned on, so that the inductor L1 is connected in series with the capacitor C1 and the capacitor C2 between the ground potential and the output voltage VOUT , And the inductor L2 is connected in series with the capacitor C3 between the ground potential and the output voltage VOUT. The capacitor of this conventional power converter needs to withstand a higher rated voltage. For example, the DC bias of the capacitor C1 is 3 times the output voltage Vc1=3VOUT, and the DC bias of the capacitor C2 is 2 times the output voltage Vc2=2VOUT, The DC bias voltage of the capacitor C3 is equivalent to the output voltage Vc3=VOUT. Because the DC bias voltage of the capacitor is relatively high, the conventional power converter needs to use a capacitor with a larger volume. In addition, the capacitance value of the capacitor usually decreases with the increase of the DC bias voltage. When the input voltage range is between 36V and 76V, the DC bias voltage range of the capacitor C1 will be between 27V and 57V. The bias voltage has a wide variation range. Therefore, the capacitance value of the conventional power converter varies greatly, and its resonant frequency also changes with the variation of the capacitance. This will cause a large switching power loss and require complex control to change the power conversion efficiency. Furthermore, the voltage conversion ratio between the input voltage VIN and the output voltage VOUT of the conventional power converter can only be 4:1 or 2:1, and a 3:1 voltage conversion ratio cannot be performed.

有鑑於此，本發明即針對上述先前技術之不足，提出一種創新的電源轉換器。In view of this, the present invention provides an innovative power converter in view of the above-mentioned shortcomings of the prior art.

於一觀點中，本發明提供一種兩級電源轉換器，用以將一輸入電壓轉換為一輸出電壓，包含：一諧振切換式電容轉換器(resonant switched-capacitor converter, RSCC)，用以接收該輸入電壓，而產生一第一級電壓；一電壓調節器，用以接收該第一級電壓，而產生該輸出電壓；以及一通訊界面及控制電路，用以產生一充電操作訊號、至少一放電操作訊號與一切換訊號，其中該充電操作訊號與該至少一放電操作訊號用以控制該RSCC，且該切換訊號用以控制該電壓調節器，以同步該RSCC之一諧振頻率與該電壓調節器之一切換頻率；其中該RSCC包含：複數電容；複數開關，與該複數電容對應耦接，每一該開關根據所對應之該充電操作訊號或該放電操作訊號，以切換所對應之該電容之電連接關係；至少一充電電感，與該複數電容中之至少其中之一對應串聯；以及至少一放電電感，與該複數電容中之至少其中之一對應串聯；其中，該充電操作訊號與該至少一放電操作訊號，分別各自切換至一導通位準一段導通期間，且該複數段導通期間彼此不重疊，以使一充電程序與至少一放電程序彼此不重疊；其中，在該充電程序中，藉由該充電操作訊號控制該複數開關的切換，使該複數電容與該至少一充電電感彼此串聯於該輸入電壓與該第一級電壓之間，以形成一充電路徑；其中，在該至少一放電程序中，藉由該至少一放電操作訊號控制該複數開關的切換，使每一該電容與對應之該放電電感串聯於該第一級電壓與一接地電位間，以同時形成或輪流形成複數放電路徑；其中，該充電程序與該至少一放電程序彼此重複地交錯排序，以將該輸入電壓轉換為該第一級電壓；其中該通訊界面及控制電路於該至少一放電程序結束後調節一延遲時間，且於該延遲時間結束時點，起始該充電程序，並於該延遲時間中，保持該複數開關不導通。In one aspect, the present invention provides a two-stage power converter for converting an input voltage into an output voltage, including: a resonant switched-capacitor converter (RSCC) for receiving the Input voltage to generate a first-level voltage; a voltage regulator to receive the first-level voltage to generate the output voltage; and a communication interface and control circuit to generate a charging operation signal and at least one discharge Operation signal and a switching signal, wherein the charging operation signal and the at least one discharging operation signal are used to control the RSCC, and the switching signal is used to control the voltage regulator to synchronize a resonance frequency of the RSCC with the voltage regulator A switching frequency; wherein the RSCC includes: a plurality of capacitors; a plurality of switches, correspondingly coupled to the plurality of capacitors, each of the switches according to the corresponding charging operation signal or the discharging operation signal to switch the corresponding capacitor Electrical connection relationship; at least one charging inductor is connected in series with at least one of the plurality of capacitors; and at least one discharge inductor is connected in series with at least one of the plurality of capacitors; wherein, the charging operation signal and the at least one of the capacitors are connected in series. A discharge operation signal is respectively switched to a conduction level for a period of conduction, and the plurality of conduction periods do not overlap with each other, so that a charging process and at least one discharging process do not overlap with each other; wherein, in the charging process, by The switching of the plurality of switches is controlled by the charging operation signal, so that the plurality of capacitors and the at least one charging inductor are connected in series between the input voltage and the first stage voltage to form a charging path; wherein, at the at least one discharge In the procedure, the switching of the plurality of switches is controlled by the at least one discharge operation signal, so that each of the capacitors and the corresponding discharge inductance are connected in series between the first-level voltage and a ground potential to form a plurality of discharges simultaneously or alternately Path; wherein the charging procedure and the at least one discharging procedure are alternately sorted repeatedly to convert the input voltage into the first-level voltage; wherein the communication interface and the control circuit adjust a delay after the at least one discharging procedure ends Time, and at the end of the delay time, the charging procedure is started, and during the delay time, the plurality of switches are kept non-conducting.

於一實施例中，該通訊界面及控制電路調整該延遲時間，以調整該RSCC之該諧振頻率。In one embodiment, the communication interface and the control circuit adjust the delay time to adjust the resonance frequency of the RSCC.

於一實施例中，上述兩級電源轉換器可更包含一電源供應單元，用以提供該輸入電壓。In one embodiment, the above-mentioned two-stage power converter may further include a power supply unit for providing the input voltage.

於一實施例中，該輸出電壓用以供應電源予一中央處理單元(center processing unit, CPU)、一圖形處理單元(graphic processing unit, GPU)或一記憶單元，且該通訊界面及控制電路調整該充電操作訊號、該至少一放電操作訊號與該切換訊號，以調節該輸入電壓與該第一級電壓之比例。In one embodiment, the output voltage is used to supply power to a central processing unit (CPU), a graphics processing unit (GPU) or a memory unit, and the communication interface and control circuit are adjusted The charging operation signal, the at least one discharging operation signal and the switching signal are used to adjust the ratio of the input voltage to the first-level voltage.

於一實施例中，該至少一充電電感為單一個充電電感，該至少一放電電感為單一個放電電感。In one embodiment, the at least one charging inductance is a single charging inductance, and the at least one discharging inductance is a single discharging inductance.

於一實施例中，該單一個充電電感之電感值相等於該單一個放電電感之電感值。In one embodiment, the inductance value of the single charging inductor is equal to the inductance value of the single discharging inductor.

於一實施例中，該至少一充電電感與該至少一放電電感為單一個相同電感。In one embodiment, the at least one charging inductor and the at least one discharging inductor are a single same inductor.

於一實施例中，該單一個相同電感為可變電感。In one embodiment, the single identical inductor is a variable inductor.

於一實施例中，該充電程序具有一充電諧振頻率，且該至少一放電程序具有一放電諧振頻率，且該充電諧振頻率與該放電諧振頻率相同。In one embodiment, the charging process has a charging resonance frequency, and the at least one discharging process has a discharging resonance frequency, and the charging resonance frequency is the same as the discharging resonance frequency.

於一實施例中，該充電程序具有一充電諧振頻率，且該至少一放電程序具有一放電諧振頻率，且該充電諧振頻率與該放電諧振頻率不同。In one embodiment, the charging process has a charging resonance frequency, and the at least one discharging process has a discharging resonance frequency, and the charging resonance frequency is different from the discharging resonance frequency.

於一實施例中，調整該充電程序的持續時間，以達到柔性切換(soft switching)之零電壓切換。In one embodiment, the duration of the charging procedure is adjusted to achieve zero-voltage switching of soft switching.

於一實施例中，調整該至少一放電程序的持續時間，以達到柔性切換(soft switching)之零電壓切換。In one embodiment, the duration of the at least one discharge process is adjusted to achieve zero voltage switching of soft switching.

於一實施例中，該諧振切換式電容轉換器為雙向諧振切換式電容轉換器。In one embodiment, the resonant switched capacitor converter is a bidirectional resonant switched capacitor converter.

於一實施例中，該諧振切換式電容轉換器之該輸入電壓與該第一級電壓之電壓轉換比率為4:1、3:1或2:1。In one embodiment, the voltage conversion ratio of the input voltage to the first stage voltage of the resonant switched capacitor converter is 4:1, 3:1, or 2:1.

本發明之一優點在於本發明可調整延遲時間、可調整諧振切換式電容轉換器之諧振頻率及電壓調節器之切換頻率，且可降低諧振切換式電容轉換器之諧振頻率及電壓調節器之切換頻率以改善低負載時的效率。One of the advantages of the present invention is that the present invention can adjust the delay time, can adjust the resonant frequency of the resonant switched capacitor converter and the switching frequency of the voltage regulator, and can reduce the resonant frequency of the resonant switched capacitor converter and the switching of the voltage regulator Frequency to improve efficiency at low loads.

本發明之另一優點在於本發明可同步諧振切換式電容轉換器之諧振頻率與電壓調節器之切換頻率以改善電磁干擾過濾的效能、可使諧振切換式電容轉換器達到具有零電流切換(ZCS)或零電壓切換(ZVS)的柔性切換以用於高電源效率、可藉由設定開關而更具彈性地調變諧振切換式電容轉換器之電壓轉換比率。Another advantage of the present invention is that the present invention can synchronize the resonant frequency of the resonant switched capacitor converter with the switching frequency of the voltage regulator to improve the efficiency of electromagnetic interference filtering, and can make the resonant switched capacitor converter achieve zero current switching (ZCS). ) Or Zero Voltage Switching (ZVS) flexible switching for high power efficiency. The voltage conversion ratio of the resonant switching capacitor converter can be adjusted more flexibly by setting the switch.

本發明之又一優點在於本發明可使諧振切換式電容轉換器之所有諧振電容具有相同的額定電流及額定電壓而能夠使用較小體積的電容，且可降低諧振切換式電容轉換器之電壓應力。Another advantage of the present invention is that the present invention can make all the resonant capacitors of the resonant switched capacitor converter have the same rated current and rated voltage, and can use smaller-volume capacitors, and can reduce the voltage stress of the resonant switched capacitor converter. .

底下藉由具體實施例詳加說明，當更容易瞭解本發明之目的、技術內容、特點及其所達成之功效。Detailed descriptions are given below by specific embodiments, so that it will be easier to understand the purpose, technical content, features, and effects of the present invention.

本發明中的圖式均屬示意，主要意在表示各電路間之耦接關係，以及各訊號波形之間之關係，至於電路、訊號波形與頻率則並未依照比例繪製。The drawings in the present invention are all schematic, and are mainly intended to show the coupling relationship between the circuits and the relationship between the signal waveforms. As for the circuits, signal waveforms, and frequencies, they are not drawn to scale.

圖2係根據本發明之一實施例顯示一兩級電源轉換器之方塊示意圖。請參照圖2，本發明之兩級電源轉換器20包含一諧振切換式電容轉換器(resonant switched-capacitor converter, RSCC)201、一電壓調節器202以及一通訊界面及控制電路203。電壓調節器202係耦接至諧振切換式電容轉換器201，而通訊界面及控制電路203係耦接至諧振切換式電容轉換器201及電壓調節器202兩者。諧振切換式電容轉換器201係用以接收輸入電壓Vin，而產生第一級電壓Vfs。電壓調節器202係用以接收上述第一級電壓Vfs，而產生輸出電壓Vout。通訊界面及控制電路203係用以產生一充電操作訊號、至少一放電操作訊號與一切換訊號。充電操作訊號與至少一放電操作訊號係用以控制諧振切換式電容轉換器201，而切換訊號係用以控制電壓調節器202，以同步諧振切換式電容轉換器201之一諧振頻率與電壓調節器202之一切換頻率。Fig. 2 is a block diagram showing a two-stage power converter according to an embodiment of the present invention. Please refer to FIG. 2, the two-stage power converter 20 of the present invention includes a resonant switched-capacitor converter (RSCC) 201, a voltage regulator 202, and a communication interface and control circuit 203. The voltage regulator 202 is coupled to the resonant switched capacitor converter 201, and the communication interface and control circuit 203 are coupled to both the resonant switched capacitor converter 201 and the voltage regulator 202. The resonant switched capacitor converter 201 is used to receive the input voltage Vin to generate the first-level voltage Vfs. The voltage regulator 202 is used to receive the above-mentioned first-stage voltage Vfs to generate an output voltage Vout. The communication interface and control circuit 203 are used to generate a charging operation signal, at least one discharging operation signal and a switching signal. The charging operation signal and at least one discharging operation signal are used to control the resonant switched capacitor converter 201, and the switching signal is used to control the voltage regulator 202 to synchronize a resonant frequency of the resonant switched capacitor converter 201 with the voltage regulator One of 202 switches the frequency.

如圖2所示，電壓調節器202及通訊界面及控制電路203可分別進一步耦接至中央處理單元/圖形處理單元/記憶單元204，輸出電壓Vout係用以供應電源予中央處理單元/圖形處理單元/記憶單元204。其中，中央處理單元/圖形處理單元/記憶單元204例如可為中央處理單元(center processing unit, CPU)、圖形處理單元(graphic processing unit, GPU)與記憶單元之其中之一或其組合電路。As shown in Figure 2, the voltage regulator 202 and the communication interface and control circuit 203 can be further coupled to the central processing unit/graphics processing unit/memory unit 204, respectively, and the output voltage Vout is used to supply power to the central processing unit/graphics processing. Unit/memory unit 204. The central processing unit/graphic processing unit/memory unit 204 can be, for example, one of a central processing unit (CPU), a graphics processing unit (GPU), and a memory unit, or a combination circuit thereof.

於一實施例中，通訊界面及控制電路203可根據中央處理單元/圖形處理單元/記憶單元204的負載需求而調整充電操作訊號、至少一放電操作訊號與切換訊號，以調節輸入電壓Vin與第一級電壓Vfs之比例及第一級電壓Vfs與輸出電壓Vout之比例。於一實施例中，上述調整充電操作訊號及/或至少一放電操作訊號可包含將充電操作訊號及/或至少一放電操作訊號之上升切換時點延遲一延遲時間，以調節輸入電壓Vin與第一級電壓Vfs之比例。於另一實施例中，通訊界面及控制電路203可根據中央處理單元/圖形處理單元/記憶單元204的負載需求而調整充電操作訊號、至少一放電操作訊號與切換訊號，以調整諧振切換式電容轉換器201之諧振頻率及電壓調節器202之切換頻率。於一實施例中，上述調整充電操作訊號及/或至少一放電操作訊號可包含將充電操作訊號及/或至少一放電操作訊號之上升切換時點延遲一延遲時間，以調整諧振切換式電容轉換器201之諧振頻率。上述通訊界面例如但不限於I 2C (Inter-Integrated Circuit)介面。 In one embodiment, the communication interface and control circuit 203 can adjust the charging operation signal, at least one discharging operation signal and the switching signal according to the load demand of the central processing unit/graphic processing unit/memory unit 204 to adjust the input voltage Vin and the first The ratio of the first-level voltage Vfs and the ratio of the first-level voltage Vfs to the output voltage Vout. In one embodiment, adjusting the charging operation signal and/or the at least one discharging operation signal may include delaying the rising switching timing of the charging operation signal and/or the at least one discharging operation signal by a delay time to adjust the input voltage Vin and the first The ratio of the level voltage Vfs. In another embodiment, the communication interface and control circuit 203 can adjust the charging operation signal, at least one discharging operation signal and the switching signal according to the load requirements of the central processing unit/graphics processing unit/memory unit 204 to adjust the resonant switching capacitor The resonant frequency of the converter 201 and the switching frequency of the voltage regulator 202. In one embodiment, adjusting the charging operation signal and/or the at least one discharging operation signal may include delaying the rising switching timing of the charging operation signal and/or the at least one discharging operation signal by a delay time to adjust the resonant switched capacitor converter The resonant frequency of 201. The aforementioned communication interface is for example but not limited to an I 2 C (Inter-Integrated Circuit) interface.

本發明優於先前技術之處，至少有以下幾項：一是根據本發明，藉由通訊界面及控制電路203整合調整充電操作訊號之頻率及/或至少一放電操作訊號之頻率及/或前述延遲時間，可以將兩級電源轉換器之第一級轉換器(即諧振切換式電容轉換器)與第二級轉換器(即電壓調節器)之功率轉換效率做最佳化調整；二是於中央處理單元/圖形處理單元/記憶單元204為輕載時，根據本發明可降低充電操作訊號之頻率及/或至少一放電操作訊號之頻率以提高功率轉換效率；三是根據本發明，藉由通訊界面及控制電路203同步充電操作訊號之頻率、至少一放電操作訊號及操作訊號，可以降低電磁干擾(electromagnetic interference, EMI)；四是根據本發明，可以在兩級電源轉換器中，達成柔性切換，進而達到零電流切換或零電壓切換，以提高功率轉換效律；五是根據本發明，諧振切換式電容轉換器具有可調整的電壓轉換比例，例如諧振切換式電容轉換器之輸入電壓Vin與第一級電壓Vfs之電壓轉換比率可為4:1、3:1或2:1；六是在相同的輸入電壓範圍，根據本發明之諧振切換式電容轉換器可採用體積較小的電容來達成相同的轉換比例。The present invention is superior to the prior art in at least the following items: First, according to the present invention, the frequency of the charging operation signal and/or the frequency of at least one discharging operation signal and/or the aforementioned The delay time can optimize the power conversion efficiency of the first-stage converter (namely the resonant switched capacitor converter) and the second-stage converter (namely the voltage regulator) of the two-stage power converter; When the central processing unit/graphics processing unit/memory unit 204 is under light load, the frequency of the charging operation signal and/or the frequency of at least one discharging operation signal can be reduced according to the present invention to improve the power conversion efficiency; third, according to the present invention, by The communication interface and the control circuit 203 synchronize the frequency of the charging operation signal, at least one discharge operation signal and the operation signal, which can reduce electromagnetic interference (EMI); fourth, according to the present invention, flexibility can be achieved in a two-stage power converter Switching to achieve zero current switching or zero voltage switching to improve the power conversion efficiency; fifth, according to the present invention, the resonant switched capacitor converter has an adjustable voltage conversion ratio, such as the input voltage Vin of the resonant switched capacitor converter The voltage conversion ratio to the first-stage voltage Vfs can be 4:1, 3:1 or 2:1; sixth, in the same input voltage range, the resonant switching capacitor converter according to the present invention can use a smaller capacitor To achieve the same conversion ratio.

圖3係根據本發明之另一實施例顯示一兩級電源轉換器之方塊示意圖。本實施例與圖2之實施例之不同在於本實施例更包含了電源供應單元305。本實施例中之諧振切換式電容轉換器301、電壓調節器302、通訊界面及控制電路303及中央處理單元/圖形處理單元/記憶單元304係類似於圖2之諧振切換式電容轉換器201、電壓調節器202、通訊界面及控制電路203及中央處理單元/圖形處理單元/記憶單元204，故不贅述。如圖3所示，本發明之兩級電源轉換器30可更包含一電源供應單元305，其耦接至諧振切換式電容轉換器301，用以提供輸入電壓Vin。於一實施例中，電源供應單元305可包含一電磁干擾抑制器，其具有一過濾頻段，前述同步的諧振切換式電容轉換器301之諧振頻率與電壓調節器302之切換頻率可位於前述電磁干擾抑制器之過濾頻段之內，藉此可同時過濾掉諧振切換式電容轉換器301及電壓調節器302之電磁雜訊而提升電磁干擾的過濾效果。FIG. 3 is a block diagram showing a two-stage power converter according to another embodiment of the present invention. The difference between this embodiment and the embodiment in FIG. 2 is that this embodiment further includes a power supply unit 305. The resonant switching capacitor converter 301, the voltage regulator 302, the communication interface and control circuit 303, and the central processing unit/graphics processing unit/memory unit 304 in this embodiment are similar to the resonant switching capacitor converter 201, The voltage regulator 202, the communication interface and control circuit 203, and the central processing unit/graphic processing unit/memory unit 204 are not described in detail. As shown in FIG. 3, the two-stage power converter 30 of the present invention may further include a power supply unit 305, which is coupled to the resonant switched capacitor converter 301 to provide an input voltage Vin. In one embodiment, the power supply unit 305 may include an electromagnetic interference suppressor with a filtering frequency band. The resonant frequency of the aforementioned synchronized resonant switched capacitor converter 301 and the switching frequency of the voltage regulator 302 may be located in the aforementioned electromagnetic interference Within the filtering frequency band of the suppressor, the electromagnetic noise of the resonant switching capacitor converter 301 and the voltage regulator 302 can be filtered at the same time to improve the filtering effect of electromagnetic interference.

圖4係根據本發明之一實施例顯示一兩級電源轉換器中之諧振切換式電容轉換器401之電路示意圖。本實施例係多個電容共用一充電電感或一放電電感，藉此無論電容數量為多少，都只需要一個充電電感及一個放電電感，可進一步減少電感的數量。如圖4所示，本發明之兩級電源轉換器中之諧振切換式電容轉換器401包含電容C1、C2、C3、開關Q1、Q2、Q3、Q4、Q5、Q6、Q7、Q8、Q9、Q10、充電電感L1以及放電電感L2。開關Q1-Q3分別與對應之電容C1-C3串聯，而開關Q4與充電電感L1串聯。應注意者為，本發明之兩級電源轉換器中之諧振切換式電容轉換器401中的電容數量並不限於本實施例的三個，亦可為二個或四個以上，本實施例所顯示之元件數量僅用以說明本發明並不用限制本發明。FIG. 4 is a schematic circuit diagram showing a resonant switched capacitor converter 401 in a two-stage power converter according to an embodiment of the present invention. In this embodiment, multiple capacitors share one charging inductance or one discharging inductance, so that no matter how many capacitors there are, only one charging inductance and one discharging inductance are needed, which can further reduce the number of inductances. As shown in FIG. 4, the resonant switching capacitor converter 401 in the two-stage power converter of the present invention includes capacitors C1, C2, C3, switches Q1, Q2, Q3, Q4, Q5, Q6, Q7, Q8, Q9, Q10, charging inductance L1 and discharging inductance L2. The switches Q1-Q3 are respectively connected in series with the corresponding capacitors C1-C3, and the switch Q4 is connected in series with the charging inductor L1. It should be noted that the number of capacitors in the resonant switched capacitor converter 401 in the two-stage power converter of the present invention is not limited to three in this embodiment, and can also be two or more than four. The number of displayed components is only used to illustrate the present invention and does not limit the present invention.

如圖4所示，開關Q5之一端耦接至開關Q1與電容C1之間的節點，開關Q6之一端耦接至開關Q2與電容C2之間的節點，而開關Q7之一端耦接至開關Q3與電容C3之間的節點。開關Q8之一端耦接至電容C1與開關Q2之間的節點，開關Q9之一端耦接至電容C2與開關Q3之間的節點，而開關Q10之一端耦接至電容C3與開關Q4之間的節點。如圖4所示，開關Q5-Q7之另一端共同電連接至一節點後，串聯至放電電感L2。開關Q8-Q10之另一端係共同耦接至接地電位。充電電感L1及放電電感L2的另一端係共同耦接至第一級電壓Vfs，開關Q1之另一端耦接至輸入電壓Vin。通訊界面及控制電路403係用以產生充電操作訊號GA與放電操作訊號GB，以分別對應一充電程序與一放電程序，而操作對應之複數開關Q1-Q10，以切換所對應之電容C1-C3之電連接關係。As shown in FIG. 4, one end of the switch Q5 is coupled to the node between the switch Q1 and the capacitor C1, one end of the switch Q6 is coupled to the node between the switch Q2 and the capacitor C2, and one end of the switch Q7 is coupled to the switch Q3 The node between and capacitor C3. One end of the switch Q8 is coupled to the node between the capacitor C1 and the switch Q2, one end of the switch Q9 is coupled to the node between the capacitor C2 and the switch Q3, and one end of the switch Q10 is coupled to the node between the capacitor C3 and the switch Q4 node. As shown in FIG. 4, after the other ends of the switches Q5-Q7 are electrically connected to a node, they are connected in series to the discharge inductor L2. The other ends of the switches Q8-Q10 are commonly coupled to the ground potential. The other ends of the charging inductor L1 and the discharging inductor L2 are commonly coupled to the first-stage voltage Vfs, and the other end of the switch Q1 is coupled to the input voltage Vin. The communication interface and the control circuit 403 are used to generate a charging operation signal GA and a discharging operation signal GB to respectively correspond to a charging process and a discharging process, and to operate the corresponding plural switches Q1-Q10 to switch the corresponding capacitors C1-C3 The electrical connection relationship.

開關Q1-Q10可根據通訊界面及控制電路403所產生之充電操作訊號GA、放電操作訊號GB，切換所對應之電容C1-C3與充電電感L1及放電電感L2之電連接關係。於一實施例中，充電操作訊號GA與放電操作訊號GB，分別各自切換至一導通位準一段導通期間，上述複數段導通期間彼此不重疊。The switches Q1-Q10 can switch the electrical connection relationship between the corresponding capacitors C1-C3 and the charging inductor L1 and the discharging inductor L2 according to the charging operation signal GA and the discharging operation signal GB generated by the communication interface and the control circuit 403. In one embodiment, the charging operation signal GA and the discharging operation signal GB are respectively switched to a conduction level for a conduction period, and the plurality of conduction periods do not overlap with each other.

在一充電程序中，根據充電操作訊號GA，開關Q1-Q4係為導通，開關Q5-Q10係為不導通，使得電容C1-C3彼此串聯後與充電電感L1串聯於輸入電壓Vin與第一級電壓Vfs之間，以形成一充電路徑。在一放電程序中，根據放電操作訊號GB，開關Q5-Q10係導通，開關Q1-Q4係不導通，使電容C1、電容C2及電容C3彼此並聯後串聯放電電感L2，而形成複數放電路徑。In a charging process, according to the charging operation signal GA, the switches Q1-Q4 are turned on, and the switches Q5-Q10 are not turned on, so that the capacitors C1-C3 are connected in series with each other and the charging inductor L1 is connected in series with the input voltage Vin and the first stage Between the voltages Vfs to form a charging path. In a discharge process, according to the discharge operation signal GB, the switches Q5-Q10 are turned on, and the switches Q1-Q4 are not turned on, so that the capacitor C1, the capacitor C2, and the capacitor C3 are connected in parallel to each other and the discharge inductor L2 is connected in series to form a plurality of discharge paths.

於一實施例中，通訊界面及控制電路403於放電程序結束後調節一延遲時間，且於延遲時間結束時點，起始充電程序，並於延遲時間中，保持複數開關Q1-Q10不導通。於一實施例中，通訊界面及控制電路403於充電程序結束後調節一延遲時間，且於延遲時間結束時點，起始放電程序，並於延遲時間中，保持複數開關Q1-Q10不導通。於一實施例中，上述延遲時間係可予以調整，以調整諧振切換式電容轉換器401之諧振頻率。於一實施例中，上述延遲時間係可予以調整，以調整諧振切換式電容轉換器401之輸入電壓Vin及第一級電壓Vfs的比例。In one embodiment, the communication interface and the control circuit 403 adjust a delay time after the discharge process ends, and at the end of the delay time, the charging process is initiated, and the plurality of switches Q1-Q10 are kept non-conducting during the delay time. In one embodiment, the communication interface and the control circuit 403 adjust a delay time after the charging process ends, and at the end of the delay time, the discharging process is initiated, and during the delay time, the plurality of switches Q1-Q10 are kept non-conducting. In one embodiment, the aforementioned delay time can be adjusted to adjust the resonant frequency of the resonant switched capacitor converter 401. In one embodiment, the aforementioned delay time can be adjusted to adjust the ratio between the input voltage Vin of the resonant switched capacitor converter 401 and the first stage voltage Vfs.

應注意者為，上述充電程序與上述放電程序係於不同的時間段重複地交錯進行，而非同時進行。其中，充電程序與放電程序彼此重複地交錯排序，以將輸入電壓Vin轉換為第一級電壓Vfs。於本實施例中，每個第一電容C1、C2、C3的直流偏壓均為Vo，故本實施例中的第一電容C1、C2、C3相對於先前技術，在相同的輸入電壓Vin與第一級電壓Vfs的應用中，僅需要承受較低的額定電壓，故可使用較小體積的電容器。It should be noted that the above-mentioned charging process and the above-mentioned discharging process are repeatedly and staggered at different time periods, rather than being performed at the same time. Wherein, the charging process and the discharging process are alternately sequenced repeatedly to convert the input voltage Vin into the first-level voltage Vfs. In this embodiment, the DC bias voltage of each of the first capacitors C1, C2, C3 is Vo. Therefore, the first capacitors C1, C2, C3 in this embodiment are compared with the prior art at the same input voltage Vin and In the application of the first-level voltage Vfs, it only needs to withstand a lower rated voltage, so a smaller-volume capacitor can be used.

於一實施例中，上述充電程序之充電諧振頻率與上述放電程序之放電諧振頻率相同。於一實施例中，上述充電程序之充電諧振頻率與上述放電程序之放電諧振頻率不同。於一實施例中，上述諧振切換式電容轉換器401可為雙向諧振切換式電容轉換器。所謂雙向諧振切換式電容轉換器，係指輸入端(提供輸入電壓Vin)與輸出端(提供第一級電壓Vfs)的角色對調，意即在如圖4所示的實施例中，諧振切換式電容轉換器401可將第一級電壓Vfs轉換為輸入電壓Vin。於一實施例中，上述諧振切換式電容轉換器401之輸入電壓Vin與第一級電壓Vfs之電壓轉換比率可為4:1、3:1或2:1。In one embodiment, the resonant frequency of charging in the charging process is the same as the resonant frequency of discharging in the discharging process. In one embodiment, the resonant frequency of charging in the charging process is different from the resonant frequency of discharging in the discharging process. In one embodiment, the above-mentioned resonant switched capacitor converter 401 may be a bidirectional resonant switched capacitor converter. The so-called two-way resonant switching capacitor converter refers to the role of the input terminal (providing the input voltage Vin) and the output terminal (providing the first-stage voltage Vfs), which means that in the embodiment shown in FIG. 4, the resonant switching capacitor The capacitance converter 401 can convert the first-stage voltage Vfs into the input voltage Vin. In one embodiment, the voltage conversion ratio between the input voltage Vin of the resonant switched capacitor converter 401 and the first-stage voltage Vfs may be 4:1, 3:1, or 2:1.

於一實施例中，上述充電程序的持續時間(Ton1)係與上述充電程序之充電諧振頻率(fr1)相關。於一較佳實施例中，上述充電程序的持續時間(Ton1)係與充電程序之充電諧振電流之正半波相關，例如開關Q1-Q4之導通時點及不導通時點係大致上同步於充電程序之一充電諧振電流之正半波之起始時點及結束時點。於一實施例中，上述放電程序的持續時間(Ton2)係與上述放電程序之放電諧振頻率(fr2)相關。於一較佳實施例中，上述放電程序的持續時間(Ton2)係與放電程序之放電諧振電流之正半波相關，例如開關Q5-Q10之導通時點及不導通時點係大致上同步於放電程序之一放電諧振電流之正半波之起始時點及結束時點。In one embodiment, the duration of the charging process (Ton1) is related to the resonant frequency (fr1) of the charging process. In a preferred embodiment, the duration of the charging process (Ton1) is related to the positive half-wave of the charging resonant current of the charging process. For example, the conduction time and non-conduction time of the switches Q1-Q4 are substantially synchronized with the charging process. One of the starting and ending points of the positive half-wave of the resonant charging current. In one embodiment, the duration (Ton2) of the above-mentioned discharge process is related to the discharge resonance frequency (fr2) of the above-mentioned discharge process. In a preferred embodiment, the duration of the discharge process (Ton2) is related to the positive half-wave of the discharge resonant current of the discharge process. For example, the conduction time and non-conduction time point of the switches Q5-Q10 are substantially synchronized with the discharge process. One is the starting point and ending point of the positive half wave of the discharge resonant current.

於上述充電程序之充電諧振頻率(fr1)等於上述放電程序之放電諧振頻率(fr2)的實施例中，當上述充電程序的持續時間(Ton1)等於上述放電程序的持續時間(Ton2)時，例如大致上等於百分之五十之工作週期時，藉此可於流經開關的電流皆在其正半波相對較低位準的時點切換，以達成柔性切換。在一種較佳的實施例中，可達到零電流切換(zero current switch, ZCS)。In the embodiment in which the charging resonance frequency (fr1) of the charging procedure is equal to the discharging resonance frequency (fr2) of the discharging procedure, when the duration of the charging procedure (Ton1) is equal to the duration of the discharging procedure (Ton2), for example When the duty cycle is roughly equal to 50%, the current flowing through the switch can be switched at a relatively low level of the positive half-wave, so as to achieve flexible switching. In a preferred embodiment, zero current switch (ZCS) can be achieved.

此外需說明的是：因電路零件的本身之寄生效應或是零件間相互的匹配不一定為理想，因此，雖然欲使充電程序的持續時間等於放電程序的持續時間(也就是於此實施例中充電程序的持續時間為百分之五十之工作週期)，以達到柔性切換(soft switching)之零電流切換。但實際可能並無法準確地為百分之五十之工作週期，而僅是接近百分之五十之工作週期，亦即，根據本發明，可接受由於電路的不理想性而使充電程序的持續時間與百分之五十之工作週期間具有一定程度的誤差，此即前述之放電至「大致上」為百分之五十之工作週期之意，本文中其他提到「大致上」之處亦同。In addition, it should be noted that the parasitic effects of the circuit components or the matching between the components are not necessarily ideal. Therefore, although it is desired to make the duration of the charging procedure equal to the duration of the discharging procedure (that is, in this embodiment) The duration of the charging procedure is 50% of the duty cycle) to achieve zero current switching of soft switching. However, in reality, it may not be exactly 50% of the duty cycle, but only close to the 50% duty cycle. That is, according to the present invention, the charging process can be accepted due to the imperfectness of the circuit. There is a certain degree of error between the duration and 50% of the work cycle. This means that the aforementioned discharge to "approximately" means 50% of the work cycle. Other references to "approximately" in this article Same place.

於一實施例中，上述充電程序的持續時間小於特定比例之工作週期一段預設期間，例如小於百分之五十之工作週期一段預設期間；藉此提前不導通開關Q1-Q4後仍維持有微小的電流，流經充電電感L1，因此，即可將開關Q10中，儲存於其中之寄生電容的累積電荷透過開關Q4之寄生二極體帶走，而降低開關Q10的跨壓，以達到柔性切換。在一種較佳的實施例中，調整預設期間，而達到零電壓切換(zero voltage switch，ZVS)。於一實施例中，相對地，上述放電程序的持續時間大於特定比例之工作週期一段預設期間，例如大於百分之五十之工作週期一段預設期間；藉此，延後不導通開關Q5-Q10後放電電感L2的負電流會通過開關Q5的寄生二極體而對開關Q1的寄生電容進行充電，而降低開關Q1的跨壓，以達到柔性切換。在一種較佳的實施例中，調整預設期間，而達到零電壓切換。In one embodiment, the duration of the above-mentioned charging process is less than a specific ratio of the duty cycle for a predetermined period, for example, less than 50% of the duty cycle for a predetermined period; thereby, the switch Q1-Q4 is not turned on in advance. There is a tiny current flowing through the charging inductor L1. Therefore, the accumulated charge of the parasitic capacitance stored in the switch Q10 can be taken away through the parasitic diode of the switch Q4, and the cross voltage of the switch Q10 can be reduced to achieve Flexible switching. In a preferred embodiment, the preset period is adjusted to achieve zero voltage switch (ZVS). In one embodiment, relatively, the duration of the above-mentioned discharge process is greater than a specific proportion of the duty cycle for a predetermined period, for example, a duty cycle greater than 50% for a predetermined period; thereby, the non-conduction switch Q5 is delayed. -After Q10, the negative current of the discharge inductor L2 will charge the parasitic capacitance of the switch Q1 through the parasitic diode of the switch Q5, and reduce the cross voltage of the switch Q1 to achieve flexible switching. In a preferred embodiment, the preset period is adjusted to achieve zero voltage switching.

圖5係根據本發明之一實施例顯示一兩級電源轉換器中之諧振切換式電容轉換器之電路示意圖。本實施例與圖4之實施例的不同在於，本實施例之放電程序為複數。通訊界面及控制電路503係用以產生充電操作訊號GA與複數放電操作訊號GB1、GB2與GB3，以分別對應一充電程序與三放電程序，而操作對應之複數開關Q1-Q10，以切換所對應之電容C1-C3之電連接關係。FIG. 5 is a circuit diagram of a resonant switching capacitor converter in a two-stage power converter according to an embodiment of the present invention. The difference between this embodiment and the embodiment of FIG. 4 is that the discharge sequence of this embodiment is plural. The communication interface and the control circuit 503 are used to generate the charging operation signal GA and the plural discharging operation signals GB1, GB2, and GB3 to correspond to a charging process and three discharging processes, respectively, and to operate the corresponding plural switches Q1-Q10 to switch the corresponding ones The electrical connection relationship between the capacitors C1-C3.

開關Q1-Q10可根據通訊界面及控制電路503所產生之充電操作訊號GA、放電操作訊號GB1、GB2與GB3，切換所對應之電容C1-C3與充電電感L1及放電電感L2之電連接關係。於一實施例中，充電操作訊號GA與放電操作訊號GB1、GB2與GB3，分別各自切換至一導通位準一段導通期間，上述複數段導通期間彼此不重疊。The switches Q1-Q10 can switch the electrical connection relationship between the corresponding capacitors C1-C3 and the charging inductor L1 and the discharging inductor L2 according to the charging operation signal GA, the discharging operation signal GB1, GB2, and GB3 generated by the communication interface and the control circuit 503. In one embodiment, the charging operation signal GA and the discharging operation signals GB1, GB2, and GB3 are respectively switched to a conduction level for one conduction period, and the plurality of conduction periods do not overlap with each other.

舉例而言，在一充電程序中，根據充電操作訊號GA，開關Q1-Q4係為導通，開關Q5-Q10係為不導通，使得電容C1-C3彼此串聯後與充電電感L1串聯於輸入電壓Vin與第一級電壓Vfs之間，以形成一充電路徑。在第一放電程序中，根據放電操作訊號GB1，開關Q5與Q8係導通，開關Q1-Q4、Q6、Q7、Q9與Q10係不導通，使電容C1串聯放電電感L2，而形成第一放電路徑。在第二放電程序中，根據放電操作訊號GB2，開關Q6與Q9係導通，開關Q1-Q4、Q5、Q7、Q8與Q10係不導通，使電容C2串聯放電電感L2，而形成第二放電路徑。在第三放電程序中，根據放電操作訊號GB3，開關Q7與Q10係導通，開關Q1-Q4、Q5、Q6、Q8與Q9係不導通，使電容C3串聯放電電感L2，而形成第三放電路徑。For example, in a charging process, according to the charging operation signal GA, the switches Q1-Q4 are turned on, and the switches Q5-Q10 are not turned on, so that the capacitors C1-C3 are connected in series with each other and the charging inductor L1 is connected in series with the input voltage Vin And the first stage voltage Vfs to form a charging path. In the first discharge procedure, according to the discharge operation signal GB1, the switches Q5 and Q8 are turned on, and the switches Q1-Q4, Q6, Q7, Q9 and Q10 are not turned on, so that the capacitor C1 is discharged in series with the inductor L2 to form the first discharge path . In the second discharge procedure, according to the discharge operation signal GB2, the switches Q6 and Q9 are turned on, and the switches Q1-Q4, Q5, Q7, Q8 and Q10 are not turned on, so that the capacitor C2 is discharged in series with the inductor L2 to form a second discharge path . In the third discharge procedure, according to the discharge operation signal GB3, the switches Q7 and Q10 are turned on, and the switches Q1-Q4, Q5, Q6, Q8 and Q9 are not turned on, so that the capacitor C3 is discharged in series with the inductor L2 to form a third discharge path .

於一實施例中，通訊界面及控制電路503於充電程序結束後調節一延遲時間，且於延遲時間結束時點，起始第一放電程序，並於延遲時間中，保持複數開關Q1-Q10不導通。於一實施例中，通訊界面及控制電路503於第一放電程序結束後調節一延遲時間，且於延遲時間結束時點，起始第二放電程序，並於延遲時間中，保持複數開關Q1-Q10不導通。於一實施例中，通訊界面及控制電路503於第二放電程序結束後調節一延遲時間，且於延遲時間結束時點，起始第三放電程序，並於延遲時間中，保持複數開關Q1-Q10不導通。於一實施例中，通訊界面及控制電路503於第三放電程序結束後調節一延遲時間，且於延遲時間結束時點，起始充電程序，並於延遲時間中，保持複數開關Q1-Q10不導通。於一實施例中，上述延遲時間係可予以調整，以調整諧振切換式電容轉換器501之諧振頻率。於一實施例中，上述延遲時間係可予以調整，以調整諧振切換式電容轉換器501之輸入電壓Vin及第一級電壓Vfs的比例。In one embodiment, the communication interface and control circuit 503 adjust a delay time after the charging process ends, and at the end of the delay time, start the first discharge process, and keep the plurality of switches Q1-Q10 non-conductive during the delay time . In one embodiment, the communication interface and the control circuit 503 adjust a delay time after the first discharge process ends, and at the end of the delay time, start the second discharge process, and maintain the plurality of switches Q1-Q10 during the delay time No conduction. In one embodiment, the communication interface and the control circuit 503 adjust a delay time after the second discharge process ends, and at the end of the delay time, start the third discharge process, and maintain the plurality of switches Q1-Q10 during the delay time No conduction. In one embodiment, the communication interface and control circuit 503 adjust a delay time after the third discharging process ends, and at the end of the delay time, the charging process is initiated, and during the delay time, the plurality of switches Q1-Q10 are kept off . In one embodiment, the aforementioned delay time can be adjusted to adjust the resonant frequency of the resonant switched capacitor converter 501. In one embodiment, the aforementioned delay time can be adjusted to adjust the ratio between the input voltage Vin of the resonant switched capacitor converter 501 and the first stage voltage Vfs.

應注意者為，上述充電程序與上述第一放電程序、第二放電程序與第三放電程序係於不同的時間段重複地交錯進行，而非同時進行。其中，充電程序與上述三個放電程序彼此重複地交錯排序，以將輸入電壓Vin轉換為第一級電壓Vfs，亦即，一個充電程序結束後，接著第一放電程序、第二放電程序、第三放電程序輪流執行，再接著執行充電程序，以此類推。It should be noted that the charging process and the first discharging process, the second discharging process, and the third discharging process are repeatedly and staggered in different time periods, instead of being performed at the same time. Among them, the charging process and the above three discharging processes are alternately sequenced repeatedly to convert the input voltage Vin to the first-level voltage Vfs, that is, after one charging process is completed, the first discharging process, the second discharging process, and the first discharging process are followed. The three discharging procedures are executed in turn, and then the charging procedure is executed, and so on.

因此，請參照圖6，其為根據本發明之再一實施例顯示一兩級電源轉換器中之諧振切換式電容轉換器601之電路示意圖。圖6中之通訊界面及控制電路603的配置與圖4類似，故不贅述。本實施例與圖4的不同在於本實施例的充電電感與放電電感可為同一個電感L3，如此之設置可更進一步地減少電感的數量。如圖6所示，本發明之兩級電源轉換器中之諧振切換式電容轉換器601包含電容C1、C2、C3、開關Q1、Q2、Q3、Q4、Q5、Q6、Q7、Q8、Q9、Q10、電感L3。開關Q1-Q3分別與對應之電容C1-C3串聯，而開關Q4與電感L3串聯。應注意者為，本發明之兩級電源轉換器中之諧振切換式電容轉換器中的電容數量並不限於本實施例的三個，亦可為二個或四個以上，本實施例所顯示之元件數量僅用以說明本發明並不用限制本發明。Therefore, please refer to FIG. 6, which is a circuit diagram showing a resonant switched capacitor converter 601 in a two-stage power converter according to another embodiment of the present invention. The configuration of the communication interface and the control circuit 603 in FIG. 6 is similar to that in FIG. 4, so it will not be repeated. The difference between this embodiment and FIG. 4 is that the charging inductance and the discharging inductance of this embodiment can be the same inductance L3, and this arrangement can further reduce the number of inductances. As shown in FIG. 6, the resonant switching capacitor converter 601 in the two-stage power converter of the present invention includes capacitors C1, C2, C3, switches Q1, Q2, Q3, Q4, Q5, Q6, Q7, Q8, Q9, Q10, inductance L3. The switches Q1-Q3 are respectively connected in series with the corresponding capacitors C1-C3, and the switch Q4 is connected in series with the inductor L3. It should be noted that the number of capacitors in the resonant switched capacitor converter in the two-stage power converter of the present invention is not limited to three in this embodiment, and can also be two or more than four, as shown in this embodiment The number of components is only used to illustrate the present invention and does not limit the present invention.

須說明的是，在本實施例中，充電電感與放電電感為單一個相同的電感L3，在放電程序中，藉由開關Q1-Q10的切換，使電容C1-C3彼此並聯後串聯單一個相同電感L3。所謂充電電感與放電電感為單一個相同的電感L3，係指在充電程序與放電程序中，充電諧振電流與放電諧振電流分別僅流經單一個電感L3，而未再流經其他電感元件。於一實施例中，上述單一個相同的電感L3可為可變電感。It should be noted that in this embodiment, the charging inductance and the discharging inductance are the same inductance L3. In the discharging process, the capacitors C1-C3 are connected in parallel and the same in series by switching the switches Q1-Q10. Inductance L3. The so-called charging inductance and discharging inductance are the same inductance L3, which means that in the charging process and the discharging process, the charging resonant current and the discharging resonant current only flow through a single inductor L3, and no other inductance components. In an embodiment, the above-mentioned single identical inductor L3 may be a variable inductor.

如圖6所示，開關Q5之一端耦接至開關Q1與電容C1之間的節點，開關Q6之一端耦接至開關Q2與電容C2之間的節點，而開關Q7之一端耦接至開關Q3與電容C3之間的節點。開關Q8之一端耦接至電容C1與開關Q2之間的節點，開關Q9之一端耦接至電容C2與開關Q3之間的節點，而開關Q10之一端耦接至電容C3與開關Q4之間的節點。如圖6所示，開關Q5-Q7之另一端共同電連接至一節點後，耦接至開關Q4與電感L3之間的節點，開關Q8-Q10之另一端係共同耦接至接地電位。電感L3的另一端係耦接至第一級電壓Vfs，開關Q1之另一端耦接至輸入電壓Vin。As shown in FIG. 6, one end of the switch Q5 is coupled to the node between the switch Q1 and the capacitor C1, one end of the switch Q6 is coupled to the node between the switch Q2 and the capacitor C2, and one end of the switch Q7 is coupled to the switch Q3 The node between and capacitor C3. One end of the switch Q8 is coupled to the node between the capacitor C1 and the switch Q2, one end of the switch Q9 is coupled to the node between the capacitor C2 and the switch Q3, and one end of the switch Q10 is coupled to the node between the capacitor C3 and the switch Q4 node. As shown in FIG. 6, after the other ends of the switches Q5-Q7 are commonly electrically connected to a node, they are coupled to the node between the switch Q4 and the inductor L3, and the other ends of the switches Q8-Q10 are commonly coupled to the ground potential. The other end of the inductor L3 is coupled to the first-stage voltage Vfs, and the other end of the switch Q1 is coupled to the input voltage Vin.

開關Q1-Q10可根據通訊界面及控制電路603所產生之充電操作訊號GA及放電操作訊號GB，切換所對應之電容C1-C3與電感L3之電連接關係。在一充電程序中，根據充電操作訊號GA，開關Q1-Q4係為導通，開關Q5-Q10係為不導通，使得電容C1-C3彼此串聯後與電感L3串聯於輸入電壓Vin與第一級電壓Vfs之間，以形成一充電路徑。在一放電程序中，根據放電操作訊號GB，開關Q5-Q10係導通，開關Q1-Q4係不導通，使電容C1、電容C2及電容C3彼此並聯後串聯電感L3，而形成複數放電路徑。應注意者為，上述充電程序與上述放電程序係於不同的時間段重複地交錯進行，而非同時進行。其中，充電程序與放電程序彼此重複地交錯排序，以將輸入電壓Vin轉換為第一級電壓Vfs。於本實施例中，每個第一電容C1、C2、C3的直流偏壓均為Vo，故本實施例中的第一電容C1、C2、C3需要耐較低的額定電壓，故可使用較小體積的電容器。The switches Q1-Q10 can switch the electrical connection relationship between the corresponding capacitors C1-C3 and the inductor L3 according to the charging operation signal GA and the discharging operation signal GB generated by the communication interface and the control circuit 603. In a charging procedure, according to the charging operation signal GA, the switches Q1-Q4 are turned on, and the switches Q5-Q10 are not turned on, so that the capacitors C1-C3 are connected in series with each other and then connected with the inductor L3 in series with the input voltage Vin and the first-stage voltage Between Vfs to form a charging path. In a discharge process, according to the discharge operation signal GB, the switches Q5-Q10 are turned on, and the switches Q1-Q4 are not turned on. The capacitor C1, the capacitor C2, and the capacitor C3 are connected in parallel and the inductor L3 is connected in series to form a plurality of discharge paths. It should be noted that the above-mentioned charging process and the above-mentioned discharging process are repeatedly and staggered at different time periods, rather than being performed at the same time. Wherein, the charging process and the discharging process are alternately sequenced repeatedly to convert the input voltage Vin into the first-level voltage Vfs. In this embodiment, the DC bias voltage of each of the first capacitors C1, C2, C3 is Vo. Therefore, the first capacitors C1, C2, C3 in this embodiment need to withstand lower rated voltages, so they can be used. Small size capacitor.

於一實施例中，通訊界面及控制電路603於放電程序結束後調節一延遲時間，且於延遲時間結束時點，起始充電程序，並於延遲時間中，保持複數開關Q1-Q10不導通。於一實施例中，通訊界面及控制電路603於充電程序結束後調節一延遲時間，且於延遲時間結束時點，起始放電程序，並於延遲時間中，保持複數開關Q1-Q10不導通。於一實施例中，上述延遲時間係可予以調整，以調整諧振切換式電容轉換器601之諧振頻率。於一實施例中，上述延遲時間係可予以調整，以調整諧振切換式電容轉換器601之輸入電壓Vin及第一級電壓Vfs的比例。In one embodiment, the communication interface and the control circuit 603 adjust a delay time after the discharge process ends, and at the end of the delay time, the charging process is initiated, and the plurality of switches Q1-Q10 are kept non-conducting during the delay time. In one embodiment, the communication interface and the control circuit 603 adjust a delay time after the charging process ends, and at the end of the delay time, the discharging process is initiated, and during the delay time, the plurality of switches Q1-Q10 are kept non-conducting. In one embodiment, the aforementioned delay time can be adjusted to adjust the resonant frequency of the resonant switched capacitor converter 601. In one embodiment, the aforementioned delay time can be adjusted to adjust the ratio between the input voltage Vin of the resonant switched capacitor converter 601 and the first stage voltage Vfs.

在充電電感與放電電感設置為單一個相同的電感L1的本實施例中，可適當配置上述充電程序的持續時間(Ton1)及放電程序的持續時間(Ton2)的比例，可達到柔性切換之零電流切換。具體而言，於一實施例中，上述充電程序的持續時間例如大致上等於百分之二十五之工作週期；藉此，開關可於流經開關的電流在其正半波相對較低位準的時點切換，以達成柔性切換。在一種較佳的實施例中，可達到零電流切換(zero current switch, ZCS)。於一實施例中，上述充電程序的持續時間小於特定比例之工作週期一段預設期間，例如小於百分之二十五之工作週期一段預設期間；藉此提前不導通開關Q1-Q4後仍維持有微小的電流，流經充電電感L1，因此，即可將開關Q10中，儲存於其中之寄生電容的累積電荷通過開關Q4之寄生二極體帶走，而降低開關Q10的跨壓，以達到柔性切換。在一種較佳的實施例中，調整預設期間，而達到零電壓切換(zero voltage switch，ZVS)。In this embodiment where the charging inductance and the discharging inductance are set to a single same inductance L1, the ratio of the duration of the charging procedure (Ton1) and the duration of the discharging procedure (Ton2) can be appropriately configured to achieve zero flexible switching. Current switching. Specifically, in one embodiment, the duration of the above-mentioned charging procedure is, for example, approximately equal to 25% of the duty cycle; thereby, the switch can be used when the current flowing through the switch is relatively low in its positive half-wave. Switch on time to achieve flexible switching. In a preferred embodiment, zero current switch (ZCS) can be achieved. In one embodiment, the duration of the charging process is less than a specific ratio of the duty cycle for a predetermined period, for example, less than 25% of the duty cycle for a preset period; thereby, the switch Q1-Q4 is not turned on in advance. A small current is maintained and flows through the charging inductor L1. Therefore, the accumulated charge of the parasitic capacitance stored in the switch Q10 can be taken away through the parasitic diode of the switch Q4, and the cross voltage of the switch Q10 can be reduced. Achieve flexible switching. In a preferred embodiment, the preset period is adjusted to achieve zero voltage switch (ZVS).

於一實施例中，相對地，上述放電程序的持續時間大於特定比例之工作週期一段預設期間，例如大於百分之七十五之工作週期一段預設期間；藉此，延後不導通開關Q5-Q10後放電電感L2的負電流會通過開關Q5的寄生二極體而對開關Q1的寄生電容進行充電，而降低開關Q1的跨壓，以達到柔性切換。在一種較佳的實施例中，調整預設期間，而達到零電壓切換(zero voltage switch，ZVS)。In one embodiment, relatively, the duration of the above-mentioned discharge process is greater than a specific proportion of the duty cycle for a predetermined period, for example, a duty cycle greater than 75% for a predetermined period; thereby, the non-conduction switch is delayed. After Q5-Q10, the negative current of the discharge inductor L2 will charge the parasitic capacitance of the switch Q1 through the parasitic diode of the switch Q5, and reduce the cross voltage of the switch Q1 to achieve flexible switching. In a preferred embodiment, the preset period is adjusted to achieve zero voltage switch (ZVS).

於一實施例中，上述諧振切換式電容轉換器601可為雙向諧振切換式電容轉換器。於一實施例中，上述諧振切換式電容轉換器601之輸入電壓Vin與第一級電壓Vfs之電壓轉換比率可為4:1、3:1或2:1。於一實施例中，諧振切換式電容轉換器601之電壓轉換比率可彈性地加以調整，例如於充電程序與放電程序中，藉由選擇將開關Q7保持導通，並選擇將開關Q10及Q4保持不導通，則可將諧振切換式電容轉換器601之電壓轉換比率調整為3:1。同樣地，例如可選擇將開關Q6保持導通，並選擇將開關Q9、Q3、Q7、Q10及Q4保持不導通，則可將諧振切換式電容轉換器601之電壓轉換比率調整為2:1。In one embodiment, the above-mentioned resonant switched capacitor converter 601 may be a bidirectional resonant switched capacitor converter. In one embodiment, the voltage conversion ratio between the input voltage Vin of the resonant switched capacitor converter 601 and the first-stage voltage Vfs may be 4:1, 3:1, or 2:1. In one embodiment, the voltage conversion ratio of the resonant switched capacitor converter 601 can be flexibly adjusted. For example, in the charging process and the discharging process, the switch Q7 is selected to be kept on, and the switches Q10 and Q4 are selected to be kept off. Turning on, the voltage conversion ratio of the resonant switched capacitor converter 601 can be adjusted to 3:1. Similarly, for example, the switch Q6 can be selected to be kept on, and the switches Q9, Q3, Q7, Q10, and Q4 can be selected to be kept non-conductive, then the voltage conversion ratio of the resonant switching capacitor converter 601 can be adjusted to 2:1.

再請參照圖7，其係根據本發明之再一實施例顯示一兩級電源轉換器中之諧振切換式電容轉換器701之電路示意圖。圖7中之通訊界面及控制電路703與圖4類似，故不贅述。如圖7所示，本發明之兩級電源轉換器中之諧振切換式電容轉換器701包含電容C1、C2、C3、開關Q1、Q2、Q3、Q4、Q5、Q6、Q7、Q8、Q9、Q10、電感L1、L2、L3。開關Q1-Q3分別與對應之電容C1-C3串聯，而電容C1-C3分別與對應之電感L1-L3串聯。應注意者為，本發明之兩級電源轉換器中之諧振切換式電容轉換器中的電容數量並不限於本實施例的三個，亦可為二個或四個以上，且電感數量亦不限於本實施例的三個，亦可為二個或四個以上，本實施例所顯示之元件數量僅用以說明本發明並不用限制本發明。Please refer to FIG. 7 again, which is a circuit diagram of a resonant switched capacitor converter 701 in a two-stage power converter according to another embodiment of the present invention. The communication interface and control circuit 703 in FIG. 7 are similar to those in FIG. 4, so they will not be described in detail. As shown in FIG. 7, the resonant switching capacitor converter 701 in the two-stage power converter of the present invention includes capacitors C1, C2, C3, switches Q1, Q2, Q3, Q4, Q5, Q6, Q7, Q8, Q9, Q10, inductors L1, L2, and L3. The switches Q1-Q3 are connected in series with the corresponding capacitors C1-C3, and the capacitors C1-C3 are connected in series with the corresponding inductors L1-L3, respectively. It should be noted that the number of capacitors in the resonant switched capacitor converter in the two-stage power converter of the present invention is not limited to three in this embodiment, and it can also be two or more than four, and the number of inductances is also different. It is limited to three in this embodiment, and it can also be two or more than four. The number of components shown in this embodiment is only used to illustrate the present invention and does not limit the present invention.

如圖7所示，開關Q5之一端耦接至開關Q1與電容C1之間的節點，開關Q6之一端耦接至開關Q2與電容C2之間的節點，而開關Q7之一端耦接至開關Q3與電容C3之間的節點。開關Q8之一端耦接至電感L1與開關Q2之間的節點，開關Q9之一端耦接至電感L2與開關Q3之間的節點，而開關Q10之一端耦接至電感L3與開關Q4之間的節點。如圖7所示，開關Q5-Q7之另一端則共同耦接至第一級電壓Vfs。開關Q8-Q10之另一端係共同耦接至接地電位。開關Q4耦接於電感L3與第一級電壓Vfs之間，開關Q1之一端耦接至輸入電壓Vin。As shown in FIG. 7, one end of the switch Q5 is coupled to the node between the switch Q1 and the capacitor C1, one end of the switch Q6 is coupled to the node between the switch Q2 and the capacitor C2, and one end of the switch Q7 is coupled to the switch Q3 The node between and capacitor C3. One end of the switch Q8 is coupled to the node between the inductor L1 and the switch Q2, one end of the switch Q9 is coupled to the node between the inductor L2 and the switch Q3, and one end of the switch Q10 is coupled to the node between the inductor L3 and the switch Q4 node. As shown in FIG. 7, the other ends of the switches Q5-Q7 are commonly coupled to the first-stage voltage Vfs. The other ends of the switches Q8-Q10 are commonly coupled to the ground potential. The switch Q4 is coupled between the inductor L3 and the first-stage voltage Vfs, and one end of the switch Q1 is coupled to the input voltage Vin.

開關Q1-Q10可根據通訊界面及控制電路703所產生之充電操作訊號GA及放電操作訊號GB，切換所對應之電容C1-C3與電感L1-L3之電連接關係。在一充電程序中，開關Q1-Q4係為導通，開關Q5-Q10係為不導通，使得電容C1-C3與電感L1-L3彼此串聯於輸入電壓Vin與第一級電壓Vfs之間，以形成一充電路徑。在一放電程序中，開關Q5-Q10係導通，開關Q1-Q4係不導通，使電容C1與對應之電感L1串聯於第一級電壓Vfs與接地電位間，電容C2與對應之電感L2串聯於第一級電壓Vfs與接地電位間，電容C3與對應之電感L3串聯於第一級電壓Vfs與接地電位間，而形成複數放電路徑。The switches Q1-Q10 can switch the electrical connection relationship between the corresponding capacitors C1-C3 and the inductors L1-L3 according to the charging operation signal GA and the discharging operation signal GB generated by the communication interface and the control circuit 703. In a charging process, the switches Q1-Q4 are turned on, and the switches Q5-Q10 are not turned on, so that the capacitors C1-C3 and the inductors L1-L3 are connected in series between the input voltage Vin and the first-stage voltage Vfs to form A charging path. In a discharge procedure, the switches Q5-Q10 are turned on, and the switches Q1-Q4 are not turned on, so that the capacitor C1 and the corresponding inductance L1 are connected in series between the first-stage voltage Vfs and the ground potential, and the capacitor C2 and the corresponding inductance L2 are connected in series Between the first-level voltage Vfs and the ground potential, the capacitor C3 and the corresponding inductance L3 are connected in series between the first-level voltage Vfs and the ground potential to form a plurality of discharge paths.

於一實施例中，通訊界面及控制電路703於放電程序結束後調節一延遲時間，且於延遲時間結束時點，起始充電程序，並於延遲時間中，保持複數開關Q1-Q10不導通。於一實施例中，通訊界面及控制電路703於充電程序結束後調節一延遲時間，且於延遲時間結束時點，起始放電程序，並於延遲時間中，保持複數開關Q1-Q10不導通。於一實施例中，上述延遲時間係可予以調整，以調整諧振切換式電容轉換器701之諧振頻率。於一實施例中，上述延遲時間係可予以調整，以調整諧振切換式電容轉換器701之輸入電壓Vin及第一級電壓Vfs的比例。In one embodiment, the communication interface and the control circuit 703 adjust a delay time after the discharge process ends, and at the end of the delay time, start the charging process, and keep the plurality of switches Q1-Q10 non-conducting during the delay time. In one embodiment, the communication interface and control circuit 703 adjust a delay time after the end of the charging process, and at the end of the delay time, start the discharge process, and keep the plurality of switches Q1-Q10 non-conducting during the delay time. In one embodiment, the aforementioned delay time can be adjusted to adjust the resonant frequency of the resonant switched capacitor converter 701. In one embodiment, the aforementioned delay time can be adjusted to adjust the ratio between the input voltage Vin of the resonant switched capacitor converter 701 and the first stage voltage Vfs.

應注意者為，上述充電程序與上述放電程序係於不同的時間段交錯進行，而非同時進行。其中，充電程序與放電程序彼此重複地交錯排序，以將輸入電壓Vin轉換為第一級電壓Vfs。於本實施例中，每個電容C1、C2、C3的直流偏壓均為Vo，故本實施例中的電容C1、C2、C3需要耐較低的額定電壓，故可使用較小體積的電容器。It should be noted that the above-mentioned charging process and the above-mentioned discharging process are staggered in different time periods, rather than being carried out at the same time. Wherein, the charging process and the discharging process are alternately sequenced repeatedly to convert the input voltage Vin into the first-level voltage Vfs. In this embodiment, the DC bias voltage of each capacitor C1, C2, C3 is Vo. Therefore, the capacitors C1, C2, C3 in this embodiment need to withstand lower rated voltages, so smaller capacitors can be used .

於一實施例中，上述充電程序的持續時間大致上為特定比例之工作週期(duty cycle)，例如但不限於大致上為百分之五十之工作週期；藉此，開關可於流經開關的電流在其正半波相對較低位準的時點切換，以達成柔性切換。在一種較佳的實施例中，可達到零電流切換(zero current switch, ZCS)。In one embodiment, the duration of the charging process is substantially a duty cycle of a specific proportion, such as but not limited to a duty cycle of substantially 50%; thereby, the switch can flow through the switch The current is switched at the relatively low level of its positive half-wave to achieve flexible switching. In a preferred embodiment, zero current switch (ZCS) can be achieved.

於一實施例中，上述特定比例係與諧振頻率相關。於一實施例中，上述充電程序具有一充電諧振頻率，上述放電程序具有一放電諧振頻率。於一較佳實施例中，上述充電諧振頻率與上述放電諧振頻率相同。於一實施例中，上述充電諧振頻率與上述放電諧振頻率不同。In one embodiment, the aforementioned specific ratio is related to the resonance frequency. In one embodiment, the charging process has a resonant frequency of charging, and the discharging process has a resonant frequency of discharging. In a preferred embodiment, the charging resonance frequency is the same as the discharging resonance frequency. In one embodiment, the resonant frequency of charging is different from the resonant frequency of discharging.

圖8A係根據本發明之一實施例顯示兩級電源轉換器中之諧振切換式電容轉換器之一充電程序與放電程序之對應之操作訊號與對應之電感電流之訊號波形示意圖。請同時參閱圖4，圖8A所示的實施例中，開關Q1~Q4之充電操作訊號GA於充電程序時為高位準，而開關Q5~Q10之放電操作訊號GB於放電程序時為高位準。於圖8A之實施例中，充電程序的持續時間大致上為百分之五十之工作週期；藉此，開關Q1可於流經開關的電流在其正半波相對較低位準的時點切換，也是在充電電感L1之充電電感電流IL1為零電流時切換，以達成柔性切換。在一種較佳的實施例中，可達到零電流切換。FIG. 8A is a schematic diagram showing the corresponding operation signal and the signal waveform of the corresponding inductor current of a charging process and a discharging process of a resonant switched capacitor converter in a two-stage power converter according to an embodiment of the present invention. Please refer to FIG. 4 at the same time. In the embodiment shown in FIG. 8A, the charging operation signal GA of the switches Q1 to Q4 is at a high level during the charging process, and the discharging operation signal GB of the switches Q5 to Q10 is at a high level during the discharging process. In the embodiment of FIG. 8A, the duration of the charging process is approximately 50% of the duty cycle; thereby, the switch Q1 can be switched at the time when the current flowing through the switch is at a relatively low level of the positive half wave It is also switched when the charging inductor current IL1 of the charging inductor L1 is zero current to achieve flexible switching. In a preferred embodiment, zero current switching can be achieved.

圖8B及8C係根據本發明之另一實施例顯示兩級電源轉換器中之諧振切換式電容轉換器之一充電程序與放電程序之對應之操作訊號與對應之電感電流之訊號波形示意圖。請同時參閱圖4，圖8B所示的實施例中，開關Q1~Q4之充電操作訊號GA於充電程序時為高位準，而開關Q5~Q10之放電操作訊號GB於放電程序時為高位準。於圖8B之實施例中，可使充電程序的持續時間大致上為小於百分之五十之工作週期一段預設期間T1；藉此，提前不導通開關Q1-Q4後仍維持有微小的電流流經充電電感L1，因此，即可將開關Q10中，儲存於其中之寄生電容的累積電荷透過開關Q4之寄生二極體放電，而降低開關Q10的跨壓，以達到柔性切換。在一種較佳的實施例中，調整預設期間T1，而達到零電壓切換。請同時參閱圖4，圖8C所示的實施例中，開關Q1~Q4之充電操作訊號GA於充電程序時為高位準，開關Q5~Q10之放電操作訊號GB於放電程序時為高位準。於圖8C之實施例中，可使放電程序的持續時間大致上為大於百分之五十之工作週期一段預設期間T2；藉此，延後不導通開關Q5-Q10後放電電感L2的負電流會通過開關Q5的寄生二極體而對開關Q1的寄生電容進行充電，而降低開關Q1的跨壓，以達到柔性切換。在一種較佳的實施例中，調整預設期間T2，而達到零電壓切換。於一實施例中，應注意者為，圖8B及8C之實施例可一起實施或僅實施其中一者。此外，請參照圖8D，其係根據本發明之另一實施例顯示兩級電源轉換器中之諧振切換式電容轉換器之一充電程序與放電程序之對應之操作訊號與對應之電容電流之訊號波形示意圖。請同時參照圖4，如圖8D所示，可調整充電程序的持續時間及/或放電程序的持續時間例如加入延遲時間Td，而更具彈性地調整輸入電壓Vin與第一級電壓Vfs的比例且可藉此調整諧振頻率。8B and 8C are schematic diagrams showing the corresponding operation signals of a charging process and a discharging process of a resonant switched capacitor converter in a two-stage power converter and the corresponding signal waveforms of the inductor current according to another embodiment of the present invention. Please refer to FIG. 4 at the same time. In the embodiment shown in FIG. 8B, the charging operation signal GA of the switches Q1 to Q4 is at a high level during the charging process, and the discharging operation signal GB of the switches Q5 to Q10 is at a high level during the discharging process. In the embodiment of FIG. 8B, the duration of the charging process can be substantially less than 50% of the duty cycle for a predetermined period T1; thereby, a small current is maintained after the switches Q1-Q4 are not turned on in advance. Flowing through the charging inductor L1, therefore, the accumulated charge of the parasitic capacitance stored in the switch Q10 can be discharged through the parasitic diode of the switch Q4, and the cross voltage of the switch Q10 is reduced to achieve flexible switching. In a preferred embodiment, the preset period T1 is adjusted to achieve zero voltage switching. Please refer to FIG. 4 at the same time. In the embodiment shown in FIG. 8C, the charging operation signal GA of the switches Q1~Q4 is at a high level during the charging process, and the discharging operation signal GB of the switches Q5~Q10 is at a high level during the discharging process. In the embodiment of FIG. 8C, the duration of the discharge process can be substantially greater than 50% of the duty cycle for a predetermined period T2; thereby, the negative of the discharge inductance L2 after the non-conducting switch Q5-Q10 is delayed The current will charge the parasitic capacitance of the switch Q1 through the parasitic diode of the switch Q5, and reduce the cross voltage of the switch Q1 to achieve flexible switching. In a preferred embodiment, the preset period T2 is adjusted to achieve zero voltage switching. In one embodiment, it should be noted that the embodiments of FIGS. 8B and 8C can be implemented together or only one of them can be implemented. In addition, please refer to FIG. 8D, which shows the corresponding operation signal and the corresponding capacitance current signal of one of the charging and discharging procedures of the resonant switching capacitor converter in the two-stage power converter according to another embodiment of the present invention. Schematic diagram of the waveform. Please refer to FIG. 4 at the same time, as shown in FIG. 8D, the duration of the charging process and/or the duration of the discharging process can be adjusted, such as adding a delay time Td, and the ratio of the input voltage Vin to the first-stage voltage Vfs can be adjusted more flexibly And can adjust the resonance frequency.

本發明如上所述提供了一種兩級電源轉換器，其藉由特殊的電路設計可調整延遲時間、可調整諧振切換式電容轉換器之諧振頻率及電壓調節器之切換頻率、可降低諧振切換式電容轉換器之諧振頻率及電壓調節器之切換頻率以改善低負載時的效率、可同步諧振切換式電容轉換器之諧振頻率與電壓調節器之切換頻率以改善電磁干擾過濾的效能、可使諧振切換式電容轉換器達到具有零電流切換(ZCS)或零電壓切換(ZVS)的柔性切換以用於高電源效率、可藉由設定開關而更具彈性地調變諧振切換式電容轉換器之電壓轉換比率、可使諧振切換式電容轉換器之所有諧振電容具有相同的額定電流及額定電壓而能夠使用較小體積的電容且可降低諧振切換式電容轉換器之電壓應力。As mentioned above, the present invention provides a two-stage power converter, which can adjust the delay time, adjust the resonant frequency of the resonant switched capacitor converter and the switching frequency of the voltage regulator through a special circuit design, and can reduce the resonant switching type The resonant frequency of the capacitor converter and the switching frequency of the voltage regulator are used to improve the efficiency at low loads, and the resonant frequency of the switched capacitor converter can be synchronized with the switching frequency of the voltage regulator to improve the efficiency of electromagnetic interference filtering and make resonance The switched capacitor converter achieves flexible switching with zero current switching (ZCS) or zero voltage switching (ZVS) for high power efficiency, and the voltage of the resonant switched capacitor converter can be adjusted more flexibly by setting the switch The conversion ratio can make all the resonant capacitors of the resonant switched capacitor converter have the same rated current and rated voltage, so that smaller capacitors can be used and the voltage stress of the resonant switched capacitor converter can be reduced.

需說明的是，前述實施例中提到的「高位準」與「低位準」僅為舉例，並非用以限制本發明之範疇，在其他實施例中，前述的「高位準」與「低位準」，在前述符合本發明相同的精神下，可依實際所採用的開關型態與邏輯基礎，而適應性地至少部分調整或交換。It should be noted that the "high level" and "low level" mentioned in the foregoing embodiments are only examples, and are not intended to limit the scope of the present invention. In other embodiments, the aforementioned "high level" and "low level" "Under the same spirit of the present invention described above, it can be adjusted or exchanged adaptively at least in part according to the actual switch type and logic basis used.

以上已針對較佳實施例來說明本發明，唯以上所述者，僅係為使熟悉本技術者易於了解本發明的內容而已，並非用來限定本發明之最廣的權利範圍。所說明之各個實施例，並不限於單獨應用，亦可以組合應用，舉例而言，兩個或以上之實施例可以組合運用，而一實施例中之部分組成亦可用以取代另一實施例中對應之組成部件。此外，在本發明之相同精神下，熟悉本技術者可以思及各種等效變化以及各種組合，舉例而言，本發明所稱「根據某訊號進行處理或運算或產生某輸出結果」，不限於根據該訊號的本身，亦包含於必要時，將該訊號進行電壓電流轉換、電流電壓轉換、及／或比例轉換等，之後根據轉換後的訊號進行處理或運算產生某輸出結果。由此可知，在本發明之相同精神下，熟悉本技術者可以思及各種等效變化以及各種組合，其組合方式甚多，在此不一一列舉說明。因此，本發明的範圍應涵蓋上述及其他所有等效變化。The present invention has been described above with respect to preferred embodiments, but the above description is only for making it easier for those skilled in the art to understand the content of the present invention, and is not intended to limit the broadest scope of rights of the present invention. The illustrated embodiments are not limited to individual applications, but can also be combined. For example, two or more embodiments can be used in combination, and part of the composition in one embodiment can also be used to replace another embodiment. Corresponding components. In addition, under the same spirit of the present invention, those skilled in the art can think of various equivalent changes and various combinations. For example, the “processing or calculation based on a certain signal or generating a certain output result” in the present invention is not limited to According to the signal itself, it also includes performing voltage-current conversion, current-voltage conversion, and/or ratio conversion on the signal when necessary, and then process or calculate an output result according to the converted signal. It can be seen from this that under the same spirit of the present invention, those skilled in the art can think of various equivalent changes and various combinations, and there are many combinations of them, which will not be listed here. Therefore, the scope of the present invention should cover all the above and other equivalent changes.

20,30:兩級電源轉換器 201,301,401,501,601,701:諧振切換式電容轉換器 202,302:電壓調節器 203,303,403,503,603,703:通訊界面及控制電路 204,304:中央處理單元/圖形處理單元/記憶單元 305:電源供應單元 C1~C3,C1(CR),C2(CF),C3(CR):電容 Co:輸出電容 GA:充電操作訊號 GB,GB1,GB2,GB3:放電操作訊號 Ic1:電容電流 IL1:充電電感電流 IL2:放電電感電流 L1:(充電)電感 L2:(放電)電感 L1(LR),L2(LR),L3:電感 Q1~Q10,Q1(S1A),Q2(S2A),Q3(S1B),Q4(S2B),Q5(S1A),Q6(S2A),Q7(S2A),Q8(S1B),Q9(S1B),Q10(S2B):開關 RL:負載電阻 T1,T2,T3:期間 Vc1:電容C1直流偏壓 Vc2:電容C2直流偏壓 Vc3:電容C3直流偏壓 Vin:輸入電壓 Vfs:第一級電壓 Vout:輸出電壓20, 30: Two-stage power converter 201, 301, 401, 501, 601, 701: resonant switched capacitor converter 202, 302: voltage regulator 203,303,403,503,603,703: communication interface and control circuit 204, 304: central processing unit/graphics processing unit/memory unit 305: power supply unit C1~C3, C1(CR), C2(CF), C3(CR): capacitance Co: output capacitance GA: Charging operation signal GB, GB1, GB2, GB3: Discharge operation signal Ic1: Capacitance current IL1: Charging inductor current IL2: discharge inductor current L1: (charging) inductance L2: (discharge) inductance L1(LR), L2(LR), L3: inductance Q1~Q10, Q1(S1A), Q2(S2A), Q3(S1B), Q4(S2B), Q5(S1A), Q6(S2A), Q7(S2A), Q8(S1B), Q9(S1B), Q10 (S2B): Switch RL: load resistance T1, T2, T3: period Vc1: Capacitor C1 DC bias Vc2: Capacitor C2 DC bias Vc3: Capacitor C3 DC bias Vin: input voltage Vfs: first level voltage Vout: output voltage

圖1係為習知的電源轉換器。Figure 1 is a conventional power converter.

圖2係根據本發明之一實施例顯示一兩級電源轉換器之方塊示意圖。Fig. 2 is a block diagram showing a two-stage power converter according to an embodiment of the present invention.

圖3係根據本發明之另一實施例顯示一兩級電源轉換器之方塊示意圖。FIG. 3 is a block diagram showing a two-stage power converter according to another embodiment of the present invention.

圖4係根據本發明之一實施例顯示一兩級電源轉換器中之諧振切換式電容轉換器之電路示意圖。FIG. 4 is a circuit diagram of a resonant switched capacitor converter in a two-stage power converter according to an embodiment of the present invention.

圖5係根據本發明之另一實施例顯示一兩級電源轉換器中之諧振切換式電容轉換器之電路示意圖。FIG. 5 is a schematic circuit diagram showing a resonant switched capacitor converter in a two-stage power converter according to another embodiment of the present invention.

圖6係根據本發明之又一實施例顯示一兩級電源轉換器中之諧振切換式電容轉換器之電路示意圖。FIG. 6 is a schematic circuit diagram showing a resonant switched capacitor converter in a two-stage power converter according to another embodiment of the present invention.

圖7係根據本發明之再一實施例顯示一兩級電源轉換器中之諧振切換式電容轉換器之電路示意圖。FIG. 7 is a schematic circuit diagram showing a resonant switched capacitor converter in a two-stage power converter according to another embodiment of the present invention.

圖8A、8B及8C係根據本發明之一實施例顯示兩級電源轉換器中之諧振切換式電容轉換器之一充電程序與放電程序之對應之操作訊號與對應之電感電流之訊號波形示意圖。8A, 8B, and 8C are schematic diagrams showing the corresponding operation signals of a charging process and a discharging process of a resonant switched capacitor converter in a two-stage power converter and the corresponding signal waveforms of the inductor current according to an embodiment of the present invention.

圖8D係根據本發明之一實施例顯示兩級電源轉換器中之諧振切換式電容轉換器之一充電程序與放電程序之對應之操作訊號與對應之電容電流之訊號波形示意圖。FIG. 8D is a schematic diagram showing the corresponding operation signal and the signal waveform of the corresponding capacitor current of a charging process and a discharging process of a resonant switched capacitor converter in a two-stage power converter according to an embodiment of the present invention.

20:兩級電源轉換器 20: Two-stage power converter

201:諧振切換式電容轉換器 201: Resonant switched capacitor converter

202:電壓調節器 202: Voltage Regulator

203:通訊界面及控制電路 203: Communication interface and control circuit

204:中央處理單元/圖形處理單元/記憶單元 204: Central Processing Unit/Graphics Processing Unit/Memory Unit

Vin:輸入電壓 Vin: input voltage

Vfs:第一級電壓 Vfs: first level voltage

Vout:輸出電壓 Vout: output voltage

Claims (14)

一種兩級電源轉換器，用以將一輸入電壓轉換為一輸出電壓，包含： 一諧振切換式電容轉換器(resonant switched-capacitor converter, RSCC)，用以接收該輸入電壓，而產生一第一級電壓； 一電壓調節器，用以接收該第一級電壓，而產生該輸出電壓；以及 一通訊界面及控制電路，用以產生一充電操作訊號、至少一放電操作訊號與一切換訊號，其中該充電操作訊號與該至少一放電操作訊號用以控制該RSCC，且該切換訊號用以控制該電壓調節器，以同步該RSCC之一諧振頻率與該電壓調節器之一切換頻率； 其中該RSCC包含： 複數電容； 複數開關，與該複數電容對應耦接，每一該開關根據所對應之該充電操作訊號或該放電操作訊號，以切換所對應之該電容之電連接關係； 至少一充電電感，與該複數電容中之至少其中之一對應串聯；以及 至少一放電電感，與該複數電容中之至少其中之一對應串聯； 其中，該充電操作訊號與該至少一放電操作訊號，分別各自切換至一導通位準一段導通期間，且該複數段導通期間彼此不重疊，以使一充電程序與至少一放電程序彼此不重疊； 其中，在該充電程序中，藉由該充電操作訊號控制該複數開關的切換，使該複數電容與該至少一充電電感彼此串聯於該輸入電壓與該第一級電壓之間，以形成一充電路徑； 其中，在該至少一放電程序中，藉由該至少一放電操作訊號控制該複數開關的切換，使每一該電容與對應之該放電電感串聯於該第一級電壓與一接地電位間，以同時形成或輪流形成複數放電路徑； 其中，該充電程序與該至少一放電程序彼此重複地交錯排序，以將該輸入電壓轉換為該第一級電壓； 其中該通訊界面及控制電路於該至少一放電程序結束後調節一延遲時間，且於該延遲時間結束時點，起始該充電程序，並於該延遲時間中，保持該複數開關不導通。 A two-stage power converter for converting an input voltage into an output voltage, including: A resonant switched-capacitor converter (RSCC) for receiving the input voltage to generate a first-level voltage; A voltage regulator for receiving the first-stage voltage and generating the output voltage; and A communication interface and a control circuit for generating a charging operation signal, at least one discharging operation signal and a switching signal, wherein the charging operation signal and the at least one discharging operation signal are used to control the RSCC, and the switching signal is used to control The voltage regulator to synchronize a resonant frequency of the RSCC with a switching frequency of the voltage regulator; The RSCC contains: Complex capacitance A plurality of switches are correspondingly coupled to the plurality of capacitors, and each of the switches switches the electrical connection relationship of the corresponding capacitors according to the corresponding charging operation signal or the discharging operation signal; At least one charging inductor in series with at least one of the plurality of capacitors; and At least one discharge inductor in series with at least one of the plurality of capacitors; Wherein, the charging operation signal and the at least one discharging operation signal are respectively switched to a conduction level for a conduction period, and the plurality of conduction periods do not overlap with each other, so that a charging process and at least one discharging process do not overlap with each other; Wherein, in the charging procedure, the switching of the plurality of switches is controlled by the charging operation signal, so that the plurality of capacitors and the at least one charging inductor are connected in series between the input voltage and the first-stage voltage to form a charging path; Wherein, in the at least one discharge procedure, the switching of the plurality of switches is controlled by the at least one discharge operation signal, so that each of the capacitors and the corresponding discharge inductance are connected in series between the first-level voltage and a ground potential to Simultaneously or alternately form multiple discharge paths; Wherein, the charging procedure and the at least one discharging procedure are alternately sequenced repeatedly to convert the input voltage into the first-level voltage; The communication interface and the control circuit adjust a delay time after the at least one discharge process ends, and at the end of the delay time, start the charging process, and keep the plurality of switches non-conducting during the delay time. 如請求項1所述之兩級電源轉換器，其中該通訊界面及控制電路調整該延遲時間，以調整該RSCC之該諧振頻率。The two-stage power converter according to claim 1, wherein the communication interface and the control circuit adjust the delay time to adjust the resonance frequency of the RSCC. 如請求項1所述之兩級電源轉換器，更包含一電源供應單元，用以提供該輸入電壓。The two-stage power converter according to claim 1 further includes a power supply unit for providing the input voltage. 如請求項1所述之兩級電源轉換器，其中該輸出電壓用以供應電源予一中央處理單元(center processing unit, CPU)、一圖形處理單元(graphic processing unit, GPU)或一記憶單元，且該通訊界面及控制電路調整該充電操作訊號、該至少一放電操作訊號與該切換訊號，以調節該輸入電壓與該第一級電壓之比例。The two-stage power converter according to claim 1, wherein the output voltage is used to supply power to a central processing unit (CPU), a graphics processing unit (GPU) or a memory unit, And the communication interface and the control circuit adjust the charging operation signal, the at least one discharging operation signal and the switching signal to adjust the ratio of the input voltage to the first level voltage. 如請求項1所述之兩級電源轉換器，其中該至少一充電電感為單一個充電電感，該至少一放電電感為單一個放電電感。The two-stage power converter according to claim 1, wherein the at least one charging inductor is a single charging inductor, and the at least one discharging inductor is a single discharge inductor. 如請求項5所述之兩級電源轉換器，其中該單一個充電電感之電感值相等於該單一個放電電感之電感值。The two-stage power converter according to claim 5, wherein the inductance value of the single charging inductor is equal to the inductance value of the single discharging inductor. 如請求項1所述之兩級電源轉換器，其中該至少一充電電感與該至少一放電電感為單一個相同電感。The two-stage power converter according to claim 1, wherein the at least one charging inductor and the at least one discharging inductor are a single same inductor. 如請求項7所述之兩級電源轉換器，其中該單一個相同電感為可變電感。The two-stage power converter according to claim 7, wherein the single identical inductor is a variable inductor. 如請求項1或5所述之兩級電源轉換器，其中該充電程序具有一充電諧振頻率，且該至少一放電程序具有一放電諧振頻率，且該充電諧振頻率與該放電諧振頻率相同。The two-stage power converter according to claim 1 or 5, wherein the charging procedure has a charging resonance frequency, and the at least one discharging procedure has a discharging resonance frequency, and the charging resonance frequency is the same as the discharging resonance frequency. 如請求項1、5、6或7所述之兩級電源轉換器，其中該充電程序具有一充電諧振頻率，且該至少一放電程序具有一放電諧振頻率，且該充電諧振頻率與該放電諧振頻率不同。The two-stage power converter according to claim 1, 5, 6, or 7, wherein the charging procedure has a charging resonance frequency, and the at least one discharging procedure has a discharge resonance frequency, and the charging resonance frequency is in resonance with the discharge resonance frequency The frequency is different. 如請求項1所述之兩級電源轉換器，其中調整該充電程序的持續時間，以達到柔性切換(soft switching)之零電壓切換。The two-stage power converter according to claim 1, wherein the duration of the charging procedure is adjusted to achieve soft switching (zero voltage switching). 如請求項1所述之兩級電源轉換器，其中調整該至少一放電程序的持續時間，以達到柔性切換(soft switching)之零電壓切換。The two-stage power converter according to claim 1, wherein the duration of the at least one discharge process is adjusted to achieve zero voltage switching of soft switching. 如請求項1、5、6或7所述之兩級電源轉換器，其中該諧振切換式電容轉換器為雙向諧振切換式電容轉換器。The two-stage power converter according to claim 1, 5, 6, or 7, wherein the resonant switched capacitor converter is a bidirectional resonant switched capacitor converter. 如請求項1、5、6或7所述之兩級電源轉換器，其中該諧振切換式電容轉換器之該輸入電壓與該第一級電壓之電壓轉換比率為4:1、3:1或2:1。The two-stage power converter according to claim 1, 5, 6, or 7, wherein the voltage conversion ratio of the input voltage of the resonant switched capacitor converter to the first-stage voltage is 4:1, 3:1, or 2:1.
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