WO2022185484A1 - 電力変換装置、モータ駆動装置、及び空気調和機 - Google Patents
電力変換装置、モータ駆動装置、及び空気調和機 Download PDFInfo
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- 238000006243 chemical reaction Methods 0.000 title claims abstract description 18
- 230000003111 delayed effect Effects 0.000 claims description 6
- 230000001934 delay Effects 0.000 claims description 2
- 239000003990 capacitor Substances 0.000 description 29
- 238000001514 detection method Methods 0.000 description 27
- 238000004364 calculation method Methods 0.000 description 20
- 238000009499 grossing Methods 0.000 description 13
- 238000010586 diagram Methods 0.000 description 12
- 238000004519 manufacturing process Methods 0.000 description 12
- 238000000034 method Methods 0.000 description 8
- 238000004904 shortening Methods 0.000 description 7
- 230000015654 memory Effects 0.000 description 6
- 239000004065 semiconductor Substances 0.000 description 6
- HBMJWWWQQXIZIP-UHFFFAOYSA-N silicon carbide Chemical compound [Si+]#[C-] HBMJWWWQQXIZIP-UHFFFAOYSA-N 0.000 description 6
- 229910010271 silicon carbide Inorganic materials 0.000 description 6
- 230000007423 decrease Effects 0.000 description 4
- 230000005855 radiation Effects 0.000 description 4
- 230000000630 rising effect Effects 0.000 description 4
- 229910002601 GaN Inorganic materials 0.000 description 3
- JMASRVWKEDWRBT-UHFFFAOYSA-N Gallium nitride Chemical compound [Ga]#N JMASRVWKEDWRBT-UHFFFAOYSA-N 0.000 description 3
- 230000003071 parasitic effect Effects 0.000 description 3
- 230000001360 synchronised effect Effects 0.000 description 3
- 230000005856 abnormality Effects 0.000 description 2
- 230000000694 effects Effects 0.000 description 2
- 230000033228 biological regulation Effects 0.000 description 1
- 239000002131 composite material Substances 0.000 description 1
- 238000009429 electrical wiring Methods 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 230000005669 field effect Effects 0.000 description 1
- 230000006870 function Effects 0.000 description 1
- 230000010354 integration Effects 0.000 description 1
- 239000000463 material Substances 0.000 description 1
- 238000005259 measurement Methods 0.000 description 1
- 229910044991 metal oxide Inorganic materials 0.000 description 1
- 150000004706 metal oxides Chemical class 0.000 description 1
- 230000010349 pulsation Effects 0.000 description 1
- 229910052710 silicon Inorganic materials 0.000 description 1
- 239000010703 silicon Substances 0.000 description 1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M7/2173—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a biphase or polyphase circuit arrangement
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
- H02M3/1586—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel switched with a phase shift, i.e. interleaved
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0043—Converters switched with a phase shift, i.e. interleaved
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
- H02M1/007—Plural converter units in cascade
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/084—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters using a control circuit common to several phases of a multi-phase system
- H02M1/0845—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters using a control circuit common to several phases of a multi-phase system digitally controlled (or with digital control)
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
Definitions
- the present disclosure relates to a power converter that converts an AC voltage output from an AC power source into a DC voltage, a motor drive device that includes the power converter, and an air conditioner that includes the motor drive device.
- Air conditioners are one of the applications of motor drive devices.
- regulations regarding harmonics of input current are stipulated.
- JIS Japanese Industrial Standards
- the air conditioner is sometimes provided with a PFC (Power Factor Correction) circuit, which is a power factor correction circuit for suppressing harmonics of the input current and improving the power factor.
- PFC Power Factor Correction
- a first example of a PFC circuit is a booster circuit using a plurality of switching elements and reactors.
- a second example of the PFC circuit is an interleave converter in which a plurality of boost chopper circuits are connected in parallel.
- the interleave converter provides a certain phase difference between the timings at which the switching elements of a plurality of boost chopper circuits are turned on, and controls the on period during which the switching elements are turned on. input current can be obtained.
- Patent Document 1 discloses an air conditioner equipped with an interleaved converter to improve the power factor.
- a surge voltage is a voltage having a spike-like rising waveform.
- the surge voltage may be higher than when the timing is far apart. In this case, it is necessary to increase the withstand voltage of the switching element, which increases the cost of the switching element, increases the size of the boost chopper circuit, and increases the manufacturing cost of the boost chopper circuit.
- the present disclosure has been made in view of the above, and an object thereof is to obtain a power conversion device capable of suppressing surge voltage generation while suppressing device size increase and manufacturing cost increase.
- the power conversion device includes a converter circuit and a control section.
- the converter circuit has circuits each having a reactor and switching elements connected to the reactor for a plurality of phases, and converts an AC voltage output from an AC power supply to a DC voltage.
- the control unit controls operations of the plurality of switching elements. When the time difference between the turn-off timing of the first switching element and the turn-on timing of the second switching element is within a threshold, the control unit advances or delays the turn-off timing of the first switching element. to implement.
- the first switching element is one of the plurality of switching elements.
- the second switching element is a switching element different from the first switching element.
- the power converter according to the present disclosure it is possible to suppress the occurrence of surge voltage while suppressing the increase in device size and manufacturing cost.
- FIG. 1 is a diagram showing a configuration example of an air conditioner including a motor drive device according to Embodiment 1.
- FIG. 1 is a diagram showing a circuit configuration of a motor drive device including a power conversion device according to Embodiment 1;
- FIG. Waveform diagram for explaining surge voltage that can occur in the converter circuit in Embodiment 1 A first waveform diagram for explaining the operation of the converter circuit according to the first embodiment.
- Flowchart showing operation flow of avoidance control in Embodiment 1 Waveform diagram for explaining the operation of the converter circuit according to the second embodiment Flowchart showing operation flow of control in Embodiment 2
- a power conversion device, a motor drive device, and an air conditioner according to embodiments of the present disclosure will be described below in detail based on the drawings.
- application to air conditioners is exemplified, but application to other uses is not excluded.
- FIG. 1 is a diagram showing a configuration example of an air conditioner including a motor drive device according to Embodiment 1.
- FIG. 2 is a diagram showing a circuit configuration of a motor drive device including the power conversion device according to the first embodiment.
- the air conditioner 100 includes an outdoor unit 5 and an indoor unit 7.
- the outdoor unit 5 and the indoor unit 7 are connected by a pipe 6 .
- the outdoor unit 5 includes a motor drive device 50 , a compressor 2 , a blower 3 and a heat exchanger 4 .
- the motor drive device 50 is connected to the compressor 2 and the blower 3 by electrical wiring (not shown).
- the motor driving device 50 is connected to the commercial power source 8 as shown in FIG.
- Commercial power supply 8 is an example of an AC power supply.
- the motor drive device 50 includes an input filter 9 , a power conversion device 1 and an inverter 13 .
- the power conversion device 1 includes a converter circuit 20 , a smoothing capacitor 12 , a control section 15 and a low-pass filter 16 .
- the power conversion device 1 supplies electric power for driving the motor 14 .
- the input side of the power converter 1 is connected to the commercial power source 8 via the input filter 9 .
- the output side of the power converter 1 is connected to the inverter 13 .
- the output side of inverter 13 is connected to motor 14 .
- the motor 14 is a compressor drive motor mounted on the compressor 2 .
- the motor 14 may be a fan-driving motor mounted on the fan 3 .
- the converter circuit 20 converts the AC voltage output from the commercial power supply 8 into a DC voltage. Smoothing capacitor 12 smoothes and holds the DC voltage converted by converter circuit 20 .
- the AC voltage output from the commercial power supply 8 will be referred to as "power supply voltage" as appropriate.
- the converter circuit 20 includes a rectifier circuit 10, boost chopper circuits 11-1 and 11-2, a snubber circuit 11-3, and a current sensor 11f.
- the snubber circuit 11-3 includes a snubber capacitor 11d and a snubber resistor 11e.
- the boost chopper circuits 11-1 and 11-2 are connected in parallel with each other.
- the boost chopper circuits 11-1 and 11-2 operate in sequence within a predetermined cycle range. This period is sometimes called the "interleave period”.
- the rectifier circuit 10 is connected between the input filter 9 and the converter circuit 20 .
- Rectifier circuit 10 applies a rectified voltage obtained by rectifying a power supply voltage to each of boost chopper circuits 11-1 and 11-2.
- a rectified voltage is a DC voltage with a pulsating component. A pulsating component of the DC voltage will be described later.
- a general configuration of the rectifier circuit 10 is a full-wave rectifier circuit in which four diodes are bridge-connected.
- one or more diodes may be replaced with switching elements such as metal oxide semiconductor field effect transistors (MOSFETs) to perform synchronous rectification.
- the rectifier circuit 10 may be configured as a half-wave rectifier circuit with only one diode. With this configuration, the number of diodes through which the input current passes can be reduced, so the loss generated in the rectifier circuit 10 can be reduced.
- the boost chopper circuit 11-1 includes a reactor 11a-1, a switching element 11b-1, and a diode 11c-1.
- the boost chopper circuit 11-2 includes a reactor 11a-2, a switching element 11b-2, and a diode 11c-2.
- FIG. 1 shows a two-phase example, which is a configuration of a two-phase interleave system. Each phase is identified by subscripts "-1" and "-2". Note that the power conversion device 1 in this specification is not limited to having only two phases, and may have a configuration of three or more phases.
- One end of the reactor 11a-1 is connected to one end of the rectifier circuit 10 and one end of the reactor 11a-2.
- the other end of the reactor 11a-1 is connected to one end of the switching element 11b-1 and the anode of the diode 11c-1.
- the cathode of diode 11 c - 1 is connected to the cathode of diode 11 c - 2 , one end of snubber capacitor 11 d and the positive terminal of smoothing capacitor 12 .
- the other end of the switching element 11b-1 is connected to the other end of the switching element 11b-2, one end of the snubber resistor 11e, the negative terminal of the smoothing capacitor 12, and the other end of the rectifier circuit .
- the other end of the reactor 11a-2 is connected to one end of the switching element 11b-2 and the anode of the diode 11c-2.
- the other end of snubber capacitor 11d is connected to the other end of snubber resistor 11e.
- the converter circuit 20 boosts the rectified voltage output from the rectifier circuit 10 and outputs it to the smoothing capacitor 12 . Further, the converter circuit 20 operates so that the peak value, average value, or effective value of the output voltage is kept constant by control described later.
- FIG. 2 shows the configuration of the interleaved converter circuit 20 using the boost chopper circuits 11-1 and 11-2, it is not limited to this configuration.
- Each of the boost chopper circuits 11-1 and 11-2 is replaced with a buck-boost chopper circuit, a flyback circuit, a flyforward circuit, a SEPIC (Single Ended Primary Inductor Converter), a Zeta converter, or a Cuk converter, and the converter circuit 20 is may be configured.
- An example of the switching elements 11b-1 and 11b-2 is the MOSFET shown in FIG. 2, but is not limited to this.
- An insulated gate bipolar transistor (IGBT) may be used instead of the MOSFET.
- each of the switching elements 11b-1 and 11b-2 has a diode connected in anti-parallel between the drain and the source.
- Anti-parallel connection means that the drain of the MOSFET and the cathode of the diode are connected, and the source of the MOSFET and the anode of the diode are connected.
- a parasitic diode that the MOSFET itself has inside may be used as the diode.
- a parasitic diode is also called a body diode.
- the switching elements 11b-1 and 11b-2 generally use semiconductor elements made of Si (silicon), but semiconductor elements made of SiC (silicon carbide) may also be used.
- SiC has a smaller conduction loss than Si and is capable of high-speed switching operation. Therefore, the use of SiC can reduce switching loss and power consumption of the air conditioner 100 .
- the use of SiC can also reduce the heat generated by the switching elements 11b-1 and 11b-2, so that heat dissipating members such as heat sinks for dissipating heat from the switching elements 11b-1 and 11b-2 can be made smaller. Can be manufactured at low cost.
- the use of SiC can suppress the temperature rise of electronic components arranged near the switching elements 11b-1 and 11b-2, thereby improving the reliability of the device.
- semiconductor elements made of GaN can be used as materials for the switching elements 11b-1 and 11b-2.
- An example of a semiconductor device made of GaN is a high electron mobility transistor (HEMT).
- HEMT high electron mobility transistor
- a HEMT has a smaller conduction loss than a MOSFET made of Si and is capable of high-speed switching operation. Therefore, by using HEMT, switching loss can be reduced and the power consumption of the air conditioner 100 can be reduced as compared with a MOSFET made of Si.
- the use of HEMTs can reduce the amount of heat generated by the switching elements 11b-1 and 11b-2.
- the heat radiation member such as a heat sink for suppressing the temperature rise of the switching elements 11b-1 and 11b-2, and to manufacture the heat radiation member at low cost.
- HEMTs HEMTs
- each of the diodes 11c-1 and 11c-2 may be replaced with a MOSFET or the HEMT described above to form a synchronous rectification circuit configuration.
- a synchronous rectification circuit configuration conduction loss generated in the diodes 11c-1 and 11c-2 can be reduced. Thereby, the power consumption of the air conditioner 100 can be reduced.
- MOSFETs or HEMTs are used, the amount of heat generated by the diodes 11c-1 and 11c-2 can be reduced.
- the size of the heat radiation member such as a heat sink for suppressing the temperature rise of the diodes 11c-1 and 11c-2, and to manufacture the heat radiation member at low cost.
- MOSFETs or HEMTs it is possible to suppress the temperature rise of electronic components arranged near the diodes 11c-1 and 11c-2, thereby improving the reliability of the device.
- the converter circuit 20 boosts the rectified voltage output from the rectifier circuit 10 and controls the average voltage of the smoothing capacitor 12 to a constant voltage.
- the rectified voltage pulsates at a frequency twice as high as the power supply frequency, which is the frequency of the power supply voltage. Therefore, the voltage output from the converter circuit 20 also pulsates at twice the frequency of the power supply.
- smoothing capacitor 12 smoothes the voltage output from converter circuit 20 . As a result, the pulsating component of twice the power supply frequency that can be included in the motor current is reduced.
- a motor current is a current supplied from the inverter 13 to the motor 14 .
- the smoothing capacitor 12 by providing the smoothing capacitor 12, the pulsation component of twice the power supply frequency that can be included in the motor current is reduced, so the vibration of the components including the motor 14 and the piping 6 is suppressed. As a result, it is possible to reduce the cost required for the anti-vibration component, thereby suppressing an increase in manufacturing cost. Moreover, since the vibration of the components including the motor 14 and the pipe 6 is suppressed, the vibration noise can be reduced. This makes it possible to improve the quality of the air conditioner 100 at low cost.
- the inverter 13 is connected between the smoothing capacitor 12 and the motor 14 .
- a voltage output from the converter circuit 20 and smoothed by the smoothing capacitor 12 is applied to the inverter 13 .
- the voltage smoothed by the smoothing capacitor 12 will be referred to as "capacitor voltage”.
- the inverter 13 converts the capacitor voltage into an AC voltage of any frequency and applies it to the motor 14 .
- inverter 13 Although the detailed configuration of the inverter 13 is not shown, an inverter circuit with a known circuit configuration can be used. Examples of known inverter circuits include full-bridge inverters, half-bridge inverters, single-switch voltage resonance circuits, and the like.
- the control unit 15 includes a drive unit 15a, a calculation unit 15b, a voltage detection unit 15c, and a current detection unit 15d.
- the voltage detection unit 15c detects the capacitor voltage.
- the detection result of the voltage detection section 15c is input to the calculation section 15b.
- the voltage detection unit 15c may directly detect the capacitor voltage, or may use a voltage dividing circuit in which a plurality of resistors are connected in series.
- the capacitor voltage can be calculated using the divided voltage of the voltage dividing circuit.
- the detected value of the current flowing through the switching elements 11b-1 and 11b-2 detected by the current sensor 11f is input to the current detection unit 15d via the low-pass filter 16.
- the current detection unit 15d detects a current value, which is the magnitude of the current flowing through the switching elements 11b-1 and 11b-2, and transmits the detection result to the calculation unit 15b.
- Examples of the current sensor 11f include a current sensor using a shunt resistor and a Hall element.
- the calculation unit 15b performs feedback control on the boost chopper circuits 11-1 and 11-2 so that the capacitor voltage becomes the set voltage based on the detected value of the capacitor voltage detected by the voltage detection unit 15c. More specifically, the calculation unit 15b turns on the switching elements 11b-1 and 11b-2 so that the difference between the voltage detection value detected by the voltage detection unit 15c and the reference voltage value becomes small. change the duration. The period during which the switching elements 11b-1 and 11b-2 are turned on is based on the time when the switching elements 11b-1 and 11b-2 are changed from off to on immediately before.
- the arithmetic unit 15b can be configured as a single circuit, a composite circuit, an ASIC (Application Specific Integrated Circuit), an FPGA (Field-Programmable Gate Array), or a processing circuit combining these.
- ASIC Application Specific Integrated Circuit
- FPGA Field-Programmable Gate Array
- the calculation unit 15b may be configured with a calculator and a memory.
- a computing unit is a microcomputer, but in addition to this, computing means called CPU (Central Processing Unit), microprocessor, DSP (Digital Signal Processor), etc. may be used.
- the memory stores the program read by the computing unit and also stores the result of computation by the computing unit. Examples of memory include non-volatile or volatile semiconductor memories such as RAM (Random Access Memory), ROM (Read Only Memory), flash memory, EPROM (Erasable Programmable ROM), and EEPROM (Electrically EPROM). can be done.
- the calculation unit 15b detects an abnormality in the operation of the converter circuit 20 based on the detection value of the current detection unit 15d.
- arithmetic unit 15b outputs a signal for turning off switching elements 11b-1 and 11b-2 to stop operation of converter circuit 20 to drive unit 15a.
- the reactor 11a-1 has a short-circuit failure, for example.
- the current flowing through the switching element 11b-1 becomes an excessive current.
- the calculation unit 15b that detects the excessive current of the switching element 11b-1 turns off the switching element 11b-1 to reduce the risk of failure due to the excessive current. Similar control is performed when an excessive current flows through the switching element 11b-2.
- a method of comparing the detection value of the current detection unit 15d and the reference current value may be used.
- the calculation unit 15b preferably has an analog-to-digital (AD) conversion function for converting analog signals transmitted from the voltage detection unit 15c and the current detection unit 15d into digital values.
- AD analog-to-digital
- the voltage detection section 15c does not need a circuit for generating a reference voltage value
- the current detection section 15d does not need a circuit for generating a reference current value.
- the voltage detection section 15c and the current detection section 15d can be configured compactly.
- integration of analog circuits including the voltage detection section 15c and the current detection section 15d is facilitated, and the control section 15 can be further miniaturized.
- the drive unit 15a receives the signal transmitted from the calculation unit 15b, and generates drive signals G1 and G2 by converting the signals into voltages capable of controlling the ON/OFF of the switching elements 11b-1 and 11b-2.
- the drive unit 15a applies the drive signals G1 and G2 to the gates of the switching elements 11b-1 and 11b-2 to switch the switching elements 11b-1 and 11b-2, respectively.
- a signal transmitted from the calculation unit 15b is a voltage of 3.3V or 5V, for example.
- the voltages of the driving signals G1 and G2 are, for example, 15V or 18V.
- FIG. 3 is a waveform diagram for explaining a surge voltage that can occur in the converter circuit according to the first embodiment.
- the horizontal axis of FIG. 3 represents time. 3 shows, in order from the top, the drive signal G1, the drain voltage Vd1 of the switching element 11b-1, the drain current Id1 of the switching element 11b-1, the drive signal G2, the drain voltage Vd2 of the switching element 11b-2, and the A waveform of the drain current Id2 of the switching element 11b-2 is shown.
- FIG. 2 also shows the measurement sites for these voltages and currents.
- the drain current is the current flowing through each switching element, and the drain voltage is the voltage applied between the drain and source of each switching element.
- Tsw is the operation period when the switching elements 11b-1 and 11b-2 are driven, and is hereinafter referred to as the "reference period”.
- T1 to T5 indicate turn-on times at which the switching elements 11b-1 and 11b-2 are switched from off to on.
- the reference period Tsw is equal to the period from time T1 to time T3.
- the switching elements 11b-1 and 11b-2 repeat ON and OFF operations at the reference period Tsw.
- a preset phase difference is provided between the timings at which the switching elements 11b-1 and 11b-2 are turned on.
- the converter circuit 20 shown in FIG. 2 has a configuration of a two-phase interleave system, and the turn-on timing is provided with a phase difference of Tsw/2. If the converter circuit 20 employs, for example, a 3-phase interleave system or a 4-phase interleave system, a phase difference of Tsw/3 or Tsw/4 is provided, respectively.
- a surge voltage is generated in the drain voltage at the timing of turning on the switching elements 11b-1 and 11b-2. For example, at time T1, a surge voltage having a height of Vs1 is generated. A surge voltage is a spike-like voltage.
- the surge voltage generated in the converter circuit 20 is caused by printed wiring connecting the components of the converter circuit 20, jumper wiring, or parasitic inductance of the smoothing capacitor 12 and the current sensor 11f.
- a surge voltage is generated when the drain current abruptly changes from zero when the switching elements 11b-1 and 11b-2 are turned on.
- switching the switching elements 11b-1 and 11b-2 from on to off that is, when the switching elements 11b-1 and 11b-2 are turned off, a surge voltage is generated.
- the snubber capacitor 11d and the snubber resistor 11e are parts for suppressing surge voltage.
- the capacitance of the snubber capacitor 11d and the resistance value of the snubber resistor 11e are selected so that the drain voltage of the switching elements 11b-1 and 11b-2 is less than the rated voltage.
- the larger the capacitance of the snubber capacitor 11d and the smaller the resistance value of the snubber resistor 11e the higher the surge voltage, that is, the magnitude of the surge voltage can be suppressed.
- the low-pass filter 16 is used for countermeasures against such noise, and can be configured using circuit elements including resistors and capacitors.
- the converter circuit 20 controls the on-time of the switching elements 11b-1 and 11b-2 so that the peak value, average value or effective value of the output voltage is constant. For this reason, the turn-off timing is not constant, and is changed, for example, as shown in FIG.
- the noise generated in the output of the current sensor 11f or other sensors placed near the switching elements 11b-1 and 11b-2 may increase. If the number of parts constituting the low-pass filter 16 is increased as a countermeasure against this noise, the size of the low-pass filter 16 becomes large and the parts become expensive.
- FIG. 4 is a first waveform diagram for explaining the operation of the converter circuit according to the first embodiment.
- FIG. 5 is a second waveform diagram for explaining the operation of the converter circuit according to the first embodiment.
- the horizontal axes in FIGS. 4 and 5 represent time.
- the upper part of FIG. 4 shows the waveform of the driving signal G1
- the lower part of FIG. 4 shows the waveform of the driving signal G2.
- 5 shows waveforms in the same order as in FIG. 4 and 5, the thick dashed line is the waveform when the control according to the first embodiment is not performed, and the thick solid line is the waveform when the control according to the first embodiment is performed.
- FIG. 4 shows the waveform of the drive signal for the switching element 11b-1
- the lower part of FIG. 4 shows the waveform of the drive signal for the switching element 11b-2.
- Ts1 before time Tb is time Ta
- Ts2 after time Tb is time Tc.
- Ts1 is called “period Ts1”
- Ts2 is called “period Ts2”. That is, the time Ta is the time before the period Ts1 has elapsed from the starting time Tb, and the time Tc is the time after the period Ts2 has elapsed from the starting time Tb.
- the rising portion A2 of the driving signal G2 rising at time Tb and the falling portion A1 of the driving signal G1 falling after time Tb are different. relatively close. Therefore, there is concern about the occurrence of the surge voltage described above. Therefore, the timing for turning off the switching element 11b-1 is changed.
- the timing of turning off the switching element 11b-1 is within a period Ts2 after the time Tb at which the switching element 11b-2 turns on, the timing of turning off the switching element 11b-1 is is delayed until time Tc.
- the turn-off timing of the switching element 11b-1 is set to the time Tb. Control to advance to Ta is implemented.
- control to advance” and “control to delay” the aforementioned turn-off timing are collectively referred to as "avoidance control” as appropriate.
- the example of changing the turn-off timing of the switching element 11b-1 has been described here, the same avoidance control is performed for the turn-off timing of the switching element 11b-2.
- the degree of surge voltage generation depends on various circuit elements such as the switching speed of the switching elements 11b-1 and 11b-2, the inductance of the reactors 11a-1 and 11a-2, and the capacitance of the snubber circuit 11-3.
- Various methods can be used as the avoidance control, but this paper exemplifies a method of comparing the time difference between the turn-off timing of the switching element 11b-1 and the turn-on timing of the switching element 11b-2 with a preset threshold value. do.
- the calculation unit 15b determines the turn-off timing of the second switching element. Accelerate control or slow control is implemented.
- the first switching element referred to here is the switching element 11b-1 or the switching element 11b-2, and the second switching element is a switching element different from the first switching element.
- FIG. 5 shows operation waveforms when the avoidance control shown in FIG. 4 is performed.
- the timing at which the switching element 11b-1 is turned off is relatively close to the timing at which the switching element 11b-2 is turned on.
- the timing at which the switching element 11b-1 is turned off is within the period Ts1. Therefore, avoidance control advances the timing of turning off the switching element 11b-1.
- This control shifts the timing at which the drain currents of the switching elements 11b-1 and 11b-2 sharply change, thereby suppressing the superimposition of the surge voltage.
- the surge voltage Vs2 shown in FIG. 3 is suppressed to a surge voltage Vs2' lower than the surge voltage Vs2 in FIG.
- FIG. 6 is a flow chart showing the operation flow of avoidance control in the first embodiment.
- the calculation unit 15b calculates the ON periods of the first and second switching elements based on the output voltage detected by the voltage detection unit 15c (step S01).
- the calculation unit 15b determines whether or not the turn-off timing of the first switching element is within the period Ts1 (step S02). As shown in FIG. 4, the period Ts1 is set based on the turn-on timing of the second switching element.
- step S02 If the turn-off timing of the first switching element is within the period Ts1 (step S02, Yes), the off-time is changed from Tb to Ta to shorten the on-period as shown in FIG. 4 (step S03). If the turn-off timing of the first switching element is not within the period Ts1 (step S02, No), it is determined whether or not the turn-off timing of the first switching element is within the period Ts2 (step S04). . As shown in FIG. 4, the period Ts2 is also set based on the turn-on timing of the second switching element.
- step S04, Yes If the turn-off timing of the first switching element is within the period Ts2 (step S04, Yes), the off-time is changed from Tb to Tc as shown in FIG. 4 to extend the on-period (step S05). If the turn-off timing of the first switching element is not within the period Ts2 (step S04, No), the ON period is not changed (step S06). Through the above process, the ON period of the first switching element is determined.
- the lengths of the periods Ts1 and Ts2 are such that the switching elements 11b-1 and 11b-2 actually operate after the drive signal G1 or the drive signal G2 is input to the gates of the switching elements 11b-1 and 11b-2. Preferably longer than the delay time to completion.
- the delay time from when the turn-off drive signal G1 is input to the gate of the switching element 11b-1 until the actual turn-off of the switching element 11b-1 is completed is Td_off
- the period Ts1 is , Ts1>Td_off.
- the switching element 11b-2 when shortening the on-period of the switching element 11b-1 or the switching element 11b-2, the turn-off timing and the turn-on timing of the switching elements 11b-1 and 11b-2 are ensured. can be inconsistent.
- the period Ts2 is Ts2> Set the time to be Td_on.
- the switching element 11b-1 when extending the ON period of the switching element 11b-1 or the switching element 11b-2, the turn-off timing and the turn-on timing of the switching elements 11b-1 and 11b-2 can be ensured. can be inconsistent.
- the control unit provided in the power conversion device according to Embodiment 1 controls the timing at which the first switching element is turned off, and the timing at which the second switching element different from the first switching element is turned on. If the time difference from the timing is within the threshold, avoidance control is performed to advance or delay the timing at which the first switching element turns off. With this control, the turn-off timing and the turn-on timing of the first and second switching elements can be reliably made different from each other. As a result, it is possible to suppress an increase in the size of the boost chopper circuit and an increase in the manufacturing cost of the boost chopper circuit. Also, it is possible to suppress an increase in the size of the snubber circuit and an increase in the manufacturing cost of the snubber circuit.
- FIG. 7 is a waveform diagram for explaining the operation of the converter circuit according to the second embodiment.
- the configuration of the power conversion device including the converter circuit is the same as or equivalent to that of the power conversion device 1 shown in FIG. 2, and redundant description will be omitted.
- FIG. 7 shows the waveforms of the drive signal G1, the reactor current Ir1 flowing through the reactor 11a-1, the drive signal G2, and the reactor current Ir2 flowing through the reactor 11a-2 in order from the top.
- the meaning of the thick broken line and the solid line in the operating waveforms is the same as in FIGS. That is, the thick dashed line is the waveform when the control according to the second embodiment is not performed, and the thick solid line is the waveform when the control according to the second embodiment is performed.
- the upper part of FIG. 7 shows how the waveform of the drive signal G1 is alternately shortened and extended.
- the lower middle part of FIG. 7 shows how the waveform of the drive signal G2 is alternately shortened and extended. That is, in the control of the second embodiment, when the turn-off timing is advanced, control is performed to delay the turn-off timing in the next switching control. Further, when the turn-off timing is delayed, control is performed to advance the turn-off timing at the next switching.
- the duty which is the ratio of the ON time of the switching element 11b-1 to the reference period Tsw, changes.
- the reactor current Ir1 fluctuates, which may increase the harmonics of the input current.
- the avoidance control according to the first embodiment shortens the ON period of the switching element 11b-1, the input current decreases due to the reduced duty. Further, when the ON period of the switching element 11b-1 is extended by the avoidance control according to the first embodiment, the input current increases due to the increased duty. The same applies to the switching element 11b-2.
- control for suppressing an increase or decrease in input current that is, control for suppressing fluctuations in the input current is performed. Specifically, the control described below is performed.
- avoidance control is performed to shorten the ON period of the switching element 11b-1.
- the current amplitude Idf1 of the average current of the reactor 11a-1 with respect to the zero level becomes smaller than when the avoidance control is not performed.
- the avoidance control for shortening the ON period of the switching element 11b-1 is further performed at time T3'', the current amplitude Idf1 becomes even smaller. Therefore, the fluctuation of the input current is also increased.
- control is performed to extend the ON period instead of shortening the ON period.
- it is possible to prevent the duty from continuing to decrease.
- a decrease in the current amplitude Idf1 is suppressed, so that fluctuations in the input current can also be suppressed.
- FIG. 8 is a flow chart showing the control operation flow in the second embodiment.
- the calculation unit 15b determines whether or not to perform avoidance control (step S11). Needless to say, the on-periods of the first and second switching elements are calculated when determining whether or not to perform avoidance control.
- step S11 If it is determined not to implement avoidance control (step S11, No), the calculation unit 15b continues the processing of step S11. On the other hand, if it is determined to implement avoidance control (step S11, Yes), avoidance control is implemented and the process proceeds to step S12.
- the calculation unit 15b determines whether or not the avoidance control performed in step S11 is the control for shortening the ON period (step S12). If the avoidance control performed in step S11 is control for shortening the ON period (step S12, Yes), the calculation unit 15b performs control for extending the ON period in the next avoidance control (step S13).
- step S11 when the avoidance control performed in step S11 is not the control for shortening the ON period (step S12, No), that is, when the avoidance control performed in step S11 is the control for extending the ON period, the calculation unit 15b In the next avoidance control, control for shortening the ON period is executed (step S14). After the processing of steps S13 and S14, the process returns to step S11 and the above processing is repeated.
- the next avoidance control of the first switching element will turn off the first switching element. Timing is controlled to be delayed. Further, when the turn-off timing of the first switching element is delayed by the avoidance control of the first embodiment, the turn-off timing of the first switching element is controlled to be advanced in the next avoidance control.
- This control can suppress fluctuations in the input current that is input to the power converter. As a result, in addition to the effect of the first embodiment, it is possible to obtain a further effect of suppressing an increase in harmonics of the input current.
- the switching elements 11b-1 and 11b-2 When the switching elements 11b-1 and 11b-2 are enclosed in one module, that is, when the switching elements 11b-1 and 11b-2 are packaged as one module, the switching element 11b -1 and 11b-2 become relatively close.
- the control in Embodiments 1 and 2 can be suitably used for such a configuration.
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Abstract
Description
図1は、実施の形態1に係るモータ駆動装置を含む空気調和機の構成例を示す図である。また、図2は、実施の形態1に係る電力変換装置を含むモータ駆動装置の回路構成を示す図である。
図7は、実施の形態2におけるコンバータ回路の動作説明に供する波形図である。なお、実施の形態2において、コンバータ回路を含む電力変換装置の構成は、図2に示す電力変換装置1と同一又は同等であり、重複する説明を省略する。
Claims (8)
- リアクトルと、前記リアクトルに接続されるスイッチング素子とを有する回路を複数の相数分有し、交流電源から出力される交流電圧を直流電圧に変換するコンバータ回路と、
複数の前記スイッチング素子の動作を制御する制御部と、
を備え、
複数の前記スイッチング素子の1つである第1のスイッチング素子がターンオフするタイミングと、前記第1のスイッチング素子とは異なる第2のスイッチング素子がターンオンするタイミングとの時間差が閾値内である場合、前記制御部は、前記第1のスイッチング素子がターンオフするタイミングを早める又は遅くする回避制御を実施する
電力変換装置。 - 前記制御部は、前記回避制御において、前記第1のスイッチング素子のターンオフのタイミングを早めた場合には、前記第1のスイッチング素子の次回の回避制御ではターンオフのタイミングを遅くする
請求項1に記載の電力変換装置。 - 前記制御部は、前記回避制御において、前記第1のスイッチング素子のターンオフのタイミングを遅くした場合には、前記第1のスイッチング素子の次回の回避制御ではターンオフのタイミングを早める
請求項1に記載の電力変換装置。 - 前記第1のスイッチング素子のターンオフのタイミングを早めた時間は、前記第1のスイッチング素子がターンオフを開始してから完了するまでの時間よりも長い
請求項1から3の何れか1項に記載の電力変換装置。 - 前記第1のスイッチング素子のターンオフのタイミングを遅くした時間は、前記第2のスイッチング素子がターンオンを開始してから完了するまでの時間よりも長い
請求項1から3の何れか1項に記載の電力変換装置。 - 複数の前記スイッチング素子は、1つのモジュール内に封入されている
請求項1から5の何れか1項に記載の電力変換装置。 - 請求項1から6の何れか1項に記載の電力変換装置を備えるモータ駆動装置。
- 請求項7に記載のモータ駆動装置を備える空気調和機。
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US18/270,668 US20240072680A1 (en) | 2021-03-04 | 2021-03-04 | Power conversion apparatus, motor drive apparatus, and air conditioner |
CN202180094852.XA CN116918229A (zh) | 2021-03-04 | 2021-03-04 | 电力转换装置、马达驱动装置以及空调机 |
PCT/JP2021/008477 WO2022185484A1 (ja) | 2021-03-04 | 2021-03-04 | 電力変換装置、モータ駆動装置、及び空気調和機 |
DE112021007193.9T DE112021007193T5 (de) | 2021-03-04 | 2021-03-04 | Energieumwandlungsvorrichtung, Motortreibervorrichtung und Klimaanlage |
JP2023503289A JP7455273B2 (ja) | 2021-03-04 | 2021-03-04 | 電力変換装置、モータ駆動装置、及び空気調和機 |
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Citations (6)
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JP2000092848A (ja) * | 1998-09-16 | 2000-03-31 | Toyo Electric Mfg Co Ltd | 電力変換装置の多数台運転方法 |
JP2013192349A (ja) * | 2012-03-13 | 2013-09-26 | Panasonic Corp | パワーコンディショナ及びそれを備えた発電システム |
JP2013220028A (ja) * | 2013-08-01 | 2013-10-24 | Mitsubishi Electric Corp | 直流電源装置 |
WO2020174531A1 (ja) * | 2019-02-25 | 2020-09-03 | 三菱電機株式会社 | 電源装置、モータ駆動装置、送風機、圧縮機及び空気調和機 |
JP2020178399A (ja) * | 2019-04-16 | 2020-10-29 | 三菱電機株式会社 | 電力変換装置 |
JP2021002925A (ja) * | 2019-06-21 | 2021-01-07 | 三菱電機株式会社 | 電力変換装置 |
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2021
- 2021-03-04 JP JP2023503289A patent/JP7455273B2/ja active Active
- 2021-03-04 WO PCT/JP2021/008477 patent/WO2022185484A1/ja active Application Filing
- 2021-03-04 DE DE112021007193.9T patent/DE112021007193T5/de active Pending
- 2021-03-04 CN CN202180094852.XA patent/CN116918229A/zh active Pending
- 2021-03-04 US US18/270,668 patent/US20240072680A1/en active Pending
Patent Citations (6)
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JP2000092848A (ja) * | 1998-09-16 | 2000-03-31 | Toyo Electric Mfg Co Ltd | 電力変換装置の多数台運転方法 |
JP2013192349A (ja) * | 2012-03-13 | 2013-09-26 | Panasonic Corp | パワーコンディショナ及びそれを備えた発電システム |
JP2013220028A (ja) * | 2013-08-01 | 2013-10-24 | Mitsubishi Electric Corp | 直流電源装置 |
WO2020174531A1 (ja) * | 2019-02-25 | 2020-09-03 | 三菱電機株式会社 | 電源装置、モータ駆動装置、送風機、圧縮機及び空気調和機 |
JP2020178399A (ja) * | 2019-04-16 | 2020-10-29 | 三菱電機株式会社 | 電力変換装置 |
JP2021002925A (ja) * | 2019-06-21 | 2021-01-07 | 三菱電機株式会社 | 電力変換装置 |
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DE112021007193T5 (de) | 2023-12-21 |
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