WO2015079518A1 - 電力変換装置 - Google Patents
電力変換装置 Download PDFInfo
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- WO2015079518A1 WO2015079518A1 PCT/JP2013/081934 JP2013081934W WO2015079518A1 WO 2015079518 A1 WO2015079518 A1 WO 2015079518A1 JP 2013081934 W JP2013081934 W JP 2013081934W WO 2015079518 A1 WO2015079518 A1 WO 2015079518A1
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- WIPO (PCT)
- Prior art keywords
- inverter circuit
- resonance
- current
- resonant
- switch element
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0009—Devices or circuits for detecting current in a converter
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/4815—Resonant converters
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the present invention relates to a power conversion device using a current resonance inverter.
- a power conversion device that converts a DC voltage into an AC voltage by a medium-frequency / resonant inverter using current resonance is used in railway vehicles, solar power generation, and the like (see Patent Document 1).
- the current resonance inverter uses the resonance of the LC circuit in the switching circuit to create a moment when the current becomes zero, and reduces the switching loss by turning off the switching element of the power semiconductor at that timing. By performing current resonance, there is an advantage that the power semiconductor device can be realized with a low loss because the turn-off loss of the power semiconductor becomes almost zero.
- Patent Literature 2 discloses a control method for preventing breakage of a switch element due to resonance loss in a series resonant converter.
- Patent Document 2 in the half-bridge current resonance converter, the current of the secondary side rectifier diode that does not flow during normal operation (normal frequency) is detected to determine the loss of resonance.
- Patent Document 3 discloses a method for controlling an induction heating power supply.
- a full-bridge current resonance inverter when the switching loss at turn-off exceeds an allowable set value, the operation of the inverter is stopped.
- the control circuit for the switching power supply described in Patent Document 4 when a resonance loss is detected from the detected value of the output current of the composite current resonance converter, the switch element is turned off.
- Patent Document 4 also describes that a signal for turning on a switch element is blocked while a current flowing through the impedance element is detected when both of the two switch elements are off.
- the switching operation is stopped when the temperature detected by a thermistor or the like exceeds a certain temperature. Since the power semiconductor cannot be protected from over-temperature by temperature protection, the power semiconductor detects the state where the current is cut off and stops. For example, if the switch element is turned off immediately after detecting the resonance failure, the inverter is temporarily stopped even if the resonance is detected due to the influence of noise or the like. However, in applications where it is not desirable to shut down the power source frequently, such as railway electric vehicles, it is necessary to keep moving as much as possible.
- the present invention has been made in view of the circumstances as described above, and when the resonant frequency of the resonant inverter circuit changes, the switch element of the resonant inverter circuit is protected and the resonant inverter circuit is not excessively stopped. With the goal.
- the power conversion device includes a resonant inverter circuit including two or more switch elements, a detector that detects an output current of the switch elements, a resonance determination unit, and a control unit.
- the resonance determination unit is configured such that the number of times that the absolute value of the current detected by the detector when the switch element is turned off is equal to or greater than a threshold value during a predetermined period that is twice or more the switching cycle of the switch element is equal to or greater than two or more predetermined times In this case, it is determined that the resonance frequency of the resonance inverter circuit is abnormal.
- the control unit stops the switching operation of the resonance inverter circuit.
- the number of times that the absolute value of the current detected by the detector when the switch element is turned off when the switch element is turned off is equal to or greater than a threshold value during a predetermined period that is twice or more the switching period.
- FIG. 1 is a block diagram illustrating a configuration example of a power conversion device according to an embodiment of the present invention.
- the power conversion device includes a resonant inverter circuit 1 and a control device 2.
- the resonant inverter circuit 1 is connected to a DC power source 3 and a ground 4 and supplied with DC power from the DC power source 3.
- the control device 2 operates the resonant inverter circuit 1, converts the DC voltage into an AC voltage by the resonant inverter circuit 1, and supplies AC power to the load circuit 5.
- the resonant inverter circuit 1 includes a filter capacitor 11, resonant capacitors 12 and 13, switch elements 14 and 15, a resonant transformer 16 and a detector 17.
- the filter capacitor 11 blocks noise from the DC power source 3 and suppresses fluctuations in the voltage applied to the switch elements 14 and 15.
- Resonant capacitors 12 and 13 are connected in series. Prior to the start of driving of the resonant inverter circuit 1, the divided DC voltage is applied to the resonant capacitors 12 and 13, respectively.
- the capacitances of the resonant capacitors 12 and 13 may be the same value or different values. When the capacitances of the resonance capacitors 12 and 13 are the same, the voltage values of the resonance capacitors 12 and 13 are the same.
- the resonant capacitors 12 and 13 may be composed of a plurality of capacitors connected in series and / or a plurality of capacitors connected in parallel. In that case, the capacitance of the resonant capacitors 12 and 13 is a combined capacitance of a plurality of capacitors.
- the switch elements 14 and 15 may be composed of a plurality of elements.
- the switch elements 14 and 15 are IGBTs (Insulated Gate Bipolar Transistors). However, the switch elements 14 and 15 are not limited to IGBTs, and may be controlled by gate signals. . The switch elements 14 and 15 are connected in series and are connected in parallel to the resonance capacitors 12 and 13.
- the resonant transformer 16 has a primary winding and a secondary winding, and both ends of the primary winding of the resonant transformer 16 are connected to a connection point of the resonance capacitors 12 and 13 and a connection point of the switch elements 14 and 15, respectively. .
- the detector 17 is disposed between one end of the resonant transformer 16 and the connection point of the switch elements 14 and 15, and outputs a voltage proportional to the output current of the switch elements 14 and 15.
- the control device 2 alternately switches on and off the switch elements 14 and 15, and generates an AC voltage at both ends of the resonant transformer 16 with the resonant capacitors 12 and 13 and the resonant transformer 16. For example, the control device 2 starts the operation of the resonant inverter circuit 1 when the input voltage to the resonant inverter circuit 1 detected by an input voltage detector (not shown) falls within a predetermined range. For example, when the input voltage to the resonant inverter circuit 1 exceeds the threshold value and becomes an overvoltage, the control device 2 stops the resonant inverter circuit 1.
- the capacitances of the resonant capacitors 12 and 13 are set to the same value, and the control device 2 outputs a gate signal for turning on the switch element 14 for a predetermined conduction time when starting the drive of the resonant inverter circuit 1. It shall be.
- the control device 2 outputs a gate signal so that the switch elements 14 and 15 are alternately turned on during the conduction time. Note that a short-circuit prevention time in which both the switch elements 14 and 15 are turned off is provided.
- the current vibrates at a resonant frequency determined by the inductance of the resonant transformer 16 and the capacitance of the resonant capacitors 12 and 13. .
- Switching loss can be reduced by turning off the switch elements 14 and 15 when the current becomes zero.
- FIG. 2 is a diagram showing a current waveform when the resonant frequency of the resonant inverter circuit is normal.
- the upper part of FIG. 2 shows the current of the switch element 14.
- the lower part of FIG. 2 shows the current detected by the detector 17. Since the switch element 15 is turned on while the switch element 14 is off, the detection current alternately appears positively and negatively.
- the current changes to oscillate at a resonance frequency determined by the resonance transformer 16 and the resonance capacitors 12 and 13. Therefore, the switch element is turned off while the current is zero.
- the resonance frequency determined by the resonance transformer 16 and the resonance capacitors 12 and 13 decreases for some reason, the period in which the current vibrates becomes longer. In that case, if the switch elements 14 and 15 are turned off at the same timing after the switch elements 14 and 15 are turned on, a current still flows when the switch elements 14 and 15 are turned off.
- FIG. 3 is a diagram showing a current waveform when the resonant frequency of the resonant inverter circuit is lowered. It is shown that the current is still flowing when the period of the resonance current is increased and the switch elements 14 and 15 are turned off.
- the 1 includes a current detection unit 21, a resonance frequency determination unit 22, and a control unit 23.
- the current detection unit 21 performs A / D conversion on a voltage proportional to the current detected by the detector 17 and outputs a current value.
- the resonance frequency determination unit 22 counts the number of times that the absolute value of the current detected by the detector 17 when the switch elements 14 and 15 are turned off is greater than or equal to a threshold value during a predetermined period that is twice or more the switching cycle of the switch elements 14 and 15. However, when the number of times is equal to or greater than two, the resonance frequency of the resonant inverter circuit 1 is determined to be abnormal.
- the control unit 23 stops the switching operation of the resonant inverter circuit 1 when the resonant frequency determination unit 22 determines that the resonant frequency of the resonant inverter circuit 1 is abnormal.
- the control device 2 also stops the resonant inverter circuit 1 when the current flowing through the resonant transformer 16 detected by the detector 17 exceeds the threshold value and becomes an overcurrent.
- the condition for determining that the resonance frequency is abnormal by the resonance frequency determination unit 22 can be appropriately determined according to the characteristics and application of the resonance inverter circuit 1.
- the determination period is M times the switching period (M is an integer of 2 or more), and the resonance frequency abnormality is the number of times that the absolute value of the current detected by the detector 17 when the switch elements 14 and 15 are turned off is equal to or greater than the threshold value.
- N N is an integer equal to or greater than 2
- a predetermined number of times for determination can be arbitrarily set within a range of M ⁇ N ⁇ 2.
- FIG. 4 is a diagram illustrating an example of a logic circuit of the resonance frequency determination unit.
- the resonance frequency determination unit 22 compares the current value output from the current detection unit 21 with the threshold value of the register 24 by the comparator 26, and the current value is equal to or greater than the threshold value. Then, “1” is output to the shift register 28 and the adder 29.
- the shift registers (flip-flops) 28 are connected in series to M ⁇ 1, with the switching cycle period to be determined being M cycles (M is an integer of 2 or more).
- M is an integer of 2 or more).
- the output of the final shift register 28 is input to the subtracter 30.
- the subtracter 30 receives the result of the adder 29 and subtracts the output of the final stage of the shift register 28 from the result of the adder 29.
- the result of the subtracter 30 is input to the comparator 27 and returned to the adder 29 in the next cycle.
- the adder 29 and the subtracter 30 add the results of the current comparator 26 and subtract the results of the comparator 26 before M cycles.
- the comparator 27 compares the result of the subtracter 30 with a specified number of times (for example, N) of the register 25. If the number is equal to or greater than the specified number, “1 (resonance frequency abnormality)” is set. Is output to the control unit 23.
- the resonance frequency determination unit 22 determines that the number of times that the absolute value of the current detected by the detector 17 when the switch elements 14 and 15 are turned off when the switch elements 14 and 15 are turned off is equal to or greater than the threshold value is N In the above case, it is determined that the resonance frequency is abnormal.
- the current when the switch elements 14 and 15 are turned off may be detected only when either the switch element 14 or the switch element 15 is turned off, or may be detected when both the switch elements 14 and 15 are turned off. May be.
- the period when the current is detected and determined when both switch elements 14 and 15 are turned off is half that when the current is detected when either one is turned off.
- FIG. 5 is a flowchart showing an example of the operation of the resonance frequency abnormality stop process according to the first embodiment.
- the resonance frequency determination unit 22 first sets 0 to a counter representing the number of times that the absolute value of the current detected by the detector 17 when the switch elements 14 and 15 are turned off is greater than or equal to a threshold value (step S01). Each time the switch elements 14 and 15 are turned off, the current value detected by the detector 17 is input (step S02).
- the current value is compared with the threshold value, and if the current value is equal to or greater than the threshold value (step S03; YES), 1 is added to the counter (step S04). If the current value is less than the threshold value (step S03; NO), the counter value is maintained. If the current value before M cycles (M is an integer of 2 or more) is greater than or equal to the threshold (step S05; YES), 1 is subtracted from the counter (step S06). If the current value before M cycles (M is an integer of 2 or more) is less than the threshold (step S05; NO), the value of the counter is maintained.
- step S07 The counter value is compared with the specified number of times, and if the counter value is equal to or greater than the specified number of times (step S07; YES), the switching operation of the resonant inverter circuit 1 is stopped (step S08). If the counter value is less than the specified number of times (step S07; NO), the process returns to step S02 and is repeated from the input of the current value.
- FIG. 6 is a flowchart showing an example of the operation of the stop process when the resonance frequency is abnormal according to the second embodiment.
- the resonance frequency determination unit 22 first sets 0 to a counter indicating the number of times that the absolute value of the current detected by the detector 17 when the switch elements 14 and 15 are turned off is equal to or greater than a threshold value (step S11). Each time the switch elements 14 and 15 are turned off, the current value detected by the detector 17 is input (step S12).
- step S13 The current value is compared with the threshold value, and if the current value is equal to or greater than the threshold value (step S13; YES), 1 is added to the counter (step S14). If the current value is less than the threshold value (step S13; NO), the process returns to step S11 and is repeated from resetting the counter (setting 0).
- step S14 After adding 1 to the counter in step S14, the counter value is compared with the specified number of times. If the counter value is equal to or greater than the specified number of times (step S15; YES), the switching operation of the resonant inverter circuit 1 is stopped (step S16). If the counter value is less than the specified number (step S15; NO), the process returns to step S12 without repeating the counter and repeats from the input of the current value.
- the configuration of the resonance frequency determination unit 22 can be simplified.
- a power conversion device including an upper arm (switch element 14) and a lower arm (switch element 15) in which a leg generates one single-phase alternating current will be described as an example. did.
- the configuration of the embodiment can also be applied to a power conversion device that includes three legs and generates a three-phase alternating current.
- the power conversion device may be configured to use, for the switch elements 14 and 15, a switch element formed of a wide band gap semiconductor having a larger band gap than silicon.
- the wide band gap semiconductor is, for example, silicon carbide, a gallium nitride material, or diamond.
- a switch element formed of a wide band gap semiconductor has high withstand voltage and allowable current density. Therefore, the switch element can be miniaturized, and the semiconductor module incorporating the switch element can be miniaturized by using the miniaturized switch element.
- the wide band gap semiconductor has high heat resistance, it is possible to reduce the size of the heat sink fins and the air cooling of the water-cooled part, thereby further reducing the size of the semiconductor module. Furthermore, since the power loss is low, it is possible to increase the efficiency of the switch element, and consequently to increase the efficiency of the semiconductor module.
- both the switch elements 14 and 15 are formed of a wide band gap semiconductor, but either one of the elements may be formed of a wide band gap semiconductor. Even in this case, the effect described in the first embodiment can be obtained.
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Abstract
Description
図1は、本発明の実施の形態に係る電力変換装置の構成例を示すブロック図である。電力変換装置は、共振インバータ回路1および制御装置2から構成される。共振インバータ回路1は、直流電源3および接地4に接続し、直流電源3から直流電力が供給される。制御装置2は、共振インバータ回路1を作動させて、共振インバータ回路1で直流電圧を交流電圧に変換し、負荷回路5に交流電力を供給する。
実施の形態2では、スイッチ素子14、15をターンオフするごとに検出器17で検出した電流の絶対値が閾値以上である回数が、連続して規定回数以上の場合に、共振周波数異常であると判定する。すなわち、実施の形態1の構成で、判定する期間のM周期(Mは2以上の整数)と、共振周波数が異常であると判定する規定回数N(Nは2以上の整数)が等しい、M=N≧2の場合である。
Claims (4)
- 2つ以上のスイッチ素子を含む共振インバータ回路と、
前記スイッチ素子の出力電流を検出する検出器と、
前記スイッチ素子のスイッチング周期の2倍以上の定めた期間に、前記スイッチ素子をターンオフする時に前記検出器で検出した電流の絶対値が閾値以上である回数が、2以上の定めた回数以上の場合に、前記共振インバータ回路の共振周波数異常と判定する共振判定部と、
前記共振判定部で前記共振インバータ回路の共振周波数異常と判定した場合に、前記共振インバータ回路のスイッチング動作を停止させる制御部と、
を備える電力変換装置。 - 前記共振判定部は、前記スイッチ素子をターンオフするごとに前記検出器で検出した電流の絶対値が、前記閾値以上である状態が連続して定めた回数継続した場合に、前記共振インバータ回路の共振周波数異常と判定する、請求項1に記載の電力変換装置。
- 前記スイッチ素子は、ワイドバンドギャップ半導体によって形成されている、請求項1または2に記載の電力変換装置。
- 前記ワイドバンドギャップ半導体は、炭化ケイ素、窒化ガリウム系材料またはダイヤモンドである請求項3に記載の電力変換装置。
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PCT/JP2013/081934 WO2015079518A1 (ja) | 2013-11-27 | 2013-11-27 | 電力変換装置 |
US15/027,874 US9853568B2 (en) | 2013-11-27 | 2013-11-27 | Power conversion device |
DE112013007649.7T DE112013007649T5 (de) | 2013-11-27 | 2013-11-27 | Stromumwandlungsvorrichtung |
AU2013406393A AU2013406393B2 (en) | 2013-11-27 | 2013-11-27 | Power conversion device |
CA2931657A CA2931657A1 (en) | 2013-11-27 | 2013-11-27 | Power conversion device |
JP2015550254A JP6067136B2 (ja) | 2013-11-27 | 2013-11-27 | 電力変換装置 |
CN201380081225.8A CN105765838B (zh) | 2013-11-27 | 2013-11-27 | 功率转换装置 |
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PCT/JP2013/081934 WO2015079518A1 (ja) | 2013-11-27 | 2013-11-27 | 電力変換装置 |
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JP (1) | JP6067136B2 (ja) |
CN (1) | CN105765838B (ja) |
AU (1) | AU2013406393B2 (ja) |
CA (1) | CA2931657A1 (ja) |
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US9729085B2 (en) * | 2014-09-26 | 2017-08-08 | Majid Pahlevaninezhad | Observer-based control system for grid-connected DC/AC converters with LCL-filter |
JP6663813B2 (ja) * | 2016-07-15 | 2020-03-13 | 矢崎総業株式会社 | 半導体スイッチ制御装置 |
CN108668386B (zh) * | 2017-03-29 | 2021-08-31 | 广东美的生活电器制造有限公司 | 电加热设备、电加热控制电路、电加热控制方法及装置 |
CN108736727B (zh) * | 2017-04-14 | 2020-02-21 | 台达电子工业股份有限公司 | 电源转换器及其控制方法 |
JP6389945B1 (ja) * | 2017-11-01 | 2018-09-12 | 高周波熱錬株式会社 | インバータ用負荷異常検出回路 |
JP7005286B2 (ja) | 2017-11-01 | 2022-01-21 | 株式会社東芝 | 電気車用電源装置 |
US10666147B1 (en) * | 2018-11-14 | 2020-05-26 | Navitas Semiconductor, Inc. | Resonant converter control based on zero current detection |
JP2022121050A (ja) * | 2021-02-08 | 2022-08-19 | 株式会社東芝 | 電力変換装置 |
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US9008528B2 (en) * | 2011-12-13 | 2015-04-14 | Samsung Electronics Co., Ltd. | Induction heating fusing device and image forming apparatus |
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2013
- 2013-11-27 DE DE112013007649.7T patent/DE112013007649T5/de not_active Withdrawn
- 2013-11-27 CN CN201380081225.8A patent/CN105765838B/zh active Active
- 2013-11-27 US US15/027,874 patent/US9853568B2/en active Active
- 2013-11-27 AU AU2013406393A patent/AU2013406393B2/en not_active Ceased
- 2013-11-27 JP JP2015550254A patent/JP6067136B2/ja not_active Expired - Fee Related
- 2013-11-27 WO PCT/JP2013/081934 patent/WO2015079518A1/ja active Application Filing
- 2013-11-27 CA CA2931657A patent/CA2931657A1/en not_active Abandoned
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JPH11215826A (ja) * | 1998-01-21 | 1999-08-06 | Hitachi Ltd | 自励発振型電流共振コンバータ |
JP2005071841A (ja) * | 2003-08-26 | 2005-03-17 | Matsushita Electric Works Ltd | 電源装置 |
JP2012248292A (ja) * | 2011-05-25 | 2012-12-13 | Panasonic Corp | 誘導加熱装置 |
Also Published As
Publication number | Publication date |
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DE112013007649T5 (de) | 2016-10-06 |
CN105765838A (zh) | 2016-07-13 |
JP6067136B2 (ja) | 2017-01-25 |
AU2013406393B2 (en) | 2017-02-23 |
JPWO2015079518A1 (ja) | 2017-03-16 |
CN105765838B (zh) | 2018-10-02 |
US9853568B2 (en) | 2017-12-26 |
CA2931657A1 (en) | 2015-06-04 |
AU2013406393A1 (en) | 2016-04-21 |
US20160276955A1 (en) | 2016-09-22 |
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