WO2015064131A1 - コンバータの制御装置及び制御方法並びに空気調和機 - Google Patents
コンバータの制御装置及び制御方法並びに空気調和機 Download PDFInfo
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- WO2015064131A1 WO2015064131A1 PCT/JP2014/063071 JP2014063071W WO2015064131A1 WO 2015064131 A1 WO2015064131 A1 WO 2015064131A1 JP 2014063071 W JP2014063071 W JP 2014063071W WO 2015064131 A1 WO2015064131 A1 WO 2015064131A1
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- phase correction
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0009—Devices or circuits for detecting current in a converter
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the present invention relates to a control device and a control method for a converter, and an air conditioner including the same.
- an apparatus disclosed in Patent Document 1 is known as a converter apparatus.
- the converter device disclosed in Patent Document 1 is a device that converts AC power into DC power, and for the purpose of reducing harmonic components and improving power factor, two switching circuits comprising a basic switching circuit and an additional switching circuit. have. When the load is small, only the basic switching circuit is operated, and when the load is large, both the basic switching circuit and the additional switching circuit are operated.
- the converter device disclosed in Patent Document 1 includes a comparison circuit that determines whether or not the current output from the rectifier is smaller than the reference current, and the voltage across the smoothing capacitor is larger than the reference voltage. And a control signal switch that is turned on / off in response to the output signals from the two comparison circuits.
- the control signal switch is a switch for disconnecting the connection between the additional switching circuit and the converter device.
- the converter device disclosed in Patent Document 1 has a large change in the amount of harmonic suppression with respect to the phase change, as shown in FIG. That is, when the phase is between -1.0 and 0, the minimum harmonic margin is 0 or more, and a predetermined harmonic standard can be satisfied. However, in the region where the phase exceeds +0.5, the minimum harmonic margin is less than 0, and the predetermined harmonic standard cannot be satisfied. This is because when the phase is shifted, as shown in FIG. 13, the distortion of the input current at the zero cross point increases.
- Patent Document 1 cannot follow the change in the harmonic suppression amount with respect to the phase change as shown in FIG. 12, and simultaneously achieves the harmonic standard and the power factor improvement. It was difficult to realize. Further, if a high-precision zero-cross point detection circuit or phase detection circuit is used, it is possible to simultaneously realize harmonic reduction and power factor improvement, but it is expensive and not practical.
- the present invention has been made in view of such circumstances, and without using an expensive phase detection circuit or the like, a harmonic standard (for example, IEC61000-3-2 for an air conditioner) is used.
- An object of the present invention is to provide a converter device and an air conditioner capable of improving the power factor while being satisfied.
- a first aspect of the present invention is a converter control device in which a plurality of power factor correction circuits having an inductor, a switching element, and a diode are connected in parallel, and calculates a phase based on a zero-cross point of an input voltage
- a phase calculating unit that sets a phase correction value using the input current detection signal, and a phase correction value that is set by the first phase correcting unit.
- a drive signal generation unit that generates a drive signal for driving the switching element using the corrected phase, and the first phase correction unit receives an input from the input current detection signal.
- a waveform rate calculating means for acquiring a maximum current value and an average input current value, and calculating a waveform rate obtained by dividing the maximum input current value by the average input current value;
- One of the shape ratios is set as a target waveform ratio, the first waveform information that associates the target waveform ratio and the input current in advance is held, and the target waveform ratio that acquires the target waveform ratio according to the input current value from the first information
- It is a control device for a converter including an acquisition unit and a first phase correction value setting unit that sets a phase correction value for bringing the waveform rate close to the target waveform rate.
- the maximum input current value and the average input current value are obtained from the input current detection signal, the waveform rate is calculated from these values, and the phase correction value is set such that the waveform rate becomes the target waveform rate.
- a drive signal for setting and driving the switching element is generated using the phase correction value.
- the control device of the converter selects a single mode in which one power factor correction circuit is operated when the input current value is equal to or less than a predetermined current value, and the input current value exceeds the predetermined current value.
- Mode switching means for selecting a double mode for operating at least two power factor circuits, the first phase correction means for setting a phase correction value for double mode, and a second for setting a phase correction value for single mode A phase correction unit, wherein the second phase correction unit uses any one of the phase correction values having a power factor of a predetermined value or more as a target phase correction value, and associates the target phase correction value and the input current in advance.
- a target phase correction value acquisition unit that holds the second information and acquires a target phase correction value corresponding to the input current value from the second information, and a phase correction value that matches the target phase correction value is set.
- Phase correction value setting means, and the drive signal generation means uses the phase correction value set by the second phase correction means when the single mode is selected by the mode switching means.
- a drive signal may be generated, and when the double mode is selected by the mode switching unit, the drive signal may be generated using a phase correction value set by the first phase correction unit.
- the single mode for operating one power factor correction circuit is selected, so that it is possible to reduce the loss due to switching.
- the drive signal is generated using the phase correction value set by the second phase correction unit for the single mode, so that an appropriate phase correction value corresponding to the mode is used. It becomes possible to perform switching control using the.
- the 2nd mode of the present invention is a converter device provided with the above-mentioned control device.
- a third aspect of the present invention is a motor drive device including the converter device.
- the 4th aspect of this invention is an air conditioner provided with the said motor drive device.
- a fifth aspect of the present invention is a converter control method in which a plurality of power factor correction circuits having an inductor, a switching element, and a diode are connected in parallel, and calculates a phase based on a zero cross point of an input voltage.
- a drive signal generation process for generating a drive signal for driving the switching element using the corrected phase
- the phase correction process includes an input current maximum value and an input current from the input current detection signal.
- the average value is obtained, and the target waveform is either a waveform rate calculation process for calculating a waveform rate obtained by dividing the maximum input current value by the average input current value, or a waveform rate at which the power factor exceeds a predetermined value.
- the target waveform rate and the input current are stored in advance, and the target waveform rate acquisition process for acquiring the target waveform rate according to the input current from the information, and the waveform rate close to the target waveform rate And a phase correction value setting process for setting a phase correction value for the converter.
- a sixth aspect of the present invention is a converter control method in which a plurality of power factor correction circuits having an inductor, a switching element, and a diode are connected in parallel, and calculates a phase based on a zero-cross point of an input voltage
- a drive signal generation process for generating a drive signal for driving the switching element using the corrected phase, and the phase correction process includes any of the phase correction values for which the power factor takes a predetermined value or more.
- the target phase correction value is obtained by storing information in which the target phase correction value is associated with the input current in advance, and acquiring the target phase correction value corresponding to the input current value from the information.
- Degree is a control method of the converter and a phase correction value setting process of setting a phase correction value as to match the target phase correction value.
- the power factor can be improved while satisfying the harmonic standard without using an expensive phase detection circuit or the like.
- the application destination of the converter device of the present invention is not limited to an air conditioner, and can be widely applied to devices that convert AC power from an AC power source into DC power.
- FIG. 1 is a diagram showing a schematic configuration of a motor drive device according to a first embodiment of the present invention.
- the motor drive device 1 includes a converter device 2 that converts AC power from an AC power source 4 into DC power and outputs the DC power, and converts DC power output from the converter device 2 into three-phase AC power.
- the inverter device 3 that outputs to the compressor motor (load) 20 is provided as a main configuration.
- the converter device 2 includes a rectifier circuit 5 that converts AC power input from the AC power source 4 into DC power, a smoothing capacitor 12 that is connected in parallel to the rectifier circuit 5 on the DC output side of the rectifier circuit 5, and a rectifier circuit. 5 and the smoothing capacitor 12, a plurality of power factor correction circuits 10a and 10b provided in parallel with each other, and a converter control unit (converter control device) 15 for controlling the power factor correction circuits 10a and 10b are mainly used. It is prepared as a simple configuration. In the present embodiment, the case where two power factor correction circuits 10a and 10b are provided is illustrated, but the number of installations is not particularly limited, and three or more may be provided.
- the power factor correction circuit 10a is connected in series to an inductor (inductive element) 6a provided in series on the positive electrode bus Lp connecting the rectifier circuit 5 and the smoothing capacitor 12, and to the current output side of the inductor 6a.
- One end of the diode 7 a is connected between the inductor 6 a and the diode 7 a, and the switching element 8 a is connected in parallel with the rectifier circuit 5.
- the power factor correction circuit 10b includes an inductor 6b provided in series on the positive electrode bus Lp connecting the rectifier circuit 5 and the smoothing capacitor 12, and a diode 7b connected in series on the current output side of the inductor 6b.
- a switching element 8b having one end connected between the inductor 6b and the diode 7b and connected in parallel with the rectifier circuit 5.
- switching elements 8a and 8b examples include a field effect transistor (FET), an IGBT (Insulated Gate Bipolar Transistor), and the like.
- FET field effect transistor
- IGBT Insulated Gate Bipolar Transistor
- Switching elements 8a and 8b and diodes 7a and 7b may be elements using silicon carbide (SiC).
- SiC silicon carbide
- the AC power supply 4 is provided with a zero cross detector 21 for detecting a zero cross point.
- the zero cross signal from the zero cross detection unit 21 is output to the converter control unit 15.
- An input current detector 22 for detecting an input current input from the AC power supply 4 to the rectifier circuit 5 is provided.
- FIG. 2 shows a configuration example of the input current detection unit 22. As shown in FIG. 2, the input current detection unit 22 is configured to be able to detect the waveform of the input current.
- the input current detection signal detected by the input current detection unit 22 is output to the converter control unit 15.
- the inverter device 3 includes a bridge circuit 18 including six switching elements, and an inverter control unit 19 that controls opening and closing of the switching elements in the bridge circuit 18.
- the inverter control unit 19 generates a gate drive signal Spwm for each switching element based on a required rotation speed command input from a host device (not shown), and supplies the gate drive signal Spwm to the bridge circuit 18.
- Specific examples of the inverter control include vector control, sensorless vector control, V / F control, overmodulation control, and 1 pulse control.
- the converter control unit 15 is, for example, an MPU (Micro Processing Unit), and includes a computer-readable recording medium in which a program for executing each process described below is recorded. The following processing is realized by reading the program recorded in the main memory device such as a RAM and executing it.
- the computer-readable recording medium include a magnetic disk, a magneto-optical disk, and a semiconductor memory.
- FIG. 3 is a functional block diagram of the converter control unit 15.
- the converter control unit 15 includes a phase calculation unit (phase calculation means unit) 30, a phase correction unit (first phase correction unit) 40, and a drive signal generation unit (drive signal generation unit) 50.
- phase calculation unit phase calculation means unit
- phase correction unit first phase correction unit
- drive signal generation unit drive signal generation unit
- the phase calculation unit 30 calculates and outputs the phase ⁇ based on the zero cross signal detected by the zero cross detection unit 21.
- the phase correction unit 40 calculates a phase correction value using the input current detection signal detected by the input current detection unit 22.
- the phase correction unit 40 includes a waveform rate calculation unit (waveform rate calculation unit) 41, a target waveform rate acquisition unit (target waveform rate acquisition unit) 42, and a phase correction value setting unit (first phase correction value). Setting means) 43 as a main component.
- the waveform rate calculation unit 41 obtains the input current maximum value and the input current average value from the input current detection signal, and calculates the waveform rate by dividing the input current maximum value by the input current average value.
- the target waveform rate acquisition unit 42 has a target waveform rate table (first information) in which any one of the waveform rates at which the power factor takes a predetermined value or more is set as the target waveform rate and the target waveform rate and the input current are associated in advance.
- the target waveform rate corresponding to the input current is acquired from the target waveform rate table.
- FIG. 4 shows an example of the target waveform rate table. In FIG. 4, the horizontal axis represents the input current (effective value), and the vertical axis represents the target waveform rate.
- This target waveform rate table is created based on, for example, data obtained by performing tests and simulations in advance.
- phase angle-power factor characteristic as shown in FIG. 5 and a waveform rate-phase angle characteristic as shown in FIG. 6 are obtained.
- any phase angle having a power factor equal to or greater than a predetermined value for example, a phase angle at which the maximum power factor is taken is specified as a representative phase angle.
- the waveform rate at the time of taking is obtained from the phase angle-waveform rate characteristic shown in FIG.
- the waveform rate obtained in this way is set as the target waveform rate for the input current (for example, effective value).
- a target waveform rate table in which the input current and the target waveform rate are associated as shown in FIG. 4 is created.
- the phase correction value setting unit 43 sets a phase correction value for bringing the waveform rate calculated by the waveform rate calculation unit 41 closer to the target waveform rate acquired by the target waveform rate acquisition unit 42. For example, as shown in FIG. 7, the phase correction value setting unit 43 calculates a difference between the target waveform rate and the actual waveform rate (step SA1), and the difference is within a predetermined allowable range (eg, ⁇ 0.5 °). If it is within the range of + 0.5 ° or less), the target phase correction value is set to zero (step SA2). If the difference exceeds the upper limit value of the predetermined allowable range, the target phase correction value is increased by +1. If the difference is less than the lower limit value of the predetermined allowable range (step SA3), the target phase correction value is set to -1 ° (step SA4).
- a predetermined allowable range eg, ⁇ 0.5 °
- step SA5 the difference between the target phase correction value set in steps SA2 to SA4 and the previous value of the phase correction value (that is, the phase correction value determined before one sampling period) is calculated (step SA5).
- step SA6 when the difference is zero, the phase correction value is set to zero (step SA6), when the difference is larger than 0, the phase correction value is set to + 1 ° (step SA7), and when the difference is less than zero.
- step SA8 sets the phase correction value to -1 ° (step SA8), and outputs the set phase correction value to the drive signal generator 50 (step SA9).
- the drive signal generation unit 50 corrects the phase ⁇ calculated by the phase calculation unit 30 using the phase correction value calculated by the phase correction unit 40, and drives the switching elements 8a and 8b using the corrected phase.
- Drive signals Sg1 and Sg2 are generated respectively.
- the phase ⁇ is corrected by adding the phase correction value ⁇ to the phase ⁇ , a voltage waveform is generated based on the corrected phase and the modulation rate command, and the voltage waveform and the carrier signal are compared.
- the drive signals Sg1 and Sg2 are generated.
- the drive signals Sg1 and Sg2 are provided with a dead time so that there is no time to turn them on at the same time.
- the drive signals Sg1 and Sg2 generated by the drive signal generation unit 50 are given to the gate drive circuits of the switching elements 8a and 8b, whereby the on / off of the switching elements 8a and 8b is controlled.
- the zero cross point of the input power supply 4 is detected by the zero cross detection unit 21, and a zero cross signal is output to the converter control unit 15. Further, the input current detection unit 22 detects the input current, and an input current detection signal is output to the converter control unit 15.
- the phase calculation unit 30 calculates the phase ⁇ based on the zero cross signal from the zero cross detection unit 21, and the phase ⁇ is output to the drive signal generation unit 50.
- the waveform rate calculation unit 41 obtains the input current maximum value and the input current average value from the input current detection signal detected by the input current detection unit 22, and uses them to calculate the waveform rate.
- the target waveform rate acquisition unit 42 acquires the target waveform rate corresponding to the input current effective value of the input current detection signal from the target waveform rate table as shown in FIG.
- phase correction value setting unit 43 a phase correction value for bringing the waveform rate calculated by the waveform rate calculation unit 41 closer to the target waveform rate acquired by the target waveform rate acquisition unit 42 in accordance with the procedure of FIG.
- the phase correction value is set and output to the drive signal generator 50.
- the phase ⁇ calculated by the phase correction unit 40 is added to the phase ⁇ calculated by the phase calculation unit 30, thereby correcting the phase ⁇ and using the corrected phase.
- drive signals Sg1 and Sg2 for driving the switching elements 8a and 8b are generated.
- the drive signals Sg1 and Sg2 generated by the drive signal generation unit 50 are given to the gate drive circuits of the switching elements 8a and 8b, whereby the on / off of the switching elements 8a and 8b is controlled.
- the input current maximum value and the input current average value are acquired from the input current detection signal, the waveform rate is calculated from these values, A phase correction value is set such that the waveform rate becomes the target waveform rate, and a drive signal for driving the switching elements 8a and 8b is generated using the phase correction value.
- the phase correction value is determined using the waveform rate, it is possible to set an appropriate phase correction value in consideration of the actual waveform situation. As a result, harmonics can be reduced without using a highly accurate phase detection circuit, and the harmonic standards can be satisfied.
- the target waveform rate is a waveform rate at which the power factor takes a predetermined value or more, the power factor can be improved at the same time.
- FIG. 8 is a functional block diagram of the converter control unit 15 ′ of the converter device according to the present embodiment.
- the converter control unit 15 ′ includes a mode switching unit (mode switching unit) 60, a first phase correction unit (first phase correction unit) 46, and a second phase correction unit (second phase correction unit).
- Means 47 and an output switching unit 48 are different from the converter control unit 15 in the first embodiment described above.
- differences from the converter control unit 15 according to the first embodiment will be mainly described, and descriptions of common points will be omitted.
- the mode switching unit 60 selects a single mode in which one power factor correction circuit 10a is operated when the input current effective value is equal to or less than a predetermined current value, and at least when the input current effective value exceeds the predetermined current value A double mode for operating the two power factor correction circuits 10a and 10b is selected.
- the single mode is selected by the mode switching unit 60, for example, the drive signal Sg1 described above is output only from the converter control unit 15 ′ to the gate drive device (not shown) of the switching element 8a, and the gate of the switching element 8b.
- a drive signal Sg2 that maintains OFF is output to the drive device (not shown).
- the first phase correction unit 46 sets a phase correction value for double mode, and has the same configuration and function as the phase correction unit 40 according to the first embodiment described above.
- the second phase correction unit 47 sets a single mode phase correction value, and includes a target phase correction value acquisition unit (target phase correction value acquisition unit) 71 and a phase correction value setting unit (second phase correction value). Setting means) 72 as a main component.
- the target phase correction value acquisition unit 71 sets any one of the phase correction values at which the power factor takes a predetermined value or more as the target phase correction value, and associates the target phase correction value and the input current in advance with the target phase correction value table (first step). 2), and a target phase correction value corresponding to the input current is acquired from this target phase correction value table.
- FIG. 9 shows an example of the target phase correction value table.
- the horizontal axis represents the input current
- the vertical axis represents the target phase correction value.
- This target phase correction value table is created based on, for example, data obtained by performing tests and simulations in advance.
- the phase correction value setting unit 72 sets the phase correction value based on the target phase correction value acquired by the target phase correction value acquisition unit 71. For example, as shown in FIG. 10, the phase correction value setting unit 72 calculates the difference between the target phase correction value and the previous value of the phase correction value (step SB1), and if the difference is zero, the phase correction value is set. Set to zero (step SB2), if the difference is greater than 0, the phase correction value is set to + 1 ° (step SB3), and if the difference is less than 0, the phase correction value is set to ⁇ 1 ° (step SB4). ), And outputs the set phase correction value (step SB5).
- the output switching unit 48 When the double mode is selected by the mode switching unit 60, the output switching unit 48 outputs the phase correction value output from the first phase correcting unit 46 to the drive signal generating unit 50, and the single mode is selected. If so, the phase correction value output from the second phase correction unit 47 is output to the drive signal generation unit 50.
- the drive signal generation unit 50 corrects the phase ⁇ calculated by the phase calculation unit 30 using the phase correction value set by the first phase correction unit 46.
- Drive signals Sg1 and Sg2 for driving the switching elements 8a and 8b are respectively generated using the corrected phase.
- the drive signal generation unit 50 corrects the phase ⁇ calculated by the phase calculation unit 30 using the phase correction value set by the second phase correction unit 47, A drive signal Sg1 for driving the switching element 8a is generated using the corrected phase.
- the single mode for operating one power factor correction circuit 10a is selected. Therefore, it is possible to reduce loss due to switching.
- the phase ⁇ calculated by the phase calculation unit 30 is corrected using the phase correction value set by the second phase correction unit 47 for single mode. Switching control using an appropriate phase correction value according to the mode can be performed.
- the power factor correction circuits 10a and 10b are provided closer to the inverter device than the rectifier circuit 5.
- the power factor correction circuits 10a and 10b are not limited to the above-described configuration, and are also installed positions.
- power factor correction circuits 10a ′ and 10b ′ may be provided between the AC power supply 4 and the rectifier circuit 5 ′.
- the diode 7b is connected so that the current flows in both directions.
- the converter control units 15 and 15 ′ in the first or second embodiment can also be applied to the converter device 2 ′ having such power factor correction circuits 10a ′ and 10b ′.
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Abstract
Description
本発明の第3態様は、上記コンバータ装置を備えるモータ駆動装置である。
本発明の第4態様は、上記モータ駆動装置を備える空気調和機である。
本発明の第5態様は、インダクタと、スイッチング素子と、ダイオードとを有する複数の力率改善回路が並列に接続されたコンバータの制御方法であって、入力電圧のゼロクロス点に基づいて位相を演算する位相演算過程と、入力電流検出信号を用いて、位相補正値を演算する位相補正過程と、前記位相演算過程で演算された位相を前記位相補正過程で演算された位相補正値を用いて補正し、補正後の位相を用いて前記スイッチング素子を駆動するための駆動信号を生成する駆動信号生成過程とを有し、前記位相補正過程は、前記入力電流検出信号から入力電流最大値と入力電流平均値とを取得し、該入力電流最大値を前記入力電流平均値で除算した波形率を算出する波形率算出過程と、力率が所定値以上をとる波形率のいずれかを目標波形率とし、該目標波形率と入力電流とを予め関連付けた情報を保有し、該情報から入力電流に応じた目標波形率を取得する目標波形率取得過程と、前記波形率を前記目標波形率に近づけるための位相補正値を設定する位相補正値設定過程とを備えるコンバータの制御方法である。
図1は、本発明の第1実施形態に係るモータ駆動装置の概略構成を示した図である。図1に示すように、モータ駆動装置1は、交流電源4からの交流電力を直流電力に変換して出力するコンバータ装置2と、コンバータ装置2から出力された直流電力を三相交流電力に変換して圧縮機モータ(負荷)20に出力するインバータ装置3とを主な構成として備えている。
同様に、力率改善回路10bは、整流回路5と平滑コンデンサ12とを接続する正極母線Lpに、直列的に設けられたインダクタ6bと、インダクタ6bの電流出力側に直列に接続されるダイオード7bと、インダクタ6bとダイオード7bとの間に一端が接続され、かつ、整流回路5と並列に接続されたスイッチング素子8bとを有する。
また、スイッチング素子8a、8b、ダイオード7a,7bは、炭化シリコン(SiC)を用いた素子であってもよい。このように、炭化シリコンを用いた半導体を利用することにより、スイッチング特性やオン損失特性を向上させることが可能となる。
位相補正部40は、入力電流検出部22によって検出された入力電流検出信号を用いて位相補正値を演算する。具体的には、位相補正部40は、波形率算出部(波形率算出手段)41と、目標波形率取得部(目標波形率取得手段)42と、位相補正値設定部(第1位相補正値設定手段)43とを主な構成として備えている。
波形率算出部41は、入力電流検出信号から入力電流最大値と入力電流平均値とを取得し、入力電流最大値を入力電流平均値で除算することにより、波形率を算出する。
そして、上記手順を所定範囲における各入力電流値において行うことにより、図4に示すような、入力電流と目標波形率とが関連付けられた目標波形率テーブルが作成される。
この結果、差分がゼロの場合には位相補正値をゼロに(ステップSA6)、差分が0よりも大きい場合には位相補正値を+1°に(ステップSA7)、差分が0未満である場合には位相補正値を-1°に設定し(ステップSA8)、設定した位相補正値を駆動信号生成部50に出力する(ステップSA9)。
具体的には、位相θに位相補正値φを加算することにより位相θを補正し、補正後の位相と変調率指令とに基づいて電圧波形を生成し、該電圧波形とキャリア信号とを比較することにより駆動信号Sg1,Sg2を生成する。なお、駆動信号Sg1、Sg2は同時にオンする時間がないように、デッドタイムが設けられる。
駆動信号生成部50によって生成された駆動信号Sg1、Sg2が各スイッチング素子8a,8bのゲート駆動回路に与えられることにより、スイッチング素子8a、8bのオンオフが制御される。
まず、入力電源4のゼロクロス点がゼロクロス検出部21によって検出され、ゼロクロス信号がコンバータ制御部15に出力される。また、入力電流検出部22によって、入力電流が検出され、入力電流検出信号がコンバータ制御部15に出力される。
位相補正部40では、波形率算出部41において、入力電流検出部22によって検出された入力電流検出信号から入力電流最大値と入力電流平均値とが取得され、これらを用いて波形率が算出される。また、目標波形率取得部42では、入力電流検出信号の入力電流実効値に対応する目標波形率が図3に示したような目標波形率テーブルから取得される。
続いて、位相補正値設定部43において、図7の手順に従って、波形率算出部41によって演算された波形率を目標波形率取得部42によって取得された目標波形率に近づけるための位相補正値が設定され、位相補正値が駆動信号生成部50に出力される。
次に、本発明の第2実施形態に係るコンバータ装置及び空気調和機について説明する。図8は、本実施形態に係るコンバータ装置のコンバータ制御部15´の機能ブロック図を示した図である。図8に示すように、コンバータ制御部15´は、モード切替部(モード切替手段)60と、第1位相補正部(第1位相補正手段)46と、第2位相補正部(第2位相補正手段)47と、出力切替部48とを備える点で、上述した第1実施形態におけるコンバータ制御部15と異なる。
以下、第1実施形態に係るコンバータ制御部15と異なる点について主に説明し、共通の点については説明を省略する。
第2位相補正部47は、シングルモード用の位相補正値を設定するものであり、目標位相補正値取得部(目標位相補正値取得手段)71と、位相補正値設定部(第2位相補正値設定手段)72とを主な構成として備えている。目標位相補正値取得部71は、力率が所定値以上をとる位相補正値のいずれかを目標位相補正値とし、該目標位相補正値と入力電流とを予め関連付けた目標位相補正値テーブル(第2情報)を保有し、この目標位相補正値テーブルから入力電流に応じた目標位相補正値を取得する。
これにより、ダブルモードが選択されている場合には、駆動信号生成部50において、位相演算部30によって演算された位相θが第1位相補正部46によって設定された位相補正値を用いて補正され、補正後の位相を用いて、スイッチング素子8a、8bを駆動するための駆動信号Sg1、Sg2がそれぞれ生成される。また、シングルモードが選択されている場合には、駆動信号生成部50において、位相演算部30によって演算された位相θが第2位相補正部47によって設定された位相補正値を用いて補正され、補正後の位相を用いて、スイッチング素子8aを駆動するための駆動信号Sg1が生成される。
2,2´ コンバータ装置
3 インバータ装置
4 交流電源
5 整流回路
6a,6b インダクタ
7a,7b ダイオード
8a,8b スイッチング素子
10a,10b 力率改善回路
12 平滑コンデンサ
15,15´ コンバータ制御部
21 ゼロクロス検出部
22 入力電流検出部
30 位相演算部
40 位相補正部
41 波形率算出部
42 目標波形率取得部
43 位相補正値設定部
46 第1位相補正部
47 第2位相補正部
48 出力切替部
71 目標位相補正値取得部
72 位相補正値設定部
50 駆動信号生成部
60 モード切替部
Lp 正極母線
L1 電力線
Claims (7)
- インダクタと、スイッチング素子と、ダイオードとを有する複数の力率改善回路が並列に接続されたコンバータの制御装置であって、
入力電圧のゼロクロス点に基づいて位相を演算する位相演算手段と、
入力電流検出信号を用いて、位相補正値を設定する第1位相補正手段と、
前記位相演算手段によって演算された位相を前記第1位相補正手段によって設定された位相補正値を用いて補正し、補正後の位相を用いて前記スイッチング素子を駆動するための駆動信号を生成する駆動信号生成手段と
を有し、
前記第1位相補正手段は、
前記入力電流検出信号から入力電流最大値と入力電流平均値とを取得し、該入力電流最大値を前記入力電流平均値で除算した波形率を算出する波形率算出手段と、
力率が所定値以上をとる波形率のいずれかを目標波形率とし、該目標波形率と入力電流とを予め関連付けた第1情報を保有し、該第1情報から入力電流値に応じた目標波形率を取得する目標波形率取得手段と、
前記波形率を前記目標波形率に近づけるための位相補正値を設定する第1位相補正値設定手段と
を具備するコンバータの制御装置。 - 前記入力電流値が所定の電流値以下の場合に1つの前記力率改善回路を動作させるシングルモードを選択し、前記入力電流値が前記所定の電流値を超える場合に少なくとも2つの前記力率回路を動作させるダブルモードを選択するモード切替手段と、
ダブルモード用の位相補正値を設定する前記第1位相補正手段と、
シングルモード用の位相補正値を設定する第2位相補正手段と
を有し、
前記第2位相補正手段は、
力率が所定値以上をとる位相補正値のいずれかを目標位相補正値とし、該目標位相補正値と入力電流とを予め関連付けた第2情報を保有し、該第2情報から入力電流値に応じた目標位相補正値を取得する目標位相補正値取得手段と、
前記目標位相補正値に一致するような位相補正値を設定する第2位相補正値設定手段と
を具備し、
前記駆動信号生成手段は、前記モード切替手段により前記シングルモードが選択されている場合に、前記第2位相補正手段によって設定された位相補正値を用いて前記駆動信号を生成し、前記モード切替手段により前記ダブルモードが選択されている場合に、前記第1位相補正手段によって設定された位相補正値を用いて前記駆動信号を生成する請求項1に記載のコンバータの制御装置。 - 請求項1または請求項2に記載の制御装置を備えるコンバータ装置。
- 請求項3に記載のコンバータ装置を備えるモータ駆動装置。
- 請求項4に記載のモータ駆動装置を備える空気調和機。
- インダクタと、スイッチング素子と、ダイオードとを有する複数の力率改善回路が並列に接続されたコンバータの制御方法であって、
入力電圧のゼロクロス点に基づいて位相を演算する位相演算過程と、
入力電流検出信号を用いて、位相補正値を演算する位相補正過程と、
前記位相演算過程で演算された位相を前記位相補正過程で演算された位相補正値を用いて補正し、補正後の位相を用いて前記スイッチング素子を駆動するための駆動信号を生成する駆動信号生成過程と
を有し、
前記位相補正過程は、
前記入力電流検出信号から入力電流最大値と入力電流平均値とを取得し、該入力電流最大値を前記入力電流平均値で除算した波形率を算出する波形率算出過程と、
力率が所定値以上をとる波形率のいずれかを目標波形率とし、該目標波形率と入力電流とを予め関連付けた情報を保有し、該情報から入力電流に応じた目標波形率を取得する目標波形率取得過程と、
前記波形率を前記目標波形率に近づけるための位相補正値を設定する位相補正値設定過程と
を備えるコンバータの制御方法。 - インダクタと、スイッチング素子と、ダイオードとを有する複数の力率改善回路が並列に接続されたコンバータの制御方法であって、
入力電圧のゼロクロス点に基づいて位相を演算する位相演算過程と、
入力電流検出信号を用いて、位相補正値を演算する位相補正過程と、
前記位相演算過程で演算された位相を前記位相補正過程で演算された位相補正値を用いて補正し、補正後の位相を用いて前記スイッチング素子を駆動するための駆動信号を生成する駆動信号生成過程と
を有し、
前記位相補正過程は、
力率が所定値以上をとる位相補正値のいずれかを目標位相補正値とし、該目標位相補正値と入力電流とを予め関連付けた情報を保有し、該情報から入力電流値に応じた目標位相補正値を取得する目標位相補正値取得過程と、
前記目標位相補正値に一致するような位相補正値を設定する位相補正値設定過程と
を備えるコンバータの制御方法。
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JP2010233439A (ja) | 2009-03-03 | 2010-10-14 | Toshiba Corp | 電源制御装置、及びそれを用いた電源装置 |
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