WO2014208261A1 - ボルテージレギュレータ - Google Patents
ボルテージレギュレータ Download PDFInfo
- Publication number
- WO2014208261A1 WO2014208261A1 PCT/JP2014/064267 JP2014064267W WO2014208261A1 WO 2014208261 A1 WO2014208261 A1 WO 2014208261A1 JP 2014064267 W JP2014064267 W JP 2014064267W WO 2014208261 A1 WO2014208261 A1 WO 2014208261A1
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- WIPO (PCT)
- Prior art keywords
- voltage
- output
- differential amplifier
- amplifier circuit
- circuit
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Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
-
- G—PHYSICS
- G05—CONTROLLING; REGULATING
- G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
- G05F1/00—Automatic systems in which deviations of an electric quantity from one or more predetermined values are detected at the output of the system and fed back to a device within the system to restore the detected quantity to its predetermined value or values, i.e. retroactive systems
- G05F1/10—Regulating voltage or current
- G05F1/46—Regulating voltage or current wherein the variable actually regulated by the final control device is dc
- G05F1/56—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices
- G05F1/565—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices sensing a condition of the system or its load in addition to means responsive to deviations in the output of the system, e.g. current, voltage, power factor
- G05F1/569—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices sensing a condition of the system or its load in addition to means responsive to deviations in the output of the system, e.g. current, voltage, power factor for protection
- G05F1/573—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices sensing a condition of the system or its load in addition to means responsive to deviations in the output of the system, e.g. current, voltage, power factor for protection with overcurrent detector
-
- G—PHYSICS
- G05—CONTROLLING; REGULATING
- G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
- G05F1/00—Automatic systems in which deviations of an electric quantity from one or more predetermined values are detected at the output of the system and fed back to a device within the system to restore the detected quantity to its predetermined value or values, i.e. retroactive systems
- G05F1/10—Regulating voltage or current
- G05F1/46—Regulating voltage or current wherein the variable actually regulated by the final control device is dc
- G05F1/56—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices
- G05F1/565—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices sensing a condition of the system or its load in addition to means responsive to deviations in the output of the system, e.g. current, voltage, power factor
- G05F1/569—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices sensing a condition of the system or its load in addition to means responsive to deviations in the output of the system, e.g. current, voltage, power factor for protection
- G05F1/571—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices sensing a condition of the system or its load in addition to means responsive to deviations in the output of the system, e.g. current, voltage, power factor for protection with overvoltage detector
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
Definitions
- the present invention relates to a voltage regulator that outputs a constant voltage, and more particularly to an overcurrent protection circuit that protects a circuit by reducing the output current when an overcurrent flows through an output terminal.
- the voltage regulator inputs a high power supply voltage such as a lithium ion secondary battery or battery, and outputs a voltage lower than the power supply voltage to a device such as a microcomputer. If the output terminal of the voltage regulator is short-circuited to the GND voltage (0 V) for some reason, the voltage regulator controls to lower the resistance value of the output transistor, so that a large current flows through the output terminal.
- the voltage regulator requires an overcurrent protection circuit to protect the circuit from a large current flowing through the output terminal.
- FIG. 3 is a block diagram of a conventional voltage regulator.
- the conventional voltage regulator includes a constant voltage control circuit 320 and an overcurrent protection circuit 321.
- the input voltage source 101 is connected between the power supply terminal 10 and the ground terminal 11.
- a load resistor 103 is connected between the output terminal 12 and the ground terminal 11.
- a resistor 111 and an output transistor 102 are connected in series between the power supply terminal 10 and the output terminal 12.
- the constant voltage control circuit 320 will be described.
- the differential amplifier circuit 304 the feedback voltage Vfb obtained by dividing the output voltage Vout by the voltage dividing resistor circuit 306 is input to the inverting input terminal, the reference voltage Vref of the reference voltage circuit 305 is input to the non-inverting input terminal, and the output terminal To output a current I1.
- the NPN transistor 308 and the resistor 307 constitute a common source amplifier circuit.
- the overcurrent protection circuit 321 will be described.
- the voltage Vin of the input voltage source 101 is input to the non-inverting input terminal, and the voltage VR generated in the resistor 111 is input to the inverting input terminal.
- the output voltage of the differential amplifier circuit 312 is input to the non-inverting input terminal, the reference voltage Vref2 of the reference voltage circuit 314 is input to the inverting input terminal, and the current I2 is output.
- Current I2 is mirrored by NPN transistor 315 and NPN transistor 316 to become current I3.
- the collector of the NPN transistor 316 is connected to the output of the differential amplifier circuit 304.
- the output terminal 12 when the output terminal 12 is short-circuited to the ground terminal 11, the feedback voltage Vfb becomes the ground voltage Vss. Therefore, the output voltage Vdrv of the source ground amplifier circuit is lowered, and the output transistor 102 is turned on. As a result, the output current Iout increases. Accordingly, since the voltage VR is lowered due to the voltage drop caused by the resistor 111, the output voltage of the differential amplifier circuit 312 is increased. When the output voltage of the differential amplifier circuit 312 becomes higher than the reference voltage Vref2, the differential amplifier circuit 313 increases the current I2 that flows through the collector of the NPN transistor 315. Therefore, since the current I3 mirrored by the mirror circuit increases, the base current (I1-I3) of the NPN transistor 308 decreases.
- the negative feedback for the output voltage control and the negative feedback for the output current control are operating during the operation of the overcurrent protection circuit. Therefore, if the negative feedback gain of the output current control is larger than the negative feedback gain of the output voltage control, the output voltage Vout is likely to oscillate, and therefore a large-capacity phase compensation circuit is required, which increases the chip area. End up. Further, when the negative feedback gain of the output current control is smaller than the negative feedback gain of the output voltage control, the influence of the negative feedback of the output voltage control is strong, so that the overcurrent protection of the output current Iout is difficult to be effective. there were.
- a voltage regulator including an overcurrent protection circuit includes a first differential amplifier circuit that compares a first reference voltage and a feedback voltage, and an output voltage of the first differential amplifier circuit.
- a constant voltage control circuit having an output transistor controlled by the output, a resistor for measuring an output current, a second differential amplifier circuit for measuring a voltage difference between both ends of the resistor, and a second differential amplifier circuit
- a comparator that compares the output voltage with the second reference voltage
- an overcurrent protection circuit that includes a switch controlled by a detection signal of the comparator, and the second difference is detected when the output current exceeds the overcurrent protection set value.
- the output voltage of the dynamic amplifier circuit is input to the first differential amplifier circuit via a switch, and the control of the output transistor is switched from the control by the constant voltage control circuit to the control by the overcurrent protection circuit.
- the voltage regulator provided with the overcurrent protection circuit of the present invention it is possible to accurately and stably control the output current to the overcurrent protection set value without requiring a phase compensation circuit having a large area element.
- FIG. 1 is a block diagram showing a voltage regulator of this embodiment.
- the voltage regulator of this embodiment includes a constant voltage control circuit 120 and an overcurrent protection circuit 121.
- An input voltage source 101 is connected between the power supply terminal 10 and the ground terminal 11.
- a load resistor 103 is connected between the output terminal 12 and the ground terminal 11.
- a resistor 111 and an output transistor 102 are connected in series between the power supply terminal 10 and the output terminal 12.
- the constant voltage control circuit 120 includes a differential amplifier circuit 104, a reference voltage circuit 105, and a voltage dividing resistor circuit 106.
- the voltage dividing resistor circuit 106 is connected between the output terminal 12 and the ground terminal 11.
- the output terminal of the voltage dividing resistor circuit 106 is connected to the first non-inverting input terminal
- the output terminal of the overcurrent protection circuit 121 is connected to the second non-inverting input terminal
- the reference terminal is connected to the inverting input terminal.
- the voltage circuit 105 is connected and the output terminal is connected to the gate of the output transistor 102.
- the overcurrent protection circuit 121 includes a differential amplifier circuit 112, a comparator 113, a reference voltage circuit 114, switches 115 and 116, and an inverter 117.
- the connection point of the power supply terminal 10 and one terminal of the resistor 111 is connected to the non-inverting input terminal, and the other terminal of the resistor 111 is connected to the inverting input terminal.
- the comparator 113 has the non-inverting input terminal connected to the output terminal of the differential amplifier circuit 112 and the inverting input terminal connected to the reference voltage circuit 114.
- the switch 115 is connected between the output terminal of the differential amplifier circuit 112 and the output terminal of the overcurrent protection circuit 121, and the output terminal of the comparator 113 is connected to the control terminal.
- the switch 116 is connected between the output terminal of the differential amplifier circuit 112 and the ground terminal 11, and the control terminal is connected to the output terminal of the comparator 113 via the inverter 117.
- the voltage dividing resistor circuit 106 outputs a feedback voltage Vfb obtained by dividing the output voltage Vout.
- the reference voltage circuit 105 outputs a reference voltage Vref.
- the differential amplifier circuit 104 amplifies the difference between the feedback voltage Vfb and the reference voltage Vref and outputs the output voltage Vdrv to the gate of the output transistor 102. Thereby, negative feedback for controlling the output voltage is configured, and the output voltage Vout is controlled to the set voltage.
- the differential amplifier circuit 112 amplifies and outputs the voltage difference between both ends of the resistor 111.
- the comparator 113 compares the output voltage of the differential amplifier circuit 112 with the reference voltage Vref2, and outputs the signal Vd.
- the switch 115 is short-circuited when the output voltage of the differential amplifier circuit 112 is higher than the reference voltage Vref2, that is, when the signal Vd is High.
- the switch 116 is turned on when the output voltage of the differential amplifier circuit 112 is lower than the reference voltage Vref2, that is, the signal Vd is Low.
- the output voltage of the differential amplifier circuit 112 is input to the second non-inverting input terminal of the differential amplifier circuit 104 as the output voltage V121 from the output terminal of the overcurrent protection circuit 121 via the switch 115.
- the differential amplifier circuit 104 amplifies the difference between the feedback voltage Vfb and the output voltage V121, and outputs the output voltage Vdrv to the gate of the output transistor 102. Thereby, a negative feedback for controlling the output current is configured, and the output current Iout is controlled to the overcurrent protection setting current.
- FIG. 2 is a circuit diagram showing an example of the differential amplifier circuit 104.
- the differential amplifier circuit 104 includes a first non-inverting input terminal 201, a second non-inverting input terminal 202, an inverting input terminal 203, an output terminal 204, NMOS transistors 205, 206, and 207, and PMOS transistors 208 and 209.
- the gate of the NMOS transistor 205 is connected to the first non-inverting input terminal 201.
- the NMOS transistor 206 has a gate connected to the second non-inverting input terminal 202.
- the NMOS transistor 207 has a gate connected to the inverting input terminal 203.
- Each source is connected to the current source 210 in common.
- the drain of the PMOS transistor 208 is connected to the drains of the NMOS transistor 205 and the NMOS transistor 206 and the input terminal of the inverting amplifier circuit 211.
- the PMOS transistor 209 has a drain and a gate connected in common to the drain of the NMOS transistor 207 and the gate of the PMOS transistor 208.
- the inverting amplifier circuit 211 has an output terminal connected to the output terminal 204.
- the feedback voltage Vfb is input to the first non-inverting input terminal 201, the voltage V121 is input to the second non-inverting input terminal 202, the reference voltage Vref is input to the inverting input terminal 203, and the output terminal 204 outputs the output voltage Vdrv.
- the differential amplifier circuit 104 configured as described above operates as follows with respect to the input voltage.
- the current flowing through the PMOS transistor 208 is smaller than the current flowing through the NMOS transistor 205. Accordingly, the drain voltage of the PMOS transistor 208 decreases and the output voltage Vdrv increases. At this time, since the resistance of the NMOS transistor 205 is smaller than that of the NMOS transistor 206, the NMOS transistor 205 predominantly passes current.
- the current flowing through the PMOS transistor 208 is smaller than the current flowing through the NMOS transistor 206. Accordingly, the drain voltage of the PMOS transistor 208 decreases and the output voltage Vdrv increases. At this time, since the resistance of the NMOS transistor 206 is smaller than that of the NMOS transistor 205, the NMOS transistor 206 predominantly passes current.
- the differential amplifier circuit 104 In normal operation, since the output voltage of the differential amplifier circuit 112 is lower than the reference voltage Vref2, the output Vd of the comparator 113 is Lo output, the switch 115 is opened, and the switch 116 is short-circuited. Accordingly, since the ground voltage Vss is input to the second non-inverting input terminal, the differential amplifier circuit 104 has a voltage based on the voltage of the first non-inverting input terminal and the inverting input terminal, that is, the feedback voltage Vfb and the reference voltage Vref. Is output.
- the feedback voltage Vfb becomes the ground voltage Vss, so that the output voltage Vdrv of the differential amplifier circuit 104 decreases. Since the output transistor 102 is turned on, the output current Iout increases. When the output current Iout increases, the voltage VR decreases due to the voltage drop of the resistor 111, and the output voltage of the differential amplifier circuit 112 increases. When the output voltage of the differential amplifier circuit 112 becomes higher than the reference voltage Vref2, the output Vd of the comparator 113 becomes a high output, the switch 115 is short-circuited, and the switch 116 is opened.
- the differential amplifier circuit 104 prevents the overcurrent by controlling the gate of the output transistor 102 based on the output voltage of the overcurrent protection circuit 121.
- the comparator 113 has hysteresis added to prevent chattering.
- the reference voltage Vref and the reference voltage Vref2 are preferably the same voltage so that the differential amplifier circuit 104 can smoothly switch from the control of the first non-inverting input terminal to the control of the second non-inverting input terminal.
- the output voltage of the differential amplifier circuit 112 increases in proportion to the output current Iout, but is lower than the reference voltage Vref2, so that the output Vd of the comparator 113 is a Low output. Accordingly, since the switch 115 is open and the switch 116 is short-circuited, the output terminal of the overcurrent protection circuit 121 is connected to the ground terminal 11 and the output voltage V121 is 0V. Therefore, in the differential amplifier circuit 104, the feedback voltage Vfb works as a non-inverting input signal, and the output voltage Vout is controlled to the set voltage by the negative feedback of the constant voltage control circuit 120. At this time, the voltage of the first non-inverting input terminal becomes equal to the voltage of the inverting input terminal by the action of the differential amplifier circuit 104, so that the feedback voltage Vfb becomes equal to the reference voltage Vref.
- the output voltage of the differential amplifier circuit 112 rises and becomes higher than the reference voltage Vref2, the output Vd of the comparator 113 becomes a high output. Therefore, since the switch 115 is short-circuited and the switch 116 is open, the output voltage V121 of the overcurrent protection circuit 121 is the same voltage as the output voltage of the differential amplifier circuit 112.
- the reference voltages Vref and Vref2 are set to the same voltage, the output voltage V121 is higher than the feedback Vfb, so that the output voltage V121 functions as a non-inverted input signal of the differential amplifier circuit 104 and the overcurrent protection circuit. Due to the negative feedback 121, the output current Iout is controlled to the overcurrent protection set current.
- the voltage regulator including the overcurrent protection circuit of the present embodiment when the output current exceeding the overcurrent protection set value flows, the negative feedback of the output voltage control is disconnected, and the output current control Therefore, it is possible to control the output current to the overcurrent protection set value with high accuracy and stability.
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Abstract
Description
113 コンパレータ
106 分圧抵抗回路
120 定電圧制御回路
121 過電流保護回路
210 電流源
211 反転増幅回路
Claims (3)
- 出力電圧を制御する負帰還回路を構成する定電圧制御回路と、出力電流を制御する負帰還回路を構成する過電流保護回路と、を備えたボルテージレギュレータであって、
前記定電圧制御回路は、
第一基準電圧と帰還電圧を比較する第一差動増幅回路と、前記第一差動増幅回路の出力電圧で制御される出力トランジスタを備え、
前記過電流保護回路は、
出力電流を測定するための抵抗と、前記抵抗の両端の電圧の差を測定する第二差動増幅回路と、前記第二差動増幅回路の出力電圧と第二基準電圧を比較するコンパレータと、前記コンパレータの検出信号によって制御されるスイッチと、を備え、
前記出力電流が過電流保護設定値以上流れた時に、前記第二差動増幅回路の出力電圧が前記スイッチを介して前記第一差動増幅回路に入力され、前記出力トランジスタの制御を、前記定電圧制御回路による制御から、前記過電流保護回路による制御に切り替える、
ことを特徴とするボルテージレギュレータ。 - 前記第一基準電圧と前記第二基準電圧は等しい電圧である、
ことを特徴とする請求項1に記載のボルテージレギュレータ。 - 前記第一差動増幅回路は、第一非反転入力端子と第二非反転入力端子と反転入力端子を有し、
前記第一非反転入力端子に前記帰還電圧が入力され、前記第二非反転入力端子に前記第二差動増幅回路の出力電圧が入力され、前記反転入力端子に前記第一基準電圧が入力される、
ことを特徴とする請求項1に記載のボルテージレギュレータ。
Priority Applications (4)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
KR1020157036127A KR20160022829A (ko) | 2013-06-25 | 2014-05-29 | 볼티지 레귤레이터 |
EP14817875.9A EP3015943A1 (en) | 2013-06-25 | 2014-05-29 | Voltage regulator |
CN201480036667.5A CN105308529A (zh) | 2013-06-25 | 2014-05-29 | 稳压器 |
US14/969,688 US10177655B2 (en) | 2013-06-25 | 2015-12-15 | Voltage regulator including a non-regulated state detection circuit |
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP2013132965A JP6170354B2 (ja) | 2013-06-25 | 2013-06-25 | ボルテージレギュレータ |
JP2013-132965 | 2013-06-25 |
Related Child Applications (1)
Application Number | Title | Priority Date | Filing Date |
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US14/969,688 Continuation US10177655B2 (en) | 2013-06-25 | 2015-12-15 | Voltage regulator including a non-regulated state detection circuit |
Publications (1)
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WO2014208261A1 true WO2014208261A1 (ja) | 2014-12-31 |
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PCT/JP2014/064267 WO2014208261A1 (ja) | 2013-06-25 | 2014-05-29 | ボルテージレギュレータ |
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US (1) | US10177655B2 (ja) |
EP (1) | EP3015943A1 (ja) |
JP (1) | JP6170354B2 (ja) |
KR (1) | KR20160022829A (ja) |
CN (1) | CN105308529A (ja) |
TW (1) | TWI626520B (ja) |
WO (1) | WO2014208261A1 (ja) |
Families Citing this family (9)
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DE102015225804A1 (de) * | 2015-12-17 | 2017-06-22 | Dialog Semiconductor (Uk) Limited | Spannungsregler mit Impedanzkompensation |
US11342852B2 (en) * | 2017-06-23 | 2022-05-24 | Intel Corporation | Apparatus, system, and method for reducing voltage overshoot in voltage regulators |
JP6986999B2 (ja) * | 2018-03-15 | 2021-12-22 | エイブリック株式会社 | ボルテージレギュレータ |
JP7065660B2 (ja) | 2018-03-22 | 2022-05-12 | エイブリック株式会社 | ボルテージレギュレータ |
CN109947163B (zh) * | 2018-09-04 | 2020-08-07 | 合肥鑫晟光电科技有限公司 | 数字稳压器及其稳压方法 |
IT201900003331A1 (it) | 2019-03-07 | 2020-09-07 | St Microelectronics Srl | Circuito regolatore di tensione e corrispondente procedimento |
JP2021039596A (ja) | 2019-09-04 | 2021-03-11 | 株式会社東芝 | 電源回路 |
CN112732000A (zh) * | 2021-01-26 | 2021-04-30 | 灿芯半导体(上海)有限公司 | 一种新型瞬态响应增强ldo |
KR20220131063A (ko) * | 2021-03-19 | 2022-09-27 | 에스케이하이닉스 주식회사 | 저전압 강하 레귤레이터 |
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JP2005301439A (ja) * | 2004-04-07 | 2005-10-27 | Ricoh Co Ltd | ボルテージレギュレータ |
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JP5099505B2 (ja) * | 2008-02-15 | 2012-12-19 | セイコーインスツル株式会社 | ボルテージレギュレータ |
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JP2012159870A (ja) * | 2011-01-28 | 2012-08-23 | Seiko Instruments Inc | ボルテージレギュレータ |
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JP6257323B2 (ja) * | 2013-12-27 | 2018-01-10 | エスアイアイ・セミコンダクタ株式会社 | ボルテージレギュレータ |
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2013
- 2013-06-25 JP JP2013132965A patent/JP6170354B2/ja not_active Expired - Fee Related
-
2014
- 2014-05-29 EP EP14817875.9A patent/EP3015943A1/en not_active Withdrawn
- 2014-05-29 CN CN201480036667.5A patent/CN105308529A/zh active Pending
- 2014-05-29 KR KR1020157036127A patent/KR20160022829A/ko not_active Application Discontinuation
- 2014-05-29 WO PCT/JP2014/064267 patent/WO2014208261A1/ja active Application Filing
- 2014-06-09 TW TW103119881A patent/TWI626520B/zh active
-
2015
- 2015-12-15 US US14/969,688 patent/US10177655B2/en active Active
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JP2003005847A (ja) * | 2001-06-25 | 2003-01-08 | Texas Instr Japan Ltd | レギュレータ回路 |
JP2005051854A (ja) * | 2003-07-30 | 2005-02-24 | Mitsumi Electric Co Ltd | 起動処理回路 |
Also Published As
Publication number | Publication date |
---|---|
US10177655B2 (en) | 2019-01-08 |
CN105308529A (zh) | 2016-02-03 |
KR20160022829A (ko) | 2016-03-02 |
TW201523187A (zh) | 2015-06-16 |
JP6170354B2 (ja) | 2017-07-26 |
EP3015943A1 (en) | 2016-05-04 |
US20160105113A1 (en) | 2016-04-14 |
TWI626520B (zh) | 2018-06-11 |
JP2015007903A (ja) | 2015-01-15 |
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