WO2010095641A1 - 電源装置 - Google Patents
電源装置 Download PDFInfo
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- WO2010095641A1 WO2010095641A1 PCT/JP2010/052338 JP2010052338W WO2010095641A1 WO 2010095641 A1 WO2010095641 A1 WO 2010095641A1 JP 2010052338 W JP2010052338 W JP 2010052338W WO 2010095641 A1 WO2010095641 A1 WO 2010095641A1
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- WIPO (PCT)
- Prior art keywords
- capacitor
- precharge
- switching circuit
- semiconductor switching
- power supply
- Prior art date
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- 239000003990 capacitor Substances 0.000 claims abstract description 122
- 239000004065 semiconductor Substances 0.000 claims description 53
- 229910001416 lithium ion Inorganic materials 0.000 claims description 5
- HBBGRARXTFLTSG-UHFFFAOYSA-N Lithium ion Chemical compound [Li+] HBBGRARXTFLTSG-UHFFFAOYSA-N 0.000 claims description 4
- 238000001514 detection method Methods 0.000 description 12
- 238000000034 method Methods 0.000 description 11
- 238000010586 diagram Methods 0.000 description 9
- 230000000903 blocking effect Effects 0.000 description 8
- 230000017525 heat dissipation Effects 0.000 description 8
- 230000006866 deterioration Effects 0.000 description 4
- 230000008569 process Effects 0.000 description 4
- CURLTUGMZLYLDI-UHFFFAOYSA-N Carbon dioxide Chemical compound O=C=O CURLTUGMZLYLDI-UHFFFAOYSA-N 0.000 description 2
- 230000004913 activation Effects 0.000 description 2
- 238000004891 communication Methods 0.000 description 2
- 238000001816 cooling Methods 0.000 description 2
- 238000011161 development Methods 0.000 description 2
- 239000000446 fuel Substances 0.000 description 2
- 238000012544 monitoring process Methods 0.000 description 2
- 239000000758 substrate Substances 0.000 description 2
- 239000002253 acid Substances 0.000 description 1
- 239000011149 active material Substances 0.000 description 1
- 229910002092 carbon dioxide Inorganic materials 0.000 description 1
- 239000001569 carbon dioxide Substances 0.000 description 1
- 230000007423 decrease Effects 0.000 description 1
- 238000007599 discharging Methods 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 238000009499 grossing Methods 0.000 description 1
- 229910052739 hydrogen Inorganic materials 0.000 description 1
- 239000001257 hydrogen Substances 0.000 description 1
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- 230000006872 improvement Effects 0.000 description 1
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/36—Means for starting or stopping converters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
- H02H7/00—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions
- H02H7/10—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers
- H02H7/12—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers
- H02H7/1216—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers for AC-AC converters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
- H02H7/00—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions
- H02H7/16—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for capacitors
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
- H02H9/00—Emergency protective circuit arrangements for limiting excess current or voltage without disconnection
- H02H9/001—Emergency protective circuit arrangements for limiting excess current or voltage without disconnection limiting speed of change of electric quantities, e.g. soft switching on or off
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5375—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with special starting equipment
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
- H02J7/34—Parallel operation in networks using both storage and other dc sources, e.g. providing buffering
- H02J7/345—Parallel operation in networks using both storage and other dc sources, e.g. providing buffering using capacitors as storage or buffering devices
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
- Y02E60/00—Enabling technologies; Technologies with a potential or indirect contribution to GHG emissions mitigation
- Y02E60/10—Energy storage using batteries
Definitions
- the present invention relates to a power supply device having a hybrid configuration including a capacitor and a battery.
- Such a hybrid vehicle employs a power supply system that drives a motor or the like by a battery or regenerates energy during deceleration to the battery.
- Such power supply systems have evolved from sealed lead batteries to Ni-hydrogen batteries and further to Li-ion batteries due to the emergence of new batteries, reduction in size and weight, and increase in power density.
- the development of battery active materials and the development of high-capacity and high-power battery structures have been carried out, and efforts have been made to realize power sources with high output density and longer usage time. ing.
- the power supply is directed to a direction that requires a lower-loss power source, that is, a power source having a smaller internal resistance.
- an electric double layer capacitor (EDLC) is generally known as an example.
- An electric double layer capacitor exhibits intermediate characteristics between a capacitor and a battery used for smoothing and the like.
- a hybrid capacitor (HC) doped with lithium ions can be cited as a higher energy density capacitor that exhibits intermediate characteristics between an electric double layer capacitor and a battery.
- capacitors are known to be applied to an idling stop system that requires instantaneous output because the energy density is small but the output density is higher than that of the battery.
- a capacitor since a capacitor generally has a large self-discharge, it is used in a hybrid configuration with a battery such as a lead storage battery.
- a semiconductor switching element such as a mechanical relay or MOSFET (metal-oxide-field-effect-transistor) is used as a switch for connecting the lead storage battery and the capacitor.
- the capacitor since the capacitor has a large self-discharge, for example, when restarting after long-term storage, a large potential difference is likely to occur between the lead-acid battery and the capacitor.
- the switch between the lead storage battery and the capacitor is turned on in such a state where there is a potential difference, an excessive current flows from the lead storage battery because the internal resistance of the capacitor is small, leading to deterioration of the life of the lead storage battery.
- a first aspect of a power supply device includes a capacitor connected in parallel with a battery, two switching circuits connected in series with the capacitor, and precharge switching connected in parallel to one of the two switching circuits. And a control unit that controls the precharge switching circuit and at least one of the two switching circuits to limit the precharge current of the capacitor when the voltage of the capacitor is lower than the voltage of the battery.
- Each of the two switching circuits and the precharge switching circuit connected in series with the capacitor may include one semiconductor switching element or a plurality of semiconductor switching elements connected in parallel.
- the semiconductor switching elements constituting the respective switching circuits connected in series with the capacitors are turned off, and the semiconductor switching elements constituting the precharge switching circuit are turned on, whereby the precharge switching circuit And a built-in diode of a semiconductor switching element of a switching circuit in which the precharge switching circuit is not connected in parallel may be energized.
- the semiconductor switching element constituting the precharge switching circuit is turned on, and the switching circuit connected in parallel to the precharge switching circuit out of the two switching circuits connected in series with the capacitor is controlled.
- the semiconductor switching element may be PWM (Pulse Width Modulation) controlled, and the semiconductor switching element of the other switching circuit may be off-controlled.
- the semiconductor switching element constituting the precharge switching circuit may be controlled by PWM (Pulse Width Modulation), or the semiconductor switching element constituting the precharge switching circuit is controlled to control the gate voltage. Adjust the on-resistance. You may do it.
- the capacitor may be a hybrid capacitor doped with lithium ions. In that case, each semiconductor switching element of the precharge switching circuit may be turned on stepwise so that a pseudo increase in the internal resistance of the hybrid capacitor occurs when the precharge current is limited.
- a second aspect of the power supply device according to the present invention includes a capacitor connected in parallel with the battery, and two switching circuits including a semiconductor switching element connected in series with the capacitor or a plurality of semiconductor switching elements connected in parallel.
- the semiconductor switching element of each switching circuit is controlled so as to share the loss at the time of current limitation by the two switching circuits, and the precharge current limitation of the capacitor And a control unit for performing.
- the semiconductor switching element of one switching circuit is turned off and the semiconductor switching element of the other switching circuit is PWM-controlled so that the built-in diode of the semiconductor switching element of one switching circuit and the other
- These switching circuits may be used for energization.
- the semiconductor switching element of one switching circuit When the precharge current is limited, the semiconductor switching element of one switching circuit is turned off, the gate voltage of the semiconductor switching element of the other switching circuit is controlled, the built-in diode of the semiconductor switching element of one switching circuit, and the other These switching circuits may be energized.
- the present invention it is possible to charge the capacitor in a usable state in a short time while suppressing deterioration of the battery and downsizing the power supply device.
- FIG. 1 is a schematic block diagram when the power supply device according to the first embodiment of the present invention is used for driving a rotating electrical machine.
- FIG. 2 is a diagram illustrating a charging current path during precharging.
- FIG. 3 is a flowchart showing a control procedure.
- FIG. 4 is a diagram showing a case where the charge cutoff MOSFET 31 and the discharge cutoff MOSFET 32 are each constituted by a plurality of MOSFETs connected in parallel.
- FIG. 5 is a diagram for explaining a power supply device according to the second embodiment of the present invention.
- FIG. 6 is a diagram for explaining a power supply device according to the third embodiment of the present invention.
- FIG. 1 is a schematic block diagram when the power supply device according to the first embodiment of the present invention is used for driving a rotating electrical machine.
- the power supply device 2 is connected to the inverter device 4 via relays 5a and 5b.
- the rotating electrical machine 3 is rotationally driven by the inverter device 4.
- the rotating electrical machine 3 constitutes a starter motor and a motor generator for starting an engine in an idling stop system of a vehicle.
- the power supply device 2 includes a capacitor 10 connected in parallel with a secondary battery 1 such as a lead storage battery, a charge cutoff MOSFET 31, a discharge cutoff MOSFET 32, a precharge MOSFET 33, a gate driver 12, a control unit 14, a voltage detection unit 16, a temperature A detection unit 18 and a current detection unit 20 are provided.
- an electric double layer capacitor is used as the capacitor 10, but the present invention is applicable to any large-capacity capacitor that requires the same protection control as the electric double layer capacitor.
- the capacitor 10 is composed of a plurality of cells.
- an N-channel MOSFET is used for each of the MOSFETs 31 to 33, so that the resistance is lower.
- a P-channel MOSFET may be used for all or any one of the MOSFETs, Any device that can realize the same function is applicable.
- a boost gate driver is used as the gate driver 12 for driving the gate of the MOSFET.
- the boosting gate driver may be any type as long as it can drive the gate of an N-channel MOSFET such as a charge pump type.
- the control unit 14 controls the entire power supply device, and a dedicated IC or general-purpose microcomputer is used. However, the control unit 14 is not limited to these as long as the same function can be realized. In addition to the control function for controlling the gate driver 12, the control unit 14 includes a function for monitoring each part voltage, a balance switch function for adjusting each cell voltage of the capacitor 10, and a function for communicating to the host.
- the total voltage of the secondary battery 1 As the respective voltages monitored by the control unit 14, the total voltage of the secondary battery 1, each cell voltage and total voltage of the capacitor 10 detected by the voltage detection unit 16, the output of the current detection unit 20, and the output of the temperature detection unit 18. and so on.
- the output from each unit is A / D converted by an A / D converter provided in the control unit 14 and taken in.
- any necessary functions such as CAN (Controller Area Network), I2C (Inter-Integrated Circuit), and SPI (System Packet Interface) may be used.
- the starting signal (IGN signal) at the time of starting the rotary electric machine 3 is input from a high-order via a communication function.
- a current detection unit 20 that detects current using a Hall element is used.
- differential amplifier detection of both-end voltages from the discharge cutoff MOSFET 32 to the charge cutoff MOSFET 31 and voltage measurement of the shunt resistor are used.
- the current may be detected by measuring the voltage of the current transformer.
- the detected current value is acquired by an A / D converter built in the control unit 14, but any value may be used as long as the same function can be realized.
- the temperature detection unit 18 may be detected by dividing a NTC thermistor or a PTC thermistor and a resistor in series, detection by a temperature IC, or the like, as long as the same function can be realized.
- a capacitor cell, a substrate on which a MOSFET is mounted, a housing, and the like are conceivable, but they may be added as necessary.
- the temperature detector 18 in FIG. 1 detects the temperature of the substrate on which the MOSFET is mounted.
- the temperature detection value is obtained by an A / D converter built in the control unit 14, any value may be used as long as the same function can be realized.
- a discharge cutoff MOSFET 32 and a charge cutoff MOSFET 31 are provided in series with the capacitor 10 in the + side supply path from the capacitor 10 to the secondary battery 1.
- a precharge MOSFET 33 is connected in parallel to the charge cutoff MOSFET 31. If necessary, either the discharge cutoff MOSFET 32, the charge cutoff MOSFET 31 or the precharge MOSFET 33 may be moved to the ground side, or an additional MOSFET may be added to the + side or the ground side. good.
- the discharge cutoff MOSFET 32 is configured such that the forward direction of the body diode 321 is opposite to the discharge current direction of the capacitor 10.
- the charge cutoff MOSFET 31 and the precharge MOSFET 33 are configured such that the forward direction of the body diodes 311 and 333 and the direction of the charge current to the capacitor 10 are opposite to each other.
- the charge cutoff MOSFET 31 Since the charge cutoff MOSFET 31 has the body diode 311 connected in the reverse direction, even if the charge cutoff MOSFET 31 is turned off, the discharge current from the capacitor 10 can flow through the body diode 311 in the forward direction. The discharge current is not interrupted. As a switch for cutting off the discharge current, a discharge cut-off MOSFET 32 is provided in series. When the discharge cutoff MOSFET 32 is turned off, the discharge current is cut off. However, since the forward direction of the body diode 321 is the same as the direction of the charging current, the charging current can flow through the body diode 321 even if the discharge cutoff MOSFET 32 is turned off. As described above, by connecting the two MOSFETs 31 and 32 in series in opposite directions, it is possible to perform a blocking / non-blocking operation on both the charging current and the discharging current.
- the charge cutoff MOSFET 31 is disposed on the power supply line side (+ side) and the discharge cutoff MOSFET 32 is disposed on the capacitor 1 side.
- the charge cutoff MOSFET 31, the discharge cutoff MOSFET 32 and the precharge MOSFET 33 are all turned on. ing. Since a large current flows through the rotating electrical machine 3 at the time of IGN startup, MOSFETs corresponding to the large current are used for the charge cutoff MOSFET 31 and the discharge cutoff MOSFET 32.
- FIG. 2 is a diagram illustrating a charging current path during precharging.
- FIG. 2 shows the capacitor 10, the secondary battery 1, and the MOSFETs 31 to 33 necessary for explaining the control method.
- FIG. 3 is a flowchart showing a control procedure, and the control program is executed by the control unit 14.
- step S100 the control unit 14 compares the total voltage of the secondary battery 1 with the total voltage of the capacitor 10, and determines whether or not the potential difference is equal to or greater than a preset potential difference threshold. That is, it is determined whether the voltage of the capacitor 10 is lower than the voltage of the secondary battery 1 and precharge is necessary.
- a forward voltage for example, 0.5 V
- the body diode 321 of the discharge cutoff MOSFET 32 can be considered, but is not necessarily limited thereto.
- step S100 If it is determined in step S100 that the potential difference between the secondary battery 1 and the capacitor 10 is smaller than the potential difference threshold value, the process proceeds to step S120, and the MOSFETs 31 to 33 are turned on, that is, the capacitor 1 is freely charged and discharged. Set to the normal use state that can be used. Then, it progresses to step S130 and the normal operation
- step S100 determines whether the potential difference is equal to or greater than the threshold value. If it is determined in step S100 that the potential difference is equal to or greater than the threshold value, the process proceeds to step S115 to execute a process for the precharge operation.
- step S115 in order to perform the precharge operation, the control unit 14 instructs the gate driver 12 to turn off the charge cutoff MOSFET 31 and the discharge cutoff MOSFET 32 and turn on the precharge MOSFET 33. At this time, the charging current flows into the capacitor 10 through a path indicated by a broken line.
- the charging current passes only through the body diode 321.
- the charging current cannot pass through the off-state charge cutoff MOSFET 31 and flows into the capacitor 10 via the on-state precharge MOSFET 33. In this way, the capacitor 10 is charged.
- the precharge MOSFET 33 is normally controlled so as to maintain the on state at a necessary gate voltage, but by adjusting the gate voltage to adjust the on resistance of the precharge MOSFET 33, the charge current value can be further increased. You may make it adjust to an optimal value.
- a PWM (Pulse Width Modulation) pulse may be applied to the gate of the precharge MOSFET 33 to adjust the amount of charge current by PWM control.
- the loss in the current limitation at the time of precharging is shared by the loss due to the body diode 321 of the discharge cutoff MOSFET 32 and the loss due to the on-resistance of the precharge MOSFET 33, so that heat dissipation is 2
- the heat dissipation performance can be improved by being distributed to the two MOSFETs 31 and 32.
- the capacitor 10 since the capacitor 10 has an internal resistance, it is shared by the loss due to the internal resistance.
- the magnitudes of the losses W (32), W (33), and W (10) of the MOSFETs 32 and 33 and the capacitor 10 when a large current is passed by precharging is W (32). > W (33) ⁇ W (10) in that order, and is characterized in that the loss is dispersed in the discharge cutoff MOSFET 32 which is originally designed for large current application and excellent in heat dissipation.
- the case where the electric double layer capacitor is applied to the capacitor 10 has been described as an example.
- a hybrid capacitor in which lithium ions are doped in the negative electrode is applied to the capacitor 10
- pre-charging is performed.
- the voltage application to the gate of the charging MOSFET 33 is abruptly performed stepwise.
- a phenomenon in which the terminal voltage greatly decreases with respect to the open circuit voltage is observed. That is, the internal resistance can be increased in a pseudo manner by increasing the current stepwise.
- one MOSFET is used as the charge cutoff MOSFET 31, the discharge cutoff MOSFET 32, and the precharge MOSFET 33.
- the charge cutoff MOSFET 31 and the discharge cutoff MOSFET 32 that are assumed to flow a large current during normal use may each be composed of a plurality of MOSFETs connected in parallel.
- the precharge MOSFET 33 may also be constituted by a plurality of MOSFETs connected in parallel.
- the charge cutoff MOSFET 31 and the precharge MOSFET 33 that are connected in parallel may be integrated, and a one-chip product that can drive the gates separately may be used.
- the capacitor 10 is charged in a usable state in a short time while limiting the precharge current value to a value that does not become a burden on the secondary battery 1 and suppressing the temperature rise and deterioration of the secondary battery 1. It becomes possible.
- the MOSFETs 31 and 32 have a function of a switching circuit that opens and closes the power path of the capacitor 10, and the MOSFET 32 shares a loss by causing a current during precharging to flow only through the body diode 321 of the MOSFET 32. It also functions as an element.
- each of the MOSFETs 31 and 32 as the switching circuit with a plurality of MOSFETs connected in parallel, it is possible to easily cope with a large current and to distribute the loss in the MOSFET 32 to a larger number of elements. be able to.
- the precharge MOSFET 33 is also composed of a plurality of MOSFETs connected in parallel, whereby the loss can be further dispersed and a MOSFET with a small rated capacity can be used. Further, instead of simply turning on the precharge MOSFET 33, it is possible to adjust the precharge current value to a desired value by adjusting the gate voltage or PWM control.
- FIG. 5 is a diagram for explaining a power supply device according to the second embodiment of the present invention, and corresponds to FIG. 2 in the first embodiment. Other configurations are the same as those of the first embodiment, and the description thereof is omitted.
- a discharge cutoff MOSFET 32 and a charge cutoff MOSFET 31 are provided in series with the capacitor 10 in the + side supply path from the capacitor 10 to the secondary battery 1.
- one of the MOSFETs 31 and 32 may be moved to the ground side as necessary, or an additional MOSFET may be added to the + side or the ground side.
- both MOSFETs 31 and 32 are turned on.
- the discharge cutoff MOSFET 32 is turned off and the gate of the charge cutoff MOSFET 31 is PWM-controlled.
- the charging current flows into the capacitor 10 through the body diode 321 of the discharge cutoff MOSFET 32 and the charge cutoff MOSFET 31 as indicated by a broken line.
- the PWM control in the charge cutoff MOSFET 31 is adjusted according to the potential difference between the secondary battery 1 and the capacitor 10.
- the loss is shared by the internal resistances of the MOSFETs 31 and 32 and the capacitor 10 corresponding to a large current, and the heat dissipation performance can be improved.
- the losses W (31), W (32), and W (10) of the MOSFETs 31 and 32 and the capacitor 10 when a large current is flowed by precharging are W (32) ⁇ W (31)>
- the loss is distributed to the discharge cutoff MOSFET 32 and the charge cutoff MOSFET 31 which are designed in the order of W (10) and originally designed to handle a large current and have excellent heat dissipation.
- the charge cutoff MOSFET 31 and the discharge cutoff MOSFET 32 connected in series with the capacitor 10 are switched.
- the charge cutoff MOSFET 31 and the discharge cutoff MOSFET 32 share the loss at the time of current limitation.
- the capacitor 10 is charged in a usable state in a short time while limiting the precharge current value to a value that does not become a burden on the secondary battery 1 and suppressing the temperature rise and deterioration of the secondary battery 1. It becomes possible. Further, when compared with the first embodiment, the precharge MOSFET 33 is omitted, so that the cost and size can be further reduced.
- the precharge MOSFET 33 may be connected in parallel to the charge cutoff MOSFET 31 so that the loss is shared by the three MOSFETs. In that case, the precharge MOSFET 33 may be controlled not only to be turned on, but also to control the gate voltage, or to perform PWM control. Further, as described in the first embodiment, the MOSFETs 31 to 33 may be composed of a plurality of MOSFETs connected in parallel.
- FIG. 6 is a diagram for explaining a power supply device according to the third embodiment of the present invention, and corresponds to FIG. 2 in the first embodiment.
- a MOSFET is used as the semiconductor switching element.
- a high-voltage capacitor module is used as the capacitor 10
- an IGBT (insulated gate bipolar transistor) module is used instead of the MOSFET. To use.
- a discharge cutoff IGBT 42 and a charge cutoff IGBT 41 are provided in series with the capacitor 10 in the + side supply path from the capacitor 10 to the secondary battery 1.
- a precharge IGBT 43 is connected in parallel to the charge cutoff IGBT 41. That is, MOSFETs 31 to 33 shown in FIG. 2 are replaced with IGBTs 41 to 43.
- either the discharge blocking IGBT 42, the charge blocking IGBT 41, or the precharge IGBT 43 may be moved to the ground side, or an IGBT may be additionally added to the + side or the ground side. good.
- a hybrid capacitor is applied to the high voltage capacitor 10. By applying a hybrid capacitor having a maximum cell voltage higher than that of the electric double layer capacitor, the number of series cells can be reduced.
- the discharge blocking IGBT 42 is configured such that the body diode is connected in the direction opposite to the discharge current direction of the capacitor 10.
- the charge blocking IGBT 41 and the precharging IGBT 43 are configured such that the body diode is connected in the direction opposite to the charging current direction to the capacitor 10.
- a precharge relay may be used instead of the precharge IGBT 43.
- the control method in the third embodiment will be described.
- the charge blocking IGBT 41, the discharge blocking IGBT 42, and the precharge IGBT 43 are all in the on state.
- the total voltage of the capacitor 10 and the voltage of the secondary battery 1 are compared.
- the potential difference threshold which is a determination criterion at this time, is set to be equal to or higher than the forward voltage (for example, 0.5 V) of the body diode of the discharge cutoff IGBT 42, but may be changed as necessary.
- the charging current path to the capacitor 10 at the time of precharging is as shown by a broken line in FIG. 6, and the charging current passes through the body diode of the discharge cutoff IGBT 42 and then flows into the capacitor 10 through the precharging IGBT 43.
- the hybrid capacitor can increase the internal resistance in a pseudo manner by controlling the current stepwise. Therefore, by driving the precharge IGBT 43 in a stepwise manner, the loss borne by the capacitor 10 can be increased due to a pseudo increase in internal resistance. As a result, even when the potential difference between the secondary battery 1 and the capacitor 10 is large, it is possible to cope with it sufficiently.
- a gate voltage that is normally required is applied stepwise to the precharge IGBT 43, but the on-resistance of the precharge IGBT 43 can be adjusted by adjusting the gate voltage, or the gate of the precharge IGBT 43 can be adjusted.
- the precharge current may be adjusted by PWM control by applying a PWM pulse.
- the loss in order to limit the current during precharging, the loss must be borne only by the limiting resistor or the semiconductor switching element (MOSFET). Furthermore, since the allowable loss of the limiting resistor and the switching element is small, there is a drawback that it is difficult to flow a large current of several tens to several hundreds of A. However, in the present embodiment, the loss is shared by the discharge cutoff IGBT 42, the precharge IGBT 43, and the internal resistance of the capacitor 10 corresponding to the large current discharge, so that the heat radiation performance can be improved.
- MOSFET semiconductor switching element
- loss W (10), W (42), and W (43) of capacitor 10 (hybrid capacitor) and IGBTs 42 and 43 when a large current is passed by precharging is W (10)> W (42)> W (43) in order, and the characteristic is that the loss is dispersed in the discharge interrupting IGBT 42 which is originally designed to have excellent heat dissipation for large current discharge.
- the capacitor 10 can be used in a short time.
- a semiconductor switching element is used in place of the conventionally used relay and limiting resistor, it is possible to reduce the size and cost.
- precharge relay is used instead of the precharge IGBT 43, the relay is closed during precharge. The loss is shared by the discharge cutoff IGBT 42 and the internal resistance of the capacitor 10.
- the present invention is not limited to this, and can be applied to a power supply apparatus having a hybrid configuration that supplies electric power to various loads.
- the above description is an example to the last, and this invention is not limited to the said embodiment at all unless the characteristic of this invention is impaired. Further, it is possible to combine one or a plurality of embodiments and modification examples.
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Charge And Discharge Circuits For Batteries Or The Like (AREA)
- Electric Propulsion And Braking For Vehicles (AREA)
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Abstract
Description
なお、キャパシタと直列に接続された2つのスイッチング回路およびプリチャージスイッチング回路の各々が、1つの半導体スイッチング素子または並列接続された複数の半導体スイッチング素子を備えるようにしても良い。
さらに、プリチャージ電流制限時に、キャパシタと直列に接続された各スイッチング回路を構成する半導体スイッチング素子をオフ制御すると共に、プリチャージスイッチング回路を構成する半導体スイッチング素子をオン制御して、プリチャージスイッチング回路と、該プリチャージスイッチング回路が並列接続されていないスイッチング回路の半導体スイッチング素子の内蔵ダイオードとを通電状態とするようにしても良い。
また、プリチャージ電流制限時に、プリチャージスイッチング回路を構成する半導体スイッチング素子をオン制御すると共に、キャパシタと直列に接続された2つのスイッチング回路の内、プリチャージスイッチング回路に並列接続されたスイッチング回路の半導体スイッチング素子をPWM(Pulse Width Modulation)制御し、他方のスイッチング回路の半導体スイッチング素子をオフ制御するようにしても良い。
さらに、プリチャージスイッチング回路を構成する半導体スイッチング素子をPWM(Pulse Width Modulation)制御するようにしても良いし、プリチャージスイッチング回路を構成する半導体スイッチング素子のゲート電圧を制御して、該半導体スイッチング素子のオン抵抗を調整する。ようにしても良い。
また、キャパシタを、リチウムイオンをドープさせたハイブリッドキャパシタしても良い。その場合に、プリチャージ電流制限時に、ハイブリッドキャパシタの内部抵抗に擬似的増加が生じるように、プリチャージスイッチング回路の各半導体スイッチング素子をステップ的にオン制御するようにしても良い。
本発明による電源装置の第2の態様は、電池と並列に接続されるキャパシタと、キャパシタと直列に接続され、1つの半導体スイッチング素子または並列接続された複数の半導体スイッチング素子から成る2つのスイッチング回路と、キャパシタの電圧が前記電池の電圧よりも低いときに、2つのスイッチング回路で電流制限時の損失を分担するように各スイッチング回路の半導体スイッチング素子を制御して、前記キャパシタのプリチャージ電流制限を行う制御部と、を備える。
なお、プリチャージ電流制限時に、一方のスイッチング回路の半導体スイッチング素子をオフ制御すると共に、他方のスイッチング回路の半導体スイッチング素子をPWM制御して、一方のスイッチング回路の半導体スイッチング素子の内蔵ダイオードと、他方のスイッチング回路とを通電状態とする用にしても良い。
プリチャージ電流制限時に、一方のスイッチング回路の半導体スイッチング素子をオフ制御すると共に、他方のスイッチング回路の半導体スイッチング素子のゲート電圧を制御して、一方のスイッチング回路の半導体スイッチング素子の内蔵ダイオードと、他方のスイッチング回路とを通電状態としても良い。
―第1の実施の形態―
図1は、本発明の第1の実施の形態による電源装置を、回転電機の駆動に用いた場合の概略ブロック図である。図1において、電源装置2は、リレー5a,5bを介してインバータ装置4に接続される。回転電機3は、インバータ装置4により回転駆動される。回転電機3は、車両のアイドリングストップシステムにおけるエンジン起動用のスタータモータやモータジェネレータを構成している。
図5は、本発明の第2の実施の形態による電源装置を説明する図であり、第1の実施の形態における図2に対応するものである。なお、その他の構成は第1の実施の形態と同様であり、説明を省略する。第2の実施の形態では、図5に示すようにキャパシタ10から二次電池1への+側の供給経路において、キャパシタ10と直列に放電遮断用MOSFET32と充電遮断用MOSFET31が設けられている。なお、第1の実施の形態の場合と同様に、必要に応じてMOSFET31,32のどちらかをグランド側に移動させても良いし、+側やグランド側にMOSFETを追加で加えても良い。
図6は、本発明の第3の実施の形態による電源装置を説明する図であり、第1の実施の形態における図2に対応するものである。上述した第1の実施の形態では、半導体スイッチング素子としてMOSFETを使用したが、本実施の形態では、キャパシタ10として高電圧のキャパシタモジュールを使用し、MOSFETに代えてIGBT(insulated gate bipolar transistor)モジュールを使用するようにした。
日本国特許出願2009年第34019号(2009年2月17日出願)
Claims (11)
- 電池と並列に接続されるキャパシタと、
前記キャパシタと直列に接続された2つのスイッチング回路と、
前記2つのスイッチング回路の一方に並列に接続されたプリチャージスイッチング回路と、
前記キャパシタの電圧が前記電池の電圧よりも低いときに、前記プリチャージスイッチング回路と前記2つのスイッチング回路の少なくとも1つとを制御して前記キャパシタのプリチャージ電流制限を行う制御部と、を備えた電源装置。 - 請求項1に記載の電源装置において、
前記キャパシタと直列に接続された2つのスイッチング回路および前記プリチャージスイッチング回路の各々は、1つの半導体スイッチング素子または並列接続された複数の半導体スイッチング素子を備える。 - 請求項2に記載の電源装置において、
前記制御部は、
前記プリチャージ電流制限時に、前記キャパシタと直列に接続された各スイッチング回路を構成する半導体スイッチング素子をオフ制御すると共に、前記プリチャージスイッチング回路を構成する半導体スイッチング素子をオン制御して、前記プリチャージスイッチング回路と、該プリチャージスイッチング回路が並列接続されていないスイッチング回路の半導体スイッチング素子の内蔵ダイオードとを通電状態とする。 - 請求項2に記載の電源装置において、
前記制御部は、
前記プリチャージ電流制限時に、前記プリチャージスイッチング回路を構成する半導体スイッチング素子をオン制御すると共に、前記キャパシタと直列に接続された2つのスイッチング回路の内、前記プリチャージスイッチング回路に並列接続されたスイッチング回路の半導体スイッチング素子をPWM(Pulse Width Modulation)制御し、他方のスイッチング回路の半導体スイッチング素子をオフ制御する。 - 請求項3または4に記載の電源装置において、
前記プリチャージスイッチング回路を構成する半導体スイッチング素子はPWM(Pulse Width Modulation)制御される。 - 請求項3または4に記載の電源装置において、
前記制御部は、前記プリチャージスイッチング回路を構成する半導体スイッチング素子のゲート電圧を制御して、該半導体スイッチング素子のオン抵抗を調整する。 - 請求項2に記載の電源装置において、
前記キャパシタは、リチウムイオンをドープさせたハイブリッドキャパシタである。 - 請求項7に記載の電源装置において、
前記制御部は、
プリチャージ電流制限時に、前記ハイブリッドキャパシタの内部抵抗に擬似的増加が生じるように、前記プリチャージスイッチング回路の各半導体スイッチング素子をステップ的にオン制御する。 - 電池と並列に接続されるキャパシタと、
前記キャパシタと直列に接続され、1つの半導体スイッチング素子または並列接続された複数の半導体スイッチング素子から成る2つのスイッチング回路と、
前記キャパシタの電圧が前記電池の電圧よりも低いときに、前記2つのスイッチング回路で電流制限時の損失を分担するように各スイッチング回路の半導体スイッチング素子を制御して、前記キャパシタのプリチャージ電流制限を行う制御部と、を備えた電源装置。 - 請求項9に記載の電源装置において、
前記制御部は、
前記プリチャージ電流制限時に、一方のスイッチング回路の半導体スイッチング素子をオフ制御すると共に、他方のスイッチング回路の半導体スイッチング素子をPWM制御して、前記一方のスイッチング回路の半導体スイッチング素子の内蔵ダイオードと、前記他方のスイッチング回路とを通電状態とする。 - 請求項9に記載の電源装置において、
前記制御部は、
前記プリチャージ電流制限時に、一方のスイッチング回路の半導体スイッチング素子をオフ制御すると共に、他方のスイッチング回路の半導体スイッチング素子のゲート電圧を制御して、前記一方のスイッチング回路の半導体スイッチング素子の内蔵ダイオードと、前記他方のスイッチング回路とを通電状態とする。
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- 2010-02-17 EP EP10743767A patent/EP2400649A1/en not_active Withdrawn
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CN103069154A (zh) * | 2010-08-27 | 2013-04-24 | 罗伯特·博世有限公司 | 用于运行机动车的起动器的方法和装置 |
US20130229019A1 (en) * | 2010-08-27 | 2013-09-05 | Rasmus Rettig | Method and device for operating a starter of a vehicle |
US20130264975A1 (en) * | 2010-12-20 | 2013-10-10 | Toyota Jidosha Kabushiki Kaisha | Electrically powered vehicle and method for controlling the same |
US9166515B2 (en) * | 2010-12-20 | 2015-10-20 | Toyota Jidosha Kabushiki Kaisha | Electrically powered vehicle and method for controlling the same |
FR2984623A1 (fr) * | 2011-12-19 | 2013-06-21 | Valeo Equip Electr Moteur | Dispositif de connexion/deconnexion de charge pour unite de stockage d'energie dans un vehicule automobile |
WO2013093273A1 (fr) * | 2011-12-19 | 2013-06-27 | Valeo Equipements Electriques Moteur | Dispositif de connexion/deconnexion de charge pour unite de stockage d'energie dans un vehicule automobile |
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Also Published As
Publication number | Publication date |
---|---|
JP2010193588A (ja) | 2010-09-02 |
KR101273820B1 (ko) | 2013-06-11 |
EP2400649A1 (en) | 2011-12-28 |
CN102318176B (zh) | 2015-05-13 |
US8803486B2 (en) | 2014-08-12 |
JP5200986B2 (ja) | 2013-06-05 |
US20110316489A1 (en) | 2011-12-29 |
KR20110105001A (ko) | 2011-09-23 |
CN102318176A (zh) | 2012-01-11 |
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