JPS5944995A - Controlling method for motor - Google Patents
Controlling method for motorInfo
- Publication number
- JPS5944995A JPS5944995A JP57152620A JP15262082A JPS5944995A JP S5944995 A JPS5944995 A JP S5944995A JP 57152620 A JP57152620 A JP 57152620A JP 15262082 A JP15262082 A JP 15262082A JP S5944995 A JPS5944995 A JP S5944995A
- Authority
- JP
- Japan
- Prior art keywords
- value
- current
- difference
- calculated
- gain
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
- 238000000034 method Methods 0.000 title claims description 12
- 230000003247 decreasing effect Effects 0.000 abstract 1
- 238000010304 firing Methods 0.000 description 4
- 230000003111 delayed effect Effects 0.000 description 3
- 238000010586 diagram Methods 0.000 description 3
- 230000000694 effects Effects 0.000 description 3
- 238000004804 winding Methods 0.000 description 2
- 101100027969 Caenorhabditis elegans old-1 gene Proteins 0.000 description 1
- 239000002253 acid Substances 0.000 description 1
- 230000003321 amplification Effects 0.000 description 1
- JLQUFIHWVLZVTJ-UHFFFAOYSA-N carbosulfan Chemical compound CCCCN(CCCC)SN(C)C(=O)OC1=CC=CC2=C1OC(C)(C)C2 JLQUFIHWVLZVTJ-UHFFFAOYSA-N 0.000 description 1
- 238000004519 manufacturing process Methods 0.000 description 1
- 238000003199 nucleic acid amplification method Methods 0.000 description 1
- 239000011435 rock Substances 0.000 description 1
- 238000011144 upstream manufacturing Methods 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P7/00—Arrangements for regulating or controlling the speed or torque of electric DC motors
- H02P7/06—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current
- H02P7/18—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power
- H02P7/24—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices
- H02P7/28—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices using semiconductor devices
- H02P7/285—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices using semiconductor devices controlling armature supply only
- H02P7/292—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices using semiconductor devices controlling armature supply only using static converters, e.g. AC to DC
- H02P7/295—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices using semiconductor devices controlling armature supply only using static converters, e.g. AC to DC of the kind having one thyristor or the like in series with the power supply and the motor
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Control Of Direct Current Motors (AREA)
Abstract
Description
【発明の詳細な説明】
本発明はブイリスク変換器により直流電流を供給する直
流電動機の゛電流制御方法に係り、特にデジタル処理を
採用した電動機の電流制御方法に関する。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a current control method for a DC motor that supplies DC current using a buoy risk converter, and more particularly to a current control method for a motor that employs digital processing.
第１図は従来この種のサイリスタ変換器を用いた（α流
電動機の電ｂ１を制御装置の一例を示しだ４．’＋’？
成図である。電源トランス１にまりが［尾の′市川にさ
れた交流がサイリスタ変換器（’Ｉｊｊ、’力開閉素子
）２に入力され、ここで曲流電流に変換きれて電ＩＩＩ
ＩＩ機３の電機子４に供給される。尚符乞５は′１ｔ：
動磯３の界磁巻線である。′４（、源トランス１と一す
−イリスタ交換器２とを接続−ｊ゛る電力線には変６ｆ
Ｌ器６が取伺けられており、この変流器６の２次巻１課
は電流検出器７に入力されている。この電流検出器７の
出力である′電流帰還値８は電流割面１器９に入力され
る。この電流側１７１１１ 慢９には′電流指令値１０
が人力され、その出力はゲートパルス発生器１１に入力
される。このゲートパルス発生器１１の出力であるゲー
トパルス１２はツ“イリスタ変換器２のゲート回路に入
力される。Figure 1 shows an example of a control device for controlling the electric current b1 of an α-flow motor using a conventional thyristor converter of this type.4.'+'?
It is a complete drawing. The alternating current generated in the power transformer 1 is input to the thyristor converter ('Ijj,' force switching element) 2, where it is converted into a curved current and the electric current is
It is supplied to the armature 4 of the II machine 3. Please beg 5 is '1t:
This is the field winding of the moving rock 3. '4 (, the power line connecting the source transformer 1 and the Iristor exchanger 2 is connected to the power line 6F.
An L transformer 6 is taken, and the first section of the secondary winding of this current transformer 6 is inputted to a current detector 7. A current feedback value 8 which is the output of this current detector 7 is inputted to a current dividing plane 1 unit 9. On this current side 17111, the current command value is 10.
is input manually, and its output is input to the gate pulse generator 11. A gate pulse 12, which is the output of the gate pulse generator 11, is input to the gate circuit of the twinning converter 2.
第２図は」皿回電流制御器９の処にＩｌｊフローを示し
たチャート図で、所定の周期で起動されるものである。FIG. 2 is a chart showing the Ilj flow in the counter current controller 9, which is activated at a predetermined period.
先ず、ステップ２０で電流帰還ｆｉｔζ８を取込み、ス
テップ２１で電流指令値１０を取込む。次にステソゲ２
２で電流指令値１０と’ＦＷ流帰還値８との差を演算す
る。次に、ステップ２３はステップ２２の演算結果に電
流制御系（電流検出器７の増幅率等）のゲインを乗算す
る。ステップ２４はステップ２３の演算結果よりゲート
パルスの位相角を演算する。ステップ２５はステツ／２
４で演算された位相角をカウンタにセットすイ′）。First, in step 20, the current feedback fitζ8 is fetched, and in step 21, the current command value 10 is fetched. Next, Stesogame 2
2, the difference between the current command value 10 and the FW flow feedback value 8 is calculated. Next, step 23 multiplies the calculation result of step 22 by the gain of the current control system (such as the amplification factor of the current detector 7). Step 24 calculates the phase angle of the gate pulse from the calculation result of step 23. Step 25 is STETSU/2
Set the phase angle calculated in step 4 in the counter.
上流制御器９のステップ２５でカウンタにセントされた
位相角より、ゲートパルス発生器１１はゲートパルス１
２を作シ、ツーイリスタ変換器２のゲート回路に印加す
る。このサイリスタ変換器２に印加されたゲートパルス
１２により、主回路電流１３の大きさが決まシ、この電
流が変流器６゜電流検出器７を通って電流帰還値８とな
る。これ等の動作の繰返しにより、′屯ｌ１ＩＩＩ機３
に供給される主回路電流１３は電流指令値ｌＯに見合う
値に制御される。Based on the phase angle entered in the counter in step 25 of the upstream controller 9, the gate pulse generator 11 generates a gate pulse 1.
2 is applied to the gate circuit of the twin-ristor converter 2. The gate pulse 12 applied to the thyristor converter 2 determines the magnitude of the main circuit current 13, and this current passes through the current transformer 6° current detector 7 and becomes a current feedback value 8. By repeating these operations,
The main circuit current 13 supplied to the main circuit is controlled to a value commensurate with the current command value lO.
第３図は上記の電流指令値１０Ｓ電流帰還値８及びゲー
トパルス１２との関係を示した！（山作タイムヂャート
である。′、ｕ流指令値１ｏが変化した時、電流帰還値
８＆−ｊ：これに追従する様に！１１１１ （。ゲート
パルス１２の８点では電流指令（１０１０と電流４１”
（ｉ ｊ１割値８との差が犬さく、この差で次回の点弧
信相すが演算される。次にゲートパルス１２のＬ）点で
も、市、流指令値１（）ど１１チ流帰還帥８との差Ｖ」
大きく、この差で次回の点弧位相Ｃかｆｉｔ、 Ｊｊ？
： ’Ｊれる。回４）ｚに０点でも電流指令ｊ１ｆＩ、
１．０と亜流帰還（１（ｉ、 ８との差が大きく、こ
の差で次回の点弧位、（’１．１１ （＋が通常；１ｌ
ｊｊり演算される。ところが、ｄ点では巾；θｉｉ’、
４量還（１１！１８が（・〕、ぼ目標値に達している／
こめ、ここで発生しん、ゲートパルスにより′「に流部
速値８は大きくオーバシュートシてしまう。この為ゲー
トパルス１２の０点の点弧位相が遅れ、電流Ｑ）速値８
は振動波形となってしまい、円滑に目１票値にＱＩＪ達
することが出来ない。即ち、これは主回路１ｄ流１３が
倣動することを意味している。この傾向は、市、流の変
化率設定が大きい程大きく、又Ｎ ＋ｆｆ１ｆ流？ｔ３
、動機３に代表される主回路時定数をそれ以下の時定数
で制御しようとした場合に大きく現われる。この市流帰
ｊＹ’１．仙８のオーバシュート量は、主回路１［Ｉ７
流１３のη’ＳＪ ’ｊｔｔ’流に対応する為、通常、
主回路に設置される渦電流検出器（とこでは図示されず
）を−Ｉ！ＩＪｈ作させてしまう欠点も生じる。FIG. 3 shows the relationship between the above current command value 10S current feedback value 8 and gate pulse 12! (This is a Yamasaku time chart.', When the u flow command value 1o changes, the current feedback value 8&-j: Follow this! 1111 (.At the 8 points of the gate pulse 12, the current command (1010 and the current 41 ”
(The difference from the i j 10% value 8 is calculated, and the next ignition signal is calculated from this difference.Next, at the L) point of gate pulse 12, the current, flow command value 1 (), and 11 points are calculated. Difference with Flow Return Marshal 8 V”
This difference is large, and the next firing phase C or fit, Jj?
：'J reru. 4) Current command j1fI even if z is 0 point,
There is a large difference between 1.0 and subcurrent return (1 (i, 8), and this difference determines the next firing position, ('1.11 (+ is usually; 1l
jj is calculated. However, at point d, the width; θii',
4 amount return (11! 18 (・), almost reached the target value /
However, due to the gate pulse, the flow section speed value 8 greatly overshoots.As a result, the firing phase of the 0 point of the gate pulse 12 is delayed, and the current Q) speed value 8 is delayed.
becomes an oscillating waveform, and QIJ cannot reach the first vote value smoothly. That is, this means that the main circuit 1d flow 13 follows. This tendency increases as the rate of change setting for city and style increases, and also for N + ff1f style? t3
, which appears significantly when trying to control the main circuit time constant, as represented by Motive 3, with a time constant smaller than that. This market returns jY'1. The overshoot amount of Sen8 is the main circuit 1 [I7
In order to correspond to the η'SJ 'jtt' flow of flow 13, normally,
An eddy current detector (not shown here) installed in the main circuit -I! There is also the disadvantage of causing IJh production.
本発明の目的は、上記の欠点全解消１１、オーバシュー
トが少なく安定に目標１１Ｌ流値に到達する’ｆＷ！！
！Ｉ磯の電流制御方法を提供することにイ）る本発明は
、ツーイリスタ変換器を用いて１〔１流電動機の電流を
制イ即する１（ｉ流制御装置に於いて、電流指令値と電
流帰還値との差が所定領置１・とηす、且つ、電流帰還
値の変化率が所定舶以トの’）、ｉ＋４ｒに、電流制御
系のゲインを通常より−１・げると、とにより、上記目
的を達成する。The purpose of the present invention is to completely eliminate the above-mentioned drawbacks 11, and to stably reach the target 11L flow value with little overshoot!'fW! !
! The present invention aims to provide a current control method using a twin-ristor converter. If the difference from the current feedback value is 1·η for a predetermined value, and the rate of change of the current feedback value is less than a predetermined value (i+4r), then if the gain of the current control system is increased by −1· from normal, , the above objective is achieved.
以下本発明の一実施例を従来例と同（Ｘｌ−分ケ」同符
号を用いて図面に従って説明する。An embodiment of the present invention will be described below with reference to the drawings using the same reference numerals as those of the conventional example.
第４図は本発明の′市動機の電流：１ｔｌｌσ１１方法
の一実施例を適用した電流制御装置を構成する′「１１
流制御器の処理フローを示したチャート図である。本実
施例の処理フローは第２図で示した従来例の処理フロー
にステップ２６，２７，２８．２９を付加したイＲ成を
有しておシ、所定の周期で起動される。FIG. 4 shows a current control device configuring an embodiment of the ``city motor current: 1tllσ11 method'' of the present invention.
FIG. 3 is a chart diagram showing the processing flow of the flow controller. The process flow of this embodiment has a structure in which steps 26, 27, 28, and 29 are added to the process flow of the conventional example shown in FIG. 2, and is started at a predetermined period.
ステップ２０で電流帰還値８を取込み、スーアソグ２１
で電流指令値１０全取込む。次のスウーノプ２６で電流
帰還値８の変化量を演算する。ステップ２２で電流指令
値１０と１（１，流ｊｊ１） ｊη“（値８との差を演
算する。ステップ２７でステソゲ２２により演算した差
が所定値以下であるかどうかを１（］断し７、以下であ
った場合ｔ」、ステツノ２８に、超過した場合はステッ
プ２：目こ行く。ステソゲ２８−Ｃｔ：１．ステップ２
６で演やし／こ電流帰う■植８の変化ＢＨが所シ、（埴
以上かどうか全’Ｉ′ｌｌ断し、所定イ的未満であれｔ
まステップ２３に行へ、）九定値以上であれ（ｒ」：ス
テツノ２９に行く。ス′ｒッグ２３ではステップ２２の
演算結果に電流制御系の通常のゲインを乗り−する。In step 20, the current feedback value 8 is taken in, and the current feedback value 21 is taken in.
Take in all 10 current command values. The next step 26 calculates the amount of change in the current feedback value 8. In step 22, the difference between the current command value 10 and 1 (1, flow jj1) 7. If it is less than t, go to step 28, if it exceeds step 2: go to step 28. Step 28-Ct: 1. Step 2
Play with 6 / Return to the current ■ Change BH of plant 8 is the place, (I'll cut it all off if it's more than Hani, and if it's less than the prescribed A)
Go to step 23.) If it is greater than the nine constant (r), go to step 29. In step 23, the calculation result of step 22 is multiplied by the normal gain of the current control system.
又、ステソゲ２ ｇではステップ２２の演３つ、結果に
電流１ｂ］制御系の通常のゲインより低いゲインを乗算
する。ステップ２４ではステップ２３又はステップ２９
の演算結果よりゲートパルスの位４１１角を演算し、こ
の演算結果である位相角をステップ２５でカウンタにセ
ットする。その後の動作Ｃ」、σに来例と同様である為
説明は省略する。」、た、本１’ｎ’３す」を適用した
電動機ｊｌｉ制御装置の全体構成例ケよ、第１図に示し
た４、゛ｑ成図と同一であり、上述した通り電流制御器
の処理フローが異なるだけであるため図示は省略する。In addition, in step 2g, the result of the three operations in step 22 is multiplied by a gain lower than the normal gain of the current 1b control system. In step 24, step 23 or step 29
The digit 411 angle of the gate pulse is calculated from the calculation result, and the phase angle, which is the calculation result, is set in a counter in step 25. The subsequent operations C'' and σ are the same as those in the previous example, so the explanation will be omitted. An example of the overall configuration of a motor control device to which ``, 1'n'3'' is applied is the same as the 4, q configuration shown in Figure 1, and as described above, the current controller Since the only difference is the processing flow, illustration is omitted.
第５図は本実施例の電流指令値１０と、電流帰還値８と
ゲートパルス１２との動作関係を示した線図である。電
流指令値１０が変化した時、電流帰還値８はこれに追従
する様に動く。ゲートパルス１２の３点では、電流指令
値１０とｒ［流部速値８との差が大きく、この差で次回
の点φ］（位相すが演算される。次にゲートパルス１２
の５点でも、電流指令値１０と電流帰還値８との差は大
きく、この差で次回の点弧位相Ｃが演算される。次に、
ゲートパルス１２の０点では、目標値（′Ｆ比泥流指令
値１０と゛′酸原流帰還値８の差が所定値以内に入シ、
伺且つ電流帰還値の変化率が所定値以上となっている為
、電流指令値１０と電流帰還値８との差に乗算される飄
流？１ｊｌＪ御系のゲインは通常のものよシ低ゲインの
ものが採用され、次回の点弧位相角ｄが少し遅れた角度
となる。このことにより、′電流帰還値８の目標値に対
するオーバシュート１．Ｊ。FIG. 5 is a diagram showing the operational relationship between the current command value 10, the current feedback value 8, and the gate pulse 12 in this embodiment. When the current command value 10 changes, the current feedback value 8 moves to follow it. At the three points of the gate pulse 12, there is a large difference between the current command value 10 and r[flow section velocity value 8, and this difference is used to calculate the next point φ] (phase.Next, the gate pulse 12
Even at the five points, the difference between the current command value 10 and the current feedback value 8 is large, and the next firing phase C is calculated based on this difference. next,
At the 0 point of the gate pulse 12, the difference between the target value ('F ratio mud flow command value 10 and '' acid source flow feedback value 8) is within a predetermined value,
Since the rate of change of the current feedback value is equal to or higher than the predetermined value, the current feedback value is multiplied by the difference between the current command value 10 and the current feedback value 8. The gain of the 1jlJ system is lower than the normal one, and the next ignition phase angle d is a little delayed. This results in an overshoot of the current feedback value 8 with respect to the target value. J.
は極端に少なくなり、安定した；！ｉｌｌ ｉｉ！ｌ応
谷に実」Ｊ（、することが出来る。ここで、上記ｆｉｊ
’ｔ）Ｌ ４＋σ、）１旧１（１の変化率の所定値は
、制御系の応答で決′まる最大変化率の７０〜８０％が
最適である。又、′電流指令ｆ１白１０と電流帰還佃８
との差の所定値は、（−Ｌ−、ｉｉｔ’３変化率の所定
値）×（−丈ングリングビツヂ時出口×１１０〜１２０
％どするのが最適である。同、上記電流帰還値の変化率
の利足を省１（Ｉ５すると、疋常状態で常時低ゲインが
乗算されることになる為、効果が半減する。又、８５４
図に７」＜シだ処理フローのステップの順序を入れ替え
ても同一の効果が４（Ｉられることはいう址でもない。has become extremely low and stable;! ill ii! It is possible to do this. Here, the above fij
't) L 4 + σ, ) 1 old 1 (1) The optimum predetermined value for the rate of change is 70 to 80% of the maximum rate of change determined by the response of the control system. Current feedback Tsukuda 8
The predetermined value of the difference between
It is best to use %. Similarly, if the rate of change of the current feedback value is omitted by 1 (I5), the effect will be halved because the low gain will always be multiplied in the normal state.
It is not true that the same effect can be obtained even if the order of the steps in the process flow is changed.
本実施例によれば、′１）Ｌ流？１５１Ｊ御器に力４い
て１（１：γＪｉｉｌｉｊ令値１０と電流値１０（ｆ速
値８どの差がノシ「定餡以ドで、且つ、’ｌｋｌ帰流値
８の変化量が所定１１１１以上である場合、電流指令値
１０と電流加速１１１′ｉ８とのＺ：に電流制御系の通
常ゲインよシ低ゲインを乗算することによシ、電流帰還
値８、即ち主回路Ｆ（を流のオーバシュート量を大幅に
低減し得る効果があシ、主回路電流を円滑に目標′電流
値に到達して安定した電動機電流の制御応答を実現し得
る効果がある。According to this embodiment, '1) L flow? 151J control force 4 and 1 (1: γJiillij value 10 and current value 10 (f speed value 8) Which difference is less than the constant value, and the amount of change in 'lkl return value 8 is more than the predetermined 1111 In this case, the current feedback value 8, that is, the main circuit F (of the current This has the effect of greatly reducing the amount of overshoot, and also allows the main circuit current to smoothly reach the target current value, thereby realizing a stable motor current control response.
特に、従来では高応答時に約３０％以上のオーバ／ニー
ト量があったが、本実施例ではぞのオーバシュートはを
約５％以下に低減さぜることか可能となった。なお、上
記電流７１７１ｊ御器し、１、マイクロコンビ３−夕等
で構成される。In particular, in the past, there was an over/neat amount of about 30% or more during high response, but in this embodiment, it is possible to reduce the overshoot to about 5% or less. In addition, the above-mentioned current 7171j is controlled and is composed of 1, a micro combination 3, and the like.
以上記述した如く本発明の電動機の市１０Ｍ、’ｄｉ１
．制御方法によれば、オーバシュートが少なく安＞’ｊ
ＪｌにＬ１標電流値に到達させることが出来る。As described above, the electric motor city 10M, 'di1 of the present invention
．． According to the control method, the overshoot is small and the safety>'j
Jl can be made to reach the L1 standard current value.
第１図は従来のブイリスク変換器を月１いた直流′電動
機の電流／１ｌｉｌＪ御装置の一例を示した））’ＩＩ
Ｊν、図、第２図はＣ（１１図で示した′〔ｄしｔｊ
ｔｌｉｌｌ （ｉ１４１器の処理ノローチャート図、第
３図は第１図で示した制ｎ１１１装置の電流指令値と電
流帰還値とゲートパルスとの動作関係を示したタイムチ
ャート図、４４図は本発明の電動機の電流１１ｊｌＪ御
方法の一実施例を適用した電流制御装置の要部である電
流制御器の処理フローチャー１・図、第５図は本実施例
の電流指令（＋にと、電流帰還値とゲートパルスとの動
作関係を示したタイムチャート図である。
２・・・ブイリスク変換器、３・・・電動機、９・・・
電流制御器、１１・・・ゲーレ（ルス発生器。
第２１図
弔３図
（ＬｂＣｄ ｅｆ（ｉ
第４図
弔５図
（ＬｂＣｄｅｆ’ｊFigure 1 shows an example of a device that controls the current/1lilJ of a DC motor using a conventional builisk converter once a month))'II
Jν, Figure 2 shows C ('[d and tj shown in Figure 11)
tlill (I141 device processing flow chart, Figure 3 is a time chart showing the operational relationship between the current command value, current feedback value, and gate pulse of the control n111 device shown in Figure 1, and Figure 44 is the main Processing flowchart 1 of the current controller, which is the main part of the current control device to which an embodiment of the method for controlling the current 11jlJ of a motor according to the invention is applied, and FIG. It is a time chart diagram showing the operational relationship between the feedback value and the gate pulse. 2... Builisk converter, 3... Electric motor, 9...
Current controller, 11...Gere (Russ generator.
Claims (1)
’？！動機に供給するもので、この１ａ汐１１、（ＩＩ
、ｒ（（ｆ１機に供給される電流を電流制御系を通して
検出プることによって電流帰還値を得、この′ｔ１ε流
Ｊｉ１ｔ 、ｌＹ＋ｆ他が設定電流指令値になるように
制御する′ｌｌｉ動磯の動機方法において、電流指令値
と電流錦還値との差が所定値以下であるかどうかを判定
するＪ一段と、電流帰還値の変化率が所定値以上である
かどうかを判定する手段とを設け、前記２つの判＞１手
段によシ両条件が同時に満足された時、前記電流制御系
のゲインを通常のそれよりも低下させることを特徴とす
る電動機の制御方法。(II
. The motive method includes a step J for determining whether the difference between the current command value and the current feedback value is less than or equal to a predetermined value, and a means for determining whether the rate of change of the current feedback value is greater than or equal to the predetermined value. A method for controlling an electric motor, characterized in that the gain of the current control system is lowered than a normal gain when both conditions are simultaneously satisfied according to the two conditions>1 means.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP57152620A JPS5944995A (en) | 1982-09-03 | 1982-09-03 | Controlling method for motor |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP57152620A JPS5944995A (en) | 1982-09-03 | 1982-09-03 | Controlling method for motor |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS5944995A true JPS5944995A (en) | 1984-03-13 |
| JPH0156639B2 JPH0156639B2 (en) | 1989-11-30 |
Family
ID=15544355
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP57152620A Granted JPS5944995A (en) | 1982-09-03 | 1982-09-03 | Controlling method for motor |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS5944995A (en) |
-
1982
- 1982-09-03 JP JP57152620A patent/JPS5944995A/en active Granted
Also Published As
| Publication number | Publication date |
|---|---|
| JPH0156639B2 (en) | 1989-11-30 |
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