JPH0815396B2 - Controller for three-phase PWM inverter - Google Patents
Controller for three-phase PWM inverterInfo
- Publication number
- JPH0815396B2 JPH0815396B2 JP61170153A JP17015386A JPH0815396B2 JP H0815396 B2 JPH0815396 B2 JP H0815396B2 JP 61170153 A JP61170153 A JP 61170153A JP 17015386 A JP17015386 A JP 17015386A JP H0815396 B2 JPH0815396 B2 JP H0815396B2
- Authority
- JP
- Japan
- Prior art keywords
- signal
- wave
- phase
- circuit
- voltage
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Lifetime
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- Inverter Devices (AREA)
Description
【発明の詳細な説明】 〔産業上の利用分野〕 本発明は、交流電動機の可変速駆動装置や、交流無停
電電源装置に用いる電圧形三相PWMインバータの制御装
置に関する。Description: TECHNICAL FIELD The present invention relates to a variable speed drive device for an AC motor and a control device for a voltage type three-phase PWM inverter used in an AC uninterruptible power supply device.
交流電動機を可変速駆動する場合あるいは、発電機か
ら一定周波数の交流電圧を得るために電圧形三相PWMイ
ンバータが使用されている。A voltage type three-phase PWM inverter is used to drive an AC motor at a variable speed or to obtain an AC voltage of a constant frequency from a generator.
第７図に、代表的な電圧形三相PWMインバータのブロ
ック図を、第８図に各部の波形を示す。第８図におい
て、（ａ）は信号波である三相正弦波と三角波である搬
送波の関係を示し、（ｂ），（ｃ），（ｄ）はそれぞれ
各相のパルス幅変調波形を示している。これらの図にお
いて、直流回路中性点ndcに対する相電圧の基本波成分
は、Ｕ相に例をとると、 eu＝1/2kEdcsinωｔ（ただし、ｋは変調率） となる。また、Ｕ−Ｖ間の線間電圧は、 となり、ｋ＝１の場合でも出力線間電圧のピーク値は、
直流電圧の 倍しか出ず、直流電圧を十分に利用することはできな
い。FIG. 7 shows a block diagram of a typical voltage-type three-phase PWM inverter, and FIG. 8 shows the waveform of each part. In FIG. 8, (a) shows the relationship between the three-phase sine wave which is the signal wave and the carrier wave which is the triangular wave, and (b), (c) and (d) show the pulse width modulation waveforms of the respective phases. There is. In these figures, the fundamental wave component of the phase voltage with respect to the DC circuit neutral point n dc is e u = 1 / 2kE dc sin ωt (where k is the modulation factor) when the U phase is taken as an example. The line voltage between U and V is Therefore, even when k = 1, the peak value of the output line voltage is
DC voltage The output is only doubled and the DC voltage cannot be fully utilized.
この問題点を解消するための方策として、PWMの指令
信号波形に３倍の周波数（及びその高調波を含む）成分
の高調波（３倍調波）を重畳させる方法が、昭和59年の
電気学会全国大会発表等により広く知られている。これ
は、三相インバータの場合、３次及びその倍調波成分
は、同相成分となり、線間電圧には現れず、負荷の中性
点が浮動状態である限り、電流に影響を与えないことを
利用したものである。As a measure to solve this problem, a method of superimposing a harmonic (triple harmonic) of a triple frequency component (and its harmonics) on the PWM command signal waveform It is widely known for announcements at national conferences. This is because in the case of a three-phase inverter, the third-order and its harmonic components become in-phase components, do not appear in the line voltage, and do not affect the current as long as the neutral point of the load is floating. Is used.
第９図に３倍調波重畳の効果を波形で示す。同図にお
いて、eu,evは相電圧、eu′,ev′は相電圧eu,evに基本
波の1/6の振幅の３倍調波を注入した後の波形である。
このとき、eu′,ev′のピーク値は相電圧eu,evより低く
なるので、eu,evのピーク値まで持ち上げることができ
る。eu′,ev′は持ち上げた後の波形である。また、e
u-vは３倍調波を入れないときの線間電圧、eu′-v′は
３倍調波を注入した後の線間電圧で、後者は前者の 電圧が上昇する。FIG. 9 shows a waveform of the effect of the triple harmonic superposition. In the figure, is e u, e v is the phase voltage, e u ', e v' is the phase voltage e u, e v after injection of 3 times harmonics amplitude of 1/6 of the fundamental wave to the waveform .
In this case, e u ', e v' peak value phase voltage e u of, becomes lower than e v, it can be lifted up to the peak value of e u, e v. e u ′ and e v ′ are the waveforms after lifting. Also, e
uv at line voltage when no put 3 times harmonics, e u '-v' is a line voltage after injection of the triple harmonics, the latter of the former The voltage rises.
しかしながら、この提案は、理論上のみに留まり、実
際にどのような手段によって実現するかについての提案
はなされていない。一般的には、３倍調波を得るために
は、三角関数の公式 3sinθ−4sin3θ＝sin3θ を適用し、基本波の３乗回路及び減算回路を組み合わ
せ、更に各相がアンバランスの場合の補正回路等が必要
となり、かなり複雑な構成としなければならない。この
ように、３倍調波を重畳するためには、実用面では、３
倍調波の信号を発生させるのが簡単でないという問題が
あった。However, this proposal remains only in theory, and no proposal has been made as to what kind of means is actually realized. In general, in order to obtain the 3-fold harmonics applies the official 3sinθ-4sin 3 θ = sin3θ trigonometric, combining cube circuit and a subtraction circuit of the fundamental wave, further if each phase unbalanced A correction circuit and the like are required, and the configuration must be fairly complicated. In this way, in order to superimpose the triple harmonic, in practical terms,
There is a problem that it is not easy to generate a harmonic signal.
予め決められた周波数，振幅の電圧であれば３倍調波
を重畳した波形が得られるように信号発生器をプログラ
ムしておけばよいが、任意の周波数，振幅を持った三相
の電圧指令信号から３倍調波を得るのは簡単ではない。If the voltage has a predetermined frequency and amplitude, the signal generator may be programmed so that a waveform in which the triple harmonic is superimposed can be obtained. However, a three-phase voltage command with an arbitrary frequency and amplitude Obtaining the third harmonic from a signal is not trivial.
本発明は、このような現状の問題点に鑑みてなされた
ものであり、簡単な方法により３倍調波を得ることを目
的とする。The present invention has been made in view of such problems in the present situation, and an object thereof is to obtain a triple harmonic wave by a simple method.
この目的を達成するため、本発明の三相PWMインバー
タの制御装置は、三相正弦波PWMインバータの三相の電
圧指令信号を全波整流し、その直流出力回路の中性点電
位を３倍調波信号として得る手段と、この３倍調波信号
と搬送波とを加算して変調波を得る手段と、この変調波
と前記三相の各電圧指令信号とを比較し、PWM制御信号
を発生する手段とを備えたことを特徴とする。In order to achieve this object, the control device of the three-phase PWM inverter of the present invention full-wave rectifies the three-phase voltage command signal of the three-phase sine wave PWM inverter, and triples the neutral point potential of the DC output circuit. A means for obtaining a harmonic signal, a means for obtaining a modulated wave by adding the triple harmonic signal and a carrier wave, and a comparison between this modulated wave and each of the three-phase voltage command signals to generate a PWM control signal And means for doing so.
第１図に本発明による３倍調波を得るためのの基本的
構成を示す。この回路は、三相正弦波電圧指令信号の最
大値及び最小値そしてこれらの和信号e3をとる回路より
構成されている。これらの回路は、具体的には、第３図
に示すD1〜D6からなるダイオードブリッジと抵抗器R1,R
2からなる加算器という簡単な構成により実現する。図
１において、eA,eB,eCは三層正弦波電圧指令信号であ
る。最大値回路及び最小値回路によってこれらの三相正
弦波電圧指令信号eA,eB,eCの最大値及び最小値をとる
と、第２図にそれぞれ太線で示すeH,eLとなる。さらに
これらの最大値信号eH及び最小値信号eLは、eA,eB,eCの
３倍の周波数を持っているので、重畳すべき３倍調波と
して有効である。また、好都合なことにeA,eB,eCの原点
（ゼロクロス）とe3の原点が一致しているので、重畳後
の波形の対称性が確保される。FIG. 1 shows a basic configuration for obtaining a triple harmonic according to the present invention. This circuit is composed of a circuit that takes the maximum value and the minimum value of the three-phase sine wave voltage command signal and the sum signal e 3 of these values. These circuits, specifically, D 1 to D 6 diode bridge consisting of a resistor R 1 shown in FIG. 3, R
It is realized by a simple configuration of an adder consisting of 2 . In FIG. 1, e A , e B , and e C are three-layer sinusoidal voltage command signals. When the maximum value and the minimum value of these three-phase sine wave voltage command signals e A , e B , and e C are taken by the maximum value circuit and the minimum value circuit, they become e H and e L shown by the bold lines in FIG. 2, respectively. . Further, since the maximum value signal e H and the minimum value signal e L have a frequency three times as high as e A , e B , and e C , they are effective as triple harmonics to be superimposed. Further, since the origins (zero crossings) of e A , e B , and e C and the origin of e 3 are coincident with each other, the symmetry of the waveform after superposition is ensured.
このようにして３倍調波信号を容易に得ることができ
る。In this way, the third harmonic signal can be easily obtained.
以下、本発明の実施例について説明する。 Examples of the present invention will be described below.
第３図は３倍調波信号を得るための実施例を示すもの
であり、三相の正弦波電圧指令信号eA,eB,eCはダイオー
ドブリッジで構成された三相全波整流回路に接続されて
いる。Ａ点電位は、各相の最大値信号eHとなり、Ｂ点電
位は同じく最小値信号eLとなる（第２図参照）。この最
大値信号eHと最小値信号eLとの和をとることにより、３
倍調波信号e3を得ることができる。Figure 3 is shows an example for obtaining a triple harmonic signal, three-phase sinusoidal voltage command signal e A, e B, e C is three-phase full-wave rectifier circuit composed of a diode bridge It is connected to the. The potential at the point A becomes the maximum value signal e H of each phase, and the potential at the point B becomes the minimum value signal e L (see FIG. 2). By taking the sum of the maximum value signal e H and the minimum value signal e L ,
A subharmonic signal e 3 can be obtained.
第４図は、３倍調波信号を得るための他の実施例を示
すものであり、信号の電圧が低い場合のダイオードによ
る電圧降下を補償したものである。即ち、ダイオードD7
及びD8によってダイオードブリッジの電圧降下を補償
し、演算増幅器OPA1によって最大値信号eHと最小値信号
eLとの和をとることにより３倍調波信号e3を得る。FIG. 4 shows another embodiment for obtaining the third harmonic signal, in which the voltage drop due to the diode when the voltage of the signal is low is compensated. That is, the diode D7
And D8 compensate the diode bridge voltage drop, and the operational amplifier OPA1 provides the maximum value signal e H and the minimum value signal.
The third harmonic signal e 3 is obtained by taking the sum with e L.
第５図に、第３図の回路で得られた３倍調波と搬送波
とを加算し、それを元の信号波と比較し、PWM制御を行
う本発明実施例の回路を示す。第６図に示すように、３
倍調波e3と搬送波e4とを演算増幅器OPA2で加算すること
により変調波e5を作り、これを元の信号波と比較するこ
とによりインバータのPWM制御を行うことができる。FIG. 5 shows a circuit of an embodiment of the present invention which performs PWM control by adding the third harmonic wave and the carrier wave obtained by the circuit of FIG. 3 and comparing the result with the original signal wave. As shown in FIG. 6, 3
The harmonic wave e 3 and the carrier wave e 4 are added by the operational amplifier OPA 2 to create a modulated wave e 5 , and by comparing this with the original signal wave, the PWM control of the inverter can be performed.
以上に説明したように、本発明においては、三相の電
圧指令信号を全波整流し、その直流出力回路の中性点電
位を３倍調波信号として得るようにしている。これによ
り、簡単な回路で任意の周波数，振幅を持った三相の電
圧指令信号から３倍調波信号を得ることができ、出力電
圧を増加し、同一電流容量の装置で出力の向上を図るこ
とができる。As described above, in the present invention, the three-phase voltage command signals are full-wave rectified, and the neutral point potential of the DC output circuit is obtained as the triple harmonic signal. This makes it possible to obtain a triple harmonic signal from a three-phase voltage command signal having an arbitrary frequency and amplitude with a simple circuit, increase the output voltage, and improve the output with a device having the same current capacity. be able to.
第１図は本発明に係る３倍調波信号を得るための回路の
基本的構成を示すブロック図、第２図はその作用を示す
波形図、第３図は３倍調波信号を得るための具体的実施
例を示す回路図、第４図は３倍調波信号を得るための他
の実施例を示す回路図、第５図は本発明の制御装置を用
いてPWM制御を行うための回路図、第６図は同回路の動
作を示す波形図、第７図は従来のPWM制御回路構成を示
す回路図、第８図は同回路の動作波形図、第９図は３倍
調波を用いた場合の効果を示す波形図である。FIG. 1 is a block diagram showing a basic configuration of a circuit for obtaining a triple harmonic signal according to the present invention, FIG. 2 is a waveform diagram showing its operation, and FIG. 3 is a diagram showing a triple harmonic signal. FIG. 4 is a circuit diagram showing a specific embodiment of the present invention, FIG. 4 is a circuit diagram showing another embodiment for obtaining a triple harmonic signal, and FIG. 5 is a circuit diagram for performing PWM control using the control device of the present invention. Circuit diagram, FIG. 6 is a waveform diagram showing the operation of the circuit, FIG. 7 is a circuit diagram showing a conventional PWM control circuit configuration, FIG. 8 is an operation waveform diagram of the circuit, and FIG. 9 is a triple harmonic wave. It is a wave form diagram which shows the effect at the time of using.
Claims (1)
令信号を全波整流し、その直流出力回路の中性点電位を
３倍調波信号として得る手段と、この３倍調波信号と搬
送波とを加算して変調波を得る手段と、この変調波と前
記三相の各電圧指令信号とを比較し、PWM制御信号を発
生する手段とを備えたことを特徴とする三相PWMインバ
ータの制御装置。1. A means for full-wave rectifying a three-phase voltage command signal of a three-phase sine wave PWM inverter to obtain a neutral point potential of a DC output circuit thereof as a triple harmonic signal, and the triple harmonic signal. And a carrier wave to obtain a modulated wave, and the modulated wave and each of the three-phase voltage command signals are compared, and a means for generating a PWM control signal is provided. Inverter control device.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP61170153A JPH0815396B2 (en) | 1986-07-18 | 1986-07-18 | Controller for three-phase PWM inverter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP61170153A JPH0815396B2 (en) | 1986-07-18 | 1986-07-18 | Controller for three-phase PWM inverter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS6328276A JPS6328276A (en) | 1988-02-05 |
| JPH0815396B2 true JPH0815396B2 (en) | 1996-02-14 |
Family
ID=15899664
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP61170153A Expired - Lifetime JPH0815396B2 (en) | 1986-07-18 | 1986-07-18 | Controller for three-phase PWM inverter |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPH0815396B2 (en) |
Families Citing this family (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP5879821B2 (en) * | 2011-08-25 | 2016-03-08 | 日産自動車株式会社 | Motor control device and motor control method |
Family Cites Families (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH0720373B2 (en) * | 1984-03-26 | 1995-03-06 | サンケン電気株式会社 | 3-phase static power converter |
-
1986
- 1986-07-18 JP JP61170153A patent/JPH0815396B2/en not_active Expired - Lifetime
Also Published As
| Publication number | Publication date |
|---|---|
| JPS6328276A (en) | 1988-02-05 |
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