JPH0283461A - Method for measuring insulation resistance compensated in effect of earth resistance - Google Patents
Method for measuring insulation resistance compensated in effect of earth resistanceInfo
- Publication number
- JPH0283461A JPH0283461A JP23696488A JP23696488A JPH0283461A JP H0283461 A JPH0283461 A JP H0283461A JP 23696488 A JP23696488 A JP 23696488A JP 23696488 A JP23696488 A JP 23696488A JP H0283461 A JPH0283461 A JP H0283461A
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- output
- voltage
- insulation resistance
- component
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Links
- 238000009413 insulation Methods 0.000 title claims abstract description 30
- 238000000034 method Methods 0.000 title claims description 14
- 230000000694 effects Effects 0.000 title description 2
- 238000005259 measurement Methods 0.000 claims description 14
- 238000000691 measurement method Methods 0.000 claims description 4
- 238000001514 detection method Methods 0.000 abstract description 10
- 230000001360 synchronised effect Effects 0.000 abstract description 9
- 238000010586 diagram Methods 0.000 description 6
- 238000007796 conventional method Methods 0.000 description 2
- 238000006243 chemical reaction Methods 0.000 description 1
- 230000007547 defect Effects 0.000 description 1
- 230000007812 deficiency Effects 0.000 description 1
- 230000000149 penetrating effect Effects 0.000 description 1
- 230000010363 phase shift Effects 0.000 description 1
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- Measurement Of Resistance Or Impedance (AREA)
Abstract
Description
【発明の詳細な説明】 （産業上の利用分野） 本発明は電路等の絶縁抵抗を測定する方法。[Detailed description of the invention] (Industrial application field) The present invention is a method for measuring insulation resistance of electrical circuits, etc.
殊に対地浮遊容量大なる場合無視し得なくなる接地抵抗
の影響を補償した絶縁抵抗測定方法に関する。In particular, the present invention relates to an insulation resistance measurement method that compensates for the influence of ground resistance, which cannot be ignored when stray capacitance to ground becomes large.
（従来技術）
従来、漏電等の早期発見の為には第２図に示す如き電路
の絶縁抵抗測定方法を用いるのが一般的であった。(Prior Art) Conventionally, for early detection of electrical leakage, etc., it has been common to use a method of measuring the insulation resistance of electrical circuits as shown in FIG.
即ち、Ｚなろ負荷を有する受電変圧器Ｔの第２種接地線
ＬＥｙ介して発振器Ｏ８Ｃから商用周波数と異なった周
波数ｆ１なる測定用低周波信号電圧を電路Ｌ１及びＬ２
に印加し、前記接地線Ｌｇ？：貫通する変流器ＺＣ’ｌ
’によって絶縁抵抗Ｒ及び浮遊容量Ｃを介して帰還する
漏洩電流を検出する。That is, a low frequency signal voltage for measurement having a frequency f1 different from the commercial frequency is transmitted from the oscillator O8C to the electric lines L1 and L2 through the second type grounding line LEy of the power receiving transformer T having a Z-shaped load.
and the ground wire Lg? : Penetrating current transformer ZC'l
' detects the leakage current that returns via the insulation resistance R and stray capacitance C.
この際前記変流器ｚＣＴの出力に含まれる周波数ｆ１の
成分をフィルタＦＩＬＴにて検出しその漏洩電流を例え
ば前記発振器Ｏ８Ｃの出力を用いて掛算器ＭＵＬＴで同
期検波して有効分電流を分離して得、これによって電路
の絶縁抵抗を測定するものであった。At this time, a frequency f1 component included in the output of the current transformer zCT is detected by a filter FILT, and its leakage current is synchronously detected by a multiplier MULT using, for example, the output of the oscillator O8C to separate the effective component current. This was used to measure the insulation resistance of the electrical circuit.
その測定理論を第３図の等節回路を用いて更に説明する
ならば前記接地線ＬＥの接地点Ｅを介して前記発掘器Ｏ
８Ｃに帰還する電流を工とすると
であるから印加する測定信号電圧と同相の成分。To further explain the measurement theory using the equinodal circuit shown in FIG. 3, the excavator O
If we consider the current that returns to 8C, it is a component that is in phase with the applied measurement signal voltage.
即ち上記（１）式右辺第１項に比例した値を同期検波等
の手法を用いて検出すれば絶縁抵抗Ｒに逆比例した測定
値を得るものである。That is, if a value proportional to the first term on the right side of the above equation (1) is detected using a method such as synchronous detection, a measured value inversely proportional to the insulation resistance R can be obtained.
しかしながら上記（１）式からも明らかな如くこの測定
法は接地Ｉｖｌ！ＬＥに大地を介して帰還する電流を測
定するにも拘らず接地抵抗を無視しているので対地浮遊
容量Ｃが大きくなると接地抵抗の影響が現われ測定値が
現実の電路の絶縁抵抗とはなはだしくかけ離れたものと
なる。即ち正確な絶縁抵抗の測定が不可能になるという
欠陥があった。However, as is clear from equation (1) above, this measurement method is effective at grounding Ivl! Although the current returning to the LE via the ground is measured, the grounding resistance is ignored, so when the stray capacitance C to ground becomes large, the influence of the grounding resistance appears, and the measured value becomes extremely different from the insulation resistance of the actual electrical circuit. Become something. That is, there was a defect that accurate measurement of insulation resistance was impossible.
（発明の目的）
本発明は上記欠点に鑑みなされたものであって、対地浮
遊容量Ｃの影響を受けることなく正確な絶縁抵抗測定を
行なう絶縁抵抗測定方法を提供することを目的とする。(Object of the Invention) The present invention has been made in view of the above-mentioned drawbacks, and an object of the present invention is to provide an insulation resistance measuring method that accurately measures insulation resistance without being affected by the stray capacitance C to the ground.
（発明の概’ｆｆ）
この目的を達成するために本発明の絶縁抵抗測定方法は
電路に商用周波数と異なる周波数ｆ１なる低周波の測定
信号電圧を印加し、接地線に帰還する周波数ｆｔの漏洩
電流中の有効分並びに無効分を検出すると共に上記電路
と大地間の周波数ｆｔの電圧を検出し、該周波数ｆ１の
電圧と上記測定信号電圧との位相差を得、前記有効分に
前記無効分と前記位相差とのｆｆ’に加算することによ
り絶縁抵抗を測定するよう手段を講する。(Summary of the Invention 'ff) In order to achieve this object, the insulation resistance measuring method of the present invention applies a low frequency measurement signal voltage having a frequency f1 different from the commercial frequency to the electric line, and leaks a frequency ft which returns to the ground line. The effective component and the reactive component in the current are detected, and the voltage at the frequency ft between the electric circuit and the ground is detected, the phase difference between the voltage at the frequency f1 and the measurement signal voltage is obtained, and the reactive component is added to the effective component. Measures are taken to measure the insulation resistance by adding ff' between the phase difference and the phase difference.
（実施例）
以下本発明を図面に示す実施例とに基づいて詳細に説明
する。(Example) The present invention will be described in detail below based on an example shown in the drawings.
先ず２本発明に係る絶縁抵抗測定方法を説明する前に、
その理解を助けろ為従来の手法の欠陥を少しく詳細に説
明する。First, before explaining the insulation resistance measuring method according to the present invention,
To help you understand this, I will explain the deficiencies of the conventional method in some detail.
第４図は接地抵抗γを考慮した場合の等価回路図である
。FIG. 4 is an equivalent circuit diagram in consideration of ground resistance γ.
この場合接地点Ｅを介して発掘器ＯＳＣに帰還する電流
を１１としこれを
Ｉ ＋ ＝ （Ａ＋ ｊ Ｂ ） Ｖ −（２）と
する。このとき
→Ｒとすると
であり（２）式で接地抵抗γを無視すれば前記（１）式
と同一になることはいうまでもない。In this case, the current returned to the excavator OSC via the ground point E is 11, which is I + = (A+ j B ) V - (2). In this case, if →R, then it goes without saying that if the grounding resistance γ is ignored in equation (2), it becomes the same as equation (1).
さて、（３）式において、対地浮遊容量Ｃ＝０のときＡ
は一工−となるが一般にＲ）γであるかＲ＋γ
らＡは１／Ｒと考えてよく前記（２）式の同相分はＶ／
Ｒとなシ、同相分を検出することにより絶縁抵抗を測定
することができる。しかし浮遊容量Ｃが太きいときには
同相分を検出しても（３）式で示される如く正しい絶縁
抵抗を測定していないことになる。Now, in equation (3), when the stray capacitance to ground C=0, A
is one step -, but generally R) γ or R + γ and A can be considered to be 1/R, and the in-phase component of the above equation (2) is V/
Insulation resistance can be measured by detecting the in-phase component of R. However, when the stray capacitance C is large, even if the in-phase component is detected, the correct insulation resistance will not be measured as shown by equation (3).
このような誤差が実際上どの程度になるかを以下に示す
。The actual extent of such errors will be shown below.
一般にＲ）γであるから（３）式においてＲ＋ｒと表し
得る。Generally R) γ, so it can be expressed as R+r in formula (3).
ここで例えば ｆｔ＝２０Ｈｚ、Ｃ＝−５ｚｌＦ。Here, for example, ft=20Hz, C=-5zlF.
γ＝１００Ωとすると
（ω１Ｃγ）＝（２πＸ２０Ｘ５Ｘ１０ Ｘ１００）
２主３．９５ ｘ １０−’
となり（ω１Ｃγ）（１である。If γ = 100Ω, (ω1Cγ) = (2πX20X5X10 X100)
2 main 3.95 x 10-' (ω1Cγ) (1).
したがって（４）式は とみなしてよい。Therefore, equation (4) is It can be considered as
従ッテ９例えばｆｌ＝２０Ｈｚ 、Ｃ＝５μＦ、Ｒ＝１
００にΩ、γ＝１００Ωの場合前記（５）式の（）内は
１＋（ω１Ｃ）■ｔγ＝４．９５
となり、同相分から検出されるべき絶縁抵抗値１００
ＫΩは １００にΩ／４．９５ ＝２０．２ ＫΩ と
して測定されてしまうことになる。For example, fl=20Hz, C=5μF, R=1
00Ω and γ = 100Ω, the value in parentheses in the above equation (5) becomes 1 + (ω1C) tγ = 4.95, and the insulation resistance value to be detected from the in-phase component is 100Ω.
KΩ will be measured as 100Ω/4.95 = 20.2 KΩ.
斯くの如く、従来の接ｔｌｔ１．抵抗を無視した絶縁抵
抗測定方法では対地浮遊容量が大きい場合極めて測定誤
差が大きくなる欠陥を有すること前述の通）である。更
に対地浮遊容量には一般電子機器の電源回路に付加され
るノイズフィルタのキャパシタンスも含まれるので今後
対地浮遊客引は大きくなっていく傾向にあるから従来の
方法ではますます正確な測定結果が得られないことにな
る。As such, the conventional contact tlt1. As mentioned above, an insulation resistance measurement method that ignores resistance has the drawback that the measurement error becomes extremely large when the stray capacitance to ground is large. Furthermore, the stray capacitance to the ground includes the capacitance of noise filters added to the power supply circuits of general electronic equipment, so the stray capacitance to the ground is likely to increase in the future, so conventional methods cannot provide increasingly accurate measurement results. You will not be able to do so.
この問題を解決する為本発明に於いては以下の如き手法
欠とろ。In order to solve this problem, the following method is required in the present invention.
即ち２周波数ｆｌの印加信号によって得られる同相分’
ｇｉｇ１ とすると前記（２）弐及び（５）式から
がイＱられる。In other words, the in-phase component' obtained by the applied signals of two frequencies fl
If gig1 is set, then equations (2) and (5) above are expressed as follows.
一方、（３）式から印加信号と９０°位相のずれた成分
Ｂは
であり、又、一般にＲ＞Ｔであるため
と表わされ、更には（ωＩ Ｃｒ ） ＜ １ であ
るのでＢ≧ω Ｃ・・・・・・・・ （力
となるので接地抵抗ｒの影響は実用上はとんど受けない
ことになる。On the other hand, from equation (3), the component B that is 90° out of phase with the applied signal is , and it can be expressed that generally R>T, and furthermore, since (ωI Cr ) < 1, B≧ω C... (Since it becomes a force, the influence of grounding resistance r is hardly affected in practice.
従ってｆ＝なろ印加信号によって得られろ無効分ｉｇ２
とすれば（７）式から
ｉｇ、＝：ω１ｃｖ ・・・・・・・・・（８）
となる。Therefore, f = the invalid component ig2 obtained by the applied signal
Then, from equation (7), ig, =:ω1cv (8)
becomes.
ところで電路と大地間に存在する周波数ｆｔの電圧Ｅけ
１２＝Ｖ−１１γ ・・・・・・・・・（９）であり
、 （６１、＋８１式から漏洩電流工１は■
ｌ１＝１−＋（ω１Ｃ）γＶ十」ω、Ｃｖ ・・・・
・・・・・ （ト）と弄されるから（転）式ヲ（９）式
に代入するとＥ＝（１−−−（ω１Ｃγ） −Ｊω１Ｃ
γ）■ ・・・・・・・・・ （６）となり、ｒ／Ｒ（
１、（鮨Ｃγ）（１であるのでＥ＝（１−ｊω１Ｃγ）
■ ・・・・・・・・・（２）が得られろ。電路と大
地間に存在する周波数ｆｌの電圧Ｅと測定信号電圧■と
の位相差ψは−ψ＝−ω、Ｃｒ であり ω、Ｃｒ＜
１ であるためψ＝−ωＩＣγ ・・・・・・・
・・（至）となる。By the way, the voltage of frequency ft existing between the electric circuit and the ground Eke12=V-11γ (9), (From equations 61 and +81, the leakage current factor 1 is ■ l1=1- +(ω1C)γV0”ω, Cv...
・・・・・・ Since (g) is confused, substituting the (conversion) equation into equation (9) gives E=(1−−−(ω1Cγ) −Jω1C
γ)■ ・・・・・・・・・ (6), and r/R(
1, (Sushi Cγ) (1, so E = (1-jω1Cγ)
■ ・・・・・・・・・(2) should be obtained. The phase difference ψ between the voltage E of frequency fl existing between the electric circuit and the ground and the measurement signal voltage ■ is -ψ=-ω, Cr, and ω, Cr<
1, so ψ=-ωICγ...
... (to).
したがって、（６）式のｉｇに（８）式の１ｇ２と（至
）式のψの積を加算すると
■
。 °°゛°°°゛（２）
となるので接地抵抗γの影響なく絶縁抵抗を測定しうろ
ことが分かる。Therefore, if we add the product of 1g2 in equation (8) and ψ in equation (to) to ig in equation (6), we get ■. °°゛°°°゛(2) Therefore, it can be seen that the insulation resistance can be measured without the influence of the grounding resistance γ.
上述したような理論に基づいて測定を実際に行なうため
には以下の如くすればよい。In order to actually carry out measurements based on the above-mentioned theory, the following steps can be taken.
第１図は本発明に係る絶縁抵抗測定方法を実現する為の
回路の一実施例を示す図である。FIG. 1 is a diagram showing an embodiment of a circuit for realizing the insulation resistance measuring method according to the present invention.
即ち、接地線Ｌｒ、に周波数ｆｌなろ低周波信号発生用
の発振器Ｏ８Ｃを直列に接続して、電圧■なろ電圧を印
加する。−万前記零相変流器ＺＣＴ出力を周波数ｆｌ成
分を検出するフィルタＦＩＬＴに印加して、商用周波成
分と分離し該フィルタＦＩＬ’ｌ’のｍ力を第１の同期
検波回路Ｍ［ＪＬＴｌの一万の入力端に入力せしめろと
共に前記発振器Ｏ８Ｃの出力を第１の同期検波回路ＭＵ
Ｌ’ｐｔの第２の入力端に入力せしめる。かくして第１
の同期検波回路ＭＵＬＴＩの出力を第１のローパスフィ
ルタＬＰＦ’ｒに印加し直流分のみを得れば、前述の（
６）式に和尚する有効分ｉｇ１が得られる。That is, an oscillator O8C for generating a low frequency signal having a frequency of fl is connected in series to the ground line Lr, and a voltage of about 1 is applied. - The output of the zero-phase current transformer ZCT is applied to the filter FILT that detects the frequency fl component, and is separated from the commercial frequency component. The output of the oscillator O8C is inputted to the input terminal of the first synchronous detection circuit MU.
It is input to the second input terminal of L'pt. Thus the first
By applying the output of the synchronous detection circuit MULTI to the first low-pass filter LPF'r and obtaining only the DC component, the above (
6) An effective component ig1 is obtained that satisfies the equation.
一方、前記バンドパスフィルタＢＰＦの出力を分岐して
第２の同期検波回路ＭＵＬＴ２の一万の入力端に入力せ
しめると共に前記発振器Ｏ８Ｃの出力な移相器ＰＳに印
加して９０°位相を推移せしめその出力を第２の同期検
波回路ＭＬＩＬ’ｌ’ｔの第２の入力端に入力せしめろ
。かくして第２の同期検波回路ＭＵＬＴ２の出力を第２
のローパスフィルｐＬＰＦｚに印加し直流分のみ乞得れ
ば前述の（８）式に相当する無効分ｉｇ２が得られろ。On the other hand, the output of the band pass filter BPF is branched and inputted to the input terminal of the second synchronous detection circuit MULT2, and also applied to the phase shifter PS, which is the output of the oscillator O8C, to shift the phase by 90°. Input the output to the second input terminal of the second synchronous detection circuit MLIL'lt. In this way, the output of the second synchronous detection circuit MULT2 is
If only the DC component is obtained by applying it to the low-pass filter pLPFz, the reactive component ig2 corresponding to the above-mentioned equation (8) can be obtained.
更に接地（１１ｉ１電路Ｌ２と大地Ｅ８との間の電圧Ｅ
を高入力インピーダンス増幅器Ａで検出し。Furthermore, the voltage E between the ground (11i1 electric circuit L2 and the earth E8)
is detected by high input impedance amplifier A.
その出力を位相差検出のためのかけ算器ＭＵＬ’ｌ’３
の一万の入力端に印加し、他方の入力端には発揚器Ｏ８
Ｃ出力を印加する。The output is multiplier MUL'l'3 for phase difference detection.
10,000 input terminal, and the other input terminal is an oscillator O8.
Apply C output.
斯くして前記かけ算器ＭＴＪＬ’ｌ’ｓの出力をｏ −
バスフィルタＬＰＦａに加えろことにより得ろ直流分は
日式に相当する位相差ψとなる。これは（２）式からも
明らかなように電圧ｅの振幅は〔１＋（ω１Ｃγ）２Ｊ
２Ｔ’−１であるから電路と大地間に存在する周波数ｆ
ｌの電圧ｅと測定用低周波信号電圧■との大きさは変わ
らないが位相のみψだけシフトしているので１発揚器Ｏ
８Ｃ出力と高入力インピーダンス増幅器器Ａの出力に得
られる周波数ｆ１の電圧ｅとをかけ算器ＭＬＩＬ’ｌ’
ｓに印加することにより位相差ψを得るものである。Thus, the output of the multiplier MTJL'l's becomes o −
The DC component obtained by adding it to the bus filter LPFa becomes a phase difference ψ corresponding to the Japanese type. As is clear from equation (2), the amplitude of voltage e is [1+(ω1Cγ)2J
2T'-1, so the frequency f that exists between the electric line and the ground
The magnitude of the voltage e of l and the low frequency signal voltage for measurement ■ is the same, but only the phase is shifted by ψ.
8C output and the voltage e of frequency f1 obtained at the output of high input impedance amplifier A, multiplier MLIL'l'
The phase difference ψ is obtained by applying it to s.
ｍＫローパスフィルタＬＰＦｓの出力をかけ算器ＭＬＪ
ＬＴ ４の一入力端に印加し、他の入力端にはローパス
フィルタＬＰＦｚの出力を印加すれば該ＭＵＬＴ４の出
力は１ｇ２Ｘψとなシ該ＭＴＪＬＴ４出力を加算器ＡＤ
Ｄに印加すると共に更に該加算６ＡＤＤ Ｋローパスフ
ィルタＬＰＦ １の出力を加えることにより加算器ＡＤ
Ｄの出力０［ＪＴはＯＬＩＴ＝ｉｇ ”ｇ２ψ
となるので絶縁抵抗を測定することが可能となる。The output of the mK low-pass filter LPFs is the multiplier MLJ.
If the voltage is applied to one input terminal of LT4 and the output of the low-pass filter LPFz is applied to the other input terminal, the output of the MULT4 becomes 1g2Xψ.The output of the MTJLT4 is applied to the adder AD.
By adding the output of the adder 6ADD K low-pass filter LPF1 to
Since the output of D is 0 [JT is OLIT=ig ``g2ψ'', the insulation resistance can be measured.
同、実施例に於いては説明簡単の為単相２線の場合を示
したが本発明はこれに限定する必然性は全くなく一端接
地の単相３線或は３相３線の場合であっても同一の原理
に基づいて実施可能なことは明らかであろう。Similarly, in the embodiment, a single-phase, two-wire case is shown for ease of explanation, but the present invention is not necessarily limited to this, and the present invention may be applied to a single-phase, three-wire case with one end grounded, or a three-phase, three-wire case. It will be clear that any method can be implemented based on the same principle.
なお、上記実施例においては零相電流の検出に零相変流
器を用いているが接地線Ｌｇを切断しこれに低抵抗を直
列接続しこの抵抗の両端電圧をもって零相電流を検出し
てもよい。また電路への低周波電圧の印加に当っては接
地線ＬＥを切断してこれに発掘器を直列に挿入接続する
のではなく、接地線を発振器出力のトランスを貫通させ
る等してもよい。高入力インピーダンス増幅器Ａの出力
に大きな商用周波成分が含まれるときは、商用周波成分
除去フィルタを増幅器Ａと同期検波器ＭＬＩＬＴ８の一
万の大力間に入れろことがのぞましい。In the above embodiment, a zero-sequence current transformer is used to detect the zero-sequence current, but it is also possible to cut the grounding wire Lg, connect a low resistance in series with it, and detect the zero-sequence current using the voltage across this resistance. Good too. Furthermore, when applying a low frequency voltage to the electric circuit, instead of cutting the ground line LE and inserting and connecting the excavator in series thereto, the ground line may be passed through an oscillator output transformer. When the output of the high input impedance amplifier A contains a large commercial frequency component, it is desirable to insert a commercial frequency component removal filter between the amplifier A and the synchronous detector MLILT8.
（発明の効果）
本発明は以上説明した如き手法によって電路の絶縁抵抗
を測定するものであるから接地抵抗の影響を完全にキャ
ンセルすることが可能となるのみならず発掘器等の出力
抵抗の影響をも接地抵抗に加味して補償するので対地浮
遊容量が大きい電路等の絶縁抵抗を正確に測定する上で
著しい効果を発揮する。(Effects of the Invention) Since the present invention measures the insulation resistance of an electric circuit using the method described above, it is possible to completely cancel the influence of ground resistance as well as the influence of output resistance of excavators, etc. Since it also takes into account the grounding resistance and compensates for it, it is extremely effective in accurately measuring the insulation resistance of electrical circuits with large stray capacitances to the ground.
第１図は本発明に係る絶縁抵抗測定方法を実現する為の
一実施例を示すブロック図、第２図は従来の絶縁抵抗測
定方法を説明する図、第３図は等価回路図、第４図は接
地抵抗を考慮した場合の等価回路図である。
Ｔ・・・・・・・・変圧器、 Ｌｌ及びＬ２・・
・・・・・・・電路、 ＬＥ・・・・・・・・接
地ｇ 、 ｏｓｃ・・・・・・・・発録器、
ＬＰＦｌ、２．ａ・・・・・・・・ローパスフィル
タ、 ＡＤＤ・・・・・・・・・加ｊｌ［。
Ｆ工ＬＴ・・・・・・・・・フィルタ、 ＰＳ
・・・・・・・・・９０°移相６． Ａ−・・・
・・・・・高入力インピーダンス増幅器。FIG. 1 is a block diagram showing an embodiment of the insulation resistance measuring method according to the present invention, FIG. 2 is a diagram explaining a conventional insulation resistance measuring method, FIG. 3 is an equivalent circuit diagram, and FIG. The figure is an equivalent circuit diagram when grounding resistance is considered. T......Transformer, Ll and L2...
......Electric circuit, LE......Grounding g, osc......Emitter,
LPFl, 2. a・・・・・・Low pass filter, ADD・・・・・・Additional jl[. F Engineering LT・・・・・・Filter, PS
...90° phase shift 6. A-...
...High input impedance amplifier.
Claims (1)
定信号電圧を印加し、接地線に帰還する周波数ｆ＿１の
漏洩電流中の有効分並びに無効分を検出すると共に上記
電路と大地間の周波数ｆ＿１の電圧を検出する絶縁抵抗
測定方法に於いて、前記電路と大地間の電圧と上記測定
信号電圧との位相差を検出し、前記有効分に前記無効分
と前記位相差との積を加算することにより絶縁抵抗を測
定することを特徴とした接地抵抗の影響を補償した絶縁
抵抗測定方法。A low-frequency measurement signal voltage with a frequency f_1 different from the commercial frequency is applied to the electric line, and the effective and reactive components of the leakage current at the frequency f_1 that returns to the ground line are detected, and the voltage at the frequency f_1 between the electric line and the earth is detected. In the insulation resistance measuring method for detecting the voltage between the electric circuit and the ground and the measurement signal voltage, the phase difference between the voltage and the measurement signal voltage is detected, and the product of the reactive component and the phase difference is added to the effective component. An insulation resistance measurement method that compensates for the influence of grounding resistance, which is characterized by measuring insulation resistance.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP23696488A JP2929197B2 (en) | 1988-09-21 | 1988-09-21 | Insulation resistance measurement method that compensates for the effect of ground resistance |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP23696488A JP2929197B2 (en) | 1988-09-21 | 1988-09-21 | Insulation resistance measurement method that compensates for the effect of ground resistance |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPH0283461A true JPH0283461A (en) | 1990-03-23 |
| JP2929197B2 JP2929197B2 (en) | 1999-08-03 |
Family
ID=17008376
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP23696488A Expired - Fee Related JP2929197B2 (en) | 1988-09-21 | 1988-09-21 | Insulation resistance measurement method that compensates for the effect of ground resistance |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JP2929197B2 (en) |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE102008006375A1 (en) | 2007-01-31 | 2008-08-21 | Fuji Jukogyo Kabushiki Kaisha | monitoring system |
-
1988
- 1988-09-21 JP JP23696488A patent/JP2929197B2/en not_active Expired - Fee Related
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE102008006375A1 (en) | 2007-01-31 | 2008-08-21 | Fuji Jukogyo Kabushiki Kaisha | monitoring system |
Also Published As
| Publication number | Publication date |
|---|---|
| JP2929197B2 (en) | 1999-08-03 |
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