JP5481165B2 - DC power supply device and air conditioner using the same - Google Patents

DC power supply device and air conditioner using the same Download PDF

Info

Publication number
JP5481165B2
JP5481165B2 JP2009254541A JP2009254541A JP5481165B2 JP 5481165 B2 JP5481165 B2 JP 5481165B2 JP 2009254541 A JP2009254541 A JP 2009254541A JP 2009254541 A JP2009254541 A JP 2009254541A JP 5481165 B2 JP5481165 B2 JP 5481165B2
Authority
JP
Japan
Prior art keywords
short
power supply
circuit
voltage
circuits
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
JP2009254541A
Other languages
Japanese (ja)
Other versions
JP2011101505A (en
Inventor
正博 田村
敦 奥山
聡明 岩城
建司 田村
知恵 右ノ子
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Hitachi Appliances Inc
Original Assignee
Hitachi Appliances Inc
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Hitachi Appliances Inc filed Critical Hitachi Appliances Inc
Priority to JP2009254541A priority Critical patent/JP5481165B2/en
Priority to KR1020100077235A priority patent/KR101194483B1/en
Priority to CN201010260619.8A priority patent/CN102055350B/en
Publication of JP2011101505A publication Critical patent/JP2011101505A/en
Application granted granted Critical
Publication of JP5481165B2 publication Critical patent/JP5481165B2/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/083—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the ignition at the zero crossing of the voltage or the current
    • F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
    • F24—HEATING; RANGES; VENTILATING
    • F24F—AIR-CONDITIONING; AIR-HUMIDIFICATION; VENTILATION; USE OF AIR CURRENTS FOR SCREENING
    • F24F11/00—Control or safety arrangements
    • F24F11/89—Arrangement or mounting of control or safety devices
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R19/00—Arrangements for measuring currents or voltages or for indicating presence or sign thereof
    • G01R19/175—Indicating the instants of passage of current or voltage through a given value, e.g. passage through zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Chemical & Material Sciences (AREA)
  • Combustion & Propulsion (AREA)
  • Mechanical Engineering (AREA)
  • General Engineering & Computer Science (AREA)
  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Rectifiers (AREA)
  • Control Of Ac Motors In General (AREA)
  • Inverter Devices (AREA)

Description

この発明は交流電源から得られる交流電圧を直流電源に変換し、電源高調波電流を抑制しつつ高力率，高効率を実現する直流電源装置およびこれを用いた空気調和機に関する。   The present invention relates to a DC power supply device that converts an AC voltage obtained from an AC power supply into a DC power supply and suppresses a power supply harmonic current while realizing a high power factor and high efficiency, and an air conditioner using the same.

インバータ駆動されるモータ負荷をもつ空気調和機などの機器において、その高効率化の手法の一つとして、モータのコイル巻線を多く巻き込み、モータに流れる電流を小さくすることで、インバータにおける損失を低減する方法がよく知られている。   In devices such as air conditioners with motor loads driven by inverters, one way to increase efficiency is to reduce the current in the inverter by winding a large number of motor coil windings and reducing the current flowing through the motor. Methods for reducing are well known.

しかしながら、この方法を実際に行う場合には、モータの誘起電圧がコイル巻数に比例して増加するため、機器に搭載される直流電源装置は、誘起電圧の増加見合分だけインバータへ供給する直流電圧を高くする必要がある。   However, when this method is actually performed, the induced voltage of the motor increases in proportion to the number of coil turns, so that the DC power supply device mounted on the device supplies the DC voltage supplied to the inverter by an amount corresponding to the increase in the induced voltage. Need to be high.

同時に、電力送電設備の負担軽減のため、直流電源装置には高力率，低高調波電流が求められており、リアクタを接続し短絡することで、入力電流の波形と直流電圧を制御する種々の方法が提案されている。この種の従来技術として、特公昭６３−１３２０４号公報，特許２８０９４６３号公報，特開平１０−２０１２４８号公報，特開２００３−１５３５４３号公報，特開２００６−１７４６８９号公報，特許０３４８５０４７号公報，特開２００９−１００４９９号公報が知られている。   At the same time, in order to reduce the burden on power transmission facilities, DC power supply devices are required to have high power factor and low harmonic current. By connecting and short-circuiting reactors, various control of input current waveform and DC voltage is possible. A method has been proposed. As this type of prior art, Japanese Patent Publication No. 63-13204, Japanese Patent No. 2809463, Japanese Patent Application Laid-Open No. 10-201248, Japanese Patent Application Laid-Open No. 2003-153543, Japanese Patent Application Laid-Open No. 2006-174689, Japanese Patent No. 034885047 No. 2009-1000049 is known.

特許文献１は交流電源電流を検出する電源電流検出回路を備え、電流の上限値と下限値を定め、検出電流と比較することにより短絡タイミングを制御するものである。これにより電源半周期に数回の短絡で電源電流を改善できるため、高効率と高力率を両立させることができる電源回路について述べている。   Patent Document 1 includes a power source current detection circuit that detects an AC power source current, determines an upper limit value and a lower limit value of the current, and controls a short circuit timing by comparing with a detected current. Thus, since the power supply current can be improved by short-circuiting several times in the power supply half cycle, a power supply circuit that can achieve both high efficiency and high power factor is described.

特許文献２は瞬時電源電流検出回路を備え、負荷状態に合わせて係数を設定し、この係数と電流情報との積に基づいてスイッチング素子の動作を規定する通流比を作成し、スイッチング素子を動作させるものである。これは特許文献１におけるスイッチングタイミングを明確に規定したものであり、これにより電源高調波電流の抑制と高力率を実現し、直流電圧の制御も可能である。さらに負荷に応じて係数を変更し電源電流のピーク付近でのスイッチング動作を停止することでスイッチング回数と直流電圧を変化させ高効率動作が可能である。電源装置および力率改善方法について述べている。   Patent Document 2 includes an instantaneous power supply current detection circuit, sets a coefficient according to the load state, creates a current ratio that defines the operation of the switching element based on the product of this coefficient and current information, It is what makes it work. This clearly defines the switching timing in Patent Document 1, thereby realizing suppression of the power supply harmonic current and high power factor, and control of the DC voltage is also possible. Furthermore, by changing the coefficient in accordance with the load and stopping the switching operation near the peak of the power supply current, the switching frequency and the DC voltage can be changed to enable high-efficiency operation. The power supply and the power factor improvement method are described.

特許文献３は交流電源の半周期毎にゼロクロス点を検出し、ゼロクロス点から所定の時間だけ遅延してスイッチング手段をオンし、所定のオン期間後オフすることで、交流電源からの入力電流の通電幅を拡大し、力率を改善するとともにリアクタに蓄えられたエネルギーを平滑コンデンサへ供給することで高い直流電圧を得ることができる。１回しかオンしないことで、高い効率で力率改善できる電源装置について述べている。   Patent Document 3 detects a zero-cross point every half cycle of an AC power source, turns on a switching unit with a predetermined time delay from the zero-cross point, and turns off after a predetermined ON period. A high DC voltage can be obtained by expanding the energization width, improving the power factor, and supplying the energy stored in the reactor to the smoothing capacitor. It describes a power supply device that can be improved in power factor with high efficiency by being turned on only once.

特許文献４は交流電源にその一端が接続されたリアクトルと、リアクトルを介して交流電源を短絡／開放する双方向通電性の短絡素子とを設け、負荷量に応じて、短絡素子を、短絡動作無しの力率改善無しモード、或いは短絡動作を電源半周期に１回もしくは複数回行う部分スイッチングモード、或いは短絡動作を高周波で行う高周波スイッチングモードのいずれかのモードにて制御する。これにより、負荷の広い運転領域全体に渡り損失を低減して効率向上を可能にし、力率改善により電力供給を安定に行うこと。更に、負荷及び電源共に高周波問題を解消することができる電力供給装置，電動機駆動装置，電力供給装置の制御方法について述べている。   Patent Document 4 provides a reactor having one end connected to an AC power source and a bidirectionally conductive short-circuit element that short-circuits / opens the AC power source via the reactor, and short-circuits the short-circuit element according to the amount of load. Control is performed in one of a power factor improvement mode without power supply, a partial switching mode in which a short circuit operation is performed once or a plurality of times in a half cycle of a power supply, or a high frequency switching mode in which a short circuit operation is performed at a high frequency. As a result, it is possible to improve efficiency by reducing loss over the entire operation area with a wide load, and to stably supply power by improving the power factor. Furthermore, a power supply device, a motor drive device, and a control method for the power supply device that can solve the high-frequency problem for both the load and the power supply are described.

特許文献５〜特許文献７はスイッチング素子の短絡回数を負荷に応じて変更することにより高力率の直流電源装置を実現する直流電源装置，空気調和機について述べている。   Patent Documents 5 to 7 describe a DC power supply device and an air conditioner that realize a high power factor DC power supply device by changing the number of short circuits of the switching element according to the load.

特公昭６３−１３２０４号公報Japanese Examined Patent Publication No. 63-13204 特許２８０９４６３号公報Japanese Patent No. 2809463 特開平１０−２０１２４８号公報Japanese Patent Laid-Open No. 10-201248 特開２００３−１５３５４３号公報JP 2003-153543 A 特開２００６−１７４６８９号公報Japanese Patent Laid-Open No. 2006-174689 特許０３４８５０４７号公報Japanese Patent No. 03485047 特開２００９−１００４９９号公報JP 2009-1000049 A

現在、家庭用の空気調和機は、環境への配慮が求められ、省資源，省エネを強く要求されるようになった。加えて、電子制御機器の急増に伴い電源に悪影響を与える高調波電流の規制に適合する製品が求められている。   Currently, home air conditioners are required to be environmentally friendly, and resource and energy savings are strongly demanded. In addition, there is a need for products that meet the regulations on harmonic currents that adversely affect power supplies due to the rapid increase in electronic control devices.

しかしながら、上記で述べた先行技術ではこれらの要求を部分的に満たすだけであり、次のような問題がある。   However, the prior art described above only partially satisfies these requirements, and has the following problems.

特許文献１では瞬時の交流電流を検出する電流検出回路およびスイッチングタイミングを決定するスイッチング素子駆動回路が必要なため、回路が複雑になる。さらに直流電圧の制御法や最適な電流の上限値、下限値の決め方について述べられておらず、コイル巻き線を多く巻き込んだ直流電圧の昇圧が必要な電動機の高効率制御には適さない。また、直流出力電圧の維持方法についての言及が無い。   In Patent Document 1, since a current detection circuit that detects an instantaneous alternating current and a switching element drive circuit that determines switching timing are required, the circuit becomes complicated. Furthermore, it does not describe a DC voltage control method and how to determine the optimum upper limit value and lower limit value of the current, and is not suitable for high-efficiency control of an electric motor that requires boosting of a DC voltage with many coil windings. There is no mention of a method for maintaining the DC output voltage.

特許文献２では負荷が小さいときは直流電圧を低く、スイッチング回数を少なくし、高効率運転を行い、負荷が大きいときは直流電圧を高く、スイッチング回数を多くし、高力率運転を行うことが可能である。しかし瞬時の交流電源電流が必要であり、回路が複雑になる。また効率を優先して数回までスイッチング回数を落とした場合、交流電流のリップルが大きくなり、力率の低下や高調波電流の増加が見られる。また、直流出力電圧の維持は短絡回数と開閉デューティの増減で行っている。   In Patent Document 2, when the load is small, the DC voltage is lowered, the number of switching is reduced, and high efficiency operation is performed. When the load is large, the DC voltage is increased, the number of switching is increased, and high power factor operation is performed. Is possible. However, instantaneous AC power supply current is required, and the circuit becomes complicated. In addition, when the number of switching is reduced to several times in order to prioritize efficiency, the ripple of the alternating current increases, and the power factor decreases and the harmonic current increases. The DC output voltage is maintained by increasing or decreasing the number of short circuits and the switching duty.

特許文献３では直流電圧を高くしようとした場合、短絡した波形は歪んでしまうため、電源高調波電流が多くなり、高い力率を得ながらもＪＩＳ規格値を満足できない。また、この発明は電源の半周期に１回だけ短絡動作をするもので、パルス間隔についての言及が無い。   In Patent Document 3, when the DC voltage is increased, the short-circuited waveform is distorted, so that the power supply harmonic current increases and the JIS standard value cannot be satisfied while obtaining a high power factor. Further, the present invention performs a short-circuit operation only once in a half cycle of the power supply, and there is no mention of a pulse interval.

特許文献４では部分スイッチングモードではスイッチング素子の短絡開始時間，短絡時間、および短絡回数を制御することで直流出力電圧を制御できるが、高調波を抑制する具体的な手段は述べられていない。したがってモードの切り替えにより高効率と高調波抑制（高力率）のどちらかは選択できるが、高効率と高調波抑制の両立はできなかった。   In Patent Document 4, in the partial switching mode, the DC output voltage can be controlled by controlling the short circuit start time, the short circuit time, and the number of short circuits of the switching element, but no specific means for suppressing harmonics is described. Therefore, either high efficiency or harmonic suppression (high power factor) can be selected by switching the mode, but high efficiency and harmonic suppression cannot be achieved at the same time.

特許文献５〜特許文献７では最適なスイッチングタイミングについて明確な記載がなかった。   In Patent Documents 5 to 7, there is no clear description about the optimum switching timing.

本発明の目的は、電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する直流電源装置を提供することにある。   An object of the present invention is to provide a DC power supply device that achieves high efficiency and appropriate power factor at low loads while realizing high power factor and appropriate efficiency at high loads while suppressing power supply harmonic current. is there.

本発明が解決しようとする課題は、交流電源より入力された交流電力を直流電力に変換する整流回路と、前記交流電源と前記整流回路との間に接続されたリアクタと、前記交流電源を前記リアクタを介して短絡するスイッチング手段と、前記直流電力の目標電圧設定手段と、前記交流電源の周波数を検出する周波数検出手段と、前記交流電源の電源電圧を検出する電源電圧検出手段と、前記交流電源のゼロクロス点を検出するゼロクロス検出手段と、前記整流回路の出力である直流電圧を検出する直流電圧検出手段と、前記ゼロクロス点に同期させて前記スイッチング手段を短絡，開放するスイッチング制御手段とを備える直流電源装置において、前記スイッチング制御手段は前記目標電圧設定手段で設定された目標直流電圧と前記電源電圧検出手段で検出された電源電圧との比の値が所定値未満の場合に前記ゼロクロス検出手段で検出された前記交流電源のゼロクロス点からの１／２周期中に、前記スイッチング手段を２回短絡し、前記ゼロクロス点から１回目の短絡開始までの時間を予め設定した遅延時間とし、この２回短絡の１回目と２回目の短絡間隔を、前記周波数検出手段で検出された電源周波数が５０Ｈｚの時には０.２〜０.４ｍｓで、前記電源周波数が６０Ｈｚの時には０.１６〜０.３３ｍｓとし、その後に前記比の値が所定値以上の場合に前記スイッチング手段の短絡回数を前記比の値に応じて前記２回よりも多い回数で且つ、組み込まれる機器のモータの運転騒音周波数に対して直流電源装置の騒音周波数が超えない短絡回数に切り替えることにより達成される。 The problems to be solved by the present invention include a rectifier circuit that converts AC power input from an AC power source into DC power, a reactor connected between the AC power source and the rectifier circuit, and the AC power source Switching means for short-circuiting via a reactor, target voltage setting means for the DC power, frequency detection means for detecting the frequency of the AC power supply, power supply voltage detection means for detecting the power supply voltage of the AC power supply, and the AC Zero cross detection means for detecting a zero cross point of a power supply, DC voltage detection means for detecting a DC voltage as an output of the rectifier circuit, and switching control means for short-circuiting and opening the switching means in synchronization with the zero cross point. In the direct current power supply apparatus, the switching control means includes the target direct current voltage set by the target voltage setting means and the power supply voltage. When the value of the ratio with the power supply voltage detected by the output means is less than a predetermined value, the switching means is short-circuited twice during a half cycle from the zero cross point of the AC power supply detected by the zero cross detection means. The time from the zero cross point to the first short-circuit start is set as a delay time, and the first and second short-circuit intervals of the second short-circuit are determined by the power supply frequency detected by the frequency detection means being 50 Hz. Sometimes it is 0.2 to 0.4 ms, and when the power supply frequency is 60 Hz, it is 0.16 to 0.33 ms, and then the number of short circuits of the switching means is set to the value of the ratio when the value of the ratio is a predetermined value or more. Accordingly, it is achieved by switching to a number of short-circuits that is greater than the above two times and that does not exceed the noise frequency of the DC power supply device with respect to the operating noise frequency of the motor of the apparatus to be incorporated.

請求項２に記載の直流電源装置は請求項１の直流電源装置において、前記スイッチング制御手段は前記目標電圧設定手段で設定された目標直流電圧と前記電源電圧検出手段で検出された電源電圧との比の値が所定値以上の場合に、前記２回短絡の場合と同様に、前記ゼロクロス検出手段で検出された前記交流電源のゼロクロス点からの１／２周期中に、前記スイッチング手段を２回短絡し、この２回短絡の１回目と２回目の短絡間隔を、前記周波数検出手段で検出された電源周波数が５０Ｈｚの時には０.２〜０.４ｍｓで、前記電源周波数が６０Ｈｚの時には０.１６〜０.３３ｍｓとし、その後に前記比の値が所定値以上の場合に前記スイッチング手段の短絡回数を前記比の値に応じて前記２回よりも多い回数で且つ、組み込まれる機器のモータの運転騒音周波数に対して直流電源装置の騒音周波数が超えない短絡回数に切り替えるものである。   According to a second aspect of the present invention, there is provided the direct current power supply device according to the first aspect, wherein the switching control means includes a target direct current voltage set by the target voltage setting means and a power supply voltage detected by the power supply voltage detection means. When the ratio value is equal to or greater than a predetermined value, the switching means is operated twice during a half cycle from the zero cross point of the AC power source detected by the zero cross detection means, as in the case of the two-time short circuit. When the power supply frequency detected by the frequency detecting means is 50 Hz, the first and second short-circuit intervals of the two short-circuits are 0.2 to 0.4 ms, and the power supply frequency is 60 Hz. When the value of the ratio is equal to or greater than a predetermined value after that, the number of short-circuits of the switching means is more than the two times according to the value of the ratio and the mode of the device to be incorporated is set. The number of short-circuits is switched so that the noise frequency of the DC power supply does not exceed the operating noise frequency of the inverter.

請求項３に記載の直流電源装置は請求項１乃至２の直流電源装置において、前記スイッチング制御手段は３回目以降の短絡時間を前記電源周波数が５０Ｈｚの時は０.２５ｍｓ、６０Ｈｚの時は０.２ｍｓ以下の範囲とするものである。   According to a third aspect of the present invention, there is provided the direct current power supply device according to the first or second aspect, wherein the switching control means sets the short circuit time for the third and subsequent times to 0.25 ms when the power supply frequency is 50 Hz and zero when the power supply frequency is 60 Hz. The range is less than 0.2 ms.

請求項４に記載の直流電源装置は請求項１乃至２の直流電源装置において、前記スイッチング手段の短絡回数をＭ回からＭ＋１回に増加させる時に、短絡回数増加後のＭ回目までの短絡時間の合計値を、短絡回数増加前の短絡時間の合計値より、減少させるものである。   According to a fourth aspect of the present invention, there is provided the direct current power supply device according to the first or second aspect, wherein when the number of short circuits of the switching means is increased from M times to M + 1 times, The total value is decreased from the total value of the short circuit time before the increase in the number of short circuits.

請求項５に記載の直流電源装置は請求項１乃至２の直流電源装置において、前記スイッチング手段の短絡回数をＭ回からＭ＋１回に増加させる時に、Ｍ＋１回目までの短絡時間の合計値を、短絡回数増加前のＭ回目までの短絡時間の合計値と等しくするものである。   The direct current power supply device according to claim 5 is the direct current power supply device according to claim 1 or 2, wherein when the number of short circuits of the switching means is increased from M times to M + 1 times, a total value of short circuit times up to M + 1 time is short-circuited. This is equal to the total value of the short-circuiting time up to the Mth time before the number of times increases.

請求項６に記載の直流電源装置は請求項１乃至２の直流電源装置において、前記スイッチング手段の短絡回数をＭ回からＭ−１回に減少させる時に、短絡回数減少後の短絡時間の合計値を、短絡回数減少前のＭ−１回目までの短絡時間の合計値より、増加させるものである。   The direct current power supply device according to claim 6 is the direct current power supply device according to claim 1 or 2, wherein when the number of short circuits of the switching means is reduced from M times to M-1 times, the total value of short circuit times after the short circuit number is reduced. Is increased from the total value of the short-circuiting time up to the (M-1) th time before the number of short-circuits is decreased.

請求項７に記載の直流電源装置は請求項１乃至２の直流電源装置において、前記スイッチング手段の短絡回数をＭ回からＭ−１回に減少させる時に、短絡回数減少後の短絡時間の合計値を、短絡回数減少前のＭ回目までの短絡時間の合計値と等しくするものである。   The direct current power supply device according to claim 7 is the direct current power supply device according to claim 1 or 2, wherein when the number of short circuits of the switching means is decreased from M times to M-1 times, the total value of short circuit times after the number of short circuits is reduced. Is made equal to the total value of the short-circuiting time up to the M-th before the number of short-circuits is reduced.

請求項８に記載の直流電源装置は請求項３の直流電源装置において、前記交流電源からの入力電流を検出する入力電流検出手段を更に備え、前記スイッチング制御手段は前記スイッチング手段の２〜６回までの短絡回数を前記比の値と前記入力電流検出手段で検出した入力電流に応じて定めるものである。   The direct current power supply device according to claim 8 is the direct current power supply device according to claim 3, further comprising input current detection means for detecting an input current from the alternating current power supply, wherein the switching control means is 2 to 6 times the switching means. The number of short circuits up to is determined according to the value of the ratio and the input current detected by the input current detecting means.

請求項９に記載の直流電源装置は請求項３の直流電源装置において、前記直流電力に接続された負荷量を検出する負荷量検出手段を更に備え、前記スイッチング制御手段は前記スイッチング手段の２〜６回までの短絡回数を前記比の値と前記負荷量検出手段で検出された負荷量に応じて定めるものである。   The DC power supply device according to claim 9 is the DC power supply device according to claim 3, further comprising load amount detection means for detecting a load amount connected to the DC power, wherein the switching control means is a second to second switching means. The number of short circuits up to 6 is determined according to the value of the ratio and the load detected by the load detection means.

請求項１０に記載の直流電源装置は請求項９の直流電源装置において、前記直流電力に接続される負荷をモータとし、前記負荷量を前記モータへの印加電圧とし、前記負荷量検出手段としてモータへの印加電圧を検出するモータ印加電圧検出手段を備え、前記スイッチング制御手段は前記スイッチング手段の２〜６回までの短絡回数を前記比の値と前記モータ印加電圧検出手段で検出されたモータ印加電圧に応じて定めるものである。   The DC power supply device according to claim 10 is the DC power supply device according to claim 9, wherein the load connected to the DC power is a motor, the load amount is an applied voltage to the motor, and the motor is used as the load amount detecting means. And a motor application voltage detecting means for detecting a voltage applied to the switching means, wherein the switching control means detects the number of short circuits from 2 to 6 times of the switching means and the motor application detected by the motor applied voltage detection means. It is determined according to the voltage.

請求項１１に記載の直流電源装置は請求項９の直流電源装置において、前記直流電力に接続される負荷をモータとし、前記負荷量を前記モータの回転数として、前記負荷量検出手段としてモータの回転数を検出するモータ回転数検出手段を備え、前記スイッチング制御手段は前記スイッチング手段の２〜６回までの短絡回数を前記比の値と前記モータ回転数検出手段で検出されたモータ回転数に応じて定めるものである。   The direct current power supply device according to claim 11 is the direct current power supply device according to claim 9, wherein the load connected to the direct current power is a motor, the load amount is the number of rotations of the motor, and the load amount detecting means is a motor. Motor rotation number detection means for detecting the rotation number is provided, and the switching control means converts the number of short circuits from 2 to 6 times of the switching means to the value of the ratio and the motor rotation number detected by the motor rotation number detection means. It is determined accordingly.

さらには、請求項１２により、安価で、電源高調波電流規制を満足し、電源容量を最大限に活用した高能力で、効率の良い空気調和機を提供することができる。   Furthermore, according to the twelfth aspect, it is possible to provide an air conditioner that is inexpensive, satisfies the power supply harmonic current regulation, has a high capacity and uses the power supply capacity to the maximum, and is efficient.

請求項１に記載の発明によれば、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する。   According to the first aspect of the invention, while suppressing the power supply harmonic current with an inexpensive circuit configuration, a high efficiency and an appropriate power factor are realized at a low load, and a high power factor and an appropriate efficiency are achieved at a high load. Realize.

請求項２によれば、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する。   According to the second aspect, high efficiency and appropriate power factor are realized at low load while high power factor and appropriate efficiency are realized at high load while suppressing power supply harmonic current with an inexpensive circuit configuration.

請求項３によれば、短絡回数を多くして力率を改善しつつ、電源高調波電流規制を満足する。   According to the third aspect, the power harmonic current regulation is satisfied while the power factor is improved by increasing the number of short circuits.

請求項４によれば、電源高調波電流の抑制や力率の改善のために、短絡回数を増しても、直流電圧がほとんど変化せず、負荷となる機器の安定した運転を確保できる。   According to the fourth aspect, in order to suppress the power harmonic current and improve the power factor, the DC voltage hardly changes even when the number of short-circuits is increased, and stable operation of the load device can be ensured.

請求項５によれば、電源高調波電流の抑制や力率の改善のために、短絡回数を増しても、直流電圧がほとんど変化せず、負荷となる機器の安定した運転を確保できる。   According to the fifth aspect, in order to suppress the power harmonic current and improve the power factor, even if the number of short-circuits is increased, the DC voltage hardly changes and a stable operation of the load device can be ensured.

請求項６によれば、電源高調波電流の抑制や力率の改善のために、短絡回数を増しても、直流電圧がほとんど変化せず、負荷となる機器の安定した運転を確保できる。   According to the sixth aspect, the DC voltage hardly changes even when the number of short-circuits is increased in order to suppress the power supply harmonic current and improve the power factor, and it is possible to ensure stable operation of the load device.

請求項７によれば、電源高調波電流の抑制や力率の改善のために、短絡回数を増しても、直流電圧がほとんど変化せず、負荷となる機器の安定した運転を確保できる。   According to the seventh aspect, the DC voltage hardly changes even when the number of short circuits is increased in order to suppress the power supply harmonic current and improve the power factor, and a stable operation of the load device can be ensured.

請求項８によれば、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する。   According to the eighth aspect, while suppressing the power supply harmonic current with an inexpensive circuit configuration, a high efficiency and an appropriate power factor are realized at a low load, and a high power factor and an appropriate efficiency are realized at a high load.

請求項９によれば、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する。   According to the ninth aspect, high efficiency and an appropriate power factor are realized at a low load, and a high power factor and an appropriate efficiency are realized at a high load while suppressing a power supply harmonic current with an inexpensive circuit configuration.

請求項１０によれば、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する。   According to the tenth aspect, high efficiency and an appropriate power factor are realized at a low load while a high power factor and an appropriate efficiency are realized at a high load while suppressing a power supply harmonic current with an inexpensive circuit configuration.

請求項１１によれば、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する。   According to the eleventh aspect, while suppressing the power supply harmonic current with an inexpensive circuit configuration, a high efficiency and an appropriate power factor are realized at a low load, and a high power factor and an appropriate efficiency are realized at a high load.

請求項１２によれば、安価で、電源高調波電流規制を満足し、電源容量を最大限に活用した高能力で、効率の良い空気調和機を実現する。   According to the twelfth aspect of the present invention, an air conditioner that is inexpensive, satisfies the power supply harmonic current regulation, and uses the power supply capacity to the maximum and has high efficiency is realized.

実施例１の電源装置の回路構成を示すブロック図。1 is a block diagram illustrating a circuit configuration of a power supply device according to a first embodiment. 同電源装置で１回短絡時の電源電圧・入力電流波形。Power supply voltage / input current waveform when the power supply is short-circuited once. 同電源装置で２回短絡時の電源電圧・入力電流波形。Power supply voltage and input current waveforms when the same power supply is short-circuited twice. 同電源装置で３回短絡時の電源電圧・入力電流波形。Power supply voltage and input current waveforms when the power supply is short-circuited three times. 同電源装置で５回短絡時の電源電圧・入力電流波形。Power supply voltage / input current waveform when the same power supply is short-circuited 5 times. 同電源装置の短絡回数制御部の記憶装置の記憶内容説明図。Storage contents explanatory drawing of the memory | storage device of the short circuit frequency control part of the power supply device. 同短絡回数制御部の短絡回数制御フロー要部。The short circuit count control flow main part of the same short circuit count control section. 同短絡回数制御部の前段処理フロー要部。The main part of the pre-processing flow of the short-circuit number control unit. 同短絡回数制御部の短絡回数増加処理フロー要部。The main part of the short circuit number increasing process flow of the short circuit number control unit. 同短絡回数制御部の短絡回数減少処理フロー要部。The main part of the short circuit frequency reduction processing flow of the short circuit controller. 同電源装置の回路構成を示すブロック図。The block diagram which shows the circuit structure of the power supply device. 入力電流と目標直流電圧の関係を示す図。The figure which shows the relationship between an input electric current and a target DC voltage. 負荷量と目標直流電圧の関係を示す図。The figure which shows the relationship between load amount and a target DC voltage. モータ印加電圧と目標直流電圧の関係を示す図。The figure which shows the relationship between a motor applied voltage and a target DC voltage. モータ回転数と目標直流電圧の関係を示す図。The figure which shows the relationship between a motor rotation speed and a target DC voltage. 実施例３の電源装置の回路構成を示すブロック図。FIG. 6 is a block diagram illustrating a circuit configuration of a power supply device according to a third embodiment. 実施例４の電源装置の回路構成を示すブロック図。FIG. 6 is a block diagram illustrating a circuit configuration of a power supply device according to a fourth embodiment. 実施例５の電源装置の回路構成を示すブロック図。FIG. 10 is a block diagram illustrating a circuit configuration of a power supply device according to a fifth embodiment. 実施例６の空気調和機の構成図。The block diagram of the air conditioner of Example 6. FIG. 同空気調和機の室外機の内部構造斜視図。The internal structure perspective view of the outdoor unit of the air conditioner. 同室外機の天板を外した平面図。The top view which removed the top plate of the outdoor unit. 同室外機の前面板を外した正面図。The front view which removed the front plate of the outdoor unit.

以下、本発明を空気調和機の圧縮機駆動用の直流電源装置に適用した実施例について図を用いて説明する。図における同一符号は同一物または相当物を示す。   Embodiments in which the present invention is applied to a DC power supply for driving a compressor of an air conditioner will be described below with reference to the drawings. The same reference numerals in the drawings indicate the same or equivalent.

まず、本発明の直流電源装置の全体構成について図１を用いて説明する。図１は実施例１の電源装置の回路構成を示すブロック図である。   First, the overall configuration of the DC power supply device of the present invention will be described with reference to FIG. FIG. 1 is a block diagram illustrating a circuit configuration of the power supply device according to the first embodiment.

直流電源装置１００は図１に示すように、交流電源１０１と負荷１０４に接続され、交流電圧を整流回路１０２で整流し、平滑コンデンサ１０３で平滑して直流電圧に変換し、負荷１０４に電力を供給する。   As shown in FIG. 1, the DC power supply device 100 is connected to an AC power supply 101 and a load 104, rectifies an AC voltage by a rectifier circuit 102, smoothes it by a smoothing capacitor 103, converts it to a DC voltage, and supplies power to the load 104. Supply.

通常平滑コンデンサ１０３に蓄えられた電荷による直流電圧のため、交流電圧がこの直流電圧を超えたときにしか電流は流れないので、通電区間は短く、電流波形は鋭くとがって力率が悪くなってしまう。これを改善するためリアクタ１０５を接続すると、電流波形の波高値は低くなり、通電区間が後ろに伸び力率が改善される。   Since the current flows only when the AC voltage exceeds this DC voltage because the DC voltage is usually a charge stored in the smoothing capacitor 103, the energization section is short, the current waveform is sharp and the power factor is poor. End up. When the reactor 105 is connected to improve this, the peak value of the current waveform becomes low, and the extension power factor is improved after the energization section.

さらに、交流電源１０１がリアクタ１０５を介して短絡されるようにスイッチング手段１０６が設けられ、また、交流電源１０１のゼロクロス点を検出するゼロクロス検出手段１０７が接続されており、ゼロクロス検出手段１０７で検出されたゼロクロス点に同期させて、スイッチング制御手段１０８でスイッチング手段１０６を駆動する駆動信号を生成し、スイッチング手段１０６を短絡する。   Further, a switching means 106 is provided so that the AC power supply 101 is short-circuited through the reactor 105, and a zero cross detection means 107 for detecting a zero cross point of the AC power supply 101 is connected. In synchronization with the generated zero cross point, the switching control means 108 generates a drive signal for driving the switching means 106 and short-circuits the switching means 106.

次に、スイッチング手段の１回短絡，２回短絡例について図２，図３を用いて説明する。図２は電源装置で１回短絡時の電源電圧・入力電流波形である。図３は電源装置で２回短絡時の電源電圧・入力電流波形である。   Next, examples of one-time short-circuit and two-time short-circuit of the switching means will be described with reference to FIGS. FIG. 2 shows power supply voltage / input current waveforms when the power supply is short-circuited once. FIG. 3 shows power supply voltage / input current waveforms when the power supply device is short-circuited twice.

これまで電源高調波電流を抑制するため、スイッチングの短絡，開放を複数回行えば、短絡電流のピークが下がるため有効であることがいわれてきたが、この間隔については言及されていなかった。度重なる検討の結果、発明者らは、力率の向上と電源高調波電流の抑制の両立させるためには第１の短絡と第２の短絡との間の開放時間が重要であること見出し、本発明を出願するに至った。以下、第１と第２の短絡との間の開放時間の重要性について説明する。   In the past, it has been said that if switching short-circuiting and opening are performed a plurality of times in order to suppress the power harmonic current, the peak of the short-circuit current is lowered, which is effective, but this interval has not been mentioned. As a result of repeated studies, the inventors have found that the open time between the first short circuit and the second short circuit is important in order to achieve both improvement in power factor and suppression of power supply harmonic current, The present invention has been filed. Hereinafter, the importance of the open time between the first and the second short circuit will be described.

説明に先立ち、高調波電流の指標とした高調波の余裕度について説明する。電源周波数のｎ次の高調波電流の限度値はＪＩＳ Ｃ６１０００−３−２「電磁両立性−第３−２部：限度値−高調波電流発生限度値」に規定されていて、この限度値Ｉｓｎに対して高調波電流をＩｎとしたときｎ次の余裕度を（１−Ｉｎ／Ｉｓｎ）と定義する。   Prior to the description, the harmonic margin as an index of the harmonic current will be described. The limit value of the n-th harmonic current of the power supply frequency is defined in JIS C61000-3-2, “Electromagnetic compatibility—Part 3-2: Limit value—Harmonic current generation limit value”. In contrast, when the harmonic current is In, the n-order margin is defined as (1-In / Isn).

定義から明らかなように、ｎ次の余裕度が０より小さい時は限度値Ｉｓｎ以上のｎ次の高調波電流が流れていることになるので規定不適合でＮＧとなり、ｎ次の余裕度が０より大きい時はｎ次の高調波電流が限度値以下で規定に適合している状態で、ｎ次の余裕度が１に近い時はｎ次の高調波電流が０に近づき、電源に悪影響を与えるｎ次の高調波電流がほとんどなく、非常に良好な状態であると言える。   As is clear from the definition, when the n-th order margin is smaller than 0, an n-th order harmonic current greater than the limit value Isn flows, so it is NG due to non-conformity, and the n-th order margin is 0. When the value is larger, the n-th order harmonic current is below the limit value and conforms to the regulation. When the n-order margin is close to 1, the n-th order harmonic current approaches 0, and the power supply is adversely affected. It can be said that there is almost no nth-order harmonic current to be applied, and the state is very good.

上記のｎ次の余裕度を２次から４０次まで求め最も小さいものを高調波の余裕度と定義する。   The n-th order margin is obtained from the second order to the 40th order, and the smallest one is defined as a harmonic margin.

一般に、空気調和機として家庭用の４〜５ｋＷクラスの製品を考えた場合、電源として２００Ｖが使用されることが多く、運転時間は、春，秋の肌寒い頃に弱い暖房で使用される時間が一番多く、負荷の一番大きい条件は、早朝の暖房の立上がり時で、圧縮機を高速で駆動し、大きな暖房能力で急速に室内を暖める時である。   In general, when considering a 4-5 kW class product for home use as an air conditioner, 200V is often used as a power source, and the operating time is the time used by weak heating when it is chilly in spring and autumn. The most frequent and largest load condition is when the heating starts in the early morning, when the compressor is driven at high speed, and the room is heated rapidly with a large heating capacity.

このように、暖房能力，冷房能力の大小は負荷量の大小と連動し、空気調和機には負荷量の大小と連動する圧縮機回転数，直流電圧，入力電流，機体各部の温度，冷凍サイクルの温度等に応じた運転が要求される。   In this way, the heating capacity and cooling capacity are linked to the magnitude of the load, and the air conditioner has a compressor speed, DC voltage, input current, temperature of each part of the machine, refrigeration cycle linked to the magnitude of the load. The operation according to the temperature etc. is required.

はじめに１回の短絡のみ行った場合を説明する。この場合、電源半周期の電源電圧，電源電流（入力電流）の波形は、例えば、図２のようになる。交流電源電圧２００Ｖ，５０Ｈｚとして、負荷の条件としては運転時間の長い暖房の弱運転に相当する、直流電圧Ｖｄを２６０Ｖ、出力電力を８８０Ｗを想定し、ゼロクロスからの第１の短絡までの遅延時間をＴｄとし、短絡時間をＴｏｎとして、所要の直流電圧２６０Ｖを得て、力率が最大となる遅延時間Ｔｄと短絡時間Ｔｏｎを求め、その時の高調波の余裕度と力率をシミュレーションで求めると表１のようになる。   First, the case where only one short circuit is performed will be described. In this case, the waveforms of the power supply voltage and power supply current (input current) in the half cycle of the power supply are, for example, as shown in FIG. Assuming that the AC power supply voltage is 200V, 50Hz, the load condition is equivalent to the weak operation of heating with a long operating time, the DC voltage Vd is 260V, the output power is 880W, and the delay time from the zero cross to the first short circuit Is Td, the short circuit time is Ton, the required DC voltage 260V is obtained, the delay time Td and the short circuit time Ton at which the power factor is maximized are obtained, and the margin of the harmonics and the power factor at that time are obtained by simulation. It becomes like Table 1.

Figure 0005481165
Figure 0005481165

この表から判るように、遅延時間と短絡時間を変化させることにより、高調波の余裕度は向上させることができる。表１では、高調波の余裕度が増すと力率が下がる傾向にあり、高調波の余裕度と力率はトレードオフの関係となっている。   As can be seen from this table, the margin of harmonics can be improved by changing the delay time and the short circuit time. In Table 1, the power factor tends to decrease as the harmonic margin increases, and the harmonic margin and the power factor have a trade-off relationship.

次に、具体的な２回短絡の種々の例について説明する。   Next, various specific examples of the two-time short circuit will be described.

これに対して２回短絡を行った場合、電源半周期の電源電圧，電源電流（入力電流）の波形は、例えば、図３のようになる。   On the other hand, when the short circuit is performed twice, the waveforms of the power supply voltage and power supply current (input current) in the half cycle of the power supply are as shown in FIG. 3, for example.

直流電圧Ｖｄを２６０Ｖ、出力電力を８８０Ｗ、交流電源電圧２００Ｖ、５０Ｈｚとして、ゼロクロスからの第１の短絡までの遅延時間Ｔｄを１.７ｍｓ、第１と第２の短絡時間を合計した合計短絡時間Ｔｏｎを０.６２ｍｓに固定して、第２の短絡時間を０.１〜０.５ｍｓに変化させ、第１の短絡と第２の短絡との間の開放時間を０.１〜０.８ｍｓまで変化させた場合の高調波の余裕度を表２に、力率を表３に示す。   DC voltage Vd is 260V, output power is 880W, AC power supply voltage is 200V, 50Hz, delay time Td from the zero cross to the first short circuit is 1.7ms, and the total short circuit time is the sum of the first and second short circuit time Ton is fixed at 0.62 ms, the second short-circuit time is changed from 0.1 to 0.5 ms, and the open time between the first short-circuit and the second short-circuit is 0.1 to 0.8 ms. Table 2 shows the margin of harmonics and Table 3 shows the power factor.

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

ここで直流電圧２６０Ｖとなるように２回短絡し、高い力率を得たとしても、第１と第２の短絡の間の開放時間を大きくとりすぎてしまうと高調波の余裕度がＮＧとなってしまう。高調波の余裕度と力率がよく、制御のばらつきに対して余裕があるのは、第１と第２の短絡の間の開放時間が０.２ｍｓのときで、第２の短絡時間を変化させても高調波の余裕度は０.０８〜０.１８あり、力率は９３.２〜９３.９％と高調波の規格値内でかつ高力率を実現できる。   Here, even if the DC voltage is 260V twice and a high power factor is obtained, if the open time between the first and second short circuits is too long, the margin of harmonics is NG. turn into. Harmonic margin and power factor are good, and there is a margin for control variations when the open time between the first and second short circuits is 0.2 ms and the second short circuit time is changed. Even if it is made, the margin of the harmonic is 0.08 to 0.18, the power factor is 93.2 to 93.9%, which is within the standard value of the harmonic and can realize a high power factor.

さらにゼロクロスから第１の短絡までの遅延時間Ｔｄと第１と第２の短絡時間を合計した合計短絡時間Ｔｏｎを（Ｔｄ，Ｔｏｎ）＝（２.２ｍｓ，０.４５ｍｓ），（２.７ｍｓ，０.３５ｍｓ）とした場合の高調波の余裕度，力率を表４〜表７に示す。なお、以下の表は、特に断らない限り、電源電圧２００Ｖ，電源周波数５０Ｈｚの場合の値である。   Further, the total short-circuit time Ton obtained by adding the delay time Td from the zero cross to the first short-circuit and the first and second short-circuit times is (Td, Ton) = (2.2 ms, 0.45 ms), (2.7 ms, Table 4 to Table 7 show the margin of harmonics and the power factor when 0.35 ms). The following table shows values for a power supply voltage of 200 V and a power supply frequency of 50 Hz unless otherwise specified.

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

（Ｔｄ，Ｔｏｎ）＝（２.２ｍｓ，０.４５ｍｓ）のときは第１の短絡と第２の短絡との間の開放時間は０.２〜０.４ｍｓの値がよく、このときの高調波の余裕度は０.０８〜０.３１で力率は９０.７〜９２.５％となる。１回のみの短絡では高調波に余裕がなかったが、２回短絡を行い、第１の短絡と第２の短絡との間の開放時間は０.２〜０.４ｍｓの間から選ぶことで、同等力率で高調波の余裕度を改善することができる。   When (Td, Ton) = (2.2 ms, 0.45 ms), the open time between the first short circuit and the second short circuit has a good value of 0.2 to 0.4 ms. The wave margin is 0.08 to 0.31 and the power factor is 90.7 to 92.5%. Although there was no margin in harmonics with only one short circuit, short circuit was performed twice, and the open time between the first short circuit and the second short circuit was selected from 0.2 to 0.4 ms. The harmonic margin can be improved with the same power factor.

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

（Ｔｄ，Ｔｏｎ）＝（２.７ｍｓ，０.３５ｍｓ）のときも第１の短絡と第２の短絡との間の開放時間が０.２〜０.４ｍｓの場合に良好な結果が得られ、高調波の余裕度は０.１６〜０.３７、力率は８６.８〜８９.５％となる。１回のみの短絡よりも、２回短絡を行い、第１の短絡と第２の短絡との間の開放時間を０.２〜０.４ｍｓの間から選ぶことで、同等力率で高調波の余裕度を改善することができる。   Even when (Td, Ton) = (2.7 ms, 0.35 ms), good results are obtained when the open time between the first short circuit and the second short circuit is 0.2 to 0.4 ms. The margin of harmonics is 0.16 to 0.37, and the power factor is 86.8 to 89.5%. Rather than a single short-circuit, the short-circuit is performed twice, and the open time between the first short-circuit and the second short-circuit is selected from 0.2 to 0.4 ms, so that the harmonics are equal in power factor. Can be improved.

上記条件に対して、使用するモータの巻線回数を増やしたときには、出力直流電圧のアップが必要になるが、そのような状況でも本発明の技術が使用可能か否かを検討するため、直流電圧を２７０Ｖに変えて検討した。この場合、第１と第２の短絡時間を合計した合計短絡時間Ｔｏｎは直流電圧が２６０Ｖの時に比べて、長くする必要があり、力率が最大となる遅延時間Ｔｄと短絡時間Ｔｏｎは（Ｔｄ，Ｔｏｎ）＝（１.７ｍｓ，０.７４ｍｓ），（２.２ｍｓ，０.５６ｍｓ），（２.７ｍｓ，０.４４ｍｓ）となる。１回短絡のときの高調波の余裕度，力率を表８に、２回短絡のときの高調波の余裕度，力率を表９〜表１４に示す。   When the number of windings of the motor to be used is increased with respect to the above conditions, it is necessary to increase the output DC voltage. In order to investigate whether or not the technology of the present invention can be used in such a situation, The voltage was changed to 270V and examined. In this case, the total short-circuit time Ton obtained by adding the first and second short-circuit times needs to be longer than when the DC voltage is 260 V, and the delay time Td and the short-circuit time Ton at which the power factor is maximized are (Td , Ton) = (1.7 ms, 0.74 ms), (2.2 ms, 0.56 ms), (2.7 ms, 0.44 ms). Table 8 shows the margin and power factor of the harmonic when the short circuit is performed once, and Tables 9 to 14 show the margin and power factor of the harmonic when the circuit is short-circuited twice.

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

（Ｔｄ，Ｔｏｎ）＝（１.７ｍｓ，０.７４ｍｓ）の場合、１回のみの短絡では力率が９０.８％、高調波の余裕度が−０.０８で高調波の余裕度がＮＧであるが、２回短絡の場合は、第１と第２の短絡の間の開放時間が０.２ｍｓのときに、高調波の余裕度と力率がよく、制御のばらつきに対して余裕があり、第２の短絡時間を変化させても高調波の余裕度は０.０３〜０.１６、力率は９１.５〜９２.３％と高調波の規格値内でかつ高力率を実現できる。   When (Td, Ton) = (1.7 ms, 0.74 ms), the power factor is 90.8%, the harmonic margin is -0.08, and the harmonic margin is NG with only one short circuit. However, in the case of two short-circuits, when the open time between the first and second short-circuits is 0.2 ms, the harmonic margin and power factor are good, and there is a margin for control variations. Yes, even if the second short-circuiting time is changed, the margin of harmonics is 0.03 to 0.16, the power factor is 91.5 to 92.3%, within the standard value of harmonics and high power factor. realizable.

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

（Ｔｄ，Ｔｏｎ）＝（２.２ｍｓ，０.５６ｍｓ）の場合、１回のみの短絡では力率９１.０％、高調波の余裕度０.０９で高調波の規格値に対して余裕が少ない、２回短絡の場合は、第１と第２の短絡の間の開放時間が０.２ｍｓのときに、高調波の余裕度と力率がよく、制御のばらつきに対して余裕があり、第２の短絡時間を変化させても高調波の余裕度は０.１３〜０.２８あり、力率は９１.０〜９１.５％と高調波の規格値内でかつ高力率を実現できる。   When (Td, Ton) = (2.2 ms, 0.56 ms), a power factor of 91.0% and a margin of harmonics of 0.09 are sufficient for the harmonics with a single short circuit. In the case of few short-circuits, when the open time between the first and second short-circuits is 0.2 ms, the margin and power factor of harmonics are good, and there is room for control variations. Even if the second short-circuiting time is changed, the margin of harmonics is 0.13 to 0.28, and the power factor is 91.0 to 91.5%, which is within the standard value of harmonics and achieves a high power factor. it can.

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

（Ｔｄ，Ｔｏｎ）＝（２.７ｍｓ，０.４４ｍｓ）の場合、１回のみの短絡では力率が８９.６％、高調波の余裕度が−０.０９で高調波の余裕度がＮＧであるが、２回短絡の場合は、第１と第２の短絡の間の開放時間が０.２〜０.４ｍｓのときに、高調波の余裕度と力率がよく、制御のばらつきに対して余裕があり、第２の短絡時間を変化させても高調波の余裕度は０.０５〜０.２６あり、力率は８７.７〜８９.３％と高調波の規格値内でかつ高力率を実現できる。   When (Td, Ton) = (2.7 ms, 0.44 ms), power factor is 89.6%, harmonic margin is -0.09 and harmonic margin is NG with only one short circuit. However, in the case of two short-circuits, when the open time between the first and second short-circuits is 0.2 to 0.4 ms, the harmonic margin and power factor are good, resulting in control variations. Even if the second short-circuit time is changed, the harmonic margin is 0.05 to 0.26, and the power factor is 87.7 to 89.3%, which is within the standard value of the harmonic. And a high power factor can be realized.

次に、空気調和機の暖房立上がりの時のように、圧縮機を高速回転させる必要が生じた場合は、モータの回転数を上げるために直流電圧を上げる必要があり、且つ、空気調和機から吹出す温風の温度を上げる際は高負荷となるため、出力を増加させなければならない。   Next, when it is necessary to rotate the compressor at a high speed, such as when the air conditioner is heated, it is necessary to increase the DC voltage in order to increase the rotation speed of the motor. When raising the temperature of the hot air that is blown out, the load must be increased and the output must be increased.

このため、交流電源電圧２００Ｖ，５０Ｈｚ、直流電圧Ｖｄを２８０Ｖ、出力電力を１８００Ｗで検討した。この場合、第１と第２の短絡時間を合計した合計短絡時間Ｔｏｎは更に長くする必要があり、力率が最大となる遅延時間Ｔｄと短絡時間Ｔｏｎは（Ｔｄ，Ｔｏｎ）＝（１.５ｍｓ，１.２４ｍｓ）となる。１回短絡のときの高調波の余裕度，力率を表１５に、２回短絡で第２の短絡時間を０.１〜０.９ｍｓに変化させ、第１の短絡と第２の短絡との間の開放時間を０.１〜１.０ｍｓまで変化させた場合の高調波の余裕度，力率を表１６，表１７に示す。   For this reason, the AC power supply voltage was 200 V, 50 Hz, the DC voltage Vd was 280 V, and the output power was 1800 W. In this case, the total short circuit time Ton obtained by adding the first and second short circuit times needs to be further increased, and the delay time Td and the short circuit time Ton at which the power factor is maximized are (Td, Ton) = (1.5 ms). , 1.24 ms). Harmonic margin and power factor at the time of one short-circuit are changed to Table 15. The second short-circuit time is changed from 0.1 to 0.9 ms by two short-circuits, and the first short-circuit and the second short-circuit Tables 16 and 17 show the margin of harmonics and the power factor when the open time during the period is changed from 0.1 to 1.0 ms.

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

（Ｔｄ，Ｔｏｎ）＝（１.５ｍｓ，１.２４ｍｓ）で、１回のみの短絡では力率９３.６％、高調波の余裕度０.１６で高調波規の格値内で高力率であるが、２回短絡のときは、第１と第２の短絡の間の開放時間を０.２〜０.４ｍｓの場合に良好な結果が得られ、第２の短絡時間を変化させても高調波の余裕度は０.０９〜０.３３、力率は９３.５〜９４.７％となる。１回のみの短絡よりも、２回短絡を行い、第１の短絡と第２の短絡との間の開放時間を０.２〜０.４ｍｓの間から選ぶことで、高調波の余裕度を大きく、力率を高くすることができる。   (Td, Ton) = (1.5ms, 1.24ms), power factor is 93.6% with only one short circuit, harmonic margin is 0.16, and high power factor is within the harmonic standard. However, in the case of two short-circuits, good results are obtained when the open time between the first and second short-circuits is 0.2 to 0.4 ms, and the second short-circuit time is changed. The margin of harmonics is 0.09 to 0.33, and the power factor is 93.5 to 94.7%. Rather than a single short-circuit, the short-circuit is performed twice and the open time between the first short-circuit and the second short-circuit is selected from 0.2 to 0.4 ms, so that the harmonic margin can be increased. Large, can increase the power factor.

次に、上記条件から、使用するモータの巻線回数を増やした場合などの汎用性を検討するため、直流電圧を更に高くして、交流電源電圧２００Ｖ，５０Ｈｚ、直流電圧Ｖｄを３００Ｖ、出力電力を１８００Ｗで検討した。この場合、第１と第２の短絡時間を合計した合計短絡時間Ｔｏｎは更に長くする必要があり、力率が最大となる遅延時間Ｔｄと短絡時間Ｔｏｎは（１.５ｍｓ，１.４４ｍｓ）となる。１回短絡のときの高調波の余裕度，力率を表１５に、２回短絡で第２の短絡時間を０.１〜０.９ｍｓに変化させ、第１の短絡と第２の短絡との間の開放時間を０.１〜０.９ｍｓまで変化させた場合の高調波の余裕度，力率を表１８，表１９に示す。   Next, in order to examine versatility when the number of windings of the motor used is increased from the above conditions, the DC voltage is further increased, the AC power supply voltage 200 V, 50 Hz, the DC voltage Vd is 300 V, and the output power. Was examined at 1800W. In this case, the total short-circuit time Ton obtained by adding the first and second short-circuit times needs to be further increased, and the delay time Td and the short-circuit time Ton at which the power factor becomes maximum are (1.5 ms, 1.44 ms). Become. Harmonic margin and power factor at the time of one short-circuit are changed to Table 15. The second short-circuit time is changed from 0.1 to 0.9 ms by two short-circuits, and the first short-circuit and the second short-circuit Tables 18 and 19 show the margin of harmonics and the power factor when the open time during the period is changed from 0.1 to 0.9 ms.

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

（Ｔｄ，Ｔｏｎ）＝（１.５ｍｓ，１.４４ｍｓ）の場合、１回のみの短絡では力率８９.３％、高調波の余裕度０.３４で高調波の規格値内で高力率であるが、２回短絡の場合は、第１と第２の短絡の間の開放時間を０.２〜０.３ｍｓの場合に良好な結果が得られ、第２の短絡時間を変化させても高調波の余裕度は０.１０〜０.４２、力率は８９.６〜９１.１％となる。１回のみの短絡よりも、２回短絡を行い、第１の短絡と第２の短絡との間の開放時間を０.２〜０.３ｍｓの間から選ぶことで、高調波の余裕度を大きく、力率を高くすることができる。   When (Td, Ton) = (1.5 ms, 1.44 ms), the power factor is 89.3% for a single short-circuit, and the harmonic margin is 0.34 and the high power factor is within the harmonic specification. However, in the case of two short-circuits, good results are obtained when the open time between the first and second short-circuits is 0.2 to 0.3 ms, and the second short-circuit time is changed. The margin of harmonics is 0.10 to 0.42 and the power factor is 89.6 to 91.1%. Rather than a single short-circuit, the short-circuit is performed twice, and the opening time between the first short-circuit and the second short-circuit is selected from 0.2 to 0.3 ms, so that the harmonic margin can be increased. Large, can increase the power factor.

以上のように電源高調波電流の抑制と高力率を両立させるにはスイッチング手段１０６を１回短絡させるよりも２回短絡させたほうがよく、さらに上述のように５０Ｈｚの場合は、第１の短絡と第２の短絡との間のスイッチング手段１０６の開放時間を０.２〜０.４ｍｓの間から選ぶのがよい。また、６０Ｈｚの場合は、この解放時間を５０Ｈｚの時の約５／６の０.１６〜０.３３ｍｓの間から選ぶのがよい。   As described above, in order to achieve both suppression of power supply harmonic current and high power factor, it is better to short-circuit the switching means 106 twice than to short-circuit once, and in the case of 50 Hz as described above, the first The opening time of the switching means 106 between the short circuit and the second short circuit is preferably selected from 0.2 to 0.4 ms. In the case of 60 Hz, this release time is preferably selected from 0.16 to 0.33 ms, which is about 5/6 at 50 Hz.

本実施例における直流電源装置は図３に示すようにゼロクロス検出手段１０７で検出したゼロクロスから遅延時間の後、スイッチング制御手段１０８はスイッチング手段１０６をオンして第１の短絡を行い、交流電源１０１が５０Ｈｚのときは０.３ｍｓ、６０Ｈｚのときは０.２５ｍｓの間隔だけスイッチング手段１０６を開放し、その後スイッチング手段１０６をオンして第２の短絡を行い、その後スイッチング手段１０６を開放する。   As shown in FIG. 3, the DC power supply device in the present embodiment, after a delay time from the zero cross detected by the zero cross detecting means 107, the switching control means 108 turns on the switching means 106 to perform the first short circuit, and the AC power supply 101. When the frequency is 50 Hz, the switching means 106 is opened for an interval of 0.3 ms and when it is 60 Hz, then the switching means 106 is turned on to perform a second short circuit, and then the switching means 106 is opened.

第１の短絡と第２の短絡との間放の時間は５０Ｈｚの時は０.２〜０.４ｍｓ，６０Ｈｚの時は０.１６〜０.３３ｍｓの間で選ぶ必要があるが、この間であれば状況に応じて変化させてもよい。   The time between the first short circuit and the second short circuit needs to be selected from 0.2 to 0.4 ms at 50 Hz, and from 0.16 to 0.33 ms at 60 Hz. If necessary, it may be changed according to the situation.

次に、第１の短絡時間と第２短絡時間の決定方法について説明する。
（ａ）例えば第２の短絡時間を０.１ｍｓに固定とし、第１の短絡時間は交流の複数周期間の直流電圧の平均を現在直流電圧として検出し目標直流電圧との差分でＰＩ制御を行って決定する。
（ｂ）別の方法としては第１と第２の短絡時間の比率を決めて第１と第２の短絡時間の合計について現在直流電圧を検出し目標直流電圧との差分でＰＩ制御を行ってもよい。
（ｃ）更に別の方法としては第１と第２の短絡時間の合計について現在直流電圧を検出し目標直流電圧との差分でＰＩ制御を行い、第１の短絡時間にある制限値を持たせ、第１の短絡時間が制限値を越えたら第２の短絡時間を伸ばすようにしてもよい。また、この制限値を入力電流，負荷情報，目標直流電圧，現在直流電圧等により変化させてもよい。 Next, a method for determining the first short circuit time and the second short circuit time will be described.
(A) For example, the second short-circuiting time is fixed at 0.1 ms, and the first short-circuiting time is obtained by detecting the average of the DC voltage between a plurality of AC cycles as the current DC voltage and performing PI control based on the difference from the target DC voltage. Go and decide.
(B) Another method is to determine the ratio between the first and second short-circuit times, detect the current DC voltage for the sum of the first and second short-circuit times, and perform PI control based on the difference from the target DC voltage. Also good.
(C) As another method, the current DC voltage is detected for the sum of the first and second short-circuit times, PI control is performed based on the difference from the target DC voltage, and a limit value for the first short-circuit time is given. When the first short circuit time exceeds the limit value, the second short circuit time may be extended. Further, this limit value may be changed according to input current, load information, target DC voltage, current DC voltage, and the like.

交流電源１０１の周波数が５０Ｈｚか６０Ｈｚかの判定はゼロクロス信号の間隔を計測し、例えば９ｍｓより長ければ５０Ｈｚ，９ｍｓより短ければ６０Ｈｚの如くに判定すればよい。   Whether the frequency of the AC power supply 101 is 50 Hz or 60 Hz may be determined by measuring the interval of the zero cross signal, for example, 50 Hz if longer than 9 ms and 60 Hz if shorter than 9 ms.

また、スイッチング手段を２回を超えて短絡する場合について図４，図５を用いて説明する。図４は電源装置で３回短絡時の電源電圧・入力電流波形である。図５は電源装置で５回短絡時の電源電圧・入力電流波形である。   The case where the switching means is short-circuited more than twice will be described with reference to FIGS. FIG. 4 shows power supply voltage / input current waveforms when the power supply device is short-circuited three times. FIG. 5 shows power supply voltage / input current waveforms when the power supply is short-circuited five times.

上述のように、スイッチング手段１０６を２回短絡することで高調波を抑制して力率を改善することができるが、更に、さらに高調波電流を抑制し、力率を高くする場合、短絡回数を多くすることが有効である。ただし短絡回数を増やすと損失は増える。   As described above, the power factor can be improved by suppressing the harmonics by short-circuiting the switching means 106 twice, but if the harmonic current is further suppressed and the power factor is increased, the number of short-circuits It is effective to increase However, increasing the number of short circuits increases the loss.

次に、３回短絡する場合について説明する。   Next, the case of short-circuiting three times will be described.

図４のようにゼロクロス検出手段１０７で検出したゼロクロスから１.５ｍｓ遅延時間の後、スイッチング制御手段１０８はスイッチング手段１０６をオンして第１の短絡を行い、０.２ｍｓ、だけスイッチング手段１０６をオフし、その後スイッチング手段１０６をオンして第２の短絡を行い、その後スイッチング手段１０６をオフし、その後ゼロクロスから４.０ｍｓの時点でスイッチング手段１０６をオンして第３の短絡を行い、その後スイッチング手段１０６を開放する。   As shown in FIG. 4, after a delay time of 1.5 ms from the zero cross detected by the zero cross detecting means 107, the switching control means 108 turns on the switching means 106 to perform the first short circuit, and the switching means 106 is turned on for 0.2 ms. Then, the switching means 106 is turned on to perform a second short circuit, and then the switching means 106 is turned off, and then the switching means 106 is turned on at a point of 4.0 ms from the zero cross to perform a third short circuit. The switching means 106 is opened.

第１の短絡と第２の短絡との間の開放の時間は５０Ｈｚの時は０.２〜０.４ｍｓ，６０Ｈｚの時は０.１６〜０.３３ｍｓの間で選ぶ必要があるが、この範囲であれば周囲の状況に応じて変化させてもよい。第２の短絡と第３の短絡との間の開放の時間は固定値でもよいし可変させてもよい。   The opening time between the first short circuit and the second short circuit must be selected from 0.2 to 0.4 ms at 50 Hz, and from 0.16 to 0.33 ms at 60 Hz. If it is within the range, it may be changed according to the surrounding situation. The opening time between the second short circuit and the third short circuit may be a fixed value or variable.

第１の短絡時間と第２の短絡時間と第３の短絡時間の決定方法について説明する。
（ｄ）例えば第２の短絡時間と第３の短絡時間は０.１ｍｓと固定とし、第１の短絡時間は現在直流電圧を検出し目標直流電圧との差分でＰＩ制御を行って決定する。
（ｅ）別の方法としては第３の短絡時間は０.１ｍｓと固定とし、第１と第２の短絡時間は現在直流電圧を検出し目標直流電圧との差分でＰＩ制御を行って決定し、前述の（ａ）〜（ｃ）の短絡時間の決定方法で行ってもよい。
（ｆ）別の方法としては第１と第２と第３の短絡時間の比率を決めて第１と第２と第３の短絡時間の合計について現在直流電圧を検出し目標直流電圧との差分でＰＩ制御を行ってもよい。
（ｇ）別の方法としては第１と第２の第３の短絡時間の合計について現在直流電圧を検出し目標直流電圧との差分でＰＩ制御を行い、第１と第２の短絡時間にある制限値を持たせて第１の短絡時間が制限値を越えたら第２の短絡時間をのばし第２の短絡時間が制限値を越えたら第３の短絡を伸ばすようにしてもよい。また、この制限値を入力電流，負荷情報，目標電圧，現在電圧等により変化させてもよい。 A method for determining the first short circuit time, the second short circuit time, and the third short circuit time will be described.
(D) For example, the second short circuit time and the third short circuit time are fixed to 0.1 ms, and the first short circuit time is determined by detecting the current DC voltage and performing PI control based on the difference from the target DC voltage.
(E) As another method, the third short-circuit time is fixed at 0.1 ms, and the first and second short-circuit times are determined by detecting the current DC voltage and performing PI control based on the difference from the target DC voltage. The method for determining the short-circuit time of (a) to (c) described above may be used.
(F) As another method, the ratio of the first, second, and third short-circuit times is determined, the current DC voltage is detected for the sum of the first, second, and third short-circuit times, and the difference from the target DC voltage PI control may be performed with
(G) As another method, the current DC voltage is detected with respect to the sum of the first and second third short-circuit times, and PI control is performed based on the difference from the target DC voltage, and the first and second short-circuit times are present. If the first short circuit time exceeds the limit value with a limit value, the second short circuit time may be extended, and if the second short circuit time exceeds the limit value, the third short circuit may be extended. Further, this limit value may be changed according to input current, load information, target voltage, current voltage, and the like.

尚、以上の実施例では、短絡回数を５回の場合に、２回・３回・４回・５回ときめ細かく多段階に切り替えているが、例えば２回短絡から５回短絡に切り替える２段階でもよい。   In the above embodiment, when the number of short-circuits is 5, the number of times is finely switched to two, three, four, and five times. But you can.

更に短絡回数を増やし、５回短絡を行う場合について説明する。２回目の短絡までは前述の（ａ）〜（ｃ）の短絡時間の決定方法行う。   Further, the case where the number of short circuits is increased and the short circuit is performed five times will be described. Until the second short circuit, the determination method of the short circuit time of (a) to (c) is performed.

５０Ｈｚの場合は３回目の短絡はゼロクロスから４ｍｓ後、０.１ｍｓ行い、４回目の短絡は６ｍｓ後、０.１ｍｓ、５回目の短絡は７ｍｓ後０.１ｍｓ行う。図５に交流電源１０１の電圧、電流波形を示す。６０Ｈｚの場合は３回目の短絡はゼロクロスから３.３２ｍｓ後、０.１ｍｓ行い、４回目の短絡は５ｍｓ後、０.１ｍｓ、５回目の短絡は５.８ｍｓ後０.１ｍｓ行う。   In the case of 50 Hz, the third short circuit is performed 4 ms after the zero cross, 0.1 ms is performed, the fourth short circuit is performed 6 ms, 0.1 ms, and the fifth short circuit is performed 0.1 ms after 7 ms. FIG. 5 shows the voltage and current waveforms of the AC power supply 101. In the case of 60 Hz, the third short circuit is performed 3.3 ms after the zero cross, 0.1 ms is performed, the fourth short circuit is performed 5 ms, 0.1 ms, and the fifth short circuit is performed 0.1 ms after 5.8 ms.

ここで、３，４，５回目の短絡時間は０.１ｍｓとしたが、５０Ｈｚの場合は０.２５ｍｓ、６０Ｈｚの場合は０.２ｍｓより短い時間であればもっと長くしてもよいし、３，４，５回目でそれぞれ短絡時間を変えてもよい。また入力電流，負荷情報，目標電圧，現在電圧等により変化させてもよい。   Here, the third, fourth, and fifth short-circuiting times are set to 0.1 ms, but may be longer as long as they are shorter than 0.25 ms for 50 Hz and 0.2 ms for 60 Hz. , 4 and 5 times, the short circuit time may be changed. Further, it may be changed according to input current, load information, target voltage, current voltage, and the like.

次に、電源電圧と目標直流電圧との比に応じて、短絡回数を変化させる方法について説明する。   Next, a method of changing the number of short circuits according to the ratio between the power supply voltage and the target DC voltage will be described.

空気調和機は周辺の状況に応じた能力で運転することが求められ、この能力の大小は空気調和機が受けている負荷の量の大小と連動し、負荷の量の大小は直流電源装置が電力を供給する圧縮機の回転数，直流電源装置の出力直流電圧，直流電源装置の交流入力電流，空気調和機の機体各部の温度，冷凍サイクルの温度等の周辺情報に応じて変化する。   The air conditioner is required to be operated with the capacity according to the surrounding conditions. The magnitude of this capacity is linked to the magnitude of the load received by the air conditioner, and the magnitude of the load is determined by the DC power supply. It varies according to peripheral information such as the number of rotations of the compressor that supplies power, the output DC voltage of the DC power supply, the AC input current of the DC power supply, the temperature of each part of the air conditioner body, the temperature of the refrigeration cycle, and the like.

図１において、目標電圧設定手段１１１ｈは、周辺情報検出手段１１８が検出したこれらの周辺情報に応じて目標直流電圧Ｖｇを設定し、コンバータ制御手段１１１ｆに伝える。この場合、入力する電源電圧Ｖｓ（ピーク値）を検出し目標直流電圧Ｖｇ（平均値）との比の値を昇圧比Ｒとし、この昇圧比Ｒ＝Ｖｇ／Ｖｓを計算する。   In FIG. 1, a target voltage setting unit 111h sets a target DC voltage Vg according to the peripheral information detected by the peripheral information detection unit 118 and transmits it to the converter control unit 111f. In this case, the input power supply voltage Vs (peak value) is detected, the value of the ratio with the target DC voltage Vg (average value) is set as the boost ratio R, and this boost ratio R = Vg / Vs is calculated.

コンバータ制御手段１１１ｆはマイクロコンピュータ１１１に内蔵され、電源電圧・ゼロクロス検出手段１０７の信号を受けたＡ／Ｄ変換部１１１ｂ、周波数検出手段１１１ａやインバータ制御手段１１１ｇおよび目標電圧設定手段１１１ｈからの情報を基にＰＷＭ出力部１１１ｃを通じてスイッチング制御手段１０８に信号を送り、スイッチング制御手段１０８は信号に基づきスイッチング手段１０６を制御する。   The converter control means 111f is built in the microcomputer 111 and receives information from the A / D converter 111b, the frequency detection means 111a, the inverter control means 111g, and the target voltage setting means 111h that have received the signal from the power supply voltage / zero cross detection means 107. Based on this signal, a signal is sent to the switching control means 108 through the PWM output unit 111c, and the switching control means 108 controls the switching means 106 based on the signal.

昇圧比が１以上の場合は短絡回数を６回とし、昇圧比が１未満の場合は短絡回数を２〜５回とする。この場合、短絡回数を２⇔６回，３⇔６回，５⇔６回のように短絡回数を飛び飛びに切換えても順に切換えてもよい。前述の表２〜表７，表９〜表１４，表１６，表１７で示した例は昇圧比が１未満で２回短絡の場合のデータであり、表１８，表１９の例は昇圧比が１以上で２回短絡の場合のデータである。   When the step-up ratio is 1 or more, the number of short-circuits is six, and when the step-up ratio is less than 1, the number of short-circuits is two to five. In this case, the number of short-circuits may be switched between two or six times, such as 2⇔6 times, 3⇔6 times, or 5 回 6 times, or sequentially. The examples shown in Tables 2 to 7, Tables 9 to 14, Table 16, and Table 17 are data when the step-up ratio is less than 1 and short-circuited twice. Tables 18 and 19 show examples of the step-up ratio. Is data in case of 1 or more and short circuit twice.

なお、昇圧比が運転開始時は１未満で有ったのが、運転中に変わり１以上になった場合や、最初から１以上の場合は短絡回数を３回以上の運転となるが、この場合にも、１回目と２回目の短絡間隔を前述と同じように電源周波数が５０Ｈｚの時には０.２〜０.４ｍｓで、前記電源周波数が６０Ｈｚの時には０.１６〜０.３３ｍｓにすることで良好な結果を得ることができる。   In addition, when the step-up ratio was less than 1 at the start of operation, it changed to 1 or more during operation, or when it was 1 or more from the beginning, the number of short-circuits would be 3 or more. Even in this case, the first and second short-circuit intervals should be 0.2 to 0.4 ms when the power supply frequency is 50 Hz, and 0.16 to 0.33 ms when the power supply frequency is 60 Hz. Good results can be obtained.

以上のとおり、実施例は、目標電圧設定手段で設定された目標直流電圧と電源電圧検出手段で検出された電源電圧との比の値が所定値以上の場合に、スイッチング手段の短絡回数を前記比の値に応じて２回よりも多い回数で且つ、組み込まれる機器のモータの運転騒音周波数に対して直流電源装置の騒音周波数が超えない短絡回数に切り替えるものである。   As described above, in the embodiment, when the value of the ratio between the target DC voltage set by the target voltage setting means and the power supply voltage detected by the power supply voltage detection means is a predetermined value or more, the number of short circuits of the switching means is Depending on the value of the ratio, the number of short-circuits is switched to a number that is more than two times and that the noise frequency of the DC power supply device does not exceed the operating noise frequency of the motor of the apparatus to be incorporated.

このように、実施例の直流電源装置は、交流電源より入力された交流電力を直流電力に変換する整流回路と、前記交流電源と前記整流回路との間に接続されたリアクタと、前記交流電源を前記リアクタを介して短絡するスイッチング手段と、前記直流電力の目標電圧設定手段と、前記交流電源の周波数を検出する周波数検出手段と、前記交流電源の電源電圧を検出する電源電圧検出手段と、前記交流電源のゼロクロス点を検出するゼロクロス検出手段と、前記整流回路の出力である直流電圧を検出する直流電圧検出手段と、前記ゼロクロス点に同期させて前記スイッチング手段を短絡，開放するスイッチング制御手段とを備え、前記スイッチング制御手段は前記目標電圧設定手段で設定された目標直流電圧と前記電源電圧検出手段で検出された電源電圧との比の値が所定値未満の場合に前記ゼロクロス検出手段で検出された前記交流電源のゼロクロス点からの１／２周期中に、前記スイッチング手段を２回短絡し、この２回短絡の１回目と２回目の短絡間隔を、前記周波数検出手段で検出された電源周波数が５０Ｈｚの時には０.２〜０.４ｍｓで、前記電源周波数が６０Ｈｚの時には０.１６〜０.３３ｍｓとし、その後に前記比の値が所定値以上の場合に前記スイッチング手段の短絡回数を前記比の値に応じて前記２回よりも多い回数で且つ、組み込まれる機器のモータの運転騒音周波数に対して直流電源装置の騒音周波数が超えない短絡回数に切り替える。   Thus, the DC power supply device of the embodiment includes a rectifier circuit that converts AC power input from an AC power source into DC power, a reactor connected between the AC power source and the rectifier circuit, and the AC power source. Switching means for short-circuiting via the reactor, target voltage setting means for the DC power, frequency detection means for detecting the frequency of the AC power supply, power supply voltage detection means for detecting the power supply voltage of the AC power supply, Zero cross detection means for detecting a zero cross point of the AC power supply, DC voltage detection means for detecting a DC voltage as an output of the rectifier circuit, and switching control means for short-circuiting and opening the switching means in synchronization with the zero cross point The switching control means is detected by the target DC voltage set by the target voltage setting means and the power supply voltage detection means. When the value of the ratio to the power supply voltage is less than a predetermined value, the switching means is short-circuited twice during a half cycle from the zero-cross point of the AC power source detected by the zero-cross detection means, and this two-time short circuit The first and second short-circuit intervals are 0.2 to 0.4 ms when the power frequency detected by the frequency detection means is 50 Hz, and 0.16 to 0.33 ms when the power frequency is 60 Hz. Thereafter, when the value of the ratio is equal to or greater than a predetermined value, the number of short-circuits of the switching means is greater than the number of times according to the value of the ratio and more than the two times, and the direct current with respect to the operating noise frequency of the motor of the incorporated device Switch to the number of shorts that does not exceed the noise frequency of the power supply.

一般に、交流電源を整流回路で直流電源に変換し負荷を駆動する時、交流電源と整流回路の間にリアクタを設け、リアクタを介して交流電源を短絡する短絡素子を整流回路と並列に設けて、交流電源のゼロクロス点を基準とした適宜な時期に適宜な時間だけ短絡素子を作動させ、力率を改善することが行われている。   Generally, when driving a load by converting AC power into DC power by a rectifier circuit, a reactor is provided between the AC power supply and the rectifier circuit, and a short-circuit element that short-circuits the AC power supply via the reactor is provided in parallel with the rectifier circuit. In order to improve the power factor, the short-circuit element is operated for an appropriate time at an appropriate time based on the zero cross point of the AC power supply.

これは、力率を改善することで、交流電源の供給者の設備負担を軽減することに加えて、機器を接続するブレーカー、またはコンセントの容量を目いっぱいに活用して機器の能力を最大限に発揮させ、実質的に使用者のコストパフォーマンスを良くすることができるためである。しかし、闇雲に短絡すれば良いわけではなく、短絡の仕方や負荷の状況により、電源高調波電流が増加する場合がある。   In addition to reducing the facility burden on AC power supply suppliers by improving the power factor, the capacity of the circuit breaker or outlet is fully utilized to maximize the capacity of the equipment. This is because the cost performance of the user can be substantially improved. However, it is not necessary to short-circuit to the dark clouds, and the power supply harmonic current may increase depending on the short-circuiting method and load conditions.

前述の力率を改善し、電源高調波電流を抑制するために行う短絡素子の短絡回数は１回の短絡よりも２回の短絡のほうが上記の効果が大きく、更に短絡回数を多くすることで、電源高調波電流の規制を満足しつつ、更に力率を高くすることが可能である。   The number of short-circuits of the short-circuit element performed to improve the power factor and suppress the power supply harmonic current is greater than the above-mentioned effect by two short-circuits rather than one short-circuit, and further by increasing the number of short-circuits. The power factor can be further increased while satisfying the regulation of the power supply harmonic current.

理想的には、電源高調波電流を減少させるため、短絡素子のスイッチングを高周波で行わせ、電源電流をほぼ、電源電圧の瞬時値に同期させ、且つ、比例させて変化させれば良いが、こうするためには、短絡素子として高速の応答が可能な素子を選定しなければならず、通常高価な素子を使う必要が生じる。また、短絡素子のスイッチング損失が大きくなり、短絡素子の温度上昇が増える。   Ideally, in order to reduce the power supply harmonic current, the short-circuit element is switched at a high frequency, and the power supply current may be substantially synchronized with the instantaneous value of the power supply voltage and changed in proportion. In order to do this, an element capable of high-speed response must be selected as the short-circuit element, and it is usually necessary to use an expensive element. Further, the switching loss of the short-circuit element increases, and the temperature rise of the short-circuit element increases.

これを乗切るため、必然的に周辺の部品を含めて割高な高耐熱性の部品を使用することになり、このため、コストの上昇は避けられず、また、損失が大きいため、機器を接続しているブレーカー、またはコンセントの容量を目いっぱいに活用しても、負荷に供給できる電力が必ずしも最大にはならない。   In order to survive this, inevitably, expensive and heat-resistant parts including peripheral parts are used, and as a result, an increase in cost is inevitable and the loss is large. Even if the capacity of the breaker or outlet is fully utilized, the power that can be supplied to the load is not necessarily maximized.

また、負荷として、空気調和機を想定した場合、空気調和機は運転当初には大能力で室内を空調して使用者の快適性への要求に素早く対応し、設定温度付近では、空調運転が断続して使用者に不快感を与えないように、小能力で連続運転する必要がある。このため、圧縮機の回転数を可変にして、大能力から小能力までの広範な負荷変動に対処できることが要求される。   When an air conditioner is assumed as a load, the air conditioner has a large capacity at the beginning of the operation to quickly air-condition the room and quickly respond to the user's demands for comfort. It is necessary to continuously operate with a small capacity so as not to cause discomfort to the user intermittently. For this reason, it is required to be able to cope with a wide range of load fluctuations from a large capacity to a small capacity by making the rotation speed of the compressor variable.

なお、上述の整流回路を採用する場合、電源電圧の変動により、直流電圧が変動するのを極力避ける工夫も必要となる。   In addition, when employ | adopting the above-mentioned rectifier circuit, the device which avoids fluctuation | variation of DC voltage as much as possible by the fluctuation | variation of a power supply voltage is also needed.

実施例の直流電源装置では、負荷の駆動に最適な直流電圧を目標電圧設定手段で設定し、電源電圧の実効値との比の値が所定値未満の場合、つまり、負荷が軽く小能力での運転の場合には、電源周波数に応じた適切な短絡間隔で２回短絡を行うことで、電源高調波電流を抑制しつつ、力率を上げることができる。この時、スイッチング回数は２回のみなので、スイッチング損失は小さく、効率の良い運転ができる。   In the DC power supply device of the embodiment, when the DC voltage optimum for driving the load is set by the target voltage setting means and the value of the ratio with the effective value of the power supply voltage is less than a predetermined value, that is, the load is light and has a small capacity. In the case of this operation, the power factor can be increased while suppressing the power supply harmonic current by short-circuiting twice at an appropriate short-circuit interval corresponding to the power supply frequency. At this time, since the number of times of switching is only two, the switching loss is small and an efficient operation can be performed.

また、目標電圧と、電源電圧の実効値との比の値が所定値以上の場合、つまり、負荷が重く大能力での運転の場合には、６回までの短絡回数を単調に増加させることで、電源高調波電流を規制値以下に抑制しつつ、電源電圧の変動をカバーし、且つ、直流電圧の昇圧と力率のアップを両立できる。この時、スイッチングの回数は高々６回なので、スイッチング損失も僅かな増加で済み、高効率を維持できる。   In addition, when the ratio of the target voltage to the effective value of the power supply voltage is greater than or equal to a predetermined value, that is, when the load is heavy and the operation is performed at a large capacity, the number of short circuits up to 6 times should be increased monotonously. Thus, it is possible to cover the fluctuation of the power supply voltage while suppressing the power supply harmonic current below the regulation value, and to simultaneously increase the DC voltage and increase the power factor. At this time, since the number of times of switching is 6 at most, the switching loss can be increased only slightly, and high efficiency can be maintained.

この場合、２回目までの短絡は力率の増加と電源高調波電流の抑制を主眼とし、３回目の短絡は直流電圧の昇圧を主眼とし、４回目の短絡で直流電圧の昇圧と力率の増加を図り、５回目と６回目の短絡は力率の増加を主眼として短絡動作を実行する。   In this case, the second short circuit focuses on the increase of the power factor and the suppression of the power supply harmonic current, the third short circuit focuses on the DC voltage boost, and the fourth short circuit increases the DC voltage and power factor. In order to increase, the fifth and sixth short-circuit operations are performed with a focus on increasing the power factor.

特に、駆動する負荷が空気調和機の圧縮機である場合、空気調和機は室内の温度が設定温度に近い条件での運転（圧縮機の回転数が低い、小能力での連続運転）が非常に長いことから、スイッチング損失が小さい、効率の良い運転が長く続き消費電力量を抑制することができる。   In particular, when the load to be driven is a compressor of an air conditioner, the air conditioner is very likely to operate under conditions where the indoor temperature is close to the set temperature (continuous operation with low capacity, low compressor speed). Therefore, efficient operation can be continued for a long time with low switching loss, and power consumption can be suppressed.

また、空気調和運転の開始当初のような高負荷時はスイッチングの回数を増やして、圧縮用モータが誘起電圧に打勝って高速回転し、大能力を発揮できるよう直流電圧を昇圧し、圧縮機を駆動すると共に、高力率を確保し、空気調和機を接続したブレーカー、またはコンセントの容量を目いっぱいに活用して空気調和機の能力を最大限に発揮させ、室内を素早く快適温度にすることができる。   In addition, when the load is high, such as at the beginning of air-conditioning operation, the number of switchings is increased, and the DC voltage is boosted so that the compression motor can overcome the induced voltage and rotate at a high speed to exhibit its high capacity. As well as ensuring a high power factor, the capacity of the breaker or outlet connected to the air conditioner can be fully utilized to maximize the performance of the air conditioner and quickly bring the room to a comfortable temperature. be able to.

このため、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する直流電源装置を提供することができる。   For this reason, a DC power supply device that realizes high efficiency and appropriate power factor at low load while realizing high power factor and appropriate efficiency at high load while suppressing power supply harmonic current with an inexpensive circuit configuration is provided. be able to.

なお、上記では具体的に説明するため、負荷としてインバータ制御の空気調和機を例にとったが、本発明はインバータ制御の空気調和機用の直流電源装置に限定されるものではなく、同様な構成の直流電源装置であれば同様の効果を得ることができるのは言うまでも無い。   In the above description, an inverter-controlled air conditioner is taken as an example as a load for specific description. However, the present invention is not limited to a DC power supply for an inverter-controlled air conditioner. It goes without saying that the same effect can be obtained if the DC power supply device has the configuration.

また、実施例の直流電源装置は、前記スイッチング制御手段は前記目標電圧設定手段で設定された目標直流電圧と前記電源電圧検出手段で検出された電源電圧との比の値が所定値以上の場合に、前記２回短絡の場合と同様に、前記ゼロクロス検出手段で検出された前記交流電源のゼロクロス点からの１／２周期中に、前記スイッチング手段を２回短絡し、この２回短絡の１回目と２回目の短絡間隔を、前記周波数検出手段で検出された電源周波数が５０Ｈｚの時には０.２〜０.４ｍｓで、前記電源周波数が６０Ｈｚの時には０.１６〜０.３３ｍｓとし、その後に前記比の値が所定値以上の場合に前記スイッチング手段の短絡回数を前記比の値に応じて前記２回よりも多い回数で且つ、組み込まれる機器のモータの運転騒音周波数に対して直流電源装置の騒音周波数が超えない短絡回数に切り替える。   Further, in the DC power supply device according to the embodiment, when the switching control means has a ratio value between the target DC voltage set by the target voltage setting means and the power supply voltage detected by the power supply voltage detection means is a predetermined value or more. In the same manner as in the case of the two-time short circuit, the switching unit is short-circuited twice during a half cycle from the zero-cross point of the AC power source detected by the zero-cross detection unit. The short-circuit interval between the second time and the second time is set to 0.2 to 0.4 ms when the power frequency detected by the frequency detecting means is 50 Hz, and is set to 0.16 to 0.33 ms when the power frequency is 60 Hz. When the value of the ratio is equal to or greater than a predetermined value, the number of short circuits of the switching means is greater than the number of times according to the value of the ratio and is greater than the number of times, and the DC power Switch to the number of shorts that does not exceed the noise frequency of the source device.

これにより、２を超える回数短絡した場合でも前述と同様に適切な間隔を第１の短絡と第２の短絡の間に設けることで、電源高調波電流の抑制と力率の改善を達成できる。   As a result, even when the number of short circuits exceeds two, an appropriate interval is provided between the first short circuit and the second short circuit in the same manner as described above, thereby suppressing the power supply harmonic current and improving the power factor.

このため、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する直流電源装置を提供することができる。   For this reason, a DC power supply device that realizes high efficiency and appropriate power factor at low load while realizing high power factor and appropriate efficiency at high load while suppressing power supply harmonic current with an inexpensive circuit configuration is provided. be able to.

また、実施例の直流電源装置は、前記スイッチング制御手段は３回目以降の短絡時間を前記電源周波数が５０Ｈｚの時は０.２５ｍｓ、６０Ｈｚの時は０.２ｍｓ以下の範囲とする。   In the DC power supply of the embodiment, the switching control means sets the third and subsequent short-circuit times in the range of 0.25 ms when the power frequency is 50 Hz and 0.2 ms or less when the power frequency is 60 Hz.

これにより、３回目以降の短絡によって生じる電源高調波電流の周波数が、電源周波数が５０Ｈｚの時は２,０００Ｈｚ、６０Ｈｚの時は２,５００Ｈｚ以上となり、電源周波数の４０次以上となって、電源高調波電流規制の対象から除外されるので、電源高調波電流規制を満足することができ、主として力率の向上を考慮した検討をすれば良いことになる。   As a result, the frequency of the power harmonic current generated by the third and subsequent short circuits is 2,000 Hz when the power frequency is 50 Hz, 2,500 Hz or higher when the power frequency is 60 Hz, and the power frequency is 40th or higher. Since it is excluded from the target of the harmonic current regulation, the power supply harmonic current regulation can be satisfied, and it is only necessary to consider mainly the improvement of the power factor.

これは、高調波電流を抑制し、力率を高くするためには、短絡回数を多くすることが有効であることを前述したが、シミュレーションによれば、力率に関係してくる３次〜１５次の高調波の抑制には短絡回数を多くすることが有効であるが、１５次〜４０次の高調波電流は逆に増えやすい傾向となる。   As described above, in order to suppress the harmonic current and increase the power factor, it is effective to increase the number of short-circuits. Increasing the number of short circuits is effective for suppressing the 15th harmonic, but the 15th to 40th harmonic currents tend to increase conversely.

そこで第２の短絡より後の短絡は４０次よりも高次の波形とすることが電源高調波電流の抑制に重要となることが判った。電源周波数が５０Ｈｚである時、その周期２０ｍｓの正弦波であり、電源周波数の４０次高調波の周期は０.５ｍｓとなる。   Thus, it has been found that it is important for the suppression of the power supply harmonic current that the short circuit after the second short circuit has a higher-order waveform than the 40th order. When the power supply frequency is 50 Hz, the sine wave has a period of 20 ms, and the period of the 40th harmonic of the power supply frequency is 0.5 ms.

短絡により発生する三角波がこの４０次の周期の１／２以下となれば電源高調波電流規制の対象外になり、短絡時間を０.２５ｍｓより短くすることで電源高調波電流規制を満足することができる。電源周波数が６０Ｈｚのときも同様の理由で短絡時間を０.２ｍｓより短くすることで電源高調波電流規制を満足することができる。   If the triangular wave generated by the short circuit becomes 1/2 or less of this 40th order period, it will be excluded from the power harmonic current regulation, and the power harmonic current regulation will be satisfied by making the short circuit time shorter than 0.25 ms. Can do. Even when the power supply frequency is 60 Hz, the power supply harmonic current regulation can be satisfied by shortening the short circuit time to less than 0.2 ms for the same reason.

このため、短絡回数を多くして力率を改善しつつ、電源高調波電流規制を満足する直流電源装置を提供することができる。   For this reason, it is possible to provide a DC power supply device that satisfies the power harmonic current regulation while increasing the number of short circuits and improving the power factor.

次に、短絡回数を切換える時の制御について図６〜図９を用いて交流電源の半周期を例にとって説明する。図６は電源装置の短絡回数制御部の記憶装置の記憶内容説明図である。図７は短絡回数制御部の短絡回数制御フロー要部である。   Next, control when switching the number of short circuits will be described with reference to FIGS. 6 to 9 by taking the half cycle of the AC power supply as an example. FIG. 6 is an explanatory diagram of the storage contents of the storage device of the short circuit number control unit of the power supply device. FIG. 7 shows a main part of the short circuit number control flow of the short circuit number control part.

コンバータ制御手段１１１ｆの内部には記憶装置が内蔵され、この記憶装置には前記の昇圧比Ｒに応じた設定短絡回数Ｎを選択できるように昇圧比の閾値が記憶されている。昇圧比の閾値は短絡回数が増加する時と減少する時で違えて、適度なヒシテリシスを持たせ、制御が安定するようにしている。   A converter is built in converter control means 111f, and a threshold value of the boost ratio is stored in this storage device so that the set number of short circuits N corresponding to the boost ratio R can be selected. The threshold of the step-up ratio is different depending on whether the number of short-circuits increases or decreases, and an appropriate hysteresis is provided so that the control is stabilized.

記憶装置には図６のように、この昇圧比Ｒに応じた設定短絡回数Ｎが記憶され、また設定短絡回数Ｎ及び実短絡回数Ｍに応じた、ｎ回目の短絡時の短絡時間の上限値ＴｕＮｎ、及び下限値ＴｌＮｎが記憶装置に記憶されており、更に短絡回数に応じた、目標直流電圧Ｖｇの制御許容幅ΔＶＭが記憶されている。   As shown in FIG. 6, the memory device stores the set short-circuit count N corresponding to the step-up ratio R, and the upper limit value of the short-circuit time at the n-th short-circuit according to the set short-circuit count N and the actual short-circuit count M. TuNn and the lower limit value TlNn are stored in the storage device, and further, a control allowable width ΔVM of the target DC voltage Vg corresponding to the number of short circuits is stored.

図７のステップＳ１で直流電源装置１００の動作を開始すると、先ず、ステップＳ３で各種の判断や演算に必要なデータを入手する前段の処理が行われ、ステップＳ２０に進み、直流出力電圧Ｖｄと目標直流電圧の上限値Ｖｇｕとを比較し、直流出力電圧Ｖｄが目標直流電圧の上限値Ｖｇｕ以下であればステップＳ２１に進み、直流出力電圧Ｖｄが目標直流電圧の上限値Ｖｇｕを超えていればステップＳ２６に進む。   When the operation of the DC power supply device 100 is started in step S1 in FIG. 7, first, in step S3, the previous process of obtaining data necessary for various judgments and calculations is performed, and the process proceeds to step S20, where the DC output voltage Vd The upper limit value Vgu of the target DC voltage is compared. If the DC output voltage Vd is equal to or lower than the upper limit value Vgu of the target DC voltage, the process proceeds to step S21, and if the DC output voltage Vd exceeds the upper limit value Vgu of the target DC voltage. Proceed to step S26.

ステップＳ２１で更に直流出力電圧Ｖｄと目標直流電圧Ｖｇとを比較し、直流出力電圧Ｖｄが目標直流電圧Ｖｇ未満の場合はステップＳ２５に進み、直流出力電圧Ｖｄが目標直流電圧Ｖｇ以上の場合は、直流出力電圧Ｖｄが適正な値の範囲に納まっているので、現状の制御を続行すればよいのでステップＳ６５に進み、現行の短絡時間で短絡を実行しステップＳ８０に進んで交流電源の半周期での短絡動作を終了する。   In step S21, the DC output voltage Vd is further compared with the target DC voltage Vg. If the DC output voltage Vd is less than the target DC voltage Vg, the process proceeds to step S25. If the DC output voltage Vd is greater than or equal to the target DC voltage Vg, Since the DC output voltage Vd is within an appropriate value range, it is sufficient to continue the current control. Therefore, the process proceeds to step S65, the short-circuit is executed in the current short-circuit time, and the process proceeds to step S80, where the AC power supply is half cycle. This completes the short-circuit operation.

ステップＳ２５で前回の半周期での実短絡回数Ｍと設定短絡回数Ｎとを比較し、実短絡回数Ｍが設定短絡回数Ｎより少ない場合はステップＳ４０に進み短絡回数を１回増やして各回の短絡時間を設定しなおす短絡回数増加処理を行い、ステップＳ６０に進み、設定しなおした１回目の短絡時間Ｔ′ａ１〜Ｍ＋１回目の短絡時間Ｔ′ａＭｐで短絡動作を実行し、ステップＳ８０に進んで短絡動作を終了する。   In step S25, the actual number of short circuits M in the previous half cycle is compared with the set number of short circuits N. If the actual number of short circuits M is less than the set number of short circuits N, the process proceeds to step S40, and the number of short circuits is increased by one. The short-circuiting number increasing process for resetting the time is performed, and the process proceeds to step S60. The short-circuiting operation is executed with the first short-circuiting time T'a1 to M + 1 and the first short-circuiting time T'aMp, and the process proceeds to step S80. End short circuit operation.

ステップＳ２５で実短絡回数Ｍが設定短絡回数Ｎ以上である場合はステップＳ３０に進み、実短絡回数Ｍに対する１回目の短絡時間の上限値ＴｕＭ１〜Ｍ回目（最終回）の短絡時間の上限値ＴｕＭＭを記憶装置から読込んでその短絡時間上限値合計ΣＴｕＭｎを演算し、また、前回の半周期での１回目の短絡時間Ｔａ１〜Ｍ回目（最終回）の短絡時間ＴａＭの合計である短絡時間合計ΣＴａｎを演算して比較する。   If the actual short circuit count M is equal to or greater than the set short circuit count N in step S25, the process proceeds to step S30, where the first short circuit time upper limit value TuM1 to the Mth (final) short circuit time upper limit value TuMM with respect to the actual short circuit count M. Is calculated from the storage device and the short-circuit time upper limit total ΣTuMn is calculated, and the short-circuit time total ΣTan that is the sum of the first short-circuit time Ta1 to M-th (final) short-circuit time TaM in the previous half cycle And compare.

ステップＳ３０で短絡時間上限値合計ΣＴｕＭｎが短絡時間合計ΣＴａｎ以下である場合は、Ｍ回の短絡回数ではこれ以上短絡時間を長くすることができないので短絡回数を１回増加させるべくステップ４０に進み、前述と同様に、短絡回数増加処理を行い、ステップＳ６０を介してステップＳ８０に至り、短絡動作を終了する。   If the total short circuit time upper limit value ΣTuMn is equal to or less than the total short circuit time ΣTan in step S30, the short circuit time cannot be increased any further by the number of M short circuits, so the process proceeds to step 40 in order to increase the number of short circuits by one. In the same manner as described above, the short-circuit number increasing process is performed, the process reaches step S80 via step S60, and the short-circuit operation is terminated.

ステップＳ３０で短絡時間上限値合計ΣＴｕＭｎが短絡時間合計ΣＴａｎより大きい場合は、現行のＭ回の短絡回数で短絡時間を長くする余地があるので、短絡時間が上限値に達していない回の短絡時間を長くするようステップＳ４５に進み、目標直流電圧Ｖｇと直流出力電圧Ｖｄとの差分でＰＩ制御を行い、今回の短絡時間を決定する。   If the total short circuit time upper limit ΣTuMn is larger than the total short circuit time ΣTan in step S30, there is room for increasing the short circuit time with the current M number of short circuits, so the short circuit time when the short circuit time has not reached the upper limit value. In step S45, PI control is performed using the difference between the target DC voltage Vg and the DC output voltage Vd to determine the current short circuit time.

ステップＳ４５では短絡時間の決定を前回の半周期での短絡時間に修正を加えて行い、１回目の修正短絡時間Ｔ′ａ１〜Ｍ回目（最終回）の修正短絡時間Ｔ′ａＭを決定する。次に、ステップＳ７０に進んで、修正した短絡時間Ｔ′ａ１〜Ｔ′ａＭで短絡動作を実行し、ステップＳ８０に進んで短絡動作を終了する。   In step S45, the short circuit time is determined by correcting the short circuit time in the previous half cycle, and the first corrected short circuit time T'a1 to the Mth (final) corrected short circuit time T'aM is determined. Next, it progresses to step S70, a short circuit operation is performed by corrected short circuit time T'a1-T'aM, and it progresses to step S80 and complete | finishes a short circuit operation.

ステップＳ２６で前回の半周期での実短絡回数Ｍと設定短絡回数Ｎとを比較し、実短絡回数Ｍが設定短絡回数Ｎより多い場合はステップＳ５０に進み短絡回数を１回減らして各回の短絡時間を設定しなおす短絡回数減少処理を行い、ステップＳ７５に進み、設定しなおした１回目の短絡時間Ｔ′ａ１〜Ｍ−１回目の短絡時間Ｔ′ａＭｍで短絡動作を実行し、ステップＳ８０に進んで短絡動作を終了する。   In step S26, the actual number of short circuits M in the previous half cycle is compared with the set number of short circuits N. If the actual number of short circuits M is greater than the set number of short circuits N, the process proceeds to step S50, and the number of short circuits is reduced by one. Short circuit number reduction processing for resetting the time is performed, the process proceeds to step S75, and the short circuit operation is executed with the reset first short circuit time T'a1 to M-1 first short circuit time T'aMm, and then to step S80. Proceed to complete the short-circuit operation.

ステップＳ２６で実短絡回数Ｍが設定短絡回数Ｎ以下である場合はステップＳ３５に進み、実短絡回数Ｍに対する１回目の短絡時間の下限値ＴｌＭ１〜Ｍ回目（最終回）の短絡時間の下限値ＴｌＭＭを記憶装置から読込んでその短絡時間下限値合計ΣＴｌＭｎを演算し、また、前回の半周期での１回目の短絡時間Ｔａ１〜Ｍ回目（最終回）の短絡時間ＴａＭの短絡時間合計ΣＴａｎを演算して比較する。   If the actual short circuit count M is less than or equal to the set short circuit count N in step S26, the process proceeds to step S35, where the first short circuit time lower limit value TlM1 to the Mth (final) short circuit time lower limit value TlMM with respect to the actual short circuit number M. Is calculated from the storage device and the short-circuit time lower limit total ΣTlMn is calculated, and the first short-circuit time Ta1 to M-th (final) short-circuit time TaM in the previous half cycle is calculated ΣTan. Compare.

ステップＳ３５で短絡時間下限値合計ΣＴｌＭｎが短絡時間合計ΣＴａｎ以上である場合は、Ｍ回の短絡回数ではこれ以下に短絡時間を短くすることができないので短絡回数を１回減少させるべくステップ５０に進み、前述と同様に、短絡回数減少処理を行い、ステップＳ７５を介してステップＳ８０に至り、短絡動作を終了する。   If the short-circuit time lower limit total ΣTlMn is equal to or greater than the short-circuit time total ΣTan in step S35, the short-circuit time cannot be shortened below this number of M short-circuits. In the same manner as described above, the short-circuit number reduction process is performed, and the process reaches step S80 via step S75 to end the short-circuit operation.

ステップＳ３５で短絡時間下限値合計ΣＴｌＭｎが短絡時間合計ΣＴａｎより小さい場合は、現行のＭ回の短絡回数で短絡時間を短くする余地があるので、短絡時間が下限値に達していない回の短絡時間を短くするようステップＳ４５に進み、前述と同様にＰＩ制御を行い、今回の短絡時間を決定し、ステップＳ７０を介してステップＳ８０に至り、短絡動作を終了する。   If the total short circuit time lower limit value ΣTlMn is smaller than the total short circuit time Σ Tan in step S35, there is room for shortening the short circuit time with the current M number of short circuits, so the short circuit time when the short circuit time has not reached the lower limit value. In step S45, PI control is performed in the same manner as described above, the current short-circuiting time is determined, step S70 is reached via step S70, and the short-circuiting operation is terminated.

次に、ステップＳ３の前段処理について図８を用いて説明する。図８は短絡回数制御部の前段処理フロー要部である。   Next, the pre-processing in step S3 will be described with reference to FIG. FIG. 8 is a main part of the pre-processing flow of the short circuit number control unit.

ステップＳ１０１で前段処理を開始し、ステップＳ１０５で交流電源電圧Ｖｓ、目標直流電圧Ｖｇを読込み、ステップＳ１１０に進み、昇圧比Ｒを演算し、ステップＳ１１１に進み、昇圧比Ｒに応じた設定短絡回数Ｎを記憶装置から読込む。更に、ステップＳ１１２に進んで、この短絡回数に応じて目標直流電圧の許容幅ΔＶＭを記憶装置から読込み、ステップＳ１１５に進み、目標直流電圧Ｖｇの上限値Ｖｇｕを演算する。   The pre-processing is started in step S101, the AC power supply voltage Vs and the target DC voltage Vg are read in step S105, the process proceeds to step S110, the boost ratio R is calculated, the process proceeds to step S111, and the set number of short circuits according to the boost ratio R N is read from the storage device. Further, the process proceeds to step S112, the allowable width ΔVM of the target DC voltage is read from the storage device in accordance with the number of short circuits, the process proceeds to step S115, and the upper limit value Vgu of the target DC voltage Vg is calculated.

次に、ステップＳ１１６に進み、直流出力電圧Ｖｄを読込んで、ステップＳ１２０に進み、前回の半周期での実短絡回数Ｍを調べて、実短絡回数Ｍが２より小さい場合は、短絡動作の初期状態であるとして、後刻の制御に支障のないように、Ｍの値を設定短絡回数Ｎと仮定し、ステップＳ１３０に進んで、前段処理を終了する。ステップＳ１２０でＭが２以上の場合はそのままステップＳ１３０に進んで、前段処理を終了する。   Next, the process proceeds to step S116, the direct-current output voltage Vd is read, the process proceeds to step S120, and the actual number of short circuits M in the previous half cycle is checked. Assuming that the state is in a state, the value of M is assumed to be the set number N of short-circuits so as not to hinder the later control, the process proceeds to step S130, and the pre-stage process is terminated. When M is 2 or more in step S120, the process proceeds to step S130 as it is, and the pre-process is terminated.

次に、ステップＳ４０の短絡回数増加処理について図９を用いて説明する。図９は短絡回数制御部の短絡回数増加処理フロー要部である。   Next, the short circuit number increasing process in step S40 will be described with reference to FIG. FIG. 9 shows the main part of the short circuit number increasing process flow of the short circuit number control unit.

短絡回数増加処理をステップＳ２０１で開始し、ステップＳ２０２で前の半周期の実短絡回数Ｍを調べ、Ｍ＝６つまり、前回の半周期の短絡回数が６回である場合は、ステップＳ２１０に進み、図７のステップＳ３０と同様に短絡時間合計ΣＴａｎと短絡時間上限値合計ΣＴｕＭｎを比較する。この場合、Ｍ＝６であるので、ΣＴａｎとΣＴｕ６ｎとを比較する。   The short circuit number increasing process is started in step S201, and the actual short circuit number M in the previous half cycle is checked in step S202. If M = 6, that is, if the short circuit number in the previous half cycle is 6, the process proceeds to step S210. The short circuit time total ΣTan and the short circuit time upper limit total ΣTuMn are compared as in step S30 of FIG. In this case, since M = 6, ΣTan and ΣTu6n are compared.

ステップＳ２１０で短絡時間合計ΣＴａｎが短絡時間上限値合計ΣＴｕ６ｎ以上の場合は、６Ｍ回の短絡回数でこれ以上短絡時間を長くすることができない上に、これより多い短絡回数は設定されていないので、ステップＳ２１２に進み、現行の短絡時間を維持し、ステップＳ２６５に進んで短絡回数増加処理を終了する。   If the total short circuit time ΣTan is greater than or equal to the total short circuit time upper limit value ΣTu6n in step S210, the short circuit time cannot be further increased by the number of short circuits of 6M, and the number of short circuits more than this is not set. Proceeding to step S212, the current short circuit time is maintained, and the process proceeds to step S265 to end the short circuit number increasing process.

この場合、直流出力電圧Ｖｄが目標直流電圧Ｖｇに達しないことも有りうるが、短絡時間上限値Ｔｕ６ｎは目標直流電圧Ｖｇだけではなく、電源高調波電流の大きさや、駆動素子などの温度上昇によって制限される場合もあるので、短絡時間上限値Ｔｕ６ｎの設定に当たっては、接続される負荷の種類、駆動素子などの冷却方法、周囲温度条件に応じて慎重に検討する必要がある。   In this case, the DC output voltage Vd may not reach the target DC voltage Vg. However, the short-circuit time upper limit Tu6n is not limited to the target DC voltage Vg, but depends on the magnitude of the power supply harmonic current and the temperature rise of the drive element. Since it may be limited, it is necessary to carefully consider the setting of the short-circuit time upper limit Tu6n according to the type of load to be connected, the cooling method of the drive element, and the ambient temperature conditions.

ステップＳ２１０で短絡時間合計ΣＴａｎが短絡時間上限値合計ΣＴｕ６ｎより小さい場合は、現行の６回の短絡回数で短絡時間を長くする余地があるので、短絡時間が上限値に達していない回の短絡時間を長くするようステップＳ２１５に進み、目標直流電圧Ｖｇと直流出力電圧Ｖｄとの差分でＰＩ制御を行い、今回の短絡時間を決定し、ステップＳ２６５で短絡回数増加処理を終了する。   If the short-circuit time total ΣTan is smaller than the short-circuit time upper limit total ΣTu6n in step S210, there is room for increasing the short-circuit time by the current six short-circuit times, so the short-circuit time when the short-circuit time has not reached the upper limit value. In step S215, PI control is performed based on the difference between the target DC voltage Vg and the DC output voltage Vd, the current short circuit time is determined, and the short circuit number increasing process is terminated in step S265.

ステップＳ２０２でＭ＝５である場合は、短絡回数を１回増やして６回にするべく、ステップＳ２２０に進み、６回短絡の場合の６回目の短絡時間の下限値Ｔｌ６６を記憶装置から呼出し、６回目の短絡時間Ｔ′ａ６に設定する。この場合、前の半周期での５回の短絡に、単純に６回目の短絡を追加すると直流出力電圧Ｖｄが上昇し過ぎ、駆動している負荷に悪影響を及ぼす恐れがある。   If M = 5 in step S202, the process proceeds to step S220 to increase the number of short circuits by 1 to 6 times, and the lower limit value Tl66 of the sixth short circuit time in the case of the 6th short circuit is called from the storage device. The sixth short-circuit time T′a6 is set. In this case, if the sixth short-circuit is simply added to the five short-circuits in the previous half cycle, the DC output voltage Vd increases excessively, which may adversely affect the driving load.

このように、直流出力が急変する場合は、このような急変に対応するため、接続されている負荷の電源への耐性をアップしたり、接続されている負荷の制御に、短絡回数の切換時を特異点として短絡回数の切換時のみ作動する特殊な制御を導入するなどのコストアップにつながる恐れの大きい対応を余儀なく行わなければならない。   In this way, when the DC output changes suddenly, in order to cope with such a sudden change, the resistance of the connected load to the power source is increased, or the number of short-circuits is switched to control the connected load. As a singular point, special measures that are activated only when the number of short circuits is switched must be taken.

この現象を回避するためには、短絡回数を増しても、直流出力電圧が急変しないように、追加した短絡回以外の短絡回の短絡時間を減少させることが効果的である。実施例では、追加した短絡回以外の短絡回の短絡時間を減らし、全体として、短絡を追加する前と後で合計の短絡時間がほぼ等しくなるようにした。これにより、短絡の追加の前後で直流出力電圧の変化は小さくなり、負荷に与える影響も軽微なものとすることができた。   In order to avoid this phenomenon, it is effective to reduce the short-circuit time of the short-circuit times other than the added short-circuit times so that the DC output voltage does not change suddenly even if the number of short-circuits is increased. In the example, the short-circuit time of the short-circuit times other than the added short-circuit time was reduced, and as a whole, the total short-circuit time was substantially equal before and after the addition of the short-circuit. As a result, the change in the DC output voltage before and after the addition of the short circuit was reduced, and the influence on the load could be minimized.

更に実施例では、追加した短絡回以外の短絡回の短絡時間を前の半周期での各回の短絡時間に比例させて減少させることで、短絡の追加の前後で直流出力電圧は勿論のこと、力率，電源高調波電流も急変しなくなって、連続的な変化に近くなるので、接続されている負荷の制御に短絡回数の変化に伴う特殊な制御の必要性が乏しくなり必要な短絡の追加を心置きなく行え、製品の開発スピードをアップさせることができる。   Further, in the embodiment, by reducing the short-circuit time of the short-circuit times other than the added short-circuit times in proportion to the short-circuit time of each time in the previous half cycle, the DC output voltage is of course before and after the addition of the short-circuit, Since the power factor and power supply harmonic current also do not change suddenly and become close to a continuous change, the need for special control accompanying the change in the number of shorts is reduced in controlling the connected load, and the addition of necessary shorts Can increase the speed of product development.

ステップＳ２２０からステップＳ２２１に進み、６回目の短絡時間Ｔ′ａ６を前の半周期の１〜５回目の短絡時間から各々の短絡時間に案分比例して減算する時間の合計値として案分残時間Ｔｒ６に設定し、ステップＳ２２２に進み、次式により今度の半周期の５回目の短絡時間Ｔ′ａ５を演算し、設定する。   Proceeding from step S220 to step S221, the remaining part of the sixth short circuit time T'a6 is subtracted proportionally to each of the short circuit times from the first to fifth short circuit times of the previous half cycle. The time Tr6 is set and the process proceeds to step S222, and the fifth short-circuit time T'a5 of the next half cycle is calculated and set by the following equation.

Figure 0005481165
Figure 0005481165

次に、ステップＳ２２３に進み、設定したＴ′ａ５を記憶装置から呼出した６回短絡の５回目の短絡時間下限値Ｔｌ６５と比較し、設定した短絡時間Ｔ′ａ５が記憶装置から呼び出した短絡時間下限値Ｔｌ６５以上である場合は、設定を有効としてステップＳ２２８に進み、設定した短絡時間Ｔ′ａ５が記憶装置から呼び出した短絡時間下限値Ｔｌ６５より小さい場合は、ステップＳ２２５に進んで、設定した短絡時間Ｔ′ａ５を破棄し、記憶装置から呼び出した短絡時間下限値Ｔｌ６５を今度の半周期の５回目の短絡時間Ｔ′ａ５として再設定し、ステップＳ２２８に進む。   In step S223, the set T'a5 is compared with the fifth short-circuit time lower limit value Tl65 of the sixth short-circuit called from the storage device, and the set short-circuit time T'a5 is called from the storage device. If it is not less than the lower limit value Tl65, the setting is validated and the process proceeds to step S228. If the set short circuit time T'a5 is smaller than the short circuit time lower limit value Tl65 called from the storage device, the process proceeds to step S225 and the set short circuit is set. The time T′a5 is discarded, and the short-circuiting time lower limit value Tl65 called from the storage device is reset as the fifth short-circuiting time T′a5 of the next half cycle, and the process proceeds to step S228.

ステップＳ２２８では案分残時間Ｔｒ６から５回目の短絡時間の設定での修正量Ｔａ５−Ｔ′ａ５を差引いた案分残時間Ｔｒ５を次の式により演算する。   In step S228, the promising remaining time Tr5 obtained by subtracting the correction amount Ta5-T'a5 in the setting of the fifth short-circuiting time from the promising remaining time Tr6 is calculated by the following equation.

Figure 0005481165
Figure 0005481165

次に、ステップＳ２３２に進み、上記の案分残時間Ｔｒ５を１〜４回目の短絡時間から各々の短絡時間に案分比例して減算すべく、次式により今度の半周期の４回目の短絡時間Ｔ′ａ４を演算し、設定する。   Next, the process proceeds to step S232, and in order to subtract the probable remaining time Tr5 from the first to fourth short-circuiting times proportionally to the respective short-circuiting times, the following short-cycle fourth short-circuiting is performed according to the following equation. Time T'a4 is calculated and set.

Figure 0005481165
Figure 0005481165

次に、ステップＳ２３３に進み、設定したＴ′ａ４を記憶装置から呼出したＭｐ回短絡の４回目の短絡時間下限値ＴｌＭｐ４と比較する。ここで、Ｍｐは今度の半周期での短絡回数で有り、前の半周期での短絡回数が５であるので、これに短絡回数を１回加えてＭｐは６となる。従って、具体的にステップＳ２３３を読み直すと次のようになる。   In step S233, the set T′a4 is compared with the fourth short-circuit time lower limit value TlMp4 of the Mp short-circuit called from the storage device. Here, Mp is the number of short circuits in the next half cycle, and the number of short circuits in the previous half cycle is 5. Therefore, the number of short circuits is added to this, and Mp is 6. Therefore, when step S233 is specifically reread, the following is obtained.

設定したＴ′ａ４を記憶装置から呼出した６回短絡の４回目の短絡時間下限値Ｔｌ６４と比較し、設定した短絡時間Ｔ′ａ４が記憶装置から呼び出した短絡時間下限値Ｔｌ６４以上である場合は、設定を有効としてステップＳ２３８に進む。   When the set T′a4 is compared with the fourth short circuit time lower limit value Tl64 of the sixth short circuit called from the storage device, and the set short circuit time T′a4 is equal to or greater than the short circuit time lower limit value Tl64 called from the storage device The setting is validated and the process proceeds to step S238.

設定した短絡時間Ｔ′ａ４が記憶装置から呼び出した短絡時間下限値Ｔｌ６４より小さい場合は、ステップＳ２３５に進んで、設定した短絡時間Ｔ′ａ４を破棄し、記憶装置から呼び出した短絡時間下限値Ｔｌ６４を今度の半周期の４回目の短絡時間Ｔ′ａ４として再設定し、ステップＳ２３８に進む。   If the set short circuit time T′a4 is smaller than the short circuit time lower limit value Tl64 called from the storage device, the process proceeds to step S235, the set short circuit time T′a4 is discarded, and the short circuit time lower limit value Tl64 called from the memory device is discarded. Is reset as the fourth short-circuit time T′a4 of the current half cycle, and the process proceeds to step S238.

ステップＳ２３８では５回目の短絡時間設定時に残っている１〜４回目の短絡時間から案分比例して減ずべき案分残時間Ｔｒ５から４回目の短絡時間の設定での修正量Ｔａ４−Ｔ′ａ４を差引いた案分残時間Ｔｒ４を次の式により演算する。   In step S238, the correction amount Ta4-T ′ in the setting of the fourth short-circuit time from the probable remaining time Tr5 to be reduced proportionally from the first to fourth short-circuit times remaining at the fifth short-circuit time setting. The probable remaining time Tr4 obtained by subtracting a4 is calculated by the following equation.

Figure 0005481165
Figure 0005481165

以下、同様に（５），（６）式を使用し、ステップＳ２４２〜Ｓ２４８で３回目の短絡時間Ｔ′ａ３、案分残時間Ｔｒ３を演算，設定し、（７），（８）式を使用し、ステップＳ２５２〜Ｓ２５８で２回目の短絡時間Ｔ′ａ２、案分残時間Ｔｒ２を演算，設定し、ステップＳ２６２で（９）式を使用して今度の半周期の１回目の短絡時間Ｔ′ａ１を演算，設定して、ステップＳ２６５に進んで短絡回数増加処理を終了する。   Similarly, using the equations (5) and (6), the third short circuit time T′a3 and the probable remaining time Tr3 are calculated and set in steps S242 to S248, and the equations (7) and (8) are calculated. In step S252 to S258, the second short-circuit time T'a2 and the probable remaining time Tr2 are calculated and set, and in step S262, the first short-circuit time T of the next half cycle is calculated using equation (9). 'A1 is calculated and set, the process proceeds to step S265, and the short circuit number increasing process is terminated.

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

ステップＳ２０２に戻り、前の半周期での短絡回数Ｍが５回より小さい場合は、ステップＳ２０５に進み、更に、短絡回数Ｍが３より大きい場合、つまりＭ＝４の場合には、短絡回数を１回増やして５回にするべく、ステップＳ２３０に進み、５回短絡の場合の５回目の短絡時間の下限値Ｔｌ５５を記憶装置から呼出し、５回目の短絡時間Ｔ′ａ５に設定し、ステップＳ２３１に進む。   Returning to step S202, if the number M of short circuits in the previous half cycle is smaller than 5, the process proceeds to step S205, and if the number M of short circuits is larger than 3, that is, if M = 4, the number of short circuits is set. In order to increase it by 1 to 5 times, the process proceeds to step S230, and the lower limit value Tl55 of the fifth short-circuit time in the case of the fifth short-circuit is retrieved from the storage device and set to the fifth short-circuit time T'a5. Proceed to

ステップＳ２３１では、５回目の短絡時間Ｔ′ａ５を以降のステップで設定される１回目〜４回目までの短絡時間の演算の中で、前の半周期での１回目〜４回目の短絡時間から案分比例で減ずべき時間の合計値である案分残時間Ｔｒ５として演算し、ステップＳ２３２に進む。この場合、案分残時間Ｔｒ５は上記で設定した５回目の短絡時間Ｔ′ａ５に等しい。   In step S231, the fifth short-circuit time T'a5 is calculated from the first to fourth short-circuit times in the previous half cycle in the calculation of the first to fourth short-circuit times set in the subsequent steps. A prorated portion remaining time Tr5, which is a total value of the time that should be reduced in proportion to the prorated portion, is calculated, and the process proceeds to step S232. In this case, the probable remaining time Tr5 is equal to the fifth short-circuit time T′a5 set above.

ステップＳ２３２以降は前述した通りに制御が進行し、ステップＳ２６５で短絡回数増加処理が終了する。   After step S232, the control proceeds as described above, and the short circuit number increasing process ends in step S265.

次に、ステップＳ２０５に戻り、前の半周期での短絡回数Ｍが３である場合、短絡回数を１回増やして４回にするべく、ステップＳ２４０に進み、４回短絡の場合の４回目の短絡時間の下限値Ｔｌ４４を記憶装置から呼出し、４回目の短絡時間Ｔ′ａ４に設定し、ステップＳ２４１に進む。   Next, returning to step S205, if the number of short circuits M in the previous half cycle is 3, the process proceeds to step S240 to increase the number of short circuits by 1 to 4 times, and the fourth time in the case of 4 short circuits. The lower limit value Tl44 of the short circuit time is called from the storage device, set to the fourth short circuit time T'a4, and the process proceeds to step S241.

ステップＳ２４１では、４回目の短絡時間Ｔ′ａ４を以降のステップで設定される１回目〜３回目までの短絡時間の演算の中で、前の半周期での１回目〜３回目の短絡時間から案分比例で減ずべき時間の合計値である案分残時間Ｔｒ４として演算し、ステップＳ２４２に進む。この場合、案分残時間Ｔｒ４は上記で設定した４回目の短絡時間Ｔ′ａ４に等しい。   In step S241, the fourth short-circuit time T′a4 is calculated from the first to third short-circuit times in the previous half cycle in the calculation of the first to third short-circuit times set in the subsequent steps. A prorated portion remaining time Tr4, which is a total value of the time that should be reduced in proportion to the prorated portion, is calculated, and the process proceeds to step S242. In this case, the probable remaining time Tr4 is equal to the fourth short-circuit time T′a4 set above.

ステップＳ２４２以降は前述した通りに制御が進行し、ステップＳ２６５で短絡回数増加処理が終了する。   After step S242, the control proceeds as described above, and the short circuit number increasing process ends in step S265.

また、ステップＳ２０５に戻り、前の半周期での短絡回数Ｍが３より小さい場合は、ステップＳ２０８に進み、更に、短絡回数Ｍが１より大きい場合、つまりＭ＝２の場合には、短絡回数を１回増やして３回にするべく、ステップＳ２５０に進み、３回短絡の場合の３回目の短絡時間の下限値Ｔｌ３３を記憶装置から呼出し、３回目の短絡時間Ｔ′ａ３に設定し、ステップＳ２５１に進む。   Returning to step S205, if the number M of short circuits in the previous half cycle is smaller than 3, the process proceeds to step S208. Further, if the number M of short circuits is greater than 1, that is, if M = 2, the number of short circuits. The process proceeds to step S250 in order to increase the value by 1 to 3 times, and the lower limit value Tl33 of the third short-circuit time in the case of the third short-circuit is called from the storage device and set to the third short-circuit time T'a3. The process proceeds to S251.

ステップＳ２５１では、３回目の短絡時間Ｔ′ａ３を以降のステップで設定される１回目〜２回目までの短絡時間の演算の中で、前の半周期での１回目〜２回目の短絡時間から案分比例で減ずべき時間の合計値である案分残時間Ｔｒ３として演算し、ステップＳ２５２に進む。この場合、案分残時間Ｔｒ３は上記で設定した４回目の短絡時間Ｔ′ａ３に等しい。   In step S251, the third short-circuit time T′a3 is calculated from the first and second short-circuit times in the previous half cycle in the calculation of the first to second short-circuit times set in the subsequent steps. Calculation is made as a promising remaining time Tr3 which is the total value of the time to be reduced in proportion to prorated, and the process proceeds to step S252. In this case, the promising remaining time Tr3 is equal to the fourth short-circuiting time T′a3 set above.

ステップＳ２５２以降は前述した通りに制御が進行し、ステップＳ２６５で短絡回数増加処理が終了する。   After step S252, the control proceeds as described above, and the short circuit number increasing process ends in step S265.

次に、ステップＳ２０８に戻り、前の半周期での短絡回数Ｍが１以下の場合は、ステップＳ２６０に進み、２回短絡の場合の２回目の短絡時間の下限値Ｔｌ２２を記憶装置から呼出し、２回目の短絡時間Ｔ′ａ２に設定し、ステップＳ２６１に進む。   Next, returning to step S208, if the number of short circuits M in the previous half cycle is 1 or less, the process proceeds to step S260, and the lower limit value Tl22 of the second short circuit time in the case of the second short circuit is called from the storage device. The second short-circuit time T′a2 is set, and the process proceeds to step S261.

ステップＳ２６１で、２回短絡の場合の１回目の短絡時間の下限値Ｔｌ２１を記憶装置から呼出し、１回目の短絡時間Ｔ′ａ１に設定し、ステップＳ２６５に進み短絡回数増加処理が終了する。   In step S261, the lower limit value Tl21 of the first short-circuit time in the case of two short-circuits is retrieved from the storage device, set to the first short-circuit time T'a1, and the process proceeds to step S265, where the short-circuit number increasing process ends.

このように、実施例の直流電源装置は、前記スイッチング手段の短絡回数をＭ回からＭ＋１回に増加させる時に、短絡回数増加後のＭ回目までの短絡時間の合計値を、短絡回数増加前の短絡時間の合計値より、減少させる。   Thus, when the DC power supply device of the embodiment increases the number of short circuits of the switching means from M times to M + 1 times, the total value of the short circuit time up to the Mth time after the increase in the number of short circuits is calculated. Decrease from the total value of short circuit time.

一般に、短絡時間を長くすると得られる直流電圧が上昇し、短絡時間を短くすると得られる直流電圧が下降する。また、短絡時間を数回に分けて短絡する場合も、単純に短絡を追加すると得られる直流電圧が上昇し、単純に短絡を削減すると得られる直流電圧が下降することが知られている。   In general, when the short circuit time is lengthened, the DC voltage obtained increases, and when the short circuit time is shortened, the DC voltage obtained decreases. Also, when short-circuiting is performed by dividing the short-circuit time into several times, it is known that the DC voltage obtained by simply adding a short circuit increases, and the DC voltage obtained by simply reducing the short-circuit decreases.

負荷を駆動する場合、その電源となる直流電圧が変動することは、負荷の駆動状態も変動し、負荷となっている機器の運転が安定状態から外れることになり、負荷となっている機器を安定運転するために、何らかの修正を加えて、負荷の駆動状態を元に戻さなければならず、好ましいことではない。   When driving a load, the fluctuation of the DC voltage that is the power source also changes the driving state of the load, which means that the operation of the load device is out of the stable state. In order to perform stable operation, some correction must be made to restore the driving state of the load, which is not preferable.

実施例の直流電源装置では、短絡回数をｎからｎ＋１に増やす場合に、単純に短絡回数を増やすのではなく、直流電圧がほぼ同じになるように、短絡回数を増やした後のｎ回までの短絡時間の合計を、短絡回数を増やす前のｎ回までの短絡時間の合計より短くする。これにより、短絡回数を増やした後のｎ回までの短絡により得られる直流電圧は下降し、ｎ＋１回目の短絡でこの下降した分の直流電圧分を取戻し、全体として、短絡回数を増やす前の直流電圧とほぼ等しい直流電圧を得ることができる。   In the direct current power supply device of the embodiment, when the number of short circuits is increased from n to n + 1, the number of short circuits is not simply increased, but the number of short circuits is increased to n times so that the DC voltage is substantially the same. The total short circuit time is made shorter than the total short circuit time up to n times before increasing the number of short circuits. As a result, the DC voltage obtained by the short-circuiting up to n times after increasing the number of short-circuits decreases, and the DC voltage corresponding to the decreased DC voltage is recovered at the (n + 1) th short-circuit, and as a whole, the DC voltage before increasing the number of short-circuits A DC voltage substantially equal to the voltage can be obtained.

このため、電源高調波電流の抑制や力率の改善のために、短絡回数を増しても、直流電圧がほとんど変化せず、負荷となる機器の安定した運転を確保できる直流電源装置を提供することができる。   For this reason, in order to suppress the power harmonic current and improve the power factor, there is provided a DC power supply device that can ensure stable operation of a load device, with the DC voltage hardly changing even if the number of short circuits is increased. be able to.

また、実施例の直流電源装置は、前記スイッチング手段の短絡回数をＭ回からＭ＋１回に増加させる時に、Ｍ＋１回目までの短絡時間の合計値を、短絡回数増加前のＭ回目までの短絡時間の合計値と等しくする。   In addition, when the DC power supply device of the embodiment increases the number of short-circuits of the switching means from M times to M + 1 times, the total value of the short-circuit times up to the M + 1-th time is calculated as the short-circuit time up to the M-th before the increase in the number of short-circuits. Equal to the total value.

一般に、短絡時間を数回に分けて、短絡する場合、短絡時間の合計が同じであれば得られる直流電圧はほぼ一定であることが知られている。   In general, when short-circuiting is performed by dividing the short-circuit time into several times, it is known that the DC voltage obtained is substantially constant if the total short-circuit time is the same.

実施例の直流電源装置では、短絡回数を増やした場合、短絡時間の合計が同じになるようにする。これにより、短絡回数を増やす前後の短絡時間の合計が等しくなり、得られる直流電圧をほぼ一定に維持することができる。   In the DC power supply device of the embodiment, when the number of short circuits is increased, the total short circuit time is made the same. Thereby, the sum total of the short circuit time before and behind increasing the frequency | count of a short circuit becomes equal, and the obtained DC voltage can be maintained substantially constant.

このため、電源高調波電流の抑制や力率の改善のために、短絡回数を増しても、直流電圧がほとんど変化せず、負荷となる機器の安定した運転を確保できる直流電源装置を提供することができる。   For this reason, in order to suppress the power harmonic current and improve the power factor, there is provided a DC power supply device that can ensure stable operation of a load device, with the DC voltage hardly changing even if the number of short circuits is increased. be able to.

次に、ステップＳ５０の短絡回数減少処理について図１０を用いて説明する。図１０は短絡回数制御部の短絡回数減少処理フロー要部である。   Next, the short circuit frequency reduction process in step S50 will be described with reference to FIG. FIG. 10 shows a main part of the short circuit number reduction processing flow of the short circuit number control unit.

短絡回数減少処理をステップＳ３０１で開始し、ステップＳ３０２で前の半周期の実短絡回数Ｍを調べ、Ｍ＝６つまり、前の半周期の短絡回数が６回である場合は、短絡回数を１回減らして５回にするべく、ステップＳ３２１に進む。この場合、前の半周期での６回の短絡から、単純に６回目の短絡を除去すると直流出力電圧Ｖｄが下降し過ぎ、駆動している負荷に悪影響を及ぼす恐れがあり、予期せぬコストアップにつながる。   The short circuit number reduction process is started in step S301. In step S302, the actual short circuit number M in the previous half cycle is checked. If M = 6, that is, if the short circuit number in the previous half cycle is 6, the short circuit number is set to 1. In order to reduce the number of times to 5 times, the process proceeds to step S321. In this case, if the sixth short-circuit is simply removed from the six short-circuits in the previous half cycle, the DC output voltage Vd will drop too much, which may adversely affect the driving load. Leading up.

この現象を回避するためには、短絡回数を減らしても、直流出力電圧が急変しないように、削減した短絡回以外の短絡回の短絡時間を減少させることが効果的である。実施例では、削減した短絡回以外の短絡回の短絡時間を増し、全体として、短絡を削減する前と後で合計の短絡時間がほぼ等しくなるようにした。これにより、短絡の削減の前後で直流出力電圧の変化は小さくなり、負荷に与える影響も軽微なものとすることができた。   In order to avoid this phenomenon, it is effective to reduce the short-circuit time of the short-circuit times other than the reduced short-circuit times so that the DC output voltage does not change suddenly even if the number of short-circuits is reduced. In the example, the short-circuit time of the short-circuit times other than the reduced short-circuit times was increased so that the total short-circuit time was substantially equal before and after the short-circuit reduction as a whole. As a result, the change in the DC output voltage before and after the reduction of the short circuit was reduced, and the influence on the load could be minimized.

更に実施例では、削減した短絡回以外の短絡回の短絡時間を前の半周期での各回の短絡時間に比例させて増加させることで、短絡の削減の前後で直流出力電圧は勿論のこと、力率、電源高調波電流も急変しなくなって、連続的な変化に近くなるので、接続されている負荷の制御に短絡回数の変化に伴う特殊な制御の必要性が乏しくなり必要な短絡の削減を心置きなく行え、製品の開発スピードをアップさせることができる。   Further, in the embodiment, by increasing the short-circuit time of the short-circuit times other than the reduced short-circuit times in proportion to the short-circuit time of each time in the previous half cycle, the DC output voltage is of course before and after the reduction of the short-circuit, Since the power factor and power supply harmonic current do not change suddenly and become close to a continuous change, the need for special control associated with the change in the number of shorts in the control of the connected load is reduced, reducing the number of necessary shorts. Can increase the speed of product development.

ステップＳ３２１では、前の半周期の６回目の短絡時間Ｔａ６を前の半周期の１〜５回目の短絡時間に各々の短絡時間に案分比例して加算する時間の合計値として案分残時間Ｔｒ６に設定し、ステップＳ３２２に進み、次式により今度の半周期の５回目の短絡時間Ｔ′ａ５を演算し、設定する。   In step S321, the probable remaining time as a total value of adding the sixth short-circuit time Ta6 in the previous half cycle proportionally to each short-circuit time to the first to fifth short-circuit times in the previous half cycle. In step S322, the fifth short-circuit time T'a5 of the next half cycle is calculated and set by the following equation.

Figure 0005481165
Figure 0005481165

次に、ステップＳ３２３に進み、設定したＴ′ａ５を記憶装置から呼出した５回短絡の５回目の短絡時間上限値Ｔｕ５５と比較し、設定した短絡時間Ｔ′ａ５が記憶装置から呼び出した短絡時間上限値Ｔｕ５５以下の場合は、設定を有効としてステップＳ３２８に進み、設定した短絡時間Ｔ′ａ５が記憶装置から呼び出した短絡時間上限値Ｔｕ５５より大きい場合は、ステップＳ３２５に進む。   Next, proceeding to step S323, the set T'a5 is compared with the fifth short-circuit time upper limit value Tu55 of the fifth short-circuit called from the storage device, and the set short-circuit time T'a5 is called the short-circuit time called from the storage device. If it is less than or equal to the upper limit value Tu55, the setting is validated and the process proceeds to step S328. If the set short circuit time T'a5 is greater than the short circuit time upper limit value Tu55 called from the storage device, the process proceeds to step S325.

ステップＳ３２５では、設定した短絡時間Ｔ′ａ５を破棄し、記憶装置から呼び出した短絡時間上限値Ｔｕ５５を今度の半周期の５回目の短絡時間Ｔ′ａ５として再設定し、ステップＳ３２８に進む。ステップＳ３２８では案分残時間Ｔｒ６から５回目の短絡時間の設定での修正量Ｔ′ａ５−Ｔａ５を差引いた案分残時間Ｔｒ５を次の式により演算する。   In step S325, the set short circuit time T'a5 is discarded, and the short circuit time upper limit value Tu55 called from the storage device is reset as the fifth short circuit time T'a5 of the next half cycle, and the process proceeds to step S328. In step S328, the promising remaining time Tr5 obtained by subtracting the correction amount T′a5-Ta5 in the setting of the fifth short-circuiting time from the promising remaining time Tr6 is calculated by the following equation.

Figure 0005481165
Figure 0005481165

次に、ステップＳ３３２に進み、上記の案分残時間Ｔｒ５を１〜４回目の短絡時間に各々の短絡時間に案分比例して加算すべく、次式により今度の半周期の４回目の短絡時間Ｔ′ａ４を演算し、設定する。   Next, the process proceeds to step S332, and in order to add the probable remaining time Tr5 to the first short circuit time to the fourth short circuit time in proportion to each short circuit time, the following short circuit is performed for the fourth short circuit in the next half cycle. Time T'a4 is calculated and set.

Figure 0005481165
Figure 0005481165

次に、ステップＳ３３３に進み、設定したＴ′ａ４を記憶装置から呼出したＭｍ回短絡の４回目の短絡時間上限値ＴｕＭｍ４と比較する。ここで、Ｍｍは今度の半周期での短絡回数で有り、前の半周期での短絡回数が６であるので、これから短絡回数を１回減らしてＭｍは５となる。従って、具体的にステップＳ３３３を読み直すと次のようになる。   In step S333, the set T'a4 is compared with the fourth short-circuiting time upper limit TuMm4 of the Mm short-circuit called from the storage device. Here, Mm is the number of short circuits in the next half cycle, and the number of short circuits in the previous half cycle is 6. Therefore, the number of short circuits is reduced by 1 and Mm becomes 5. Therefore, when step S333 is specifically re-read, the result is as follows.

設定したＴ′ａ４を記憶装置から呼出した５回短絡の４回目の短絡時間上限値Ｔｕ５４と比較し、設定した短絡時間Ｔ′ａ４が記憶装置から呼び出した短絡時間上限値Ｔｕ５４以下の場合は、設定を有効としてステップＳ３３８に進む。設定した短絡時間Ｔ′ａ４が記憶装置から呼び出した短絡時間上限値Ｔｕ５４より大きい場合は、ステップＳ３３５に進む。   The set T′a4 is compared with the fourth short-circuit time upper limit value Tu54 of the fifth short-circuit called from the storage device, and when the set short-circuit time T′a4 is equal to or shorter than the short-circuit time upper limit value Tu54 called from the storage device, The setting is validated and the process proceeds to step S338. If the set short-circuit time T′a4 is greater than the short-circuit time upper limit Tu54 called from the storage device, the process proceeds to step S335.

ステップＳ３３５では、設定した短絡時間Ｔ′ａ４を破棄し、記憶装置から呼び出した短絡時間上限値Ｔｕ５４を今度の半周期の４回目の短絡時間Ｔ′ａ４として再設定し、ステップＳ３３８に進む。ステップＳ３３８では、案分残時間Ｔｒ５から４回目の短絡時間の設定での修正量Ｔ′ａ４−Ｔａ４を差引いた案分残時間Ｔｒ４を次の式により演算する。   In step S335, the set short-circuit time T'a4 is discarded, and the short-circuit time upper limit value Tu54 called from the storage device is reset as the fourth short-circuit time T'a4 in the next half cycle, and the process proceeds to step S338. In step S338, the probable remaining time Tr4 obtained by subtracting the correction amount T′a4-Ta4 in the setting of the fourth short circuit time from the probable remaining time Tr5 is calculated by the following equation.

Figure 0005481165
Figure 0005481165

以下、同様に（１４），（１５）式を使用し、ステップＳ３４２〜Ｓ３４８で３回目の短絡時間Ｔ′ａ３、案分残時間Ｔｒ３を演算，設定し、（１６），（１７）式を使用し、ステップＳ３５２〜Ｓ３５８で２回目の短絡時間Ｔ′ａ２、案分残時間Ｔｒ２を演算，設定し、ステップＳ３６２で（１８）式を使用して今度の半周期の１回目の短絡時間Ｔ′ａ１を演算，設定して、ステップＳ３６５に進んで短絡回数減少処理を終了する。   Similarly, using the equations (14) and (15), the third short circuit time T′a3 and the probable remaining time Tr3 are calculated and set in steps S342 to S348, and the equations (16) and (17) are calculated. In step S352 to S358, the second short-circuit time T'a2 and the probable remaining time Tr2 are calculated and set. In step S362, the first short-circuit time T of the next half cycle is calculated using the equation (18). 'A1 is calculated and set, and the process proceeds to step S365 to end the short circuit number reduction process.

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

Figure 0005481165
Figure 0005481165

ステップＳ３０２に戻り、前の半周期での短絡回数Ｍが５回の場合は、短絡回数を１回減らして４回にするべく、ステップＳ３３１に進み、前の半周期での５回目の短絡時間Ｔ′ａ５を以降のステップで設定される１回目〜４回目までの短絡時間の演算の中で、前の半周期での１回目〜４回目の短絡時間に案分比例で加えるべき時間の合計値である案分残時間Ｔｒ５として演算し、ステップＳ３３２に進む。   Returning to step S302, if the number of short circuits M in the previous half cycle is 5, the process proceeds to step S331 to reduce the number of short circuits by 1 to 4 times, and the fifth short circuit time in the previous half cycle Total of time that should be added proportionally to the first to fourth short-circuit time in the previous half cycle in the calculation of T'a5 from the first to fourth short-circuit time set in the subsequent steps The value is calculated as the pro-rata remaining time Tr5, and the process proceeds to step S332.

ステップＳ３３２以降は前述した通りに制御が進行し、ステップＳ３６５で短絡回数減少処理が終了する。   After step S332, the control proceeds as described above, and the short circuit number reduction process ends in step S365.

再度、ステップＳ３０２に戻り、前の半周期での短絡回数Ｍが５回より小さい場合は、ステップＳ３０５に進み、更に、短絡回数Ｍが３より大きい場合、つまりＭ＝４の場合には、短絡回数を１回減らして３回にするべく、ステップＳ３４１に進み、前の半周期での４回目の短絡時間Ｔ′ａ４を以降のステップで設定される１回目〜３回目までの短絡時間の演算の中で、前の半周期での１回目〜３回目の短絡時間に案分比例で加えるべき時間の合計値である案分残時間Ｔｒ４として演算し、ステップＳ３４２に進む。   Returning to step S302 again, if the number of short circuits M in the previous half cycle is less than 5, the process proceeds to step S305. If the number of short circuits M is greater than 3, that is, if M = 4, the short circuit is performed. In order to reduce the number of times by 1 to 3 times, the process proceeds to step S341, and the fourth short-circuit time T′a4 in the previous half cycle is calculated as the first to third short-circuit times set in the subsequent steps. , The prorated remaining time Tr4 that is the total value of the time that should be added proportionally to the first to third short-circuiting times in the previous half cycle is calculated, and the process proceeds to step S342.

ステップＳ３４２以降は前述した通りに制御が進行し、ステップＳ３６５で短絡回数減少処理が終了する。   After step S342, the control proceeds as described above, and the short circuit number reduction process ends in step S365.

次に、ステップＳ３０５に戻り、前の半周期での短絡回数Ｍが３である場合、短絡回数を１回減らして２回にするべく、ステップＳ３５１に進み、前の半周期での３回目の短絡時間Ｔ′ａ３を以降のステップで設定される１回目〜２回目までの短絡時間の演算の中で、前の半周期での１回目〜２回目の短絡時間に案分比例で加えるべき時間の合計値である案分残時間Ｔｒ３として演算し、ステップＳ３５２に進む。   Next, returning to step S305, if the number of short circuits M in the previous half cycle is 3, the process proceeds to step S351 to reduce the number of short circuits by 1 to 2 times, and the third time in the previous half cycle. The time that should be added proportionally to the first and second short circuit times in the previous half cycle in the calculation of the short circuit time T'a3 in the first and second short circuit times set in the following steps Is calculated as the promising remaining time Tr3, which is the total value, and the process proceeds to step S352.

ステップＳ３５２以降は前述した通りに制御が進行し、ステップＳ３６５で短絡回数減少処理が終了する。   After step S352, the control proceeds as described above, and the short circuit number reduction process ends in step S365.

また、ステップＳ３０５に戻り、前の半周期での短絡回数Ｍが３より小さい場合は、ステップＳ３０８に進み、更に、短絡回数Ｍが１より大きい場合、つまりＭ＝２の場合には、ステップＳ３１０に進み、図７のステップＳ３５と同様に前の半周期でのＭ回の短絡時間合計ΣＴａｎを短絡回数Ｍの短絡時間下限値合計ΣＴｌＭｎと比較する。   Returning to step S305, if the number of short circuits M in the previous half cycle is less than 3, the process proceeds to step S308. If the number of short circuits M is greater than 1, that is, if M = 2, step S310 is performed. Then, as in step S35 of FIG. 7, the M short-circuit time total ΣTan in the previous half cycle is compared with the short-circuit time lower limit total ΣTlMn of the number of short-circuits M.

ステップＳ３１０で短絡時間合計ΣＴａｎが短絡時間下限値合計ΣＴｌＭｎ以下である場合は、２回の短絡回数ではこれ以下に短絡時間を短くすることができない上、これより少ない短絡回数は設定されていないので、ステップＳ３６１に進み、短絡制御の設定を解除し、短絡を行わないようにして、ステップＳ３６５で短絡回数減少処理を終了する。   If the total short circuit time ΣTan is less than or equal to the total short circuit time lower limit value ΣTlMn in step S310, the short circuit time cannot be shortened to less than two short circuit times, and the number of short circuits less than this is not set. Then, the process proceeds to step S361, the setting of the short circuit control is canceled, the short circuit is not performed, and the short circuit number reduction process is terminated in step S365.

ステップＳ３１０で短絡時間合計ΣＴａｎが短絡時間下限値合計ΣＴｌＭｎより大きい場合は、現行の２回の短絡回数で短絡時間を短くする余地があるので、短絡時間が下限値に達していない回の短絡時間を短くするようステップＳ３１５に進み、前述と同様にＰＩ制御を行い、今回の短絡時間を決定し、ステップＳ３６５で短絡回数減少処理を終了する。   If the short-circuit time total ΣTan is larger than the short-circuit time lower limit total ΣTlMn in step S310, there is room for shortening the short-circuit time with the current two short-circuit times. In step S315, PI control is performed in the same manner as described above, the current short-circuit time is determined, and the short-circuit number reduction process is terminated in step S365.

次に、ステップＳ３０８に戻り、前の半周期での短絡回数Ｍが１以下の場合は、ステップＳ３６１に進み、前述と同様に短絡の設定を解除し、ステップＳ３６５で短絡回数減少処理を終了する。   Next, returning to step S308, if the number of short circuits M in the previous half cycle is 1 or less, the process proceeds to step S361, the setting of the short circuit is canceled in the same manner as described above, and the short circuit number reduction process is terminated in step S365. .

このように、実施例の直流電源装置は、前記スイッチング手段の短絡回数をＭ回からＭ−１回に減少させる時に、短絡回数減少後の短絡時間の合計値を、短絡回数減少前のＭ−１回目までの短絡時間の合計値より、増加させる。   Thus, when the DC power supply device of the embodiment decreases the number of short circuits of the switching means from M times to M−1 times, the total value of the short circuit time after the decrease of the number of short circuits is calculated as M− before the decrease of the number of short circuits. Increase from the total value of short-circuiting time until the first time.

これにより、短絡回数をｎからｎ−１に減らす場合に、単純に短絡回数を減らすのではなく、直流電圧がほぼ同じになるように、短絡回数を減らした後の短絡時間の合計（ｎ−１回までの短絡時間の合計）を、短絡回数を減らす前のｎ−１回までの短絡時間の合計より長くする。   As a result, when the number of short circuits is reduced from n to n−1, the total number of short circuits after the number of short circuits is reduced (n−) so that the DC voltage is substantially the same, instead of simply reducing the number of short circuits. The sum of the short-circuit times up to once) is made longer than the sum of the short-circuit times up to n-1 times before the number of short-circuits is reduced.

これにより、短絡回数を減らした後の短絡（ｎ−１回までの短絡）により得られる直流電圧は、短絡回数を減らす前のｎ−１回目までの短絡で得られた直流電圧より上昇し、短絡回数を減らす前のｎ回目の短絡が無くなったことによる直流電圧の下降分を補い、全体として、短絡回数を減らす前の直流電圧とほぼ等しい直流電圧を得ることができる。   Thereby, the DC voltage obtained by the short circuit (short circuit up to n-1 times) after reducing the number of short circuits is higher than the DC voltage obtained by the short circuit up to n-1 time before reducing the number of short circuits, As a whole, it is possible to obtain a DC voltage substantially equal to the DC voltage before reducing the number of short circuits by compensating for the decrease in DC voltage due to the absence of the n-th short circuit before reducing the number of short circuits.

このため、電源高調波電流の抑制や力率の改善のために、短絡回数を増しても、直流電圧がほとんど変化せず、負荷となる機器の安定した運転を確保できる直流電源装置を提供することができる。   For this reason, in order to suppress the power harmonic current and improve the power factor, there is provided a DC power supply device that can ensure stable operation of a load device, with the DC voltage hardly changing even if the number of short circuits is increased. be able to.

また、実施例の直流電源装置は、前記スイッチング手段の短絡回数をＭ回からＭ−１回に減少させる時に、短絡回数減少後の短絡時間の合計値を、短絡回数減少前のＭ回目までの短絡時間の合計値と等しくする。   In addition, when the DC power supply device of the embodiment decreases the number of short circuits of the switching means from M times to M−1 times, the total value of the short circuit time after the number of short circuits is reduced to the Mth before the number of short circuits is decreased. Make it equal to the total value of the short circuit time.

これにより、短絡回数を減らした場合、短絡時間の合計が同じになるようにする。これにより、短絡回数を減らす前後の短絡時間の合計が等しくなり、得られる直流電圧をほぼ一定に維持することができる。   Thus, when the number of short circuits is reduced, the total short circuit time is made the same. Thereby, the sum total of the short circuit time before and after reducing the frequency | count of a short circuit becomes equal, and the direct-current voltage obtained can be maintained substantially constant.

このため、電源高調波電流の抑制や力率の改善のために、短絡回数を増しても、直流電圧がほとんど変化せず、負荷となる機器の安定した運転を確保できる直流電源装置を提供することができる。   For this reason, in order to suppress the power harmonic current and improve the power factor, there is provided a DC power supply device that can ensure stable operation of a load device, with the DC voltage hardly changing even if the number of short circuits is increased. be able to.

図１１，図１２を用いて説明する。図１１は電源装置の回路構成を示すブロック図である。図１２は入力電流と目標直流電圧の関係を示す図である。   This will be described with reference to FIGS. FIG. 11 is a block diagram showing a circuit configuration of the power supply apparatus. FIG. 12 is a diagram showing the relationship between the input current and the target DC voltage.

図１１は図１の周辺情報検出手段１１８を入力電流検出手段１１２にしたものである。入力電流により目標電圧を図１２のように変更することで、好適な直流電源装置とすることができる。   FIG. 11 shows the peripheral information detection means 118 of FIG. By changing the target voltage according to the input current as shown in FIG. 12, a suitable DC power supply device can be obtained.

このように、実施例の直流電源装置は、前記交流電源からの入力電流を検出する入力電流検出手段を更に備え、前記スイッチング制御手段は前記スイッチング手段の２〜６回までの短絡回数を前記比の値と前記入力電流検出手段で検出した入力電流に応じて定める。   Thus, the direct-current power supply device of the embodiment further includes input current detection means for detecting an input current from the alternating-current power supply, and the switching control means determines the number of short-circuits of the switching means up to 2 to 6 times. And the input current detected by the input current detecting means.

これにより、前記比の値と入力電流の大小に応じて、短絡回数を適切の定めることができるので、電源高調波電流の規制を満足しつつ、力率を改善し、高効率な運転が可能となる。この場合、最も簡単な短絡回数の定め方としては、入力電流を目標直流電圧に換算し、電源電圧との比の値を求め比の値に応じて前述の方法により短絡回数を定める方法がある。   As a result, the number of short-circuits can be appropriately determined according to the ratio value and the input current, so that the power factor can be improved and high-efficiency operation can be achieved while satisfying the regulation of the power supply harmonic current. It becomes. In this case, as the simplest method of determining the number of short circuits, there is a method of converting the input current to a target DC voltage, obtaining a value of the ratio with the power supply voltage, and determining the number of short circuits by the above-described method according to the value of the ratio. .

入力電流を目標直流電圧に換算する方法としては、例えば図２３に示すように、入力電流を機器が持つ特性に従って、適切な数値で区分し、各区分点での目標直流電圧を実験などで確認し、その中間では直線補間，階段状の変化，曲線補間などの方法で目標直流電圧を定める方法などを採用すれば良い。このようにすることで、入力電流の全域で目標直流電圧を簡単に設定でき、電源高調波電流の規制を満足しつつ、力率を改善し、高効率な運転が可能となる。   As a method for converting the input current to the target DC voltage, for example, as shown in FIG. 23, the input current is classified by an appropriate numerical value in accordance with the characteristics of the device, and the target DC voltage at each division point is confirmed by an experiment or the like. In the middle, a method of determining the target DC voltage by a method such as linear interpolation, step-like change, or curve interpolation may be adopted. In this way, the target DC voltage can be easily set over the entire input current, and the power factor can be improved and highly efficient operation can be achieved while satisfying the regulation of the power supply harmonic current.

このため、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する直流電源装置を提供することができる。   For this reason, a DC power supply device that realizes high efficiency and appropriate power factor at low load while realizing high power factor and appropriate efficiency at high load while suppressing power supply harmonic current with an inexpensive circuit configuration is provided. be able to.

図１３は図１の周辺情報検出手段１１８を負荷量検出手段１１３にしたものである。負荷量に応じて目標電圧を図１４のように変更することで、好適な直流電源装置とすることができる。   FIG. 13 is a diagram in which the peripheral information detection means 118 of FIG. By changing the target voltage as shown in FIG. 14 according to the load amount, a suitable DC power supply device can be obtained.

このように、実施例の直流電源装置は、前記直流電力に接続された負荷量を検出する負荷量検出手段を更に備え、前記スイッチング制御手段は前記スイッチング手段の２〜６回までの短絡回数を前記比の値と前記負荷量検出手段で検出された負荷量に応じて定める。   As described above, the DC power supply device according to the embodiment further includes load amount detection means for detecting the load amount connected to the DC power, and the switching control means determines the number of short-circuits of the switching means up to 2 to 6 times. It is determined according to the ratio value and the load amount detected by the load amount detecting means.

これにより、前記比の値と負荷量の大小に応じて、短絡回数を適切の定めることができるので、電源高調波電流の規制を満足しつつ、力率を改善し、高効率な運転が可能となる。この場合、最も簡単な短絡回数の定め方としては、負荷量を目標直流電圧に換算し、電源電圧との比の値を求め比の値に応じて前述の方法により短絡回数を定める方法がある。   As a result, the number of short-circuits can be determined appropriately according to the ratio value and the amount of load, so that power factor can be improved and high-efficiency operation can be achieved while satisfying the regulation of power supply harmonic current. It becomes. In this case, as the simplest method of determining the number of short circuits, there is a method of converting the load amount to a target DC voltage, obtaining a value of the ratio with the power supply voltage, and determining the number of short circuits by the method described above according to the ratio value. .

負荷量を目標直流電圧に換算する方法としては、例えば図２３に示すようなグラフに従って、前述のような方法で目標直流電圧を定めれば良い。このようにすることで、負荷量の全域で目標直流電圧を簡単に設定でき、電源高調波電流の規制を満足しつつ、力率を改善し、高効率な運転が可能となる。   As a method of converting the load amount into the target DC voltage, the target DC voltage may be determined by the method as described above, for example, according to a graph as shown in FIG. In this way, the target DC voltage can be easily set over the entire load amount, and the power factor can be improved and highly efficient operation can be performed while satisfying the regulation of the power supply harmonic current.

このため、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する直流電源装置を提供することができる。   For this reason, a DC power supply device that realizes high efficiency and appropriate power factor at low load while realizing high power factor and appropriate efficiency at high load while suppressing power supply harmonic current with an inexpensive circuit configuration is provided. be able to.

なお、負荷量としては、制御の目的に応じて例えば、得られる直流電圧，直流電流，負荷となる機器の各部の温度（例えば、冷凍サイクルの温度），負荷となる機器が置かれる環境の温度（例えば、室内外の温度）などの種々の量を使用することができる。   Note that the load amount includes, for example, the obtained DC voltage, DC current, the temperature of each part of the equipment that becomes the load (for example, the temperature of the refrigeration cycle), and the temperature of the environment in which the equipment that becomes the load is placed. Various amounts can be used such as (eg indoor and outdoor temperature).

図１５，図１６を用いて説明する。図１５はモータ回転数と目標直流電圧の関係を示す図である。図１６は実施例３の電源装置の回路構成を示すブロック図である。   This will be described with reference to FIGS. 15 and 16. FIG. 15 is a diagram showing the relationship between the motor speed and the target DC voltage. FIG. 16 is a block diagram illustrating a circuit configuration of the power supply device according to the third embodiment.

図１５は図１の負荷１０４ｂをモータ１１４とし、周辺情報検出手段１１８をモータ印加電圧検出手段１１５としたものである。モータ印加電圧に応じて目標電圧を図１６のように変更することで、好適な直流電源装置とすることができる。   FIG. 15 shows the load 104b of FIG. 1 as the motor 114 and the peripheral information detection means 118 as the motor applied voltage detection means 115. By changing the target voltage as shown in FIG. 16 according to the motor applied voltage, a suitable DC power supply device can be obtained.

このように、実施例の直流電源装置は、前記直流電力に接続される負荷をモータとし、前記負荷量を前記モータへの印加電圧とし、前記負荷量検出手段としてモータへの印加電圧を検出するモータ印加電圧検出手段を備え、前記スイッチング制御手段は前記スイッチング手段の２〜６回までの短絡回数を前記比の値と前記モータ印加電圧検出手段で検出されたモータ印加電圧に応じて定める。   As described above, in the DC power supply device of the embodiment, the load connected to the DC power is a motor, the load amount is an applied voltage to the motor, and the applied voltage to the motor is detected as the load amount detecting means. Motor application voltage detection means is provided, and the switching control means determines the number of short circuits from 2 to 6 times of the switching means according to the value of the ratio and the motor application voltage detected by the motor application voltage detection means.

これにより、前記比の値とモータ印加電圧の高低に応じて、短絡回数を適切の定めることができるので、電源高調波電流の規制を満足しつつ、力率を改善し、高効率な運転が可能となる。この場合、最も簡単な短絡回数の定め方としては、モータ印加電圧を目標直流電圧に換算し、電源電圧との比の値を求め比の値に応じて前述の方法により短絡回数を定める方法がある。   As a result, the number of short circuits can be appropriately determined according to the value of the ratio and the level of the motor applied voltage, so that the power factor is improved and high-efficiency operation is achieved while satisfying the regulation of the power supply harmonic current. It becomes possible. In this case, the simplest method of determining the number of short circuits is to convert the motor applied voltage to a target DC voltage, determine the value of the ratio with the power supply voltage, and determine the number of short circuits by the above method according to the value of the ratio. is there.

モータ印加電圧を目標直流電圧に換算する方法としては、例えば図２３に示すようなグラフに従って、前述のような方法で目標直流電圧を定めれば良い。このようにすることで、モータ印加電圧の全域で目標直流電圧を簡単に設定でき、電源高調波電流の規制を満足しつつ、力率を改善し、高効率な運転が可能となる。   As a method of converting the motor applied voltage into the target DC voltage, the target DC voltage may be determined by the method as described above, for example, according to a graph as shown in FIG. In this way, the target DC voltage can be easily set over the entire range of the motor applied voltage, and the power factor can be improved and highly efficient operation can be achieved while satisfying the regulation of the power supply harmonic current.

このため、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する直流電源装置を提供することができる。   For this reason, a DC power supply device that realizes high efficiency and appropriate power factor at low load while realizing high power factor and appropriate efficiency at high load while suppressing power supply harmonic current with an inexpensive circuit configuration is provided. be able to.

なお、モータ印加電圧に換えて、インバータ制御手段がＰＷＭ出力部に発する電圧指示値、またはＰＷＭデューティ指示値を用いても同様の効果を得ることができる。   Note that the same effect can be obtained by using a voltage instruction value or a PWM duty instruction value generated by the inverter control means to the PWM output unit instead of the motor applied voltage.

図１７，図１８を用いて説明する。図１７は実施例４の電源装置の回路構成を示すブロック図である。図１８は実施例５の電源装置の回路構成を示すブロック図である。   This will be described with reference to FIGS. FIG. 17 is a block diagram illustrating a circuit configuration of the power supply device according to the fourth embodiment. FIG. 18 is a block diagram illustrating a circuit configuration of the power supply device according to the fifth embodiment.

図１７は図１の負荷１０４ｂをモータ１１４とし、周辺情報検出手段１１８をモータ回転数検出手段１１６としたものである。モータ回転数に応じて目標電圧を図１８のように変更することで、好適な直流電源装置とすることができる。   FIG. 17 shows the load 104b of FIG. 1 as the motor 114 and the peripheral information detection means 118 as the motor rotation speed detection means 116. By changing the target voltage as shown in FIG. 18 according to the motor rotation speed, a suitable DC power supply device can be obtained.

このように、実施例の直流電源装置は、前記直流電力に接続される負荷をモータとし、前記負荷量を前記モータの回転数として、前記負荷量検出手段としてモータの回転数を検出するモータ回転数検出手段を備え、前記スイッチング制御手段は前記スイッチング手段の２〜６回までの短絡回数を前記比の値と前記モータ回転数検出手段で検出されたモータ回転数に応じて定める。   Thus, in the DC power supply device of the embodiment, the load connected to the DC power is a motor, the load amount is the rotation number of the motor, and the rotation amount of the motor is detected as the load amount detection means. The switching control means determines the number of short circuits of the switching means from 2 to 6 times according to the value of the ratio and the motor rotation speed detected by the motor rotation speed detection means.

これにより、前記比の値とモータ回転数の高低に応じて、短絡回数を適切の定めることができるので、電源高調波電流の規制を満足しつつ、力率を改善し、高効率な運転が可能となる。この場合、最も簡単な短絡回数の定め方としては、モータ回転数を目標直流電圧に換算し、電源電圧との比の値を求め比の値に応じて前述の方法により短絡回数を定める方法がある。   As a result, the number of short circuits can be appropriately determined according to the value of the ratio and the motor rotation speed, so that the power factor is improved and the highly efficient operation is achieved while satisfying the regulation of the power supply harmonic current. It becomes possible. In this case, the simplest method of determining the number of short circuits is to convert the motor rotation number to the target DC voltage, determine the ratio with the power supply voltage, and determine the number of short circuits by the above method according to the ratio value. is there.

モータ回転数を目標直流電圧に換算する方法としては、例えば図２３に示すようなグラフに従って、前述のような方法で目標直流電圧を定めれば良い。このようにすることで、モータ回転数の全域で目標直流電圧を簡単に設定でき、電源高調波電流の規制を満足しつつ、力率を改善し、高効率な運転が可能となる。   As a method for converting the motor rotational speed into the target DC voltage, the target DC voltage may be determined by the method as described above, for example, according to a graph as shown in FIG. In this way, the target DC voltage can be easily set over the entire range of the motor rotation speed, and the power factor can be improved and highly efficient operation can be achieved while satisfying the regulation of the power supply harmonic current.

このため、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する直流電源装置を提供することができる。   For this reason, a DC power supply device that realizes high efficiency and appropriate power factor at low load while realizing high power factor and appropriate efficiency at high load while suppressing power supply harmonic current with an inexpensive circuit configuration is provided. be able to.

なお、モータ回転数を換えて、インバータ制御手段がＰＷＭ出力部に発するモータ回転数指示値を用いても同様の効果を得ることができる。   It is to be noted that the same effect can be obtained by changing the motor rotation speed and using the motor rotation speed instruction value that the inverter control means issues to the PWM output section.

以下、実施例６の上述の直流電源装置を用いた空気調和機について図１９を用いて説明する。図１９は実施例６の空気調和機の構成図である。   Hereinafter, an air conditioner using the above-described DC power supply device of Example 6 will be described with reference to FIG. FIG. 19 is a configuration diagram of the air conditioner of the sixth embodiment.

図２７において、符号１で総括的に示すのは空気調和機であり、室内機２と室外機６を接続配管８でつなぎ、室内を空気調和する。室内機２は筐体２１に室内熱交換器，室内送風機，露受皿等を取付け、化粧枠２３で覆い、化粧枠２３の前面に前面パネル２５を取付けた構成になっている。化粧枠２３には室内空気を吸い込む空気吸込み口２７と、温湿度が調和された空気を吹き出す空気吹出し口２９とが上下に設けられている。   In FIG. 27, an air conditioner generally indicated by reference numeral 1 connects the indoor unit 2 and the outdoor unit 6 with a connection pipe 8 to air-condition the room. The indoor unit 2 has a configuration in which an indoor heat exchanger, an indoor blower, a dew tray, and the like are attached to a casing 21, covered with a decorative frame 23, and a front panel 25 is attached to the front surface of the decorative frame 23. The decorative frame 23 is provided with an air inlet 27 for sucking indoor air and an air outlet 29 for blowing air in which temperature and humidity are harmonized.

室内機２は、内部に図示しない電装品ボックスに制御基板を備え、該制御基板にマイコンが設けられる。該マイコンは図示しない室内温度センサー，室内湿度センサー等の各種のセンサーからの信号を受け、リモコン５からの操作信号を受光部３９６で受けると共に、室内送風機等を制御し、且つ、室外機６との通信を司るなど、室内機２を統括して制御する。   The indoor unit 2 includes a control board in an electrical component box (not shown) inside, and a microcomputer is provided on the control board. The microcomputer receives signals from various sensors such as an indoor temperature sensor and an indoor humidity sensor (not shown), receives an operation signal from the remote controller 5 at the light receiving unit 396, controls the indoor fan, and the outdoor unit 6 The overall control of the indoor unit 2 is performed, for example, controlling the communication.

室外機６は、ベース６１に圧縮機，室外熱交換器，室外送風機を搭載し、外筐６２で覆い、配管接続バルブ７８に室内機２からの接続配管８を接続している。   In the outdoor unit 6, a compressor, an outdoor heat exchanger, and an outdoor blower are mounted on a base 61, covered with an outer casing 62, and a connection pipe 8 from the indoor unit 2 is connected to a pipe connection valve 78.

この空気調和機１を運転する時には、電源（図示せず）に接続してリモコン５を操作し、所望の冷房，除湿，暖房等の運転を行う。   When the air conditioner 1 is operated, it is connected to a power source (not shown) and the remote controller 5 is operated to perform desired operations such as cooling, dehumidification, and heating.

冷房等の運転の場合、リモコン５から運転操作の信号がなされると、図示しないマイコンは、リモコン５からの操作信号または自動運転が設定されていれば各種センサからの情報に基づいて冷房等の運転モードを決定する。   In the case of driving such as cooling, when a driving operation signal is made from the remote controller 5, the microcomputer (not shown) performs an operation such as cooling based on the operation signal from the remote controller 5 or information from various sensors if automatic driving is set. Determine the operation mode.

次に、室外機６の制御部（図示せず）に決定した運転モードに応じた運転を指示すると共に、決定した運転モードに従って室内送風機を駆動し、空気吸込部２７から室内熱交換器に室内空気を流通させる。室外機６の制御部は室内機２からの指示に従い、圧縮機，送風モータ，制御弁等を制御し、圧縮機からの冷媒を冷凍サイクルに循環させると共に、室外空気吸込み部から室外熱交換器に室外空気を流通させる。斯くして、周知の冷房等の運転が行われる。   Next, the control unit (not shown) of the outdoor unit 6 is instructed to operate according to the determined operation mode, and the indoor blower is driven according to the determined operation mode, and the indoor heat exchanger is moved from the air suction unit 27 to the indoor heat exchanger. Allow air to circulate. The control unit of the outdoor unit 6 controls a compressor, a blower motor, a control valve, and the like according to an instruction from the indoor unit 2 to circulate refrigerant from the compressor to the refrigeration cycle, and from the outdoor air suction unit to the outdoor heat exchanger Allow outdoor air to flow through. Thus, a known operation such as cooling is performed.

室外機６について図２０〜図２２を用いて更に詳しく説明する。図２０は空気調和機の室外機の内部構造斜視図である。図２１は室外機の天板を外した平面図である。図２２は室外機の前面板を外した正面図である。   The outdoor unit 6 will be described in more detail with reference to FIGS. FIG. 20 is a perspective view of the internal structure of the outdoor unit of the air conditioner. FIG. 21 is a plan view of the outdoor unit with the top plate removed. FIG. 22 is a front view of the outdoor unit with the front plate removed.

外筐６２は前面板６２１，側面板６２３，天板６２２等からなり、室外熱交換器７３に対向する外面に室外空気の吸込み部が設けられ、室外ファン６３１に対向する前面板６２１に自在に空気の流通ができるファングリル６３５が設けられている。室外ファン６３１は室外熱交換器７３が上流側に、ファングリル６３５が下流側になるように回転駆動され、上述のように室外空気を室外熱交換器７３に流通させる。   The outer casing 62 includes a front plate 621, a side plate 623, a top plate 622, and the like. An outdoor air suction portion is provided on the outer surface facing the outdoor heat exchanger 73, and the front plate 621 facing the outdoor fan 631 is freely movable. A fan grill 635 capable of air circulation is provided. The outdoor fan 631 is rotationally driven so that the outdoor heat exchanger 73 is on the upstream side and the fan grill 635 is on the downstream side, and the outdoor air is circulated to the outdoor heat exchanger 73 as described above.

室外熱交換器７３は、室外機６の側面から背面にかけて略Ｌ字状に配設され、できるだけ大きい面積を確保し熱交換能力を高めている。室外ファン６３１も、できるだけ大口径のものが使用されている。室外ファン６３１と圧縮機７５の間には仕切板６１１があって、送風機室６４と機械室６８とを仕切っている。   The outdoor heat exchanger 73 is disposed in a substantially L shape from the side surface to the back surface of the outdoor unit 6, and secures as large an area as possible to enhance the heat exchange capability. The outdoor fan 631 also has a large diameter as much as possible. A partition plate 611 is provided between the outdoor fan 631 and the compressor 75 to partition the blower chamber 64 and the machine chamber 68.

送風機室６４には前述のように室外ファン６３１，室外熱交換器７３が配設されている。機械室６８には、圧縮機７５，アキュムレータ７６，冷媒送り管等が配設されている。圧縮機７５のモータ１１４を駆動する前述のインバータ１０４ａや直流電源装置１００，送風モータ６３３等を駆動する電装部品は製作時やメンテナンス時の取扱を容易にするため電装箱６５に収納されている。   As described above, the fan 631 and the outdoor heat exchanger 73 are disposed in the blower chamber 64. In the machine room 68, a compressor 75, an accumulator 76, a refrigerant feed pipe, and the like are disposed. The electric parts for driving the inverter 104a, the DC power supply device 100, the blower motor 633, and the like for driving the motor 114 of the compressor 75 are housed in the electric box 65 for easy handling during production and maintenance.

しかし、直流電源装置１００のリアクタ１０５は鉄製のコアと銅製の巻線から構成され、その質量が大きいため、電装箱６５に収納せずに送風機室６４に独立して取付けられることが多い。しかし、リアクタ１０５を除外しても電装箱６５に収納される、上記のような電装品は、圧縮機７５，送風モータ６３３等を駆動するので容量が大きく、電装部からの発熱も大きくなり、その冷却を効果的に行う必要がある。   However, the reactor 105 of the DC power supply device 100 is composed of an iron core and a copper winding, and its mass is large, so that it is often attached independently to the blower chamber 64 without being housed in the electrical box 65. However, even if the reactor 105 is excluded, the electrical components as described above, which are stored in the electrical box 65, drive the compressor 75, the blower motor 633, and the like, so that the capacity is large and the heat generated from the electrical components also increases. It is necessary to effectively perform the cooling.

このため、これらの電装品を密集して配置することができず、必然的に電装箱６５の大きさも大きくなって、機械室６８の上部に納まりきらず送風機室６４にはみ出てくる。実施例では、電装箱６５は送風機室６４と機械室６８とに跨って、仕切板６１１の上部に設置した。このように、送風機室６４には電装箱６５の仕切板６１１からはみ出した部分や、リアクタ１０５が置かれる。   For this reason, these electrical components cannot be densely arranged, and the size of the electrical box 65 inevitably increases, so that the electrical components do not fit in the upper part of the machine room 68 and protrude into the blower room 64. In the example, the electrical box 65 was installed on the upper part of the partition plate 611 across the blower chamber 64 and the machine chamber 68. As described above, the portion that protrudes from the partition plate 611 of the electrical box 65 and the reactor 105 are placed in the blower chamber 64.

送風機室６４は比較的広く見えるが、室外ファン６３１の通風を妨げる位置にリアクタ１０５を置くと、送風量の低下や騒音の増大などの負の影響が増し、望ましくない結果になる。このため、電装箱６５の仕切板６１１からはみ出した部分や、リアクタ１０５は室外ファン６３１からなるべく離れた位置、つまり送風機室６４の隅の部分に置かなければならない。   Although the blower chamber 64 appears to be relatively wide, placing the reactor 105 at a position that prevents ventilation of the outdoor fan 631 increases negative effects such as a decrease in the amount of air blown and an increase in noise, resulting in an undesirable result. Therefore, the portion of the electrical box 65 that protrudes from the partition plate 611 and the reactor 105 must be placed at a position as far as possible from the outdoor fan 631, that is, at a corner portion of the blower chamber 64.

このような事情から、リアクタ１０５は質量が大きいので、取付固定を確実にするため、ベース６１に近い、低い位置の仕切板６１１寄りに配置され、電装箱６５は、上述のように、送風機室６４と機械室６８とに跨って、仕切板６１１の上部に設置される。また、送風機室６５に置かれる部分は、室外ファン６３１に対する影響を小さくするために、できるだけ小さくする必要がある。   Because of such circumstances, the reactor 105 has a large mass. Therefore, in order to ensure mounting and fixing, the reactor 105 is disposed near the partition plate 611 at a low position close to the base 61, and the electrical box 65 is disposed in the blower chamber as described above. 64 and the machine room 68 are installed on the upper part of the partition plate 611. Further, the portion placed in the blower chamber 65 needs to be as small as possible in order to reduce the influence on the outdoor fan 631.

このため、容量の大きい電装部品の小型化を図ると共に、これらの電装部品を効率よく冷却するため、室外熱交換器７３に熱交換用の外気を通風させる室外ファン６３１の負圧を利用して電装部に冷却用の空気を導入する。このよう状況から、リアクタ１０５の容量を小さくすることは空気調和機の小型化，性能向上に対して大きな効果がある。   For this reason, in order to reduce the size of electrical components having large capacities and efficiently cool these electrical components, the negative pressure of the outdoor fan 631 that allows the outdoor heat exchanger 73 to ventilate the outside air for heat exchange is used. Air for cooling is introduced into the electrical equipment section. In this situation, reducing the capacity of the reactor 105 has a great effect on downsizing and improving the performance of the air conditioner.

このように、実施例の空気調和機は、回転数制御型圧縮機を搭載し、請求項１乃至請求項１１の直流電源装置を用いる。   As described above, the air conditioner of the embodiment is equipped with the rotation speed control type compressor and uses the DC power supply device of claims 1 to 11.

これにより、室内の温度が設定温度に近い条件での運転（圧縮機の回転数が低い、小能力での連続運転）が非常に長いことから、スイッチング損失が小さい、効率の良い運転が長く続き消費電力量を抑制することができる。   As a result, the operation under conditions where the room temperature is close to the set temperature (continuous operation with a low compressor speed and small capacity) is very long. Power consumption can be suppressed.

また、空気調和運転の開始当初のような高負荷時はスイッチングの回数を増やして、圧縮用モータが誘起電圧に打勝って高速回転し、大能力を発揮できるよう直流電圧を昇圧し、圧縮機を駆動すると共に、高力率を確保し、空気調和機を接続したブレーカー、またはコンセントの容量を目いっぱいに活用して空気調和機の能力を最大限に発揮させ、室内を素早く快適温度にすることができる。   In addition, when the load is high, such as at the beginning of air-conditioning operation, the number of switchings is increased, and the DC voltage is boosted so that the compression motor can overcome the induced voltage and rotate at a high speed to exhibit its high capacity. As well as ensuring a high power factor, the capacity of the breaker or outlet connected to the air conditioner can be fully utilized to maximize the performance of the air conditioner and quickly bring the room to a comfortable temperature. be able to.

このため、安価で、電源高調波電流規制を満足し、電源容量を最大限に活用した高能力で、効率の良い空気調和機を提供することができる。   Therefore, it is possible to provide an air conditioner that is inexpensive, satisfies the power supply harmonic current regulation, has a high capacity and uses the power supply capacity to the maximum, and is efficient.

なお、本発明は空気調和機だけでなく、直流電源装置を用いた電子機器に広く応用できる。   Note that the present invention can be widely applied not only to air conditioners but also to electronic devices using a DC power supply.

以上説明したように、請求項１記載の直流電源装置によれば、交流電源より入力された交流電力を直流電力に変換する整流回路と、前記交流電源と前記整流回路との間に接続されたリアクタと、前記交流電源を前記リアクタを介して短絡するスイッチング手段と、前記直流電力の目標電圧設定手段と、前記交流電源の周波数を検出する周波数検出手段と、前記交流電源の電源電圧を検出する電源電圧検出手段と、前記交流電源のゼロクロス点を検出するゼロクロス検出手段と、前記整流回路の出力である直流電圧を検出する直流電圧検出手段と、前記ゼロクロス点に同期させて前記スイッチング手段を短絡，開放するスイッチング制御手段とを備え、前記スイッチング制御手段は前記目標電圧設定手段で設定された目標直流電圧と前記電源電圧検出手段で検出された電源電圧との比の値が所定値未満の場合に前記ゼロクロス検出手段で検出された前記交流電源のゼロクロス点からの１／２周期中に、前記スイッチング手段を２回短絡し、この２回短絡の１回目と２回目の短絡間隔を、前記周波数検出手段で検出された電源周波数が５０Ｈｚの時には０.２〜０.４ｍｓで、前記電源周波数が６０Ｈｚの時には０.１６〜０.３３ｍｓとし、その後に前記比の値が所定値以上の場合に前記スイッチング手段の短絡回数を前記比の値に応じて前記２回よりも多い回数で且つ、組み込まれる機器のモータの運転騒音周波数に対して直流電源装置の騒音周波数が超えない短絡回数に切り替える。   As described above, according to the DC power supply device of claim 1, the rectifier circuit that converts AC power input from the AC power source into DC power, and the AC power source and the rectifier circuit are connected. A reactor, a switching means for short-circuiting the AC power supply through the reactor, a target voltage setting means for the DC power, a frequency detection means for detecting the frequency of the AC power supply, and a power supply voltage of the AC power supply. A power supply voltage detection means, a zero cross detection means for detecting a zero cross point of the AC power supply, a DC voltage detection means for detecting a DC voltage as an output of the rectifier circuit, and the switching means are short-circuited in synchronization with the zero cross point. Switching control means for opening, and the switching control means comprises a target DC voltage set by the target voltage setting means and the power supply voltage. When the value of the ratio with the power supply voltage detected by the detection means is less than a predetermined value, the switching means is short-circuited twice during a half cycle from the zero cross point of the AC power supply detected by the zero cross detection means. The first and second short-circuit intervals of the two-time short circuit are 0.2 to 0.4 ms when the power frequency detected by the frequency detecting means is 50 Hz, and 0.16 when the power frequency is 60 Hz. ˜0.33 ms, and when the ratio value is equal to or greater than a predetermined value, the number of short-circuits of the switching means is greater than the two times according to the ratio value, and the motor of the device to be incorporated is operated. Switch to the number of short circuits where the noise frequency of the DC power supply does not exceed the noise frequency.

これにより、負荷の駆動に最適な直流電圧を目標電圧設定手段で設定し、電源電圧の実効値との比の値が所定値未満の場合、つまり、負荷が軽く小能力での運転の場合には、電源周波数に応じた適切な短絡間隔で２回短絡を行うことで、電源高調波電流を抑制しつつ、力率を上げることができる。この時、スイッチング回数は２回のみなので、スイッチング損失は小さく、効率の良い運転ができる。   As a result, the optimum DC voltage for driving the load is set by the target voltage setting means, and when the value of the ratio to the effective value of the power supply voltage is less than the predetermined value, that is, when the load is light and the operation is performed with a small capacity The power factor can be increased while suppressing the power supply harmonic current by short-circuiting twice at an appropriate short-circuit interval corresponding to the power supply frequency. At this time, since the number of times of switching is only two, the switching loss is small and an efficient operation can be performed.

また、目標電圧と、電源電圧の実効値との比の値が所定値以上の場合、つまり、負荷が重く大能力での運転の場合には、６回までの短絡回数を単調に増加させることで、電源高調波電流を規制値以下に抑制しつつ、電源電圧の変動をカバーし、且つ、直流電圧の昇圧と力率のアップを両立できる。この時、スイッチングの回数は高々６回なので、スイッチング損失も僅かな増加で済み、高効率を維持できる。   In addition, when the ratio of the target voltage to the effective value of the power supply voltage is greater than or equal to a predetermined value, that is, when the load is heavy and the operation is performed at a large capacity, the number of short circuits up to 6 times should be increased monotonously. Thus, it is possible to cover the fluctuation of the power supply voltage while suppressing the power supply harmonic current below the regulation value, and to simultaneously increase the DC voltage and increase the power factor. At this time, since the number of times of switching is 6 at most, the switching loss can be increased only slightly, and high efficiency can be maintained.

この場合、２回目までの短絡は力率の増加と電源高調波電流の抑制を主眼とし、３回目の短絡は直流電圧の昇圧を主眼とし、４回目の短絡で直流電圧の昇圧と力率の増加を図り、５回目と６回目の短絡は力率の増加を主眼として短絡動作を実行する。   In this case, the second short circuit focuses on the increase of the power factor and the suppression of the power supply harmonic current, the third short circuit focuses on the DC voltage boost, and the fourth short circuit increases the DC voltage and power factor. In order to increase, the fifth and sixth short-circuit operations are performed with a focus on increasing the power factor.

特に、駆動する負荷が空気調和機の圧縮機である場合、空気調和機は室内の温度が設定温度に近い条件での運転（圧縮機の回転数が低い、小能力での連続運転）が非常に長いことから、スイッチング損失が小さい、効率の良い運転が長く続き消費電力量を抑制することができる。   In particular, when the load to be driven is a compressor of an air conditioner, the air conditioner is very likely to operate under conditions where the indoor temperature is close to the set temperature (continuous operation with low capacity, low compressor speed). Therefore, efficient operation can be continued for a long time with low switching loss, and power consumption can be suppressed.

また、空気調和運転の開始当初のような高負荷時はスイッチングの回数を増やして、圧縮用モータが誘起電圧に打勝って高速回転し、大能力を発揮できるよう直流電圧を昇圧し、圧縮機を駆動すると共に、高力率を確保し、空気調和機を接続したブレーカー、またはコンセントの容量を目いっぱいに活用して空気調和機の能力を最大限に発揮させ、室内を素早く快適温度にすることができる。   In addition, when the load is high, such as at the beginning of air-conditioning operation, the number of switchings is increased, and the DC voltage is boosted so that the compression motor can overcome the induced voltage and rotate at a high speed to exhibit its high capacity. As well as ensuring a high power factor, the capacity of the breaker or outlet connected to the air conditioner can be fully utilized to maximize the performance of the air conditioner and quickly bring the room to a comfortable temperature. be able to.

このため、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する直流電源装置を得ることができる。   For this reason, a DC power supply device that achieves high efficiency and appropriate power factor at low loads and high power factor and appropriate efficiency at high loads while suppressing power supply harmonic current with an inexpensive circuit configuration Can do.

また、請求項２記載の直流電源装置によれば、前記スイッチング制御手段は前記目標電圧設定手段で設定された目標直流電圧と前記電源電圧検出手段で検出された電源電圧との比の値が所定値以上の場合に、前記２回短絡の場合と同様に、前記ゼロクロス検出手段で検出された前記交流電源のゼロクロス点からの１／２周期中に、前記スイッチング手段を２回短絡し、この２回短絡の１回目と２回目の短絡間隔を、前記周波数検出手段で検出された電源周波数が５０Ｈｚの時には０.２〜０.４ｍｓで、前記電源周波数が６０Ｈｚの時には０.１６〜０.３３ｍｓとし、その後に前記比の値が所定値以上の場合に前記スイッチング手段の短絡回数を前記比の値に応じて前記２回よりも多い回数で且つ、組み込まれる機器のモータの運転騒音周波数に対して直流電源装置の騒音周波数が超えない短絡回数に切り替える。   According to the DC power supply device of claim 2, the switching control means has a predetermined value of a ratio between the target DC voltage set by the target voltage setting means and the power supply voltage detected by the power supply voltage detection means. When the value is equal to or greater than the value, as in the case of the two-time short circuit, the switching means is short-circuited twice during a half cycle from the zero cross point of the AC power source detected by the zero-cross detection means. The short-circuit interval between the first and second short-circuits is 0.2 to 0.4 ms when the power supply frequency detected by the frequency detection means is 50 Hz, and 0.16 to 0.33 ms when the power supply frequency is 60 Hz. Then, when the value of the ratio is equal to or greater than a predetermined value, the number of short-circuits of the switching means is more than the two times according to the value of the ratio, and the operating noise frequency of the motor of the apparatus to be incorporated. On the other hand, the number of short circuits is switched so that the noise frequency of the DC power supply does not exceed.

これにより、２を超える回数短絡した場合でも前述と同様に適切な間隔を第１の短絡と第２の短絡の間に設けることで、電源高調波電流の抑制と力率の改善を達成できる。   As a result, even when the number of short circuits exceeds two, an appropriate interval is provided between the first short circuit and the second short circuit in the same manner as described above, thereby suppressing the power supply harmonic current and improving the power factor.

このため、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する直流電源装置を得ることができる。   For this reason, a DC power supply device that achieves high efficiency and appropriate power factor at low loads and high power factor and appropriate efficiency at high loads while suppressing power supply harmonic current with an inexpensive circuit configuration Can do.

また、請求項３記載の直流電源装置によれば、前記スイッチング制御手段は３回目以降の短絡時間を前記電源周波数が５０Ｈｚの時は０.２５ｍｓ、６０Ｈｚの時は０.２ｍｓ以下の範囲とする。   According to a third aspect of the present invention, the switching control means sets the third and subsequent short-circuit times in the range of 0.25 ms when the power frequency is 50 Hz and 0.2 ms or less when the power frequency is 60 Hz. .

これにより、３回目以降の短絡によって生じる電源高調波電流の周波数が、電源周波数が５０Ｈｚの時は２,０００Ｈｚ、６０Ｈｚの時は２,５００Ｈｚ以上となり、電源周波数の４０次以上となって、電源高調波電流規制の対象から除外されるので、電源高調波電流規制を満足することができ、主として力率の向上を考慮した検討をすれば良いことになる。   As a result, the frequency of the power harmonic current generated by the third and subsequent short circuits is 2,000 Hz when the power frequency is 50 Hz, 2,500 Hz or higher when the power frequency is 60 Hz, and the power frequency is 40th or higher. Since it is excluded from the target of the harmonic current regulation, the power supply harmonic current regulation can be satisfied, and it is only necessary to consider mainly the improvement of the power factor.

これは、高調波電流を抑制し、力率を高くするためには、短絡回数を多くすることが有効であることを前述したが、シミュレーションによれば、力率に関係してくる３次〜１５次の高調波の抑制には短絡回数を多くすることが有効であるが、１５次〜４０次の高調波電流は逆に増えやすい傾向となる。   As described above, in order to suppress the harmonic current and increase the power factor, it is effective to increase the number of short-circuits. Increasing the number of short circuits is effective for suppressing the 15th harmonic, but the 15th to 40th harmonic currents tend to increase conversely.

そこで第２の短絡より後の短絡は４０次よりも高次の波形とすることが電源高調波電流の抑制に重要となることが判った。電源周波数が５０Ｈｚである時、その周期２０ｍｓの正弦波であり、電源周波数の４０次高調波の周期は０.５ｍｓとなる。   Thus, it has been found that it is important for the suppression of the power supply harmonic current that the short circuit after the second short circuit has a higher-order waveform than the 40th order. When the power supply frequency is 50 Hz, the sine wave has a period of 20 ms, and the period of the 40th harmonic of the power supply frequency is 0.5 ms.

短絡により発生する三角波がこの４０次の周期の１／２以下となれば電源高調波電流規制の対象外になり、短絡時間を０.２５ｍｓより短くすることで電源高調波電流規制を満足することができる。電源周波数が６０Ｈｚのときも同様の理由で短絡時間を０.２ｍｓより短くすることで電源高調波電流規制を満足することができる。   If the triangular wave generated by the short circuit becomes 1/2 or less of this 40th order period, it will be excluded from the power harmonic current regulation, and the power harmonic current regulation will be satisfied by making the short circuit time shorter than 0.25 ms. Can do. Even when the power supply frequency is 60 Hz, the power supply harmonic current regulation can be satisfied by shortening the short circuit time to less than 0.2 ms for the same reason.

このため、短絡回数を多くして力率を改善しつつ、電源高調波電流規制を満足する直流電源装置を得ることができる。   For this reason, it is possible to obtain a DC power supply device that satisfies the power harmonic current regulation while increasing the number of short circuits to improve the power factor.

また、請求項４記載の直流電源装置によれば、前記スイッチング手段の短絡回数をＭ回からＭ＋１回に増加させる時に、短絡回数増加後のＭ回目までの短絡時間の合計値を、短絡回数増加前の短絡時間の合計値より、減少させる。   According to the DC power supply device of claim 4, when the number of short circuits of the switching means is increased from M times to M + 1 times, the total value of the short circuit time up to M times after the increase of the number of short circuits is increased. Decrease from the total value of the previous short circuit time.

これにより、短絡回数をｎからｎ＋１に増やす場合に、単純に短絡回数を増やすのではなく、直流電圧がほぼ同じになるように、短絡回数を増やした後のｎ回までの短絡時間の合計を、短絡回数を増やす前のｎ回までの短絡時間の合計より短くする。これにより、短絡回数を増やした後のｎ回までの短絡により得られる直流電圧は下降し、ｎ＋１回目の短絡でこの下降した分の直流電圧分を取戻し、全体として、短絡回数を増やす前の直流電圧とほぼ等しい直流電圧を得ることができる。   As a result, when the number of short circuits is increased from n to n + 1, the total number of short circuits up to n times after the number of short circuits is increased so that the DC voltage is substantially the same, instead of simply increasing the number of short circuits. The short circuit time is made shorter than the total short circuit time up to n times before increasing the number of short circuits. As a result, the DC voltage obtained by the short-circuiting up to n times after increasing the number of short-circuits decreases, and the DC voltage corresponding to the decreased DC voltage is recovered at the (n + 1) th short-circuit, and as a whole, the DC voltage before increasing the number of short-circuits A DC voltage substantially equal to the voltage can be obtained.

このため、電源高調波電流の抑制や力率の改善のために、短絡回数を増しても、直流電圧がほとんど変化せず、負荷となる機器の安定した運転を確保できる直流電源装置を得ることができる。   Therefore, to suppress the power supply harmonic current and improve the power factor, a DC power supply device is obtained in which the DC voltage hardly changes even when the number of short-circuits is increased, and stable operation of the load equipment can be secured. Can do.

また、請求項５記載の直流電源装置によれば、前記スイッチング手段の短絡回数をＭ回からＭ＋１回に増加させる時に、Ｍ＋１回目までの短絡時間の合計値を、短絡回数増加前のＭ回目までの短絡時間の合計値と等しくする。   According to the DC power supply device according to claim 5, when the number of short circuits of the switching means is increased from M times to M + 1 times, the total value of the short circuit time up to the M + 1 time is increased to the Mth time before the number of short circuits is increased. It is made equal to the total value of the short circuit time.

これにより、短絡回数を増やした場合、短絡時間の合計が同じになるようにする。これにより、短絡回数を増やす前後の短絡時間の合計が等しくなり、得られる直流電圧をほぼ一定に維持することができる。   Thereby, when the frequency | count of a short circuit is increased, it is made for the sum total of a short circuit time to become the same. Thereby, the sum total of the short circuit time before and behind increasing the frequency | count of a short circuit becomes equal, and the obtained DC voltage can be maintained substantially constant.

このため、電源高調波電流の抑制や力率の改善のために、短絡回数を増しても、直流電圧がほとんど変化せず、負荷となる機器の安定した運転を確保できる直流電源装置を得ることができる。   Therefore, to suppress the power supply harmonic current and improve the power factor, a DC power supply device is obtained in which the DC voltage hardly changes even when the number of short-circuits is increased, and stable operation of the load equipment can be secured. Can do.

また、請求項６記載の直流電源装置によれば、前記スイッチング手段の短絡回数をＭ回からＭ−１回に減少させる時に、短絡回数減少後の短絡時間の合計値を、短絡回数減少前のＭ−１回目までの短絡時間の合計値より、増加させる。   According to the DC power supply device of claim 6, when the number of short circuits of the switching means is decreased from M times to M−1 times, the total value of the short circuit time after the short circuit number is reduced is the value before the short circuit number is reduced. It is increased from the total value of the short-circuiting time up to the M-1th time.

これにより、短絡回数をｎからｎ−１に減らす場合に、単純に短絡回数を減らすのではなく、直流電圧がほぼ同じになるように、短絡回数を減らした後の短絡時間の合計（ｎ−１回までの短絡時間の合計）を、短絡回数を減らす前のｎ−１回までの短絡時間の合計より長くする。   As a result, when the number of short circuits is reduced from n to n−1, the total number of short circuits after the number of short circuits is reduced (n−) so that the DC voltage is substantially the same, instead of simply reducing the number of short circuits. The sum of the short-circuit times up to once) is made longer than the sum of the short-circuit times up to n-1 times before the number of short-circuits is reduced.

これにより、短絡回数を減らした後の短絡（ｎ−１回までの短絡）により得られる直流電圧は、短絡回数を減らす前のｎ−１回目までの短絡で得られた直流電圧より上昇し、短絡回数を減らす前のｎ回目の短絡が無くなったことによる直流電圧の下降分を補い、全体として、短絡回数を減らす前の直流電圧とほぼ等しい直流電圧を得ることができる。   Thereby, the DC voltage obtained by the short circuit (short circuit up to n-1 times) after reducing the number of short circuits is higher than the DC voltage obtained by the short circuit up to n-1 time before reducing the number of short circuits, As a whole, it is possible to obtain a DC voltage substantially equal to the DC voltage before reducing the number of short circuits by compensating for the decrease in DC voltage due to the absence of the n-th short circuit before reducing the number of short circuits.

このため、電源高調波電流の抑制や力率の改善のために、短絡回数を増しても、直流電圧がほとんど変化せず、負荷となる機器の安定した運転を確保できる直流電源装置を得ることができる。   Therefore, to suppress the power supply harmonic current and improve the power factor, a DC power supply device is obtained in which the DC voltage hardly changes even when the number of short-circuits is increased, and stable operation of the load equipment can be secured. Can do.

また、請求項７記載の直流電源装置によれば、前記スイッチング手段の短絡回数をＭ回からＭ−１回に減少させる時に、短絡回数減少後の短絡時間の合計値を、短絡回数減少前のＭ回目までの短絡時間の合計値と等しくする。   According to the DC power supply device of claim 7, when the number of short circuits of the switching means is decreased from M times to M−1 times, the total value of the short circuit time after the short circuit number is reduced is the value before the short circuit number is reduced. It is set equal to the total value of the short-circuit time up to the Mth time.

これにより、短絡回数を減らした場合、短絡時間の合計が同じになるようにする。これにより、短絡回数を減らす前後の短絡時間の合計が等しくなり、得られる直流電圧をほぼ一定に維持することができる。   Thus, when the number of short circuits is reduced, the total short circuit time is made the same. Thereby, the sum total of the short circuit time before and after reducing the frequency | count of a short circuit becomes equal, and the direct-current voltage obtained can be maintained substantially constant.

このため、電源高調波電流の抑制や力率の改善のために、短絡回数を増しても、直流電圧がほとんど変化せず、負荷となる機器の安定した運転を確保できる直流電源装置を得ることができる。   Therefore, to suppress the power supply harmonic current and improve the power factor, a DC power supply device is obtained in which the DC voltage hardly changes even when the number of short-circuits is increased, and stable operation of the load equipment can be secured. Can do.

また、請求項８記載の直流電源装置によれば、前記交流電源からの入力電流を検出する入力電流検出手段を更に備え、前記スイッチング制御手段は前記スイッチング手段の２〜６回までの短絡回数を前記比の値と前記入力電流検出手段で検出した入力電流に応じて定める。   Further, according to the DC power supply device of claim 8, further comprising input current detection means for detecting an input current from the AC power supply, wherein the switching control means sets the number of short-circuits of the switching means up to 2 to 6 times. It is determined according to the value of the ratio and the input current detected by the input current detecting means.

これにより、前記比の値と入力電流の大小に応じて、短絡回数を適切の定めることができるので、電源高調波電流の規制を満足しつつ、力率を改善し、高効率な運転が可能となる。この場合、最も簡単な短絡回数の定め方としては、入力電流を目標直流電圧に換算し、電源電圧との比の値を求め比の値に応じて前述の方法により短絡回数を定める方法がある。   As a result, the number of short-circuits can be appropriately determined according to the ratio value and the input current, so that the power factor can be improved and high-efficiency operation can be achieved while satisfying the regulation of the power supply harmonic current. It becomes. In this case, as the simplest method of determining the number of short circuits, there is a method of converting the input current to a target DC voltage, obtaining a value of the ratio with the power supply voltage, and determining the number of short circuits by the above-described method according to the value of the ratio. .

入力電流を目標直流電圧に換算する方法としては、例えば図２３に示すように、入力電流を機器が持つ特性に従って、適切な数値で区分し、各区分点での目標直流電圧を実験などで確認し、その中間では直線補間，階段状の変化，曲線補間などの方法で目標直流電圧を定める方法などを採用すれば良い。このようにすることで、入力電流の全域で目標直流電圧を簡単に設定でき、電源高調波電流の規制を満足しつつ、力率を改善し、高効率な運転が可能となる。   As a method for converting the input current to the target DC voltage, for example, as shown in FIG. 23, the input current is classified by an appropriate numerical value in accordance with the characteristics of the device, and the target DC voltage at each division point is confirmed by an experiment or the like. In the middle, a method of determining the target DC voltage by a method such as linear interpolation, step-like change, or curve interpolation may be adopted. In this way, the target DC voltage can be easily set over the entire input current, and the power factor can be improved and highly efficient operation can be achieved while satisfying the regulation of the power supply harmonic current.

このため、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する直流電源装置を得ることができる。   For this reason, a DC power supply device that achieves high efficiency and appropriate power factor at low loads and high power factor and appropriate efficiency at high loads while suppressing power supply harmonic current with an inexpensive circuit configuration Can do.

また、請求項９記載の直流電源装置によれば、前記直流電力に接続された負荷量を検出する負荷量検出手段を更に備え、前記スイッチング制御手段は前記スイッチング手段の２〜６回までの短絡回数を前記比の値と前記負荷量検出手段で検出された負荷量に応じて定める。   The DC power supply device according to claim 9 further includes load amount detection means for detecting a load amount connected to the DC power, wherein the switching control means is short-circuited up to 2 to 6 times of the switching means. The number of times is determined according to the value of the ratio and the load amount detected by the load amount detection means.

これにより、前記比の値と負荷量の大小に応じて、短絡回数を適切の定めることができるので、電源高調波電流の規制を満足しつつ、力率を改善し、高効率な運転が可能となる。この場合、最も簡単な短絡回数の定め方としては、負荷量を目標直流電圧に換算し、電源電圧との比の値を求め比の値に応じて前述の方法により短絡回数を定める方法がある。   As a result, the number of short-circuits can be determined appropriately according to the ratio value and the amount of load, so that power factor can be improved and high-efficiency operation can be achieved while satisfying the regulation of power supply harmonic current. It becomes. In this case, as the simplest method of determining the number of short circuits, there is a method of converting the load amount to a target DC voltage, obtaining a value of the ratio with the power supply voltage, and determining the number of short circuits by the method described above according to the ratio value. .

負荷量を目標直流電圧に換算する方法としては、例えば図２３に示すようなグラフに従って、前述のような方法で目標直流電圧を定めれば良い。このようにすることで、負荷量の全域で目標直流電圧を簡単に設定でき、電源高調波電流の規制を満足しつつ、力率を改善し、高効率な運転が可能となる。   As a method of converting the load amount into the target DC voltage, the target DC voltage may be determined by the method as described above, for example, according to a graph as shown in FIG. In this way, the target DC voltage can be easily set over the entire load amount, and the power factor can be improved and highly efficient operation can be performed while satisfying the regulation of the power supply harmonic current.

このため、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する直流電源装置を得ることができる。   For this reason, a DC power supply device that achieves high efficiency and appropriate power factor at low loads and high power factor and appropriate efficiency at high loads while suppressing power supply harmonic current with an inexpensive circuit configuration Can do.

また、請求項１０記載の直流電源装置によれば、前記直流電力に接続される負荷をモータとし、前記負荷量を前記モータへの印加電圧とし、前記負荷量検出手段としてモータへの印加電圧を検出するモータ印加電圧検出手段を備え、前記スイッチング制御手段は前記スイッチング手段の２〜６回までの短絡回数を前記比の値と前記モータ印加電圧検出手段で検出されたモータ印加電圧に応じて定める。   According to the DC power supply device of claim 10, the load connected to the DC power is a motor, the load amount is an applied voltage to the motor, and the applied voltage to the motor is used as the load amount detecting means. Motor switching voltage detection means for detecting, the switching control means determines the number of short-circuiting of the switching means up to 2 to 6 times according to the value of the ratio and the motor application voltage detected by the motor application voltage detection means. .

これにより、前記比の値とモータ印加電圧の高低に応じて、短絡回数を適切の定めることができるので、電源高調波電流の規制を満足しつつ、力率を改善し、高効率な運転が可能となる。この場合、最も簡単な短絡回数の定め方としては、モータ印加電圧を目標直流電圧に換算し、電源電圧との比の値を求め比の値に応じて前述の方法により短絡回数を定める方法がある。   As a result, the number of short circuits can be appropriately determined according to the value of the ratio and the level of the motor applied voltage, so that the power factor is improved and high-efficiency operation is achieved while satisfying the regulation of the power supply harmonic current. It becomes possible. In this case, the simplest method of determining the number of short circuits is to convert the motor applied voltage to a target DC voltage, determine the value of the ratio with the power supply voltage, and determine the number of short circuits by the above method according to the value of the ratio. is there.

モータ印加電圧を目標直流電圧に換算する方法としては、例えば図２３に示すようなグラフに従って、前述のような方法で目標直流電圧を定めれば良い。このようにすることで、モータ印加電圧の全域で目標直流電圧を簡単に設定でき、電源高調波電流の規制を満足しつつ、力率を改善し、高効率な運転が可能となる。   As a method of converting the motor applied voltage into the target DC voltage, the target DC voltage may be determined by the method as described above, for example, according to a graph as shown in FIG. In this way, the target DC voltage can be easily set over the entire range of the motor applied voltage, and the power factor can be improved and highly efficient operation can be achieved while satisfying the regulation of the power supply harmonic current.

このため、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する直流電源装置を得ることができる。   For this reason, a DC power supply device that achieves high efficiency and appropriate power factor at low loads and high power factor and appropriate efficiency at high loads while suppressing power supply harmonic current with an inexpensive circuit configuration Can do.

また、請求項１１記載の直流電源装置によれば、前記直流電力に接続される負荷をモータとし、前記負荷量を前記モータの回転数として、前記負荷量検出手段としてモータの回転数を検出するモータ回転数検出手段を備え、前記スイッチング制御手段は前記スイッチング手段の２〜６回までの短絡回数を前記比の値と前記モータ回転数検出手段で検出されたモータ回転数に応じて定める。   According to the DC power supply device of claim 11, the load connected to the DC power is a motor, the load amount is the rotation number of the motor, and the rotation amount of the motor is detected as the load amount detection means. Motor rotation speed detection means is provided, and the switching control means determines the number of short circuits of the switching means from 2 to 6 according to the value of the ratio and the motor rotation speed detected by the motor rotation speed detection means.

これにより、前記比の値とモータ回転数の高低に応じて、短絡回数を適切の定めることができるので、電源高調波電流の規制を満足しつつ、力率を改善し、高効率な運転が可能となる。この場合、最も簡単な短絡回数の定め方としては、モータ回転数を目標直流電圧に換算し、電源電圧との比の値を求め比の値に応じて前述の方法により短絡回数を定める方法がある。   As a result, the number of short circuits can be appropriately determined according to the value of the ratio and the motor rotation speed, so that the power factor is improved and the highly efficient operation is achieved while satisfying the regulation of the power supply harmonic current. It becomes possible. In this case, the simplest method of determining the number of short circuits is to convert the motor rotation number to the target DC voltage, determine the ratio with the power supply voltage, and determine the number of short circuits by the above method according to the ratio value. is there.

モータ回転数を目標直流電圧に換算する方法としては、例えば図２３に示すようなグラフに従って、前述のような方法で目標直流電圧を定めれば良い。このようにすることで、モータ回転数の全域で目標直流電圧を簡単に設定でき、電源高調波電流の規制を満足しつつ、力率を改善し、高効率な運転が可能となる。   As a method for converting the motor rotational speed into the target DC voltage, the target DC voltage may be determined by the method as described above, for example, according to a graph as shown in FIG. In this way, the target DC voltage can be easily set over the entire range of the motor rotation speed, and the power factor can be improved and highly efficient operation can be achieved while satisfying the regulation of the power supply harmonic current.

このため、安価な回路構成で電源高調波電流を抑制しつつ、低負荷では高効率と適宜な力率を実現し、高負荷では高力率と適宜な効率を実現する直流電源装置を得ることができる。   For this reason, a DC power supply device that achieves high efficiency and appropriate power factor at low loads and high power factor and appropriate efficiency at high loads while suppressing power supply harmonic current with an inexpensive circuit configuration Can do.

また、請求項１２記載の空気調和機によれば、回転数制御型圧縮機を搭載し、請求項１乃至請求項１１の直流電源装置を用いる。   According to the air conditioner of the twelfth aspect, the rotational speed control type compressor is mounted, and the DC power supply device of the first to eleventh aspects is used.

これにより、室内の温度が設定温度に近い条件での運転（圧縮機の回転数が低い、小能力での連続運転）が非常に長いことから、スイッチング損失が小さい、効率の良い運転が長く続き消費電力量を抑制することができる。   As a result, the operation under conditions where the room temperature is close to the set temperature (continuous operation with a low compressor speed and small capacity) is very long. Power consumption can be suppressed.

また、空気調和運転の開始当初のような高負荷時はスイッチングの回数を増やして、圧縮用モータが誘起電圧に打勝って高速回転し、大能力を発揮できるよう直流電圧を昇圧し、圧縮機を駆動すると共に、高力率を確保し、空気調和機を接続したブレーカー、またはコンセントの容量を目いっぱいに活用して空気調和機の能力を最大限に発揮させ、室内を素早く快適温度にすることができる。   In addition, when the load is high, such as at the beginning of air-conditioning operation, the number of switchings is increased, and the DC voltage is boosted so that the compression motor can overcome the induced voltage and rotate at a high speed to exhibit its high capacity. As well as ensuring a high power factor, the capacity of the breaker or outlet connected to the air conditioner can be fully utilized to maximize the performance of the air conditioner and quickly bring the room to a comfortable temperature. be able to.

このため、安価で、電源高調波電流規制を満足し、電源容量を最大限に活用した高能力で、効率の良い空気調和機を得ることができる。   For this reason, it is possible to obtain an air conditioner that is inexpensive, satisfies the power supply harmonic current regulation, has a high capacity and uses the power supply capacity to the maximum, and is efficient.

１ 空気調和機
２ 室内機
５ リモコン
６ 室外機
８ 接続配管
１０ 制御装置
２０ 筐体
２１ 筐体ベース
２３ 化粧枠
２５ 前面パネル
２７ 空気吸込み口
２９ 空気吹出し口
３３ 室内熱交換器
３５ 露受皿
３７ ドレン配管
６１ ベース
６２ 外筐
６４ 送風機室
６５ 電装箱
６６ 電装箱蓋
６７ 電装品
６８ 機械室
７３ 室外熱交換器
７５ 圧縮機
７６ アキュムレータ
７８ 配管接続バルブ
８２ 接続部開口
１００ 直流電源装置
１０１ 交流電源
１０２ 整流回路
１０３ 平滑コンデンサ
１０４ 負荷
１０４ａ インバータ
１０４ｂ 外部負荷
１０５ リアクタ
１０６ スイッチング手段
１０７ 電源電圧・ゼロクロス検出手段
１０８ スイッチング制御手段
１０９ 直流電圧検出手段
１１０ インバータドライバ
１１１ マイクロコンピュータ
１１１ａ 周波数検出手段
１１１ｂ，１１１ｄ Ａ／Ｄ変換部
１１１ｃ，１１１ｅ ＰＷＭ出力部
１１１ｆ コンバータ制御手段
１１１ｇ インバータ制御手段
１１１ｈ 目標電圧設定手段
１１２ 入力電流検出手段
１１３ 負荷量検出手段
１１４ モータ
１１５ モータ印加電圧検出手段
１１６ モータ回転数検出手段
１１８ 周辺情報検出手段
２３０，２３０′ 空気吸込み部
２３１，２３１′ フィルター
２５１ 可動パネル
２９０ 吹出し風路
２９０ａ 吹出し風路上壁
２９０ｂ 吹出し風路下壁
２９１ 上側上下風向板
２９２ 下側上下風向板
２９５ 左右風向板
３１１ 送風ファン
３９６ 送受信部
３９７ 表示装置
６１１ 仕切板
６１２ リアクタカバー
６２１ 前面板
６２１ａ モータベース
６２１ｅ ファンリング
６２１ｇ 開口基部
６２２ 天板
６２３ 側面板
６３１ 室外ファン
６３３ 送風モータ
６３５ ファングリル DESCRIPTION OF SYMBOLS 1 Air conditioner 2 Indoor unit 5 Remote control 6 Outdoor unit 8 Connection piping 10 Control apparatus 20 Case 21 Case base 23 Decorative frame 25 Front panel 27 Air inlet 29 Air outlet 33 Indoor heat exchanger 35 Dew tray 37 Drain pipe 61 Base 62 Outer casing 64 Blower chamber 65 Electrical box 66 Electrical box lid 67 Electrical component 68 Machine room 73 Outdoor heat exchanger 75 Compressor 76 Accumulator 78 Pipe connection valve 82 Connection opening 100 DC power supply 101 AC power supply 102 Rectifier circuit 103 Smoothing capacitor 104 Load 104a Inverter 104b External load 105 Reactor 106 Switching means 107 Power supply voltage / zero cross detection means 108 Switching control means 109 DC voltage detection means 110 Inverter driver 111 Microcomputer 111a Frequency detection means 111b, 1 1d A / D converters 111c, 111e PWM output unit 111f Converter control unit 111g Inverter control unit 111h Target voltage setting unit 112 Input current detection unit 113 Load amount detection unit 114 Motor 115 Motor applied voltage detection unit 116 Motor rotation number detection unit 118 Peripheral information detection means 230, 230 ′ Air suction part 231, 231 ′ Filter 251 Movable panel 290 Blowing air passage 290 a Blowing air passage upper wall 290 b Blowing air passage lower wall 291 Upper vertical wind direction plate 292 Lower vertical wind direction plate 295 Left and right wind direction plate 311 Blower fan 396 Transmitter / receiver 397 Display device 611 Partition plate 612 Reactor cover 621 Front plate 621a Motor base 621e Fan ring 621g Opening base 622 Top plate 623 Side plate 631 Outdoor fan 633 Blower motor 635 Anguriru

Claims (11)

交流電源より入力された交流電力を直流電力に変換する整流回路と、
前記交流電源と前記整流回路との間に接続されたリアクタと、
前記交流電源を前記リアクタを介して短絡するスイッチング手段と、
前記直流電力の目標電圧設定手段と、
前記交流電源の周波数を検出する周波数検出手段と、
前記交流電源の電源電圧を検出する電源電圧検出手段と、
前記交流電源のゼロクロス点を検出するゼロクロス検出手段と、
前記整流回路の出力である直流電圧を検出する直流電圧検出手段と、
前記ゼロクロス点に同期させて前記スイッチング手段を短絡，開放するスイッチング制御手段とを備える直流電源装置において、
前記スイッチング制御手段は前記目標電圧設定手段で設定された目標直流電圧と前記電源電圧検出手段で検出された電源電圧との比の値が所定値未満の場合に前記ゼロクロス検出手段で検出された前記交流電源のゼロクロス点からの１／２周期中に、前記スイッチング手段を２回短絡し、前記ゼロクロス点から１回目の短絡開始までの時間を予め設定した遅延時間とし、この２回短絡の１回目と２回目の短絡間隔を、前記周波数検出手段で検出された電源周波数が５０Ｈｚの時には０.２〜０.４ｍｓで、前記電源周波数が６０Ｈｚの時には０.１６〜０.３３ｍｓとし、その後に前記比の値が所定値以上の場合に前記スイッチング手段の短絡回数を前記比の値に応じて前記２回よりも多い回数で且つ、組み込まれる機器のモータの運転騒音周波数に対して直流電源装置の騒音周波数が超えない短絡回数に切り替えることを特徴とする直流電源装置。 A rectifier circuit that converts AC power input from an AC power source into DC power;
A reactor connected between the AC power source and the rectifier circuit;
Switching means for short-circuiting the AC power supply via the reactor;
DC power target voltage setting means;
Frequency detection means for detecting the frequency of the AC power supply;
Power supply voltage detecting means for detecting a power supply voltage of the AC power supply;
Zero-cross detection means for detecting a zero-cross point of the AC power supply;
DC voltage detecting means for detecting a DC voltage that is an output of the rectifier circuit;
In a DC power supply device comprising switching control means for short-circuiting and opening the switching means in synchronization with the zero-cross point,
The switching control means detects the zero-crossing detection means when the value of the ratio between the target DC voltage set by the target voltage setting means and the power supply voltage detected by the power supply voltage detection means is less than a predetermined value. During the ½ cycle from the zero cross point of the AC power supply, the switching means is short-circuited twice, and the time from the zero-cross point to the first short-circuit start is set as a preset delay time. The second short-circuit interval is set to 0.2 to 0.4 ms when the power supply frequency detected by the frequency detection means is 50 Hz, and is set to 0.16 to 0.33 ms when the power supply frequency is 60 Hz. When the ratio value is equal to or greater than a predetermined value, the number of short-circuits of the switching means is greater than the two times according to the ratio value and the operating noise frequency of the motor of the apparatus to be incorporated In contrast, the DC power supply apparatus is switched to the number of short circuits that does not exceed the noise frequency of the DC power supply apparatus. 請求項１に記載の直流電源装置において、前記スイッチング制御手段は３回目以降の短絡時間を前記電源周波数が５０Ｈｚの時は０.２５ｍｓ、６０Ｈｚの時は０.２ｍｓ以下の範囲とすることを特徴とする直流電源装置。 2. The direct current power supply device according to claim 1 , wherein the switching control means sets the third and subsequent short-circuit times in a range of 0.25 ms when the power frequency is 50 Hz and 0.2 ms or less when the power frequency is 60 Hz. DC power supply. 請求項１に記載の直流電源装置において、前記スイッチング手段の短絡回数をＭ回からＭ＋１回に増加させる時に、短絡回数増加後のＭ回目までの短絡時間の合計値を、短絡回数増加前の短絡時間の合計値より、減少させることを特徴とする直流電源装置。 2. The DC power supply device according to claim 1 , wherein when the number of short circuits of the switching means is increased from M times to M + 1 times, the total value of short circuit times up to M times after the number of short circuits is increased is calculated as a short circuit before the number of short circuits is increased. A direct current power supply device, characterized by being reduced from a total value of time. 請求項１に記載の直流電源装置において、前記スイッチング手段の短絡回数をＭ回からＭ＋１回に増加させる時に、Ｍ＋１回目までの短絡時間の合計値を、短絡回数増加前のＭ回目までの短絡時間の合計値と等しくすることを特徴とする直流電源装置。 2. The DC power supply device according to claim 1 , wherein when the number of short circuits of the switching means is increased from M times to M + 1 times, a total value of short circuit times up to M + 1 times is calculated as a short circuit time up to M times before the number of short circuits is increased. DC power supply device characterized by being equal to the total value of 請求項１に記載の直流電源装置において、前記スイッチング手段の短絡回数をＭ回からＭ−１回に減少させる時に、短絡回数減少後の短絡時間の合計値を、短絡回数減少前のＭ−１回目までの短絡時間の合計値より、増加させることを特徴とする直流電源装置。 2. The DC power supply device according to claim 1 , wherein when the number of short circuits of the switching unit is decreased from M times to M−1 times, the total value of the short circuit times after the number of short circuits is decreased is set to M−1 before the number of short circuits is decreased. A DC power supply device characterized in that the DC power supply device is increased from the total value of short-circuiting time until the first time. 請求項１に記載の直流電源装置において、前記スイッチング手段の短絡回数をＭ回からＭ−１回に減少させる時に、短絡回数減少後の短絡時間の合計値を、短絡回数減少前のＭ回目までの短絡時間の合計値と等しくすることを特徴とする直流電源装置。 2. The DC power supply device according to claim 1 , wherein when the number of short circuits of the switching means is decreased from M times to M−1 times, the total value of the short circuit time after the number of short circuits is decreased to the Mth before the number of short circuits is decreased. A direct current power supply device characterized in that it is equal to the total value of the short-circuiting times. 請求項２に記載の直流電源装置において、前記交流電源からの入力電流を検出する入力電流検出手段を更に備え、
前記スイッチング制御手段は前記スイッチング手段の２〜６回までの短絡回数を前記比の値と前記入力電流検出手段で検出した入力電流に応じて定めることを特徴とする直流電源装置。 The direct current power supply device according to claim 2 , further comprising an input current detection means for detecting an input current from the alternating current power supply,
The DC power supply device according to claim 1, wherein the switching control means determines the number of short-circuits of the switching means from 2 to 6 times according to the value of the ratio and the input current detected by the input current detecting means. 請求項２に記載の直流電源装置において、前記直流電力に接続された負荷量を検出する負荷量検出手段を更に備え、
前記スイッチング制御手段は前記スイッチング手段の２〜６回までの短絡回数を前記比の値と前記負荷量検出手段で検出された負荷量に応じて定めることを特徴とする直流電源装置。 The DC power supply device according to claim 2, further comprising load amount detection means for detecting a load amount connected to the DC power,
The DC power supply device according to claim 1, wherein the switching control means determines the number of short-circuits of the switching means from 2 to 6 times according to the value of the ratio and the load amount detected by the load amount detection means. 請求項８に記載の直流電源装置において、前記直流電力に接続される負荷をモータとし、前記負荷量を前記モータへの印加電圧とし、前記負荷量検出手段としてモータへの印加電圧を検出するモータ印加電圧検出手段を備え、
前記スイッチング制御手段は前記スイッチング手段の２〜６回までの短絡回数を前記比の値と前記モータ印加電圧検出手段で検出されたモータ印加電圧に応じて定めることを特徴とする直流電源装置。 9. The DC power supply apparatus according to claim 8 , wherein the load connected to the DC power is a motor, the load amount is an applied voltage to the motor, and the load amount detecting means detects a voltage applied to the motor. An applied voltage detecting means;
The DC power supply apparatus according to claim 1, wherein the switching control means determines the number of short-circuits of the switching means from 2 to 6 times according to the value of the ratio and the motor applied voltage detected by the motor applied voltage detecting means. 請求項８に記載の直流電源装置において、前記直流電力に接続される負荷をモータとし、前記負荷量を前記モータの回転数として、前記負荷量検出手段としてモータの回転数を検出するモータ回転数検出手段を備え、
前記スイッチング制御手段は前記スイッチング手段の２〜６回までの短絡回数を前記比の値と前記モータ回転数検出手段で検出されたモータ回転数に応じて定めることを特徴とする直流電源装置。 9. The DC power supply apparatus according to claim 8 , wherein the load connected to the DC power is a motor, the load amount is the rotation number of the motor, and the rotation amount of the motor is detected as the load amount detection means. A detection means,
The DC power supply apparatus according to claim 1, wherein the switching control means determines the number of short-circuits from 2 to 6 times of the switching means according to the value of the ratio and the motor rotation speed detected by the motor rotation speed detection means. 回転数制御型圧縮機を搭載した空気調和機において、請求項１乃至請求項１０の何れかに記載の直流電源装置を用いることを特徴とする空気調和機。 In mounted air conditioner controls the rotational speed compressor, air conditioner, which comprises using a DC power supply device according to any one of claims 1 to 10.
JP2009254541A 2009-11-06 2009-11-06 DC power supply device and air conditioner using the same Active JP5481165B2 (en)

Priority Applications (3)

Application Number Priority Date Filing Date Title
JP2009254541A JP5481165B2 (en) 2009-11-06 2009-11-06 DC power supply device and air conditioner using the same
KR1020100077235A KR101194483B1 (en) 2009-11-06 2010-08-11 Direct current power supply apparatus and air conditioner using the same
CN201010260619.8A CN102055350B (en) 2009-11-06 2010-08-20 DC power supply device and air-conditioner using the same

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
JP2009254541A JP5481165B2 (en) 2009-11-06 2009-11-06 DC power supply device and air conditioner using the same

Publications (2)

Publication Number Publication Date
JP2011101505A JP2011101505A (en) 2011-05-19
JP5481165B2 true JP5481165B2 (en) 2014-04-23

Family

ID=43959384

Family Applications (1)

Application Number Title Priority Date Filing Date
JP2009254541A Active JP5481165B2 (en) 2009-11-06 2009-11-06 DC power supply device and air conditioner using the same

Country Status (3)

Country Link
JP (1) JP5481165B2 (en)
KR (1) KR101194483B1 (en)
CN (1) CN102055350B (en)

Families Citing this family (21)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN103973134B (en) * 2013-01-30 2016-09-07 广东美的制冷设备有限公司 Continuous-current plant and improve the pwm pulse control method of its power factor
JP6279080B2 (en) 2014-07-08 2018-02-14 三菱電機株式会社 Power converter
MY176338A (en) * 2014-07-18 2020-07-29 Daikin Ind Ltd Direct ac power converter
JP6400103B2 (en) 2014-08-05 2018-10-03 三菱電機株式会社 Power converter
EP3200336B1 (en) 2014-09-26 2023-10-04 Mitsubishi Electric Corporation Power conversion device
US9866140B2 (en) 2014-09-30 2018-01-09 Mitsubishi Electric Corporation AC/DC power converting apparatus with AC source shortcircuiting for power factor correction and harmonic suppression
JP6410834B2 (en) * 2014-09-30 2018-10-24 三菱電機株式会社 Power converter
JP6478881B2 (en) * 2015-09-07 2019-03-06 日立ジョンソンコントロールズ空調株式会社 DC power supply and air conditioner
JP6482994B2 (en) * 2015-09-08 2019-03-13 日立ジョンソンコントロールズ空調株式会社 Power converter and air conditioner
JP6712104B2 (en) * 2015-09-10 2020-06-17 日立ジョンソンコントロールズ空調株式会社 DC power supply and air conditioner
JP6959400B2 (en) * 2015-09-10 2021-11-02 日立ジョンソンコントロールズ空調株式会社 DC power supply and air conditioner
JP6403909B2 (en) * 2016-01-28 2018-10-10 三菱電機株式会社 Power converter
CN108418414A (en) * 2018-03-26 2018-08-17 广汽丰田汽车有限公司 Circuit of power factor correction, device and method
JP6506447B2 (en) * 2018-05-14 2019-04-24 東芝キヤリア株式会社 Motor drive
KR102087205B1 (en) * 2018-07-02 2020-03-11 (주)에이엠케이 The brushless dc motor with the controller of power factor correction
WO2020261496A1 (en) * 2019-06-27 2020-12-30 オムロン株式会社 Power conversion device
CN110618308B (en) * 2019-10-18 2021-11-09 Tcl空调器(中山)有限公司 Single-phase alternating-current voltage zero point detection method and device
EP4111581A4 (en) 2020-02-28 2023-10-11 Astec International Limited Power measurements in switched mode power supplies
JP7304471B2 (en) * 2020-05-28 2023-07-06 日立ジョンソンコントロールズ空調株式会社 DC power supply and air conditioner
JP7152578B2 (en) * 2020-05-28 2022-10-12 日立ジョンソンコントロールズ空調株式会社 DC power supply and air conditioner
CN113266931B (en) * 2021-05-21 2023-05-02 Tcl空调器(中山)有限公司 Variable frequency control method and system of air conditioner and air conditioner

Family Cites Families (14)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2809463B2 (en) 1990-02-02 1998-10-08 株式会社日立製作所 Power supply and power factor improvement method
JP3578874B2 (en) * 1996-08-30 2004-10-20 東芝キヤリア株式会社 Power supply and power supply for air conditioner
JP3550485B2 (en) 1997-06-27 2004-08-04 東芝キヤリア株式会社 DC power supply and air conditioner
JPH1198842A (en) 1997-07-24 1999-04-09 Toshiba Corp Dc power source apparatus, drive apparatus for motor, air-conditioner and refrigeration cycle apparatus
KR100323931B1 (en) * 1997-08-07 2002-08-08 가부시끼가이샤 도시바 Motor control unit and air conditioner using this control unit
JP3774298B2 (en) * 1997-08-07 2006-05-10 東芝キヤリア株式会社 Electric motor control device and refrigeration cycle device
JP2000217363A (en) * 1999-01-22 2000-08-04 Toshiba Corp Power supply device
JP3485047B2 (en) * 1999-11-24 2004-01-13 三菱電機株式会社 Air conditioner
JP4337316B2 (en) * 2001-09-28 2009-09-30 ダイキン工業株式会社 Power converter
JP2005245167A (en) * 2004-02-27 2005-09-08 Matsushita Electric Ind Co Ltd Dc power supply unit
JP4784207B2 (en) * 2004-11-18 2011-10-05 パナソニック株式会社 DC power supply
JP4841303B2 (en) * 2006-05-02 2011-12-21 東芝キヤリア株式会社 DC power supply
JP5073439B2 (en) 2007-10-15 2012-11-14 シャープ株式会社 DC power supply
JP2009261143A (en) * 2008-04-17 2009-11-05 Panasonic Corp Power supply apparatus and air conditioner equipped with the same

Also Published As

Publication number Publication date
CN102055350B (en) 2014-04-02
JP2011101505A (en) 2011-05-19
CN102055350A (en) 2011-05-11
KR20110050349A (en) 2011-05-13
KR101194483B1 (en) 2012-10-24

Similar Documents

Publication Publication Date Title
JP5481165B2 (en) DC power supply device and air conditioner using the same
AU2014203525B2 (en) Converter circuit and motor drive control apparatus, air-conditioner, refrigerator, and induction heating cooker provided with the circuit
JP5520119B2 (en) DC power supply device, inverter drive device, and air conditioner using the same
USRE39060E1 (en) Power supply device and air conditioner using the same
RU2175462C2 (en) Energy conversion device and conditioner using this device
JP3955285B2 (en) Inverter control device for motor drive and air conditioner
WO2016047019A1 (en) Power conversion device
JP2013106455A (en) Dc power-supply device and air conditioner using the same
JP4033628B2 (en) Power supply device and air conditioner using the power supply device
AU2013204591A1 (en) Methods and systems for controlling an electric motor
JPS60249895A (en) Frequency converter
JP2004320981A (en) Inverter control device for driving motor and air conditioner
JP2011069538A (en) Air conditioner
JP4157619B2 (en) Air conditioner
JP2001342989A (en) Method of driving and controlling dc pump
JPH10155297A (en) Inverter controlling device for air conditioner
JP2005337519A5 (en)
JP3966635B2 (en) Power supply
JPH11356051A (en) Power supply equipment and air conditioner using the same
CN111082468B (en) Power control method for standby power mode of electric equipment and electric equipment
JP5593214B2 (en) Air conditioner
JP4722541B2 (en) Power supply device and air conditioner using the same
JP6482994B2 (en) Power converter and air conditioner
JP2016144323A (en) Dc power supply device and air-conditioner using the same
JPH07190464A (en) Control method of air conditioner driven by solar cell

Legal Events

Date Code Title Description
A621 Written request for application examination

Free format text: JAPANESE INTERMEDIATE CODE: A621

Effective date: 20111130

A521 Written amendment

Free format text: JAPANESE INTERMEDIATE CODE: A523

Effective date: 20111130

A977 Report on retrieval

Free format text: JAPANESE INTERMEDIATE CODE: A971007

Effective date: 20130213

A131 Notification of reasons for refusal

Free format text: JAPANESE INTERMEDIATE CODE: A131

Effective date: 20130219

A521 Written amendment

Free format text: JAPANESE INTERMEDIATE CODE: A523

Effective date: 20130419

A131 Notification of reasons for refusal

Free format text: JAPANESE INTERMEDIATE CODE: A131

Effective date: 20131022

A521 Written amendment

Free format text: JAPANESE INTERMEDIATE CODE: A523

Effective date: 20131218

TRDD Decision of grant or rejection written
A01 Written decision to grant a patent or to grant a registration (utility model)

Free format text: JAPANESE INTERMEDIATE CODE: A01

Effective date: 20140121

A61 First payment of annual fees (during grant procedure)

Free format text: JAPANESE INTERMEDIATE CODE: A61

Effective date: 20140217

R150 Certificate of patent or registration of utility model

Ref document number: 5481165

Country of ref document: JP

Free format text: JAPANESE INTERMEDIATE CODE: R150

S111 Request for change of ownership or part of ownership

Free format text: JAPANESE INTERMEDIATE CODE: R313113

S531 Written request for registration of change of domicile

Free format text: JAPANESE INTERMEDIATE CODE: R313531

R350 Written notification of registration of transfer

Free format text: JAPANESE INTERMEDIATE CODE: R350

R250 Receipt of annual fees

Free format text: JAPANESE INTERMEDIATE CODE: R250

R250 Receipt of annual fees

Free format text: JAPANESE INTERMEDIATE CODE: R250

S111 Request for change of ownership or part of ownership

Free format text: JAPANESE INTERMEDIATE CODE: R313113

R350 Written notification of registration of transfer

Free format text: JAPANESE INTERMEDIATE CODE: R350

R250 Receipt of annual fees

Free format text: JAPANESE INTERMEDIATE CODE: R250

R250 Receipt of annual fees

Free format text: JAPANESE INTERMEDIATE CODE: R250