JP2003169473A - Dc power supply unit - Google Patents
Dc power supply unitInfo
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- JP2003169473A JP2003169473A JP2001366589A JP2001366589A JP2003169473A JP 2003169473 A JP2003169473 A JP 2003169473A JP 2001366589 A JP2001366589 A JP 2001366589A JP 2001366589 A JP2001366589 A JP 2001366589A JP 2003169473 A JP2003169473 A JP 2003169473A
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- Prior art keywords
- switch element
- series
- circuit
- power supply
- transformer
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Abstract
Description
【０００１】[0001]
【発明の属する技術分野】本発明は、スイッチング電源
装置に関するもので、特に定電力出力を給電する直流電
源装置及びその出力電力制御に関するものである。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a switching power supply device, and more particularly to a DC power supply device for supplying a constant power output and its output power control.
【０００２】[0002]
【従来の技術】成膜装置等の電源装置には、従来、図７
に示すような回路構成のスイッチング電源を使用してい
る。図７において、Q1〜Q4はスイッチ素子で、4個でフ
ルブリッジを形成し、T1はトランス、D1〜4はトランス
出力の整流ダイオード、Lは出力チョークコイル。Cは平
滑用コンデンサ。Rは負荷である。Vinは入力電圧源であ
る。2. Description of the Related Art Conventionally, a power supply device such as a film forming apparatus is shown in FIG.
A switching power supply having a circuit configuration as shown in is used. In FIG. 7, Q1 to Q4 are switching elements, four of which form a full bridge, T1 is a transformer, D1 to 4 are transformer output rectifying diodes, and L is an output choke coil. C is a smoothing capacitor. R is the load. Vin is the input voltage source.
【０００３】 成膜装置の電源を制御するには、成膜を
均一に行う必要があるため、定電力制御が必要であり、
従って電源装置の出力特性は、図９に示すような特性に
なる。図９でVoは電源装置の出力電圧、Ioは出力電流で
ある。V1とI2は夫々最大出力電圧と最大出力電流であ
る。V2とI1は夫々定電力特性の両端に位置する出力電圧
と出力電流である。従って、A,B間が定電力範囲であ
る。図９において、例えばV1＝500V、I2＝40Aとする
と、電源装置の出力容量は20kW（V1×I2）となるが、実
際には定電力制御を行っているため、この装置の最大出
力はI1×V1(＝I2×V2)で、I1＝20A、V2＝250Vとする
と、10kWとなる。In order to control the power supply of the film forming apparatus, it is necessary to perform film formation uniformly, so constant power control is necessary.
Therefore, the output characteristic of the power supply device becomes the characteristic shown in FIG. In FIG. 9, Vo is the output voltage of the power supply device, and Io is the output current. V1 and I2 are the maximum output voltage and the maximum output current, respectively. V2 and I1 are the output voltage and output current located at both ends of the constant power characteristic, respectively. Therefore, the constant power range is between A and B. In FIG. 9, for example, if V1 = 500V and I2 = 40A, the output capacity of the power supply device is 20kW (V1 × I2), but since the constant power control is actually performed, the maximum output of this device is I1. With × V1 (= I2 × V2) and I1 = 20A and V2 = 250V, it becomes 10kW.
【０００４】 従って出力トランスは、20kWの容量をも
ちながら10kWで使われてるにすぎず、利用率が悪い。一
方、スイッチ素子Q1〜Q4がフルブリッジに構成され、一
定周期T(図８)で良く知られているパルス巾制御(PWM)を
行っている。図８において(a)〜(d)の波形はQ1〜Q4のゲ
ート信号を示し、フルブリッジの出力(トランスの一次
入力)は、(e)の波形で示されるパルス巾tのパルス出力
になる。定電力出力のため、電源装置出力電流が最大値
になるときは、出力電圧が低くなり、従ってパルス巾も
小さくなるため、この電圧を整流して（波形（ｆ））平
滑するときに、平滑用フィルタが大きくなる。上記のよ
うに、従来の制御方式ではトランスの利用率が低く、フ
ィルタが大きくなる等の欠点があった。又、定電力出力
時にはパルス巾が小さいため、スイッチング変換部、出
力トランスの一次側巻き線等の実効値電流の増加によ
り、出力トランス、スイッチ素子等で発生する損失も増
加し、放熱用フィンが大きくなり小型化への障害とな
る。Therefore, the output transformer has a capacity of 20 kW and is only used at 10 kW, so that the utilization rate is poor. On the other hand, the switch elements Q1 to Q4 are configured as a full bridge and perform well-known pulse width control (PWM) with a constant period T (FIG. 8). In FIG. 8, the waveforms (a) to (d) show the gate signals of Q1 to Q4, and the output of the full bridge (the primary input of the transformer) becomes the pulse output of the pulse width t shown in the waveform of (e). . Because of the constant power output, when the output current of the power supply device reaches the maximum value, the output voltage becomes low and therefore the pulse width also becomes small. Therefore, when this voltage is rectified (waveform (f)) and smoothed, Filter becomes larger. As described above, the conventional control method has drawbacks such as a low transformer utilization rate and a large filter. In addition, since the pulse width is small during constant power output, the loss generated in the output transformer, switch element, etc. also increases due to an increase in the effective value current of the switching converter, primary winding of the output transformer, etc. It becomes large and becomes an obstacle to miniaturization.
【０００５】[0005]
【発明が解決しようとする課題】 本発明は、上記のよ
うな欠点を改善するためのもので、トランスの利用率を
高め、出力電圧のリップル分の発生要因を低減し、トラ
ンスや平滑フィルタの小型化、スイッチ素子の定電力出
力時の損失低減を図り、さらには電源装置の小型化を可
能とする電源装置を提供するものである。DISCLOSURE OF THE INVENTION The present invention is intended to improve the above-mentioned drawbacks, and enhances the utilization factor of a transformer, reduces the factors causing the ripple component of the output voltage, and improves the transformer and smoothing filter. (EN) Provided is a power supply device capable of downsizing, reduction of loss of a switch element at constant power output, and further downsizing of a power supply device.
【０００６】[0006]
【課題を解決するための手段】上記の課題を解決するた
め、本発明は、第一のスイッチ素子と第二のスイッチ素
子を直列に接続した第一の直列回路と、第三のスイッチ
素子と第四のスイッチ素子を直列に接続した第二の直列
回路と、第五のスイッチ素子と第六のスイッチ素子を直
列に接続した第三の直列回路とを夫々並列に接続し、前
記第一のスイッチ素子、前記第三のスイッチ素子、前記
第五のスイッチ素子の一端を入力電源プラス端子に直列
に接続し、前記第二のスイッチ素子、前記第四のスイッ
チ素子、前記第六のスイッチ素子の一端を入力電源マイ
ナス端子に直列に接続し、前記第一の直列回路を構成す
る前記第一のスイッチ素子他端と前記第二のスイッチ素
子他端の接続点を、第一のトランスの一次巻線の一端に
接続し、前記第二の直列回路の接続点を第二のトランス
の一次巻線の一端に接続し、前記第一のトランスの一次
巻線の他端と、前記第二のトランスの一次巻線の他端を
共通に接続して前記第三の直列回路の接続点に接続し、
前記第一及び第二のトランスの二次巻線の夫々の一端を
６ヶのダイオードで構成されるダイオードブリッジ整流
回路の交流入力端子に夫々接続し、前記第一及び第二の
トランスの二次巻線の他端を共通に接続して前記ダイオ
ードブリッジ整流回路の残りの交流入力端子に接続し、
前記ダイオードブリッジ整流回路の出力端子にリアクト
ル素子とコンデンサ素子で構成される平滑回路を接続し
たことを特徴とする。又、制御法として前記第一の直列
回路を構成する前記第一及び第二のスイッチ素子は、固
定したオン幅で交互に駆動し、同様に前記第二の直列回
路を構成する前記第三及び第四のスイッチ素子も、固定
したオン幅で交互に駆動し、前記第一の直列回路と前記
第二の直列回路を構成するスイッチ素子の位相差を変化
させ制御し、前記第一のスイッチ素子と前記第三のスイ
ッチ素子が同時にオンする時に、前記第六のスイッチ素
子をオンし、前記第二のスイッチ素子と前記第四のスイ
ッチ素子が同時にオンする時に、前記第五のスイッチ素
子をオンすることを特徴とする。In order to solve the above problems, the present invention provides a first series circuit in which a first switch element and a second switch element are connected in series, and a third switch element. A second series circuit in which a fourth switch element is connected in series and a third series circuit in which a fifth switch element and a sixth switch element are connected in series are connected in parallel, respectively, and the first One end of the switch element, the third switch element, and the fifth switch element is connected in series to the input power source positive terminal, and the second switch element, the fourth switch element, and the sixth switch element One end of the first transformer is connected to the negative terminal of the input power source in series, and the connection point between the other end of the first switch element and the other end of the second switch element that constitutes the first series circuit is connected to the primary winding of the first transformer. Connect to one end of the wire, the second The connection point of the series circuit is connected to one end of the primary winding of the second transformer, and the other end of the primary winding of the first transformer and the other end of the primary winding of the second transformer are commonly connected. Then connect to the connection point of the third series circuit,
One end of each of the secondary windings of the first and second transformers is connected to an AC input terminal of a diode bridge rectifier circuit composed of six diodes, respectively, and the secondary windings of the first and second transformers are connected. The other end of the winding is connected in common and connected to the remaining AC input terminals of the diode bridge rectifier circuit,
A smoothing circuit composed of a reactor element and a capacitor element is connected to an output terminal of the diode bridge rectifying circuit. Further, as a control method, the first and second switch elements that configure the first series circuit are alternately driven with a fixed ON width, and the third and second switch elements that similarly configure the second series circuit. The fourth switch element is also driven alternately with a fixed ON width, and the phase difference between the switch elements that form the first series circuit and the second series circuit is changed and controlled to control the first switch element. When the third switch element and the third switch element are simultaneously turned on, the sixth switch element is turned on, and when the second switch element and the fourth switch element are simultaneously turned on, the fifth switch element is turned on. It is characterized by doing.
【０００７】[0007]
【発明の実施の態様】 図1は、本発明の実施例を示す
回路図で、Q1〜Q6はスイッチ素子である。T1、T2は、ト
ランスで巻数比1：nの関係に巻装されている。DはD1〜D
6のダイオードで構成されるダイオードブリッジ整流回
路。Lは出力チョークコイル。Cは平滑用コンデンサ。R
は負荷である。Vinは入力電圧源である。次に、CONTは
制御回路で、負荷Rの電圧信号Vo_sig及び電流信号IL_si
gを制御要素として、各スイッチQ1〜Q6に制御信号を送
出する。BEST MODE FOR CARRYING OUT THE INVENTION FIG. 1 is a circuit diagram showing an embodiment of the present invention, in which Q1 to Q6 are switch elements. T1 and T2 are wound by a transformer in a winding ratio of 1: n. D is D1-D
Diode bridge rectifier circuit consisting of 6 diodes. L is the output choke coil. C is a smoothing capacitor. R
Is the load. Vin is the input voltage source. Next, CONT is a control circuit that controls the voltage signal Vo_sig and the current signal IL_si of the load R.
Control signals are sent to the switches Q1 to Q6 by using g as a control element.
【０００８】 この回路の基本動作は、スイッチ素子Q1
とQ2は固定したオン幅で交互にオン、オフ動作を行う。
同様にスイッチ素子Q3とQ4においても固定したオン幅で
交互にオン、オフ動作を行う。そして、スイッチ素子Q
1、Q2を固定して、スイッチ素子Q3、Q4の位相を可変
し、スイッチ素子Q1とQ3がオン時にはQ6、Q2とQ4がオン
時にはQ5をオンするように駆動信号を与え、スイッチ素
子Q1、Q2とスイッチ素子Q3、Q4の位相差を制御して所望
の出力電圧の安定化を行う。The basic operation of this circuit is the switching element Q1
And Q2 alternately turn on and off with a fixed on width.
Similarly, the switch elements Q3 and Q4 are alternately turned on and off with a fixed on width. And the switching element Q
1 and Q2 are fixed, the phase of the switch elements Q3 and Q4 is changed, a drive signal is given to turn on Q6 when the switch elements Q1 and Q3 are on, and Q5 when Q2 and Q4 are on, and the switch element Q1, The desired output voltage is stabilized by controlling the phase difference between Q2 and the switching elements Q3 and Q4.
【０００９】 以下、本発明実施例回路の動作について
詳述する。図2は、本発明実施例回路の各部動作波形
図、図3〜6は動作説明用の等価回路である。The operation of the circuit according to the embodiment of the present invention will be described in detail below. FIG. 2 is an operation waveform diagram of each part of the circuit of the embodiment of the present invention, and FIGS. 3 to 6 are equivalent circuits for explaining the operation.
【００１０】動作モード1(図2 時間t0〜t1)
動作モード1の等価回路を図3に示す。この状態はスイッ
チ素子Q1、Q3及びQ6が、図2で示すゲート信号が与えら
れオンしているため、夫々のトランスT1、T2の2次巻線
には図３にて矢印で示す方向にnVinが現れ、ダイオード
D1とD6が導通する。従って、整流回路Dの出力電圧VD
は、トランスT1、T2の出力が直列接続となるため2nVin
となり、出力チョークLには2nVin−Voの電圧が印加さ
れ、出力チョーク電流ILは図３にて示す矢印の向きを正
として、増加する方向に流れる。Operation Mode 1 (Time t0 to t1 in FIG. 2) An equivalent circuit of the operation mode 1 is shown in FIG. In this state, the switching elements Q1, Q3, and Q6 are turned on by the gate signal shown in FIG. 2, so that the secondary windings of the transformers T1 and T2 have nVin in the direction shown by the arrow in FIG. Appears, diode
D1 and D6 conduct. Therefore, the output voltage VD of the rectifier circuit D
Is 2nVin because the outputs of transformers T1 and T2 are connected in series.
Therefore, a voltage of 2nVin-Vo is applied to the output choke L, and the output choke current IL flows in the increasing direction with the direction of the arrow shown in FIG. 3 being positive.
【００１１】動作モード2(時間t1〜t2)
モード2の等価回路を図4に示す。この状態はスイッチ素
子Q1とQ4がオンしているため、夫々のトランスT1、T2の
1次巻線は直列につながり、2次巻線には図4にて示す矢
印方向にnVin/2が現れ、ダイオードD1とD4及びD5が導通
する。従って、整流回路9の出力電圧VDは、夫々のトラ
ンスT1、T2の出力を並列接続となるためnVin/2となり、
出力チョークLには、Vo−nVin/2の電圧が印加され、出
力チョーク電流ILは図4にて示す矢印の向きを正とし
て、減少する方向に流れる。Operation Mode 2 (Time t1 to t2) An equivalent circuit of Mode 2 is shown in FIG. In this state, since the switching elements Q1 and Q4 are on, the transformers T1 and T2 are
The primary winding is connected in series, nVin / 2 appears in the secondary winding in the direction of the arrow shown in FIG. 4, and the diodes D1, D4, and D5 conduct. Therefore, the output voltage VD of the rectifier circuit 9 becomes nVin / 2 because the outputs of the respective transformers T1 and T2 are connected in parallel,
A voltage of Vo−nVin / 2 is applied to the output choke L, and the output choke current IL flows in a decreasing direction with the direction of the arrow shown in FIG. 4 being positive.
【００１２】 モード3(t2〜t3)、モード4(t3〜t0)等価
回路を図5、図6に示す。この各モードの動作は、上記と
同様な動作を繰り返し行うため省略する。Equivalent circuits of mode 3 (t2 to t3) and mode 4 (t3 to t0) are shown in FIGS. The operation in each mode is omitted because the same operation as described above is repeated.
【００１３】 以上、本発明は、スイッチ素子に上記説
明の通りゲート信号を与えることで、2台のトランスの
二次側出力が並列及び直列に接続するモードが存在し、
その比を制御することで所望の直流出力電圧Voを得て、
定電圧及び定電力出力を給電する。因みに図1におい
て、制御回路CONTは電源装置の出力電圧検出信号Vo_sig
及び電流信号IL_sigを制御要素として、スイッチ素子Q
1、Q2にはスイッチング周期Tsで位相の固定されたゲー
ト信号が与えられ、スイッチ素子Q3、Q4にはスイッチン
グ周期Tsで且つ上記に比し一定位相遅れた(M・TS)ゲー
ト信号が与えられ、又、スイッチ素子Q1とQ3がオン時に
はQ6、Q2とQ4がオン時にはQ5をオンするように駆動信号
を与え、スイッチ素子Q1、Q2及びスイッチ素子Q3、Q4の
位相差を利用して定電圧及び定電力運転する。As described above, the present invention has a mode in which the secondary outputs of two transformers are connected in parallel and in series by applying the gate signal to the switch element as described above.
Obtaining the desired DC output voltage Vo by controlling the ratio,
Supply constant voltage and constant power output. Incidentally, in FIG. 1, the control circuit CONT is the output voltage detection signal Vo_sig of the power supply device.
And the current signal IL_sig as a control element, the switching element Q
1, Q2 is given a gate signal whose phase is fixed in the switching cycle Ts, and switch elements Q3, Q4 are given a gate signal in the switching cycle Ts and with a constant phase delay compared to the above (MTS). Moreover, when the switching elements Q1 and Q3 are turned on, a drive signal is given so that Q6 is turned on when Q2 and Q4 are turned on, and a constant voltage is applied by using the phase difference between the switching elements Q1, Q2 and the switching elements Q3, Q4. And operate at constant power.
【００１４】次に、図1において入力電圧Vinと出力電圧
Voの電圧変換比率は、以下により求められる。先ず、ス
イッチング周期をTs、トランスT1、T2の夫々1次、2次巻
数比を１：ｎ、スイッチ素子Q1と4の位相差をφ(時間領
域に変換すると、φ＝M・Ts、但し、Mはディレイ係数)
とする。モード1のチョーク電流IL(チョーク電流)の増
加方向への変化量(ΔIL)は、Next, referring to FIG. 1, the input voltage Vin and the output voltage
The Vo voltage conversion ratio is obtained by the following. First, the switching cycle is Ts, the primary and secondary turns ratios of the transformers T1 and T2 are 1: n, and the phase difference between the switch elements Q1 and 4 is φ (converted to the time domain, φ = M · Ts, where (M is the delay coefficient)
And The amount of change (ΔIL) in the increasing direction of the choke current IL (choke current) in mode 1 is
【数１】 [Equation 1]
【００１５】モード2のチョーク電流ILの減少方向への
変化量(ΔIL')は、The change amount (ΔIL ') of the choke current IL in mode 2 in the decreasing direction is
【数２】 [Equation 2]
【００１６】定常状態では(3)式を満たす。Equation (3) is satisfied in the steady state.
【数３】 [Equation 3]
【００１７】従って、Therefore,
【数４】 [Equation 4]
【００１８】(4)式を整理すると、Organizing equation (4),
【数５】 [Equation 5]
【００１９】ここで、0≦M≦１より、Here, from 0 ≦ M ≦ 1,
【数６】
となり、この範囲で入力電圧Vinと出力電圧Voの関係を
制御できる。従って、図９に示す出力特性を要求される
電源装置では、上記制御方法により出力電圧制御を可能
とする。[Equation 6] Thus, the relationship between the input voltage Vin and the output voltage Vo can be controlled within this range. Therefore, in the power supply device required to have the output characteristics shown in FIG. 9, the output voltage can be controlled by the above control method.
【００２０】なお、図2において、(h)はチョーク電流波
形、(i)、(j)、(k)はスイッチ素子Q1、Q3、Q5の電流波
形、(l)、(m)、(n)はダイオードD1、D3、D5の電流波形
を示す。In FIG. 2, (h) is the choke current waveform, (i), (j) and (k) are the current waveforms of the switching elements Q1, Q3 and Q5, (l), (m) and (n). ) Indicates the current waveform of the diodes D1, D3, D5.
【００２１】[0021]
【発明の効果】上記の説明のように、二台のトランスの
二次側電圧を直列及び並列に接続するモードを有して、
その比を制御することで出力電圧制御を行わせることに
より、夫々の回路の部品、特にトランスは自己の持つ容
量を100%利用でき、その利用率の高さからトランスの小
型化ができ、又、出力波形の変化分が少ないことから、
出力フィルタを小型化でき、定電力出力時においても各
スイッチ素子のパルス幅を固定のままで小さくする必要
が無く一次側実効値電流の増加を防ぎ、スイッチ素子の
損失の低減により放熱フィンの小型化が可能となった。
電源装置の構成において、比較的大きさと重量の比率の
大きいこれらの部品の小型化により、電源装置の小型化
ができる。As described above, with the mode in which the secondary side voltages of two transformers are connected in series and in parallel,
By controlling the output voltage by controlling the ratio, each circuit component, especially the transformer, can utilize 100% of its own capacity, and the transformer can be downsized due to its high utilization rate. Since there is little change in the output waveform,
The output filter can be miniaturized, and the pulse width of each switch element does not need to be fixed and reduced even at the time of constant power output, preventing the primary side effective value current from increasing and reducing the loss of the switch element to reduce the size of the radiation fin. Became possible.
In the configuration of the power supply device, the size of the power supply device can be reduced by reducing the size of these components having a relatively large size-weight ratio.
【図１】 本発明の実施例回路図FIG. 1 is a circuit diagram of an embodiment of the present invention.
【図２】 本発明実施例の動作波形図FIG. 2 is an operation waveform diagram of the embodiment of the present invention.
【図３】 本発明の動作説明用の等価回路FIG. 3 is an equivalent circuit for explaining the operation of the present invention.
【図４】 本発明の動作説明用の等価回路FIG. 4 is an equivalent circuit for explaining the operation of the present invention.
【図５】 本発明の動作説明用の等価回路FIG. 5 is an equivalent circuit for explaining the operation of the present invention.
【図６】 本発明の動作説明用の等価回路FIG. 6 is an equivalent circuit for explaining the operation of the present invention.
【図７】 従来例FIG. 7 Conventional example
【図８】 従来例の各部動作波形図FIG. 8 is an operation waveform diagram of each part of a conventional example
【図９】 定電力装置の出力特性図FIG. 9: Output characteristic diagram of constant power device
Q1〜Q6・・・・・・スイッチ素子 T1,T2・・・・・・・・・・・トランス D・・・・・・・整流回路 D1〜D6・・・・・・・ダイオード L・・・・・・・・・・・・・・・出力チョークコイル C・・・・・・・・・・・・・・平滑用コンデンサ R・・・・・・・・・・・・・・負荷 CONT・・・・・・・・・・制御回路 Vin・・・・・・・・・・入力電圧源 Vo_sig・・・・・・・・・・出力電圧信号 IL_sig・・・・・・・・・・電流信号 Q1 to Q6 ・ ・ ・ ・ ・ ・ Switch element T1, T2 ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ Transformer D ... Rectifier circuit D1-D6 ... Diode L: Output choke coil C ・ ・ ・ ・ ・ ・ ・ ・ ・ Smoothing capacitor R ... CONT: Control circuit Vin: Input voltage source Vo_sig ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ Output voltage signal IL_sig ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ Current signal
Claims (3)
を直列に接続した第一の直列回路と、第三のスイッチ素
子と第四のスイッチ素子を直列に接続した第二の直列回
路と、第五のスイッチ素子と第六のスイッチ素子を直列
に接続した第三の直列回路とを夫々並列に接続し、前記
第一のスイッチ素子、前記第三のスイッチ素子、前記第
五のスイッチ素子の一端を入力電源プラス端子に直列に
接続し、前記第二のスイッチ素子、前記第四のスイッチ
素子、前記第六のスイッチ素子の一端を入力電源マイナ
ス端子に直列に接続し、前記第一の直列回路を構成する
前記第一のスイッチ素子他端と前記第二のスイッチ素子
他端の接続点を、第一のトランスの一次巻線の一端に接
続し、前記第二の直列回路の接続点を第二のトランスの
一次巻線の一端に接続し、前記第一のトランスの一次巻
線の他端と、前記第二のトランスの一次巻線の他端を共
通に接続して前記第三の直列回路の接続点に接続し、前
記第一及び第二のトランスの二次巻線の夫々の一端を６
ヶのダイオードで構成されるダイオードブリッジ整流回
路の交流入力端子に夫々接続し、前記第一及び第二のト
ランスの二次巻線の他端を共通に接続して前記ダイオー
ドブリッジ整流回路の残りの交流入力端子に接続し、前
記ダイオードブリッジ整流回路の出力端子にリアクトル
素子とコンデンサ素子で構成される平滑回路を接続した
ことを特徴とする直流電源装置。1. A first series circuit in which a first switch element and a second switch element are connected in series, and a second series circuit in which a third switch element and a fourth switch element are connected in series. A fifth switch element and a sixth switch element connected in series with a third series circuit in which the first switch element, the third switch element and the fifth switch element are connected in parallel. One end of is connected in series to the positive terminal of the input power source, the second switch element, the fourth switch element, one end of the sixth switch element is connected in series to the negative terminal of the input power source, A connection point between the other end of the first switch element and the other end of the second switch element forming a series circuit is connected to one end of a primary winding of a first transformer, and a connection point of the second series circuit. At one end of the primary winding of the second transformer Next, the other end of the primary winding of the first transformer and the other end of the primary winding of the second transformer are commonly connected to the connection point of the third series circuit, Connect one end of each of the secondary windings of the first and second transformers to 6
Connected to the AC input terminals of the diode bridge rectifier circuit, and the other ends of the secondary windings of the first and second transformers are commonly connected to connect the remaining portions of the diode bridge rectifier circuit. A DC power supply device characterized in that it is connected to an AC input terminal, and a smoothing circuit composed of a reactor element and a capacitor element is connected to the output terminal of the diode bridge rectification circuit.
び第二のスイッチ素子は、固定したオン幅で交互に駆動
し、同様に前記第二の直列回路を構成する前記第三及び
第四のスイッチ素子も、固定したオン幅で交互に駆動
し、前記第一の直列回路と前記第二の直列回路を構成す
るスイッチ素子の位相差を変化させ制御することを特徴
とする請求項１記載の直流電源装置。2. The first and second switch elements constituting the first series circuit are alternately driven with a fixed ON width, and the third and second switch elements which similarly constitute the second series circuit. The fourth switch element is also driven alternately with a fixed ON width, and the phase difference between the switch elements forming the first series circuit and the second series circuit is changed and controlled. 1. The DC power supply device according to 1.
ッチ素子が同時にオンする時に、前記第六のスイッチ素
子をオンし、前記第二のスイッチ素子と前記第四のスイ
ッチ素子が同時にオンする時に、前記第五のスイッチ素
子をオンすることを特徴とする請求項１及び請求項2記
載の直流電源装置。3. The sixth switch element is turned on when the first switch element and the third switch element are turned on at the same time, and the second switch element and the fourth switch element are turned on at the same time. 3. The DC power supply device according to claim 1, wherein the fifth switch element is turned on when the DC power supply device is turned on.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2001366589A JP3743712B2 (en) | 2001-11-30 | 2001-11-30 | DC power supply |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2001366589A JP3743712B2 (en) | 2001-11-30 | 2001-11-30 | DC power supply |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JP2003169473A true JP2003169473A (en) | 2003-06-13 |
| JP3743712B2 JP3743712B2 (en) | 2006-02-08 |
Family
ID=19176463
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP2001366589A Expired - Fee Related JP3743712B2 (en) | 2001-11-30 | 2001-11-30 | DC power supply |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JP3743712B2 (en) |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| KR101594303B1 (en) * | 2014-09-24 | 2016-02-19 | 한국에너지기술연구원 | Phase-Shifted Dual Full-Bridge Converter |
Families Citing this family (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP5807667B2 (en) * | 2013-11-19 | 2015-11-10 | トヨタ自動車株式会社 | Power conversion apparatus and power correction method |
-
2001
- 2001-11-30 JP JP2001366589A patent/JP3743712B2/en not_active Expired - Fee Related
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| KR101594303B1 (en) * | 2014-09-24 | 2016-02-19 | 한국에너지기술연구원 | Phase-Shifted Dual Full-Bridge Converter |
Also Published As
| Publication number | Publication date |
|---|---|
| JP3743712B2 (en) | 2006-02-08 |
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