JP2001007882A - Orthogonal modulator, phase control method for the orthogonal demodulator and communication unit - Google Patents
Orthogonal modulator, phase control method for the orthogonal demodulator and communication unitInfo
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- JP2001007882A JP2001007882A JP11172292A JP17229299A JP2001007882A JP 2001007882 A JP2001007882 A JP 2001007882A JP 11172292 A JP11172292 A JP 11172292A JP 17229299 A JP17229299 A JP 17229299A JP 2001007882 A JP2001007882 A JP 2001007882A
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- component
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- quadrature
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Abstract
Description
【０００１】[0001]
【発明の属する技術分野】本発明は、例えば、ディジタ
ル移動通信装置に使用される最適な直交変調器および直
交復調器と、その位相誤差を校正する制御方法に関する
ものである。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to an optimum quadrature modulator and quadrature demodulator used in, for example, a digital mobile communication device, and a control method for calibrating a phase error thereof.
【０００２】[0002]
【従来の技術】ディジタル移動通信では広く線形変調方
式が採用されており、その変調および復調を行うために
直交変調器および直交復調器が用いられる。2. Description of the Related Art In digital mobile communication, a linear modulation method is widely used, and a quadrature modulator and a quadrature demodulator are used for modulation and demodulation.
【０００３】直交変調器および直交復調器を備えた通信
装置の一例を図５に示す。図５は直交変調器および直交
復調器を備えた通信装置の構成の一例を示すブロック図
である。1-1，1-2は送信側の入力端子、1-3は受信側の
入力端子、 2-1，2-2は受信側の出力端子、2-3は送信
側の出力端子、5は搬送波発振器、6-1，6-2，6-3，6-4
は乗算器、7-1，7-2は90度移相器、9は加算器、3は乗算
器6-1，6-2と90度移相器7-1と加算器9とからなる直交変
調器、4は乗算器6-3，6-4と90度移相器7-2とからなる直
交復調器である。図５において、まず送信側では、入力
端子1-1にベースバンド信号の同相成分（I成分）が入力
し、入力端子1-2にベースバンド信号の直交相成分（Q成
分）が入力され、それぞれ直交変調器3の乗算器6-1およ
び6-2に送られる。乗算器6-1および6-2には、入力信号
（I成分とQ成分）それぞれと別途に搬送波発振器5から
送られた搬送波が入力し、入力された搬送波と入力信号
のI成分またはQ成分を乗じて、それぞれ加算器9に送
る。加算器9は入力した2つの信号を加算して出力し、出
力端子2-3を介して高周波回路へ送る。このとき、搬送
波発振器5で発振した所要周波数の搬送波は乗算器6-1に
は直接入力し、乗算器6-2には90度移相器7-1を介して入
力する。90度移相器7-1は入力した搬送波の位相を90度
移相して乗算器6-2に出力する。FIG. 5 shows an example of a communication apparatus provided with a quadrature modulator and a quadrature demodulator. FIG. 5 is a block diagram illustrating an example of a configuration of a communication device including a quadrature modulator and a quadrature demodulator. 1-1 and 1-2 are input terminals on the transmitting side, 1-3 are input terminals on the receiving side, 2-1 and 2-2 are output terminals on the receiving side, 2-3 are output terminals on the transmitting side, and 5 is an output terminal on the transmitting side. Carrier oscillator, 6-1, 6-2, 6-3, 6-4
Is a multiplier, 7-1 and 7-2 are 90-degree phase shifters, 9 is an adder, and 3 is composed of multipliers 6-1 and 6-2, a 90-degree phase shifter 7-1 and an adder 9 The quadrature modulator 4 is a quadrature demodulator including multipliers 6-3 and 6-4 and a 90-degree phase shifter 7-2. In FIG. 5, first, on the transmission side, an in-phase component (I component) of a baseband signal is input to an input terminal 1-1, and a quadrature phase component (Q component) of a baseband signal is input to an input terminal 1-2. These are sent to the multipliers 6-1 and 6-2 of the quadrature modulator 3, respectively. To the multipliers 6-1 and 6-2, the input signal (I component and Q component) and the carrier wave separately sent from the carrier oscillator 5 are input, and the input carrier and the I component or Q component of the input signal are input. And send them to the adder 9 respectively. The adder 9 adds the two input signals, outputs the added signal, and sends it to the high-frequency circuit via the output terminal 2-3. At this time, the carrier of the required frequency oscillated by the carrier oscillator 5 is directly input to the multiplier 6-1 and is input to the multiplier 6-2 via the 90-degree phase shifter 7-1. The 90-degree phase shifter 7-1 shifts the phase of the input carrier by 90 degrees and outputs it to the multiplier 6-2.
【０００４】一方、受信側では、入力端子1-3から入力
された受信信号を乗算器6-3および乗算器6-4に入力す
る。乗算器6-3は入力信号と別途入力された搬送波を乗
じて出力端子2-1を介してI成分を出力する。乗算器6-4
は入力信号と別途入力された搬送波を乗じて出力端子2-
2を介してQ成分を出力する。直交復調器4には搬送波発
信器5で発振された所定周波数の搬送波が入力され、乗
算器6-3および90度移相器7-2に入力され、90度移相器7-
2は入力した搬送波の位相を90度移相して乗算器6-4に出
力する。On the other hand, on the receiving side, a received signal input from an input terminal 1-3 is input to a multiplier 6-3 and a multiplier 6-4. The multiplier 6-3 multiplies the input signal by a separately input carrier and outputs an I component through an output terminal 2-1. Multiplier 6-4
Multiplies the input signal and the separately input carrier by multiplying the output terminal 2-
Output the Q component via 2. The quadrature demodulator 4 receives a carrier wave of a predetermined frequency oscillated by the carrier wave transmitter 5, and inputs the carrier wave to the multiplier 6-3 and the 90-degree phase shifter 7-2, and the 90-degree phase shifter 7-
2 shifts the phase of the input carrier by 90 degrees and outputs it to the multiplier 6-4.
【０００５】上述の従来技術において、直交変調器3で
は、I成分とQ成分の2つの信号で搬送波を直交変調する
際に、90度移相器による位相誤差のため、変調精度の劣
化を招く。また、直交復調器4では搬送波でI成分とQ成
分の2つの信号を直交復調する際に、90度移相器による
位相誤差のため復調精度の劣化を招く。これらの変調精
度および復調精度の劣化により通信装置のデータ誤り率
が増加して通信品質が低下する。例えば、図６は90度移
相器の位相誤差と変復調精度劣化との関係を説明する図
である。横軸がI成分（I軸）、縦軸がQ成分（Q軸）、A
は理想的な識別点、A′は実際の信号点、Δθは位相誤
差、Q′軸は位相誤差Δθを有する場合の軸方向であ
る。図６において、I成分-Q成分の直交座標のベクトル
図で示すように、I軸に対してQ軸が位相誤差Δθを有す
る場合（このときのQ軸をQ′軸とする）、理想的な識別
点A（ベクトルOA）は、識別点A′（ベクトルOA′）に移
動するため、誤差ベクトルAA′によって変調精度あるい
は復調精度が劣化する。したがって、このような位相誤
差を発生する直交変調器および直交復調器を備えた通信
装置では、直交変調器および直交復調器において位相補
正を行い、受信データ誤り率の劣化を改善する必要があ
る。従来、90度移相器の位相精度はその製造プロセスに
おける精度に依存しており、また、汎用性を持たせ、広
い帯域で使用できるように一定の誤差を許容して設計さ
れるため、使用する周波数帯域によっては位相誤差に差
異が生じる。また、90度移相器の温度特性および経年変
化によりその位相誤差が変化して更に変調精度および復
調精度が劣化する。In the prior art described above, the quadrature modulator 3 causes a deterioration in modulation accuracy due to a phase error caused by a 90-degree phase shifter when quadrature modulating a carrier with two signals of an I component and a Q component. . Further, in the quadrature demodulator 4, when two signals of the I component and the Q component are quadrature-demodulated by the carrier, the demodulation accuracy is deteriorated due to a phase error caused by the 90-degree phase shifter. Due to the deterioration of the modulation accuracy and the demodulation accuracy, the data error rate of the communication device increases and the communication quality deteriorates. For example, FIG. 6 is a diagram for explaining the relationship between the phase error of the 90-degree phase shifter and the deterioration of modulation / demodulation accuracy. The horizontal axis is the I component (I axis), the vertical axis is the Q component (Q axis), A
Is an ideal discrimination point, A ′ is an actual signal point, Δθ is a phase error, and the Q ′ axis is an axial direction when there is a phase error Δθ. In FIG. 6, when the Q axis has a phase error Δθ with respect to the I axis (the Q axis at this time is assumed to be the Q ′ axis), as shown in the vector diagram of the orthogonal coordinates of the I component and the Q component, Since the discrimination point A (vector OA) moves to the discrimination point A '(vector OA'), the error vector AA 'deteriorates the modulation accuracy or demodulation accuracy. Therefore, in a communication apparatus including a quadrature modulator and a quadrature demodulator that generates such a phase error, it is necessary to correct the phase in the quadrature modulator and the quadrature demodulator to improve the deterioration of the reception data error rate. Conventionally, the phase accuracy of a 90-degree phase shifter depends on the accuracy in the manufacturing process, and it is designed to have versatility and allow a certain error so that it can be used in a wide band. There is a difference in phase error depending on the frequency band. Further, the phase error changes due to the temperature characteristic and the aging of the 90-degree phase shifter, and the modulation accuracy and the demodulation accuracy further deteriorate.
【０００６】[0006]
【発明が解決しようとする課題】前述の従来技術には、
90度移相器の製造ばらつき、温度特性および経年変化に
よる位相誤差に起因して、変調精度と復調精度が劣化す
る欠点があった。The above-mentioned prior art includes the following:
Modulation accuracy and demodulation accuracy are disadvantageously deteriorated due to manufacturing errors of 90 degree phase shifters, phase characteristics due to temperature characteristics and aging.
【０００７】本発明の目的は、上記のような欠点を除去
し、直交変調器および直交復調器における位相誤差がゼ
ロとなるように制御し、受信データ誤り率の劣化を改善
した直交変調器および直交復調器とその位相制御方法を
提供することを目的とする。SUMMARY OF THE INVENTION An object of the present invention is to provide a quadrature modulator which eliminates the above-mentioned drawbacks, controls the quadrature modulator and the quadrature demodulator so that the phase error becomes zero, and improves the reception data error rate. An object of the present invention is to provide a quadrature demodulator and a phase control method thereof.
【０００８】[0008]
【課題を解決するための手段】上記の目的を達成するた
めに、本発明の直交変調器および直交復調器は、ディジ
タル信号処理を行う、直交変調器と直交復調器とを備え
た通信装置において、直交変調器に入力する信号に乗ず
るI成分側に乗ずる第１の搬送波とQ成分側に乗ずる第２
の搬送波との間の位相差を制御信号によって調節する第
１の移相手段と、直交復調器から直交復調信号を出力す
るために、直交復調器に乗ずるI成分側に乗ずる第３の
搬送波とQ成分側に乗ずる第４の搬送波との間の位相差
を制御信号によって調節する第２の移相手段と、直交復
調器から出力するI成分とQ成分の信号から位相誤差を検
出して誤差情報を出力する検出器と、検出器から出力さ
れた誤差情報に基づき第１の移相手段および第２の移相
手段へ制御信号を出力して位相制御を行う制御手段とを
備え、制御手段によって、直交復調器出力のI成分とQ成
分の信号から検出した位相誤差信号から、直交変調器に
乗ずる搬送波の位相差が90度になるように第１の移相手
段を制御し、直交復調器に乗ずる搬送波の位相差が90度
になるように第２の移相手段を制御したものである。In order to achieve the above object, a quadrature modulator and a quadrature demodulator according to the present invention are provided in a communication apparatus for performing digital signal processing, comprising a quadrature modulator and a quadrature demodulator. , The first carrier wave on the I component side to multiply the signal input to the quadrature modulator and the second carrier wave on the Q component side
A first phase shifter for adjusting a phase difference between the carrier and the third carrier by a control signal; and a third carrier for multiplying the I component side of the quadrature demodulator to output the quadrature demodulated signal from the quadrature demodulator. A second phase shifting means for adjusting a phase difference between the fourth carrier wave on the Q component side by a control signal, and a phase error detection by detecting a phase error from the I component and Q component signals output from the quadrature demodulator; A detector for outputting information; and a control unit for outputting a control signal to the first phase shift unit and the second phase shift unit based on the error information output from the detector to perform phase control. The first phase shift means is controlled based on the phase error signal detected from the I component and Q component signals of the quadrature demodulator output so that the phase difference of the carrier multiplied by the quadrature modulator becomes 90 degrees. Phase shift so that the phase difference of the carrier wave on the filter is 90 degrees It controls the means.
【０００９】また、本発明の直交変調器と直交復調器の
位相制御方法は、直交変調器に入力する信号の入力I成
分と入力Q成分の、一方に所定の振幅、他方に振幅ゼロ
の信号を入力して、第２の移相手段の制御を初めに行
い、次に、直交変調器に入力する入力I成分と入力Q成分
の信号について、第２の移相手段を制御する時に振幅ゼ
ロとした入力成分に所定の振幅を与え、第２の移相手段
を制御する時に所定の振幅を与えた入力成分の振幅をゼ
ロとすることによって、第１の移相手段の制御を行うも
のである。Further, according to the phase control method of the quadrature modulator and the quadrature demodulator of the present invention, one of the input I component and the input Q component of the signal input to the quadrature modulator has a predetermined amplitude on one side and a signal with a zero amplitude on the other side. To control the second phase shifting means first, and then, when controlling the second phase shifting means for the input I component and input Q component signals input to the quadrature modulator, A predetermined amplitude is given to the input component set as above, and the control of the first phase shifting means is performed by controlling the amplitude of the input component having given the predetermined amplitude to zero when controlling the second phase shifting means. is there.
【００１０】更にまた、本発明の直交変調器と、直交復
調器とを備えた通信装置では、直交変調器の出力信号の
一部を帰還信号として帰還する手段と、帰還信号と直交
復調器において復調するための復調入力信号とを入力
し、帰還信号と復調入力信号のいずれか一方を、制御手
段によって切替えて直交復調器に出力する切替手段を備
えたものである。Further, in a communication apparatus provided with the quadrature modulator and the quadrature demodulator according to the present invention, means for feeding back a part of the output signal of the quadrature modulator as a feedback signal is provided. A demodulation input signal for demodulation is input, and one of a feedback signal and a demodulation input signal is switched by a control means and output to a quadrature demodulator by switching means.
【００１１】また、本発明の直交変調器と直交復調器と
を備え、電力増幅器の出力の一部を帰還して電力増幅器
の非線形歪みを補償する送信部を有する通信装置におい
て、帰還信号を直交復調器において復調したI成分とQ成
分信号とを入力し、直交変調器と直交復調器の位相誤差
を調節する制御手段を備えたものである。Further, in a communication apparatus comprising a quadrature modulator and a quadrature demodulator according to the present invention and having a transmission unit for feeding back a part of the output of the power amplifier and compensating for nonlinear distortion of the power amplifier, A quadrature modulator and a control means for adjusting the phase error between the quadrature modulator and the quadrature demodulator are provided by inputting the I component and Q component signals demodulated by the demodulator.
【００１２】[0012]
【発明の実施の形態】本発明による直交変調器および直
交復調器の位相制御方法の一実施例を図１，図２および
図４を使用して説明する。図１は本発明による直交変調
器および直交復調器の位相制御方法を実施した通信装置
の直交復調器および直交復調器の部分のブロック図であ
り、図２は制御手順の一例を示すフローチャート、図４
は図２のフローチャートに対応した検出器の構成の一例
を示すブロック図である。図１で、図５と同一のものに
は同一の番号を付した。その他、8-1と8-2は移相器、10
は検出器、11は制御装置、12は切替器、16-1は90度移相
器7-1と移相器8-1とで構成された移相回路、16-2は90度
移相器7-2と移相器8-2とで構成された移相回路、3′は
乗算器6-1，6-2，移相回路16-1，および加算器9-1とで
構成された直交変調器、4′は乗算器6-3，6-4および移
相回路16-2とで構成された直交復調器である。また、図
４の1-4はI成分の入力端子、1-5はQ成分の入力端子、2-
4はI成分の出力端子、2-5はQ成分の出力端子、15-1と15
-2は比較器、10は比較器15-1と15-2で構成された検出器
である。図１の通信装置において、送信機側では、I成
分が入力端子1-1に、Q成分が入力端子1-2に入力し、そ
れぞれ直交変調器3´の乗算器6-1および6-2に入力す
る。乗算器6-1は入力したI成分と別途入力した搬送波を
乗じて加算器9に送り、乗算器6-2は入力したQ成分と別
途移相回路16-1を介して入力した搬送波を乗じて加算器
9に送る。加算器9は入力した２つの乗算器出力を加算し
て出力端子2-3から、例えば電力増幅器のような高周波
回路へ出力する。直交変調器3′には、搬送波発振器5で
発振した所要周波数の搬送波が出力し、乗算器6-1と移
相回路16-1に入力する。移相回路16-1に入力した搬送波
は、90度移相器7-1で90度移相され、更に移相器8-1で制
御器11出力の制御信号にしたがって移相されて出力され
てから、乗算器6-2に送られる。DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS One embodiment of a quadrature modulator and quadrature demodulator phase control method according to the present invention will be described with reference to FIGS. 1, 2 and 4. FIG. FIG. 1 is a block diagram of a quadrature demodulator and a quadrature demodulator of a communication apparatus implementing a quadrature modulator and a quadrature demodulator phase control method according to the present invention. FIG. 2 is a flowchart showing an example of a control procedure. 4
FIG. 3 is a block diagram illustrating an example of a configuration of a detector corresponding to the flowchart of FIG. 2. In FIG. 1, the same components as those in FIG. 5 are denoted by the same reference numerals. 8-1 and 8-2 are phase shifters, 10
Is a detector, 11 is a control device, 12 is a switch, 16-1 is a phase shift circuit composed of a 90-degree phase shifter 7-1 and a phase shifter 8-1, and 16-2 is a 90-degree phase shifter A phase shift circuit composed of a phase shifter 7-2 and a phase shifter 8-2, and 3 'is composed of multipliers 6-1, 6-2, a phase shift circuit 16-1, and an adder 9-1. The quadrature modulator 4 'is a quadrature demodulator composed of multipliers 6-3 and 6-4 and a phase shift circuit 16-2. 4 is an input terminal of the I component, 1-5 is an input terminal of the Q component,
4 is the I component output terminal, 2-5 is the Q component output terminal, 15-1 and 15
-2 is a comparator, and 10 is a detector composed of comparators 15-1 and 15-2. In the communication device shown in FIG. 1, on the transmitter side, the I component is input to the input terminal 1-1 and the Q component is input to the input terminal 1-2, and the multipliers 6-1 and 6-2 of the quadrature modulator 3 'are respectively provided. To enter. The multiplier 6-1 multiplies the input I component by the separately input carrier and sends the result to the adder 9, and the multiplier 6-2 multiplies the input Q component and the carrier separately input via the phase shift circuit 16-1. Adder
Send to 9. The adder 9 adds the two input multiplier outputs and outputs the result from an output terminal 2-3 to a high-frequency circuit such as a power amplifier. The carrier of the required frequency oscillated by the carrier oscillator 5 is output to the quadrature modulator 3 ', and is input to the multiplier 6-1 and the phase shift circuit 16-1. The carrier wave input to the phase shift circuit 16-1 is phase-shifted by 90 degrees by the 90-degree phase shifter 7-1, and further phase-shifted by the phase shifter 8-1 according to the control signal of the controller 11 and output. Then, it is sent to the multiplier 6-2.
【００１３】一方、受信機側では、直交変調器3´から
出力した信号の一部が帰還されて復調器入力の切替器12
に入力する（切替器12の端子b）。切替器12には受信信
号入力端子1-3からの受信信号も入力しており（切替器1
2の端子a）、直交復調器4´に入力する信号は、制御器1
1出力の制御情報によって切替器12の入力を切替えるこ
とにより選択される。直交復調器4´は、切替機2の出力
信号を乗算器6-3に入力し、乗算器6-3は入力した信号
に、別途乗算器6-3に入力した搬送波を乗じてI成分を復
調して、出力端子2-1および検出器10に出力する。切替
機2の出力信号はまた、乗算器6-4に入力し、乗算器6-4
は入力信号に、別途移相回路16-2を介して送られてきた
搬送波を乗じてQ成分を復調して、出力端子2-2および検
出器10に出力する。直交復調器4′には、搬送波発信器5
で発振した所定周波数の搬送波が送られ、乗算器6-3お
よび移相回路16-2に入力する。移相回路16-2に入力した
搬送波は、90度移相器7-2で90度移相され、さらに移相
器8-2で制御器11出力の制御信号にしたがって移相され
て出力されてから、乗算器6-4に送られる。On the other hand, on the receiver side, a part of the signal output from the quadrature modulator 3 ′ is fed back to the demodulator input switch 12.
(Terminal b of switch 12). The switch 12 also receives the received signal from the received signal input terminal 1-3 (switch 1
The signal input to the terminal a) of 2 and the quadrature demodulator 4 'is
The selection is made by switching the input of the switch 12 according to the control information of one output. The quadrature demodulator 4 ′ inputs the output signal of the switch 2 to the multiplier 6-3, and the multiplier 6-3 multiplies the input signal by the carrier wave input to the multiplier 6-3 separately to obtain an I component. The signal is demodulated and output to the output terminal 2-1 and the detector 10. The output signal of switch 2 is also input to multiplier 6-4,
Multiplies the input signal by a carrier wave separately transmitted through the phase shift circuit 16-2, demodulates the Q component, and outputs the result to the output terminal 2-2 and the detector 10. The quadrature demodulator 4 'includes a carrier wave transmitter 5
The carrier wave of a predetermined frequency oscillated by is sent to the multiplier 6-3 and the phase shift circuit 16-2. The carrier wave input to the phase shift circuit 16-2 is phase-shifted by 90 degrees by the 90-degree phase shifter 7-2, and further phase-shifted by the phase shifter 8-2 according to the control signal of the controller 11 and output. After that, it is sent to the multiplier 6-4.
【００１４】検出器10は、入力した復調I成分および復
調Q成分の振幅をもとに位相誤差を検出し、検出した誤
差情報を制御器11に出力する。制御器11は、入力した誤
差信号にもとづき直交変調器3′の移相器8-1および、直
交復調器4′の移相器8-2と、切替器12とを制御する。移
相器8-1は制御器11の制御信号によって90度移相器7-1の
位相誤差を補正し、移相器8-2は制御器11の制御信号に
よって90度移相器7-2の位相誤差を補正する。即ち、制
御器11は、直交変調器3′の90度移相器7-1の位相誤差を
相殺して、入力端子1-1と1-2からそれぞれ入力するI成
分とQ成分に乗じる2つの搬送波の位相差が正確に90度に
なるように移相器8-1の移相量を制御し、直交復調器4′
の90度移相器7-2の位相誤差を相殺して、復調信号のI成
分とQ成分とを出力するために入力信号に乗じる2つの搬
送波の位相差が正確に90度になるように移相器8-2の移
相量を制御し、また、位相制御を行っている期間、復調
器入力の切替器12を直交変調器3′の出力信号が帰還し
て直交復調器4′に入力するように切替器12入力を端子b
側に接続する。The detector 10 detects a phase error based on the amplitudes of the input demodulated I component and demodulated Q component, and outputs detected error information to the controller 11. The controller 11 controls the phase shifter 8-1 of the quadrature modulator 3 ', the phase shifter 8-2 of the quadrature demodulator 4', and the switch 12 based on the input error signal. The phase shifter 8-1 corrects the phase error of the 90-degree phase shifter 7-1 by the control signal of the controller 11, and the phase shifter 8-2 changes the 90-degree phase shifter 7- by the control signal of the controller 11. Correct the phase error of 2. That is, the controller 11 cancels the phase error of the 90-degree phase shifter 7-1 of the quadrature modulator 3 ', and multiplies the I component and the Q component input from the input terminals 1-1 and 1-2 by 2 The amount of phase shift of the phase shifter 8-1 is controlled so that the phase difference between the two carriers is exactly 90 degrees, and the quadrature demodulator 4 '
The 90-degree phase shifter 7-2 cancels the phase error so that the phase difference between the two carriers multiplied by the input signal to output the I and Q components of the demodulated signal is exactly 90 degrees. The phase shifter 8-2 controls the phase shift amount, and during the phase control, the output signal of the quadrature modulator 3 'is fed back to the demodulator input switch 12 to the quadrature demodulator 4'. Switch 12 input to terminal b as input
To the side.
【００１５】更に、図２を使用して、直交変調器および
直交復調器の位相制御方法の制御手段の一例を説明す
る。図２は直交変調器および直交復調器の位相制御を行
う処理過程を説明するフローチャートである。制御開始
時、制御器11の制御により、直交復調器4′に直交変調
器3′から分岐した出力信号が帰還して入力するように
切替え器12入力を端子b側に設定する（帰還路接続ステ
ップ101）。次に、直交復調器4′の位相制御を行うた
め、直交変調器3′のI成分入力端子1-1に“A”（I=A、
A：正の定数）、Q成分入力端子1-2に“0”（Q=0）を入
力して、直交変調した直交変調波を出力する（I成分信
号入力ステップ102）。直交復調器4′のQ成分出力端子2
-2の信号の振幅を検出器10で検出し、Q成分の振幅が
“0”になるように制御器11で移相器8-2の移相量φ（制
御後のφ：φ=φ0）を調節する（復調器移相制御ステッ
プ103）。次に、直交変調器3′の位相制御を行うため、
直交変調器3′のI成分入力端子1-1に“0”（I=0）、Q成
分入力端子1-2に“B”（Q=B、B：正の定数）を入力して
直交変調した直交変調波を出力する（Q成分信号入力ス
テップ104）。直交復調器4′のI成分出力2-1の信号の振
幅を検出器10で検出し、I成分の振幅が“0”になるよう
に制御器11で移相器8-1の移相量θ（制御後のθ：θ=θ
0）を調節する（変調器位相制御ステップ105）。ステッ
プ105までの処理過程が終ると、直交変調器3′および直
交復調器4′の位相補正が完了するので、制御器11は直
交復調器4´の入力を、入力端子1-3入力の受信信号とな
るように切替器12入力を端子a側に接続する（帰還路切
断ステップ106）。以上の過程によって、通信装置の位
相が調整される。Further, an example of the control means of the phase control method of the quadrature modulator and the quadrature demodulator will be described with reference to FIG. FIG. 2 is a flowchart illustrating a process of performing phase control of the quadrature modulator and the quadrature demodulator. At the start of the control, the input of the switch 12 is set to the terminal b so that the output signal branched from the quadrature modulator 3 'is fed back to the quadrature demodulator 4' under the control of the controller 11 (return path connection Step 101). Next, in order to control the phase of the quadrature demodulator 4 ', "A" (I = A,
A: A positive constant), “0” (Q = 0) is input to the Q component input terminal 1-2, and a quadrature modulated wave is output (I component signal input step 102). Q component output terminal 2 of quadrature demodulator 4 '
The amplitude of the -2 signal is detected by the detector 10 and the phase shift amount φ of the phase shifter 8-2 (φ after control: φ = φ0) is controlled by the controller 11 so that the amplitude of the Q component becomes “0”. ) (Demodulator phase shift control step 103). Next, in order to control the phase of the quadrature modulator 3 ',
Input “0” (I = 0) to the I component input terminal 1-1 and “B” (Q = B, B: positive constant) to the Q component input terminal 1-2 of the quadrature modulator 3 ′ to perform quadrature The modulated quadrature modulated wave is output (Q component signal input step 104). The detector 10 detects the amplitude of the signal of the I component output 2-1 of the quadrature demodulator 4 ', and the controller 11 controls the phase shift amount of the phase shifter 8-1 so that the amplitude of the I component becomes "0". θ (θ after control: θ = θ
0) is adjusted (modulator phase control step 105). When the process up to step 105 is completed, the phase correction of the quadrature modulator 3 'and the quadrature demodulator 4' is completed, so that the controller 11 receives the input of the quadrature demodulator 4 'from the input terminal 1-3. The input of the switch 12 is connected to the terminal a so that the signal becomes a signal (feedback path disconnection step 106). Through the above process, the phase of the communication device is adjusted.
【００１６】前述の制御手順を実行する場合の検出器10
の一実施例を図４に示す。図４は本発明の位相制御を実
行する場合に使用する検出器の構成を表すブロック図で
ある。1-4はI成分入力端子、1-5はQ成分入力端子、15-1
と15-2は比較器、10は比較器15-1と15-2で構成された検
出器、2-4と2-5は出力端子である。図４において、I成
分入力端子1-4およびQ成分入力端子1-5が比較器15-1お
よび15-2の一方の入力に入力される。2つの比較器の他
方の入力にはそれぞれ“0”が入力されており、両者を
比較して入力信号の符号の判定結果を出力する（例え
ば、入力信号＞0ならば、比較器出力=1、入力信号≦0な
らば、比較器出力=0）。比較器15-1および15-2の出力は
出力端子2-4および2-5から制御器11に出力される。前述
の図２の復調器位相制御ステップ103において、入力端
子1-5に入力された復調Q成分の符号が比較器15-2で判定
され、制御器11は比較器15-2出力の符号の変化を観察し
ながら移相器8-2の移相量φを可変し、符号が変化する
直前の移相量φ0を決定する。また、図２の変調器位相
制御ステップ105において、入力端子1-4に入力された復
調I成分の符号が比較器15-1で判定され、制御器11は比
較器15-1出力の符号の変化を観察しながら移相器8-1の
移相量θを可変し、符号が変化する直前の移相量θ0を
決定する。Detector 10 for executing the above control procedure
FIG. 4 shows an embodiment of the present invention. FIG. 4 is a block diagram showing a configuration of a detector used when executing the phase control of the present invention. 1-4 are I component input terminals, 1-5 are Q component input terminals, 15-1
And 15-2 are comparators, 10 is a detector composed of comparators 15-1 and 15-2, and 2-4 and 2-5 are output terminals. In FIG. 4, an I component input terminal 1-4 and a Q component input terminal 1-5 are input to one input of comparators 15-1 and 15-2. “0” is input to the other input of each of the two comparators, and the two are compared to output a result of determination of the sign of the input signal (for example, if the input signal> 0, the comparator output = 1 If the input signal ≦ 0, the comparator output = 0). Outputs of the comparators 15-1 and 15-2 are output to the controller 11 from output terminals 2-4 and 2-5. In the demodulator phase control step 103 of FIG. 2 described above, the sign of the demodulated Q component input to the input terminal 1-5 is determined by the comparator 15-2, and the controller 11 determines the sign of the output of the comparator 15-2. While observing the change, the phase shift amount φ of the phase shifter 8-2 is varied, and the phase shift amount φ0 immediately before the sign change is determined. In the modulator phase control step 105 of FIG. 2, the sign of the demodulated I component input to the input terminal 1-4 is determined by the comparator 15-1, and the controller 11 determines the sign of the output of the comparator 15-1. The phase shift amount θ of the phase shifter 8-1 is varied while observing the change, and the phase shift amount θ0 immediately before the sign change is determined.
【００１７】以上の、位相制御手順により、直交復調器
4′出力のみを検出して直交変調器3′および直交復調器
4′の位相誤差を校正する。なお、直交変調器3′の移相
回路16-1および直交復調器4′の移相回路16-2は90度移
相器7-1あるいは7-2と移相器8-1あるいは8-2の２つの回
路でそれぞれ構成されているが、90度移相器を省略して
移相器8-1，8-2のみで構成し、さらに上記の制御手順に
よって移相器8-1と8-2の位相誤差を補正することもでき
る（ただし、移相器8-1，8-2の初期値は90度とする）。
また、上記制御手順および検出器の一例では、復調信号
の符号を検出して位相制御を行っているため、直交変調
器3′のI成分とQ成分の間に振幅の偏差がある場合、ま
たは、直交復調器4′のI成分とQ成分の間に振幅の偏差
がある場合においても、これらの振幅の偏差の影響を受
けずに直交変調器3′および直交復調器4′の位相制御を
行うことができる。また、上記位相制御を通信装置の電
源投入時、通信を実施するする直前、あるいは非通信時
に間欠的に実施することにより、位相誤差の経年変化お
よび温度変化を校正することができ、位相誤差による直
交変調器の変調精度および直交復調器の復調精度の劣化
なしに通信を行うことができる。According to the above phase control procedure, a quadrature demodulator
Quadrature modulator 3 'and quadrature demodulator by detecting only 4' output
Calibrate the 4 'phase error. The phase shift circuit 16-1 of the quadrature modulator 3 'and the phase shift circuit 16-2 of the quadrature demodulator 4' are composed of a 90-degree phase shifter 7-1 or 7-2 and a phase shifter 8-1 or 8- Each of the two circuits is composed of two circuits 2). However, the 90-degree phase shifter is omitted, and only the phase shifters 8-1 and 8-2 are used. The phase error of 8-2 can also be corrected (however, the initial values of the phase shifters 8-1 and 8-2 are 90 degrees).
Further, in the above control procedure and an example of the detector, since the phase control is performed by detecting the code of the demodulated signal, when there is an amplitude deviation between the I component and the Q component of the quadrature modulator 3 ′, or Even when there is an amplitude deviation between the I component and the Q component of the quadrature demodulator 4 ', the phase control of the quadrature modulator 3' and the quadrature demodulator 4 'can be performed without being affected by these amplitude deviations. It can be carried out. Further, by performing the above phase control when the power of the communication apparatus is turned on, immediately before performing communication, or intermittently during non-communication, it is possible to calibrate the aging and temperature change of the phase error, Communication can be performed without deteriorating the modulation accuracy of the quadrature modulator and the demodulation accuracy of the quadrature demodulator.
【００１８】次に、本発明の第２の実施例を図３によっ
て説明する。図３は、送信出力の一部を帰還して電力増
幅器の非線形歪みを補償する送信部を有する通信装置の
ブロック構成図である。図３の通信装置に対して、直交
変調器および直交復調器の位相制御を行った場合をいか
に説明する。1-1はベースバンド信号のI成分の入力端
子，1-2はベースバンド信号のQ成分の入力端子、9-1と9
-2は加算器、5は搬送波発振器、3′直交変調器、4′直
交復調器、13は電力増幅器、14は方向性結合器、2-6は
出力端子、10は検出器、11は制御装置である。図３にお
いて、入力端子1-1にI成分、入力端子1-2にQ成分の信号
が入力され、それぞれ加算器9-1と9-2に入力する。加算
器9-1では、別に直交復調器4′から送られてくる復調I
成分と、入力端子1-1からのI成分とを加算し、直交変調
器3′に入力する。同様に、加算器9-1では、別に直交復
調器4′から送られてくる復調Q成分と、入力端子1-2か
らのQ成分とを加算し、直交変調器3′に入力する。直交
変調器3′は搬送波発振器5から入力する搬送波をもとに
して、入力したI成分とQ成分の信号を直交変調して出力
し電力増幅器13に送る。電力増幅器13で送信する電力レ
ベルに増幅後、出力端子1-6例えばアンテナ等の高周波
回路を介して出力する。Next, a second embodiment of the present invention will be described with reference to FIG. FIG. 3 is a block diagram of a communication device having a transmission unit that compensates for nonlinear distortion of a power amplifier by feeding back part of a transmission output. The case where the phase control of the quadrature modulator and the quadrature demodulator is performed on the communication apparatus of FIG. 3 will be described. 1-1 is the input terminal of the I component of the baseband signal, 1-2 is the input terminal of the Q component of the baseband signal, 9-1 and 9
-2 is an adder, 5 is a carrier oscillator, 3 'quadrature modulator, 4' quadrature demodulator, 13 is power amplifier, 14 is directional coupler, 2-6 is output terminal, 10 is detector, 11 is control Device. In FIG. 3, an I component signal is input to an input terminal 1-1, and a Q component signal is input to an input terminal 1-2, and input to adders 9-1 and 9-2, respectively. In the adder 9-1, the demodulation I sent separately from the quadrature demodulator 4 '
The component and the I component from the input terminal 1-1 are added and input to the quadrature modulator 3 '. Similarly, the adder 9-1 adds the demodulated Q component separately sent from the quadrature demodulator 4 'and the Q component from the input terminal 1-2, and inputs the result to the quadrature modulator 3'. The quadrature modulator 3 ′ quadrature-modulates the input I-component and Q-component signals based on the carrier wave input from the carrier wave oscillator 5 and outputs the signal to the power amplifier 13. After being amplified to the power level to be transmitted by the power amplifier 13, the signal is output via a high frequency circuit such as an output terminal 1-6, for example, an antenna.
【００１９】また、電力増幅器13の信号出力の一部は、
方向性結合器14を介して帰還されて直交復調器4′に入
力する。直交復調器4′は、搬送波発振器5から入力する
搬送波をもとにして、電力増幅器13の帰還した一部出力
信号を直交復調する。直交復調器4′のI成分の出力信号
は加算器9-1に入力し、Q成分の出力信号は加算器9-2に
入力して、入力端子1-1と1-2とからのI成分信号とQ成分
信号とに対してそれぞれ負帰還されるため、電力増幅器
の非線形歪みが補償される。A part of the signal output of the power amplifier 13 is:
The signal is fed back via the directional coupler 14 and input to the quadrature demodulator 4 '. The quadrature demodulator 4 ′ quadrature demodulates a part of the output signal fed back from the power amplifier 13 based on the carrier input from the carrier oscillator 5. The output signal of the I component of the quadrature demodulator 4 'is input to the adder 9-1, the output signal of the Q component is input to the adder 9-2, and the I signal from the input terminals 1-1 and 1-2 is input. Since the component signal and the Q component signal are negatively fed back, the nonlinear distortion of the power amplifier is compensated.
【００２０】図３において、制御装置11から制御信号を
出力し、加算器9-1と9-1に送り、加算器9-1と9-1におい
て直交復調器4′からの帰還信号が加算されない（また
は入力されない）ように制御することによって、図１の
切替器12と同じ働きをさせ、図１または図２で述べた位
相制御を直交変調器3′と直交復調器4′で実行させるこ
とにより、本発明の位相制御が実施できる。即ち、制御
器11出力の制御信号によりQ相側の搬送波の位相制御を
行う直交変調器3´と、制御器11出力の制御情報によりQ
相側の搬送波の位相制御を行う直交復調器4´と、直交
復調器4´出力の信号を入力して位相誤差を検出する検
出器10と、当該検出器10出力の誤差信号を入力して直交
変調器3´と直交変調器4´の位相制御情報および加算器
9-1，9-2の制御を行う制御器11を用い、図２の制御手順
にしたがって位相制御を実行することができる（ただ
し、図２のI成分信号入力ステップ102および帰還路切断
ステップ106における帰還路の切替え制御の代わりに、
ここでは加算器9-1および9-2の制御を行う）。In FIG. 3, a control signal is output from the control device 11 and sent to adders 9-1 and 9-1. In the adders 9-1 and 9-1, the feedback signal from the quadrature demodulator 4 'is added. By controlling so as not to be performed (or not to be input), the same operation as the switch 12 in FIG. 1 is performed, and the phase control described in FIG. 1 or FIG. 2 is executed by the quadrature modulator 3 ′ and the quadrature demodulator 4 ′. Thereby, the phase control of the present invention can be performed. That is, a quadrature modulator 3 ′ for controlling the phase of the carrier on the Q-phase side by the control signal output from the controller 11, and the Q
A quadrature demodulator 4 'for controlling the phase of the carrier wave on the phase side, a detector 10 for inputting a signal output from the quadrature demodulator 4' and detecting a phase error, and an error signal for the output of the detector 10 Phase control information of quadrature modulator 3 'and quadrature modulator 4' and adder
The phase control can be executed according to the control procedure of FIG. 2 by using the controller 11 for controlling the 9-1 and 9-2 (however, the I component signal input step 102 and the feedback path disconnection step 106 of FIG. 2). Instead of the return path switching control in
Here, adders 9-1 and 9-2 are controlled).
【００２１】[0021]
【発明の効果】以上のように本発明によれば、直交変調
器と直交復調器を備える通信装置において、直交復調器
出力の復調I成分と復調Q成分の信号から直交変調器と直
交復調器の位相誤差を検出し、誤差信号に基づく位相制
御を直交変調器に備えた移相器と直交復調器に備えた移
相器で行い、直交変調器および直交復調器における２つ
の搬送波の位相差が90度になるように制御し、受信デー
タ誤り率の劣化を改善することができる。As described above, according to the present invention, in a communication apparatus including a quadrature modulator and a quadrature demodulator, a quadrature modulator and a quadrature demodulator are obtained from signals of a demodulation I component and a demodulation Q component of a quadrature demodulator output. And the phase control based on the error signal is performed by the phase shifter provided in the quadrature modulator and the phase shifter provided in the quadrature demodulator, and the phase difference between the two carrier waves in the quadrature modulator and the quadrature demodulator is obtained. Is controlled to be 90 degrees, and the deterioration of the reception data error rate can be improved.
【図１】 本発明の通信装置の一実施例の構成を示すブ
ロック図。FIG. 1 is a block diagram showing a configuration of an embodiment of a communication device according to the present invention.
【図２】 本発明の制御手段の一実施例を示すフローチ
ャート。FIG. 2 is a flowchart showing an embodiment of the control means of the present invention.
【図３】 本発明の他の実施例の構成を示すブロック
図。FIG. 3 is a block diagram showing a configuration of another embodiment of the present invention.
【図４】 本発明の実施例に関する検出器の一例を示す
ブロック構成図。FIG. 4 is a block diagram showing an example of a detector according to the embodiment of the present invention.
【図５】 従来の通信装置の構成を示すブロック図。FIG. 5 is a block diagram showing a configuration of a conventional communication device.
【図６】 位相誤差による変調精度の劣化を説明する
図。FIG. 6 is a diagram illustrating deterioration of modulation accuracy due to a phase error.
1-1，1-2，1-3，1-4，1-5：入力端子、 2-1，2-2，2-
3，2-4，2-5，2-6：出力端子、 3，3′：直交変調器、
4，4′：直交復調器、 5：搬送波発振器、6-1，6-
2，6-3，6-4：乗算器、 7-1，7-2：90度移相器、 8-
1，8-2：移相器、 9，9-1，9-2：加算器、 10：検出
器、 11：制御装置、 12：切替器、 13：電力増幅
器、 14：方向性結合器、 15-1，15-2：比較器、 16
-1，16-2：移相回路、1-1, 1-2, 1-3, 1-4, 1-5: input terminal, 2-1, 2-2, 2-
3, 2-4, 2-5, 2-6: output terminal, 3, 3 ': quadrature modulator,
4, 4 ': Quadrature demodulator, 5: Carrier oscillator, 6-1, 6-
2, 6-3, 6-4: multiplier, 7-1, 7-2: 90 degree phase shifter, 8-
1, 8-2: phase shifter, 9, 9-1, 9-2: adder, 10: detector, 11: controller, 12: switch, 13: power amplifier, 14: directional coupler, 15-1, 15-2: comparator, 16
-1, 16-2: phase shift circuit,
Claims (4)
と直交復調器とを備えた通信装置において、 前記直交変調器に入力する信号に乗ずるI成分側に乗ず
る第１の搬送波とQ成分側に乗ずる第２の搬送波との間
の位相差を制御信号によって調節する第１の移相手段
と、 前記直交復調器から直交復調信号を出力するために、前
記直交復調器に乗ずるI成分側に乗ずる第３の搬送波とQ
成分側に乗ずる第４の搬送波との間の位相差を制御信号
によって調節する第２の移相手段と、 前記直交復調器から出力するI成分とQ成分の信号から位
相誤差を検出して誤差情報を出力する検出器と、 前記検出器から出力された前記誤差情報に基づき前記第
１の移相手段および前記第２の移相手段へ制御信号を出
力して搬送波の位相制御を行う制御手段とを備え、 前記制御手段によって、前記直交復調器出力の前記I成
分とQ成分の信号から検出した位相誤差信号から、前記
直交変調器に乗ずる搬送波の位相差が90度になるように
前記第１の移相手段を制御し、前記直交復調器に乗ずる
搬送波の位相差が90度になるように前記第２の移相手段
を制御することを特徴とする直交変調器と直交復調器の
位相制御方法。1. A communication device comprising a quadrature modulator and a quadrature demodulator for performing digital signal processing, comprising: a first carrier and a Q component that multiply an I component that multiplies a signal input to the quadrature modulator. First phase shift means for adjusting the phase difference between the second carrier and the second carrier by a control signal; and multiplying the I component by which the quadrature demodulator is multiplied in order to output a quadrature demodulated signal from the quadrature demodulator. Third carrier and Q
A second phase shifting means for adjusting a phase difference between the fourth carrier and the fourth carrier by a control signal, and detecting a phase error from an I component and a Q component signals output from the quadrature demodulator to obtain an error. A detector that outputs information, and a control unit that outputs a control signal to the first phase shift unit and the second phase shift unit based on the error information output from the detector to perform phase control of a carrier wave. The control means, from the phase error signal detected from the signal of the I component and the Q component of the output of the quadrature demodulator, the phase difference of the carrier to be multiplied by the quadrature modulator is 90 degrees (1) controlling the first phase shifting means and controlling the second phase shifting means so that the phase difference of the carrier wave multiplied by the quadrature demodulator becomes 90 degrees. Control method.
の移相制御方法において、 前記直交変調器に入力する信号の入力I成分と入力Q成分
の、一方に所定の振幅、他方に振幅ゼロの信号を入力し
て、前記第２の移相手段の制御を初めに行い、 次に、前記直交変調器に入力する入力I成分と入力Q成分
の信号について、前記第２の移相手段を制御する時に振
幅ゼロとした入力成分に所定の振幅を与え、前記第２の
移相手段を制御する時に所定の振幅を与えた入力成分の
振幅をゼロとすることによって、前記第１の移相手段の
制御を行うことを特徴とする直交変調器と直交復調器の
位相制御方法。2. The phase shift control method for a quadrature modulator and a quadrature demodulator according to claim 1, wherein one of an input I component and an input Q component of a signal input to the quadrature modulator has a predetermined amplitude and the other has a predetermined amplitude. A signal having an amplitude of zero is input, and the control of the second phase shift means is first performed. Next, the signal of the input I component and the input Q component input to the quadrature modulator is subjected to the second phase shift. By providing a predetermined amplitude to an input component having an amplitude of zero when controlling the means, and setting the amplitude of the input component having a predetermined amplitude to be zero when controlling the second phase shifting means, the first A phase control method for a quadrature modulator and a quadrature demodulator, characterized by controlling a phase shift means.
と直交復調器とを備えた通信装置において、 前記直交変調器の出力信号の一部を帰還信号として帰還
する手段と、 前記帰還信号と、前記直交復調器において復調するため
の復調入力信号とを入力し、前記帰還信号と前記復調入
力信号のいずれか一方を、前記制御手段によって切替え
て前記直交復調器に出力する切替手段を備えたことを特
徴とする請求項１または請求項２記載の直交変調器と直
交復調器の位相制御方法を用いた通信装置。3. A communication device for performing digital signal processing, comprising: a quadrature modulator and a quadrature demodulator; a means for feeding back a part of an output signal of the quadrature modulator as a feedback signal; A switching unit that inputs a demodulation input signal for demodulation in the quadrature demodulator, and switches one of the feedback signal and the demodulation input signal by the control unit and outputs the switching signal to the quadrature demodulator; A communication apparatus using the quadrature modulator and quadrature demodulator phase control method according to claim 1 or 2.
と直交復調器とを備え、電力増幅器の出力の一部を帰還
して前記直交復調器において復調して前記電力増幅器の
非線形歪みを検出することによって、電力増幅器の非線
形歪みを補償する送信部を有する通信装置において、 前記直交復調器の出力を入力する位相制御手段を備えた
ことを特徴とする請求項１または請求項２記載の直交変
調器と直交復調器の位相制御方法を用いた通信装置。4. A quadrature modulator and a quadrature demodulator for performing digital signal processing, wherein a part of an output of a power amplifier is fed back and demodulated in the quadrature demodulator to detect nonlinear distortion of the power amplifier. 3. A quadrature modulation apparatus according to claim 1, further comprising a phase control unit for inputting an output of said quadrature demodulator in a communication apparatus having a transmission unit for compensating for nonlinear distortion of a power amplifier. A communication device using a phase control method between a modulator and a quadrature demodulator.
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|---|---|---|---|
| JP17229299A JP3518848B2 (en) | 1999-06-18 | 1999-06-18 | Phase control method for quadrature modulator and quadrature demodulator and communication device |
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP17229299A JP3518848B2 (en) | 1999-06-18 | 1999-06-18 | Phase control method for quadrature modulator and quadrature demodulator and communication device |
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| Publication Number | Publication Date |
|---|---|
| JP2001007882A true JP2001007882A (en) | 2001-01-12 |
| JP3518848B2 JP3518848B2 (en) | 2004-04-12 |
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Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US7872544B2 (en) | 2007-08-21 | 2011-01-18 | Kabushiki Kaisha Toshiba | Modulation/demodulation apparatus and modulation/demodulation method |
| JP2012065200A (en) * | 2010-09-16 | 2012-03-29 | Ricoh Co Ltd | Transmitter-receiver |
| US9231523B2 (en) | 2013-03-22 | 2016-01-05 | Fujitsu Limited | Modulating device and modulation method |
| CN116346558A (en) * | 2023-05-23 | 2023-06-27 | 清华大学 | Method and system for generating orthogonal signals |
-
1999
- 1999-06-18 JP JP17229299A patent/JP3518848B2/en not_active Expired - Fee Related
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US7872544B2 (en) | 2007-08-21 | 2011-01-18 | Kabushiki Kaisha Toshiba | Modulation/demodulation apparatus and modulation/demodulation method |
| JP2012065200A (en) * | 2010-09-16 | 2012-03-29 | Ricoh Co Ltd | Transmitter-receiver |
| US9231523B2 (en) | 2013-03-22 | 2016-01-05 | Fujitsu Limited | Modulating device and modulation method |
| CN116346558A (en) * | 2023-05-23 | 2023-06-27 | 清华大学 | Method and system for generating orthogonal signals |
| CN116346558B (en) * | 2023-05-23 | 2023-08-22 | 清华大学 | Method and system for generating orthogonal signals |
Also Published As
| Publication number | Publication date |
|---|---|
| JP3518848B2 (en) | 2004-04-12 |
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