EP0600799B1 - Aktive Antenne mit variabler Polarisations-Synthese - Google Patents

Aktive Antenne mit variabler Polarisations-Synthese Download PDF

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Publication number
EP0600799B1
EP0600799B1 EP93402925A EP93402925A EP0600799B1 EP 0600799 B1 EP0600799 B1 EP 0600799B1 EP 93402925 A EP93402925 A EP 93402925A EP 93402925 A EP93402925 A EP 93402925A EP 0600799 B1 EP0600799 B1 EP 0600799B1
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EP
European Patent Office
Prior art keywords
phase
shifters
controllable
polarization
circuit according
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Expired - Lifetime
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EP93402925A
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English (en)
French (fr)
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EP0600799A1 (de
Inventor
Gérard Caille
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Alcatel Lucent SAS
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Alcatel SA
Alcatel Alsthom Compagnie Generale dElectricite
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/24—Combinations of antenna units polarised in different directions for transmitting or receiving circularly and elliptically polarised waves or waves linearly polarised in any direction
    • H01Q21/245—Combinations of antenna units polarised in different directions for transmitting or receiving circularly and elliptically polarised waves or waves linearly polarised in any direction provided with means for varying the polarisation 

Definitions

  • the invention relates to active antennas, which are made up of a large number of radiating sources excited by microwave power amplifiers during transmission, or whose received signals are amplified by low noise amplifiers at reception. Such antennas are used in various applications such as telecommunications or radars; the invention will be particularly advantageous for radars.
  • the usual architecture of a monostatic radar involves the use of a lane transmission and reception channel which lead to the same radiant source.
  • a switch allows the selection of the transmission channel to transmit a radar signal in pulses, the time space between the emission pulses being used to listen, in selecting the reception channel, the radar echoes which come back from the environment.
  • the increase demand makes us look for a better use of the radio spectrum. This concern translates by the use of fine, orientable beams, and sometimes even polarized to allow the reuse of frequencies. These characteristics can be combined advantageously in realizations of array antennas.
  • the invention will find an application in such antennas telecommunications, more specifically designed but not exclusively for the broadcast.
  • antennas transmission and reception are spaced from each other others, sometimes by the tens or even hundreds of kilometers.
  • Network antennas can be designed to fulfill the two missions, emission and reception, or they can be designed to fill only one of these two missions.
  • a variant of the invention will be applicable for each of these possibilities.
  • active antennas for radars monostatic to have evolved considerably in recent years, and in the current state of the art, the radiating sources are connected to active transmission / reception modules (MAER or T ⁇ R in English), made in MMIC technology (Monolithic Microwave Integrated Circuits) or in hybrid technology. Transmission / reception switching is generally included in the active module, a schematic diagram of which is given in Figure 1, with its location within the antenna.
  • Figure 1 schematically shows an antenna active radar, operating alternately in transmission and in reception.
  • the alternation of transmission / reception is ensured by switches 25, 52 controlled by a synchronization clock 24.
  • orthogonal polarizations can be selected by switch 26, for the reception as for the emission.
  • Phase and gain are controllable by control means 23, also both in transmission and in reception.
  • the values of order which will be provided for ordering a track of reception given, are not necessarily the same as for the same channel used for transmission.
  • a single active module transmission / reception is shown, including phase shifter controllable 27 and a controllable attenuator 28, for adjust the gain of the module.
  • the transmitter 21 supplies its signals to a distributor / combiner 22, which supplies the active I / O modules.
  • the phase and the attenuation of the signal will be determined by the controllable phase shifter 27 and the controllable attenuator 28, according to the instructions given by the control computer 23.
  • the switches 25 and 52 will be controlled by the clock 24 to engage the power channel, and the signal will be amplified by the power amplifier 29, before being sent to the radiating sources S ij .
  • the receiver 31 receives the signals from the combiner / distributor 22, which are routed by the active E / R modules.
  • the signals coming from the radiating sources S ij are switched by the switches 25, 52 on the reception channel and pass through a low noise amplifier 30.
  • the phase shift and the attenuation are applied by the controllable phase shifter 27 and the controllable attenuator 28, controlled by the control computer 23.
  • Beams can also be formed, for example with stiff sides and side lobes low, to improve antenna performance when ambiguities of echoes, and in the presence of noise sources, thanks to controllable phase shifters and attenuators.
  • switches 26 one of the two orthogonal polarizations can be selected, interesting for the radar because the useful signal and the noise have different variations depending on the polarization, which allows an optimization of the signal ratio on noise by acting on the polarization.
  • Elementary sources are radiant elements capable of providing polarized radiation, the polarization of which can take at least two orthogonal values, for example horizontal (H) and vertical (V), or circular polarizations right and left (R, L).
  • Cornets with square, circular or hexagonal are radiating elements that can generate H or V polarizations. They are particularly suitable to high power antennas or ground is not a element criticized.
  • the printed radiant elements are paving stones metallic photo-etched on a thin dielectric substrate with low microwave losses. They allow the production of radiant panels comprising a lot of elementary sources, these panels can be thin, light, and even conformable. For generate orthogonal polarizations with patches it just excite them by two points offset by 90 ° by relative to the center of the patch, as shown in Figure 1.
  • the link between the MAER and the patch can be online coaxial or microstrip, for example. If only one MAER must order several patches, they can be grouped in sub-networks, connected to MAER by distributors in microstrip line for each H and V polarization
  • the circuit of Figure 2 further includes, a additional protection for low noise amplifiers against any unwanted reflections coming back radiating sources S k / ij when they are powered by power amplifiers, in case of mismatch of the antenna.
  • These protection means are switches 32a, 32b placed in shunt towards ground, on the inputs of low noise amplifiers. These switches are also controlled by the clock 24, at the same time and in synchronization with E / R switches 25a, 25b.
  • the optional isolators 33a, 33b allow evacuation to the mass the power reflected (a second time) by these protection means 32a, 32b.
  • the microwave circulators 52a, 52b replace advantageously, on the amplifier chains H, V respectively, the switch 52 of the MAER of FIG. 1.
  • the insertion losses of the circulators are lower than losses caused by conventional switches used in MAER.
  • the switches are located between the amplifiers and the radiating elements (FIG. 1), they severely strain the radar link budget (or the merit factor of the active antenna) , by their losses L e and L r which occur twice, in transmission and reception.
  • the invention overcomes these drawbacks of prior art. According to the invention, a configuration of MAER is proposed which avoid the losses of the switches of the first solution, without increasing the mass and the overall dimensions of the assembly, at equal power, as in the second solution.
  • the invention provides an alternating transmission and reception (E / R) microwave circuit for synthesis antenna with variable polarization synthesis, this E / R circuit able to supply excitation signals for at least two polarizations. orthogonal to radiating sources via two respective channels, these channels supplied respectively by two amplifying power transmission chains; this E / R circuit able to receive at least two signals having orthogonal polarizations detected by these same sources and supplying two low noise amplifier chains in reception; said E / R circuit comprising, in addition to the phase shifter located on the common channel intended to point or form the beam, at least one phase shifter controllable on a transmission channel, and at least one phase shifter controllable on a reception channel intended to choose the polarization said circuit characterized in that the two power amplifier chains operate simultaneously during transmission, and in that the two low noise amplifier chains operate simultaneously during reception.
  • E / R alternating transmission and reception
  • the polarizations H (horizontal) and V (vertical) are obtained by sum or difference of two orthogonal polarizations, inclined by 45 ° to the horizontal: each of them is connected directly to one of the two paths of the E / R circuit.
  • the two chains power amplifiers are powered from a power divider in phase, allowing easy synthesis linear orthogonal polarizations; according to another advantageous realization, the two amplifying chains of power are supplied from a hybrid coupler to two 90 ° phase-shifted outputs, allowing easy synthesis circular polarizations.
  • said phase shifters are one bit digital controllable phase shifters, this bit corresponding to its value, either at 0 ° or 180 °.
  • phase shifters are one bit digital controllable phase shifters, this bit depending on its value, either 0 ° or 90 °.
  • said phase shifters are two-bit digital controllable phase shifters, of which a first bit corresponding according to its value is 0 either 180 ° and a second corresponding bit according to its value either at 0 ° or 90 °.
  • an attenuator variable allows to adjust the gain of at least one chain power amplifier.
  • a variable attenuator adjusts the gain of at least one low noise amplifier chain.
  • said E / R circuit further includes at least two phase shifters and at least two quasi-continuously controllable attenuators, allowing the synthesis of any polarization, linear, circular, or elliptical.
  • said command quasi-continuous phase shifters and attenuators is analog design.
  • said command quasi-continuous phase shifters and attenuators is digital design, with a high number of bits, allowing the synthesis of any polarization, linear, circular, or elliptical.
  • the invention also relates to an antenna comprising E / R circuits according to one of the embodiments or previous variants.
  • the radiant sources are of printed type (or patch in English).
  • the sources radiant consist of annular slots photo-etched on one side of a dielectric substrate with low microwave losses, these slots being excited by photo-etched lines on the face opposite.
  • the slots ring fingers are excited by photo-etched lines on a hanging substrate.
  • the E / R circuits are made in MMIC technology.
  • miniature circulators are added to MMIC circuits to increase power maximum allowed.
  • duplexers miniatures comprising a circulator and an isolator are added to the circuits of the invention, in order to better isolate the transmission channels of the reception channels.
  • the antenna according to the invention is self-adaptive in polarization, for ability to extract useful radar signal in the presence of interference of any fixed polarization; to do, the antenna detects the polarization of the jammer, and adapts the phases and possibly the amplitudes of the signals emitted to work in a polarization orthogonal to that of the jammer.
  • FIG. 3 we see a first schematic example of a MAER circuit according to the invention. Compared to Figures 1 and 2 already described, we have simplified the diagram by ignoring the environment of the circuit shown; nevertheless, this circuit is intended to be installed in the same way as the circuits of the prior art, between a distributor / combiner (22 in FIG. 1) and a network of radiating sources S ij .
  • the variable attenuator 28 and phase shifter 27 are controlled by instructions given by the control computer (not shown), and the E / R switch 6 is controlled by a clock (not shown).
  • the elements 35a, 35b correspond either to the E / R switches (52 in FIG. 1), or to the circulators (52a, 52b in FIG.
  • the elements 5a are distributors and the elements 5b are combiners, the nature of which will be discussed below.
  • Elements 1, 2, 3, 4 are phase shifters, including at least one phase shifter controllable on a transmission channel (s 1 or s 3 ), and at least one phase shifter controllable on a reception channel (s 2 or s 4 ). According to the invention, it is therefore possible that there are only two controllable phase shifters, for example 3 and 4, and that the elements 1, 2 can be removed from this diagram. Several variants of the invention can be built around this general diagram, in particular by playing on the different possibilities for these elements 1, 2, 3, 4; a number of these possibilities will be described later.
  • the element 5a is a power distributor and the element 5b is a power combiner, both operating in phase, that is to say that the phase of the signals s 1 and s 3 is the same, and that the signals s 2 and s 4 are also combined in phase.
  • the elements 1 and 2 does not exist; and elements 3 and 4 are single-bit phase shifters, which introduce a phase shift of either 0 ° or 180 °, depending on the value of the control bit, supplied by control means not shown.
  • the radiating source S k / ij shown in FIG. 3 is an engraved "patch" of square shape, whose orientation is schematically significant. Indeed, the square is oriented with its diagonals respectively to the horizontal and vertically.
  • the propagation lines from switches or circulators 35a, 35b to the patch are mutually perpendicular and oriented at 45 ° from diagonals of the patch.
  • the amplitude of the signals s 1 and s 3 is the same, and the signals s 2 and s 4 have the same amplitudes too.
  • the phase shifter 3 is controlled, according to its control bit, at a value of 0 °, the two accesses are excited in phase by the two power amplifiers 29a, 29b, which results in a wave having a horizontal linear polarization.
  • the phase shifter 3 is controlled, according to its control bit, at a value of 180 °, the two accesses are excited in phase opposition by the two power amplifiers 29a, 29b, which results in a wave having a polarization vertical linear.
  • phase shifter 4 In the same way for reception, if the phase shifter 4 is controlled, according to its control bit, at a value of 0 °, the two accesses which are excited in phase, and after amplification by the two low noise amplifiers 30a, 30b, are combined in phase by the combiner 5b, which corresponds to a wave having a horizontal linear polarization on reception.
  • phase shifter 4 is controlled, according to its control bit, at a value of 180 °, the combiner 5b will have on its inputs the two signals s 2 and s 4 whose signal s 4 will have been phase shifted by 180 °, which means that, only if the two accesses are excited in phase opposition, and after amplification by the two low noise amplifiers 30a, 30b, the result is obtained which corresponds to a wave having a vertical linear polarization.
  • the schematic circuit of FIG. 3 can also provide orthogonal circular polarizations, with hybrid couplers at 90 ° 5a, 5b in place of the phase dividers / combiners considered above.
  • a hybrid coupler 5a on the transmission channel for example, the two power amplification chains will carry the same signal, except that the signal s 3 will be offset by + 90 ° in phase, compared to the signal s 1 (when the phase shifter 3 has a value of 0 °).
  • Excitation of the patch by two orthogonal accesses with a signal s 3 on the first access, offset by + 90 ° in phase with respect to the signal s 1 on the second orthogonal access, results in a wave having a right circular polarization, for example.
  • the reception channel can synthesize waves with right and left circular polarization in the same way, the design being perfectly symmetrical between the tracks transmission and reception.
  • the elements 35a, 35b can be E / R switches controlled by the clock (not shown), or they can be circulators, which allow the signal to pass through power amplifiers 29a, 29b to the radiating source S ij , or vice versa, from the source S ij to the low noise amplifiers 30a, 30b, but in no case will the signal be allowed to pass from the power amplifiers 29a, 29b to the low noise amplifiers 30a, 30b.
  • the circuit can have the ability to synthesize either linear orthogonal polarizations or orthogonal circular polarizations.
  • phase shifters with two control bits in blocks 3, 4 on the diagram, with dividers / combiners in phase for elements 5a, 5b.
  • the first command bit depending on its value, will give a phase from 0 ° or 180 ° as before, and to this phase will be added the phase controlled by the second control bit, from 0 ° or 90 °.
  • the circuit is equivalent to that discussed before where elements 5a, 5b were 90 ° hybrid couplers, that is, we we find us in a configuration that allows us to synthesize right and left circular polarizations.
  • a variant allowing the synthesis of linear orthogonal polarizations includes two 90 ° hybrid couplers 5a, 5b, and four 0 or 90 ° phase shifters to a control bit 1, 2, 3, 4.
  • a horizontal polarization of emission is obtained if the phase shifter 1 has a phase shift of 0 ° and the phase shifter 3 has a 90 ° phase shift (which is added to the 90 ° phase shift of the hybrid coupler); with the same to reception, with 0 ° on the phase shifter 2, and 90 ° on the phase shifter 4.
  • Vertical polarization is obtained by reversing the phase shifts of the four phase shifters.
  • the realization can be simplified by the fact that with identical phase shifters on all four channels, just select components with the same losses and insertion phases to approach the circuit ideal for polarization synthesis.
  • a final variant of Figure 3 will be for synthesize orthogonal circular polarizations, using the same trick as in the previous case: four phase shifters 1, 2, 3, 4 at 0 or 90 ° and one control bit, but with phase dividers / combiners 5a, 5b.
  • a right circular polarization is obtained with a 90 ° phase shift on phase shifters 1, 3 and 0 ° on phase shifters 2, 4; and conversely, a polarization left circular is obtained with a 90 ° phase shift on phase shifters 2, 4 and 0 ° on phase shifters 1 and 3.
  • the instant orientation of the polarization vector is given by the relative phases coming from the phase shifters 27a, 27b which can take arbitrary and variable values over time, and the relative amplitude of the signals passing through variable attenuators can also take arbitrary and time-varying values, for determine the length of each of the two projections of the vector of the electric field, on the two orthogonal axes, corresponding to the polarizations generated on each of the access to radiant elements.
  • the polarization will be linear when this phase shift is 180 °; it will be circular if it is +/- 90 °, and that the attenuations of the two channels are equal; we have an elliptical polarization in the case where the phase shift takes a different value, or linear, or good if the attenuations of the two channels are different.
  • the transmission signal arrives at a power divider, and is sent to the two circulators 7a, 7b after division in phase.
  • E / R circuits in parallel, the description of which conforms to the descriptions in the previous figures, with the same references representing the same elements in all the figures.
  • These two circuits deliver signals on two orthogonal accesses to the radiating source S ij , with a relative phase and a relative amplitude which are determined by the controllable attenuators and phase shifters 28a, 28b, and 27a, 27b respectively.
  • reception signal from the source S ij is probed by the two orthogonal ports, and the two received signals are amplified separately by the low noise amplifiers 30a, 30b. Their relative amplitude and their relative phase are adjusted by the controllable attenuators and phase shifters 28a, 28b and 27a, 27b respectively, according to the polarization of the received wave that one wishes to look at. These signals are then transmitted, via the circulators 7a, 7b to separate reception channels for signal processing in an appropriate computer (not shown).
  • This possibility of synthesis of a polarization arbitrary allows to obtain a self-adapting antenna, that is to say who can reconfigure to take into account a environment polluted by parasitic emissions intentional or not.
  • the principle consists in measuring the dominant polarization of the radio environment at the operating frequency band of the equipment, putting the attenuators and phase shifters in a state of reference. The polarization of the emission is then chosen orthogonal to this dominant polarization. This mode may allow operation significantly improved in the presence of interference intentional with stationary polarization, or in the case where unwanted specular reflections mask a target radar of small equivalent surface, but not presenting a specularity.
  • FIG 6 we have shown schematic a simplest configuration of a circuit microwave according to the invention. Following the characteristics of components used, this circuit will suitable for either transmitting or receiving signals polarized synthesis microwave. Such circuits find applications for radar antennas multistatic, for example, or in the antennas of telecommunications.
  • this circuit would be intended for amplification of signals for transmission.
  • element 5 is a divider of power, either a phase divider or a coupler hybrid with a 90 ° phase shift.
  • Blocks 1, 3 represent phase shifters controllable at 0, 1, or 2 bits, having values of phase shift of 0-0 °, 0-90 °, or 0-180 °, as in the Description of Figure 3.
  • the construction of the circuit is strictly analogous to the description given for this Figure 3, with regard to the transmission channel.
  • the components 20a, 20b are then amplifiers of power, which feed through channels inclined at 45 ° from the horizontal, the patches S k / ij.
  • this circuit would be intended for amplification of signals for reception.
  • a signal from very low level arriving at the radiating element S k / ij is routed by access roads inclined at 45 ° to horizontally, towards the low noise amplifiers 20a, 20b.
  • the signals will be combined either in phase or with a 90 ° phase shift, thanks to the means 5 which are either a phase combiner, i.e. a hybrid coupler with a 90 ° phase shift between its two inputs.
  • the signals will then routed through a phase shift and attenuation controllable according to the position of the radiating element in the network antenna network.
  • controllable phase shifters can to be almost continuous, as in the case of previous figure 5, to allow greater flexibility in the synthesis of polarizations, if necessary.
  • the radiating sources can also be annular slots photo-etched in an upper ground plane, excited by lines directed at 45 ° relative to the directions H and V, located in a lower plane, ie on the other face of the substrate comprising the plane mass and slots; either on a second suspended substrate, the two substrates kept spaced from each other by spacers or by a material having low microwave losses, such as foam or honeycomb.
  • Such constructions of networks of radiating sources and their power supplies are well known to those skilled in the art, and are described for example in the Proceedings of Military Microwaves 1992 , "Antennas for space scatteromertes and SARS", by R. Petersson , the description of the prior art of which forms an integral part of the present application.
  • circuits presented as an example in the figures can also be made according to different technologies without departing from the scope of the invention: if MMIC is a preferred technology for its low mass and congestion, as well as these remaining production costs reasonable for large series production, a higher transmitting power can be tolerated in using circulators instead of switches integrated downstream of the power amplifiers. The size and mass of these circulators are higher but the losses lower than the losses of MMIC switches.

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  • Radar Systems Or Details Thereof (AREA)

Claims (18)

  1. Ultrahochfrequenzschaltung zum abwechselnden Senden und Empfangen (E/R) für Gruppenantennen mit variabler Polarisations-Synthese, wobei diese E/R-schaltung fähig ist, Erregungssignale für wenigstens zwei orthogonale Polarisationen an zwei Strahlungsquellen (S k / ij) über zwei jeweilige zugangswege zu liefern, wobei diese Zugangswege von zwei Sende-Leistungsverstärkerketten (29a, 29b) gespeist werden; wobei diese E/R-Schaltung fähig ist, wenigstens zwei Signale zum empfangen, die orthogonale Polarisation haben, die von denselben Quellen erfaßt werden und zwei Empfangsverstärkerketten (30a, 30b) mit geringem Rauschen speisen; dadurch gekennzeichnet, daß die E/R-Schaltung außerdem wenigstens einen steuerbaren Phasenschieber (1, 3) auf einem der beiden Sendewege und wenigstens einen steuerbaren Phasenschieber (2, 4) auf einem der beiden Empfangswege aufweist, und daß die beiden Leistungsverstärkerketten (29a, 29b) bei Sendung gleichzeitig arbeiten und daß die beiden Verstärkerketten (30a, 30b) mit geringem Rauschen bei Empfang gleichzeitig arbeiten.
  2. Schaltung nach Anspruch 1, dadurch gekennzeichnet, daß die beiden Zugangswege mit den Strahlungsquellen (S k / ij) so verbunden sind, daß Polarisationen erzeugt werden, die in bezug auf die Horizontale um 45° geneigt sind, was beim Spielen an den Phasenschiebern (1, 2, 3, 4) gestattet, die horizontale H oder vertikale V konventionelle Polarisation herzustellen.
  3. E/R-Schaltung nach einem der Ansprüche 1 oder 2, dadurch gekennzeichnet, daß die beiden Leistungsverstärkerketten (29a, 29b) von einem Leistungsphasenteiler (5a) aus gespeist werden, der die leichte Synthese der orthogonalen, linearen Polarisationen gestattet.
  4. E/R-Schaltung nach einem der Ansprüche 1 bis 3, dadurch gekennzeichnet, daß die beiden Leistungsverstärkerketten (29a, 29b) von einem Richtkoppler (5a) mit zwei um 90° phasenverschobenen Ausgängen aus gespeist werden, der die leichte Synthese von Zirkularpolarisationen gestattet.
  5. E/R-Schaltung nach einem der Ansprüche 1 bis 4, dadurch gekennzeichnet, daß die Phasenschieber steuerbare digitale Phasenschieber mit einem Bit sind, wobei dieses Bit je nach seinem Wert entweder 0° oder 180° entspricht.
  6. E/R-Schaltung nach einem der Ansprüche 1 bis 4, dadurch gekennzeichnet, daß die Phasenschieber steuerbare digitale Phasenschieber mit zwei Bits sind, wovon ein erstes Bit je nach seinem Wert entweder 0° oder 180° entspricht und ein zweites Bit je nach seinem Wert entweder 0° oder 90° entspricht, die gestatten, eine der folgenden vier konventionellen Polarisationen herzustellen: linear H oder V, zirkular rechts oder links.
  7. E/R-Schaltung nach einem der Ansprüche 1 bis 4, dadurch gekennzeichnet, daß die Phasenschieber steuerbare digitale Phasenschieber mit einem Bit sind, wobei dieses Bit je nach seinem Wert entweder 0° oder 90° entspricht.
  8. E/R-Schaltung nach einem der Ansprüche 1 bis 7, dadurch gekennzeichnet, daß ein Regelglied das Einstellen der Verstärkung wenigstens einer der Leistungsverstärkerketten gestattet.
  9. E/R-Schaltung nach einem der Ansprüche 1 bis 8, dadurch gekennzeichnet, daß ein Regelglied das Einstellen der Verstärkung wenigstens einer der Verstärkerketten mit geringem Rauschen gestattet.
  10. E/R-Schaltung nach einem der Ansprüche 1 bis 9, dadurch gekennzeichnet, daß die E/R-Schaltung außerdem wenigstens zwei Phasenschieber und wenigstens zwei in quasikontinuierlicher Weise steuerbare Dämpfungsglieder aufweist, die die Synthese irgendeiner Linear-, Zirkular- oder elliptischen Polarisation gestatten.
  11. E/R-Schaltung nach Anspruch 10, dadurch gekennzeichnet, daß die quasi-kontinuierliche Steuerung der Phasenschieber und der Dämpfungsglieder eine analoge Gestaltung hat.
  12. E/R-Schaltung nach Anspruch 10, dadurch gekennzeichnet, daß die quasi-kontinuierliche Steuerung der Phasenschieber und der Dämpfungsglieder eine digitale Gestaltung mit einer erhöhten Anzahl von Bits hat, die die Synthese irgendeiner Linear-, Zirkular- oder elliptischen Position gestattet.
  13. Gruppenantenne mit variabler Polarisations-Synthese an strahlenden Elementen, dadurch gekennzeichnet, daß die Antenne Sende/Empfangs-Schaltungen nach einem der Ansprüche 1 bis 12 aufweist.
  14. Gruppenantenne nach Anspruch 13, dadurch gekennzeichnet, daß die Antenne Strahlungsquellen aufweist, die vom gedruckten Typ sind (oder auf englisch "patch").
  15. Gruppenantenne nach Anspruch 13, dadurch gekennzeichnet, daß die Antenne Strahlungsquellen aufweist, die auf einer Seite eines dielektrischen Substrats, das geringe Ultrahochfrequenzverluste aufweist, photogravierte, ringförmige Spalte sind, wobei diese Spalte durch photogravierte Linien auf der entgegengesetzten Seite erregt werden.
  16. Gruppenantenne nach Anspruch 15, dadurch gekennzeichnet, daß die Spalte durch photogravierte Linien auf einem aufgehängten Substrat erregt werden.
  17. E/R-Schaltung nach einem der Ansprüche 1 bis 12, dadurch gekennzeichnet, daß die Schaltung in MMIC-Technologie ausgeführt ist.
  18. Gruppenantenne nach einem der Ansprüche 13 bis 16, dadurch gekennzeichnet, daß die Antenne eine sich in der Polarisation selbst anpassende Antenne ist.
EP93402925A 1992-12-04 1993-12-02 Aktive Antenne mit variabler Polarisations-Synthese Expired - Lifetime EP0600799B1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
FR9214661 1992-12-04
FR9214661A FR2699008B1 (fr) 1992-12-04 1992-12-04 Antenne active à synthèse de polarisation variable.

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EP0600799A1 EP0600799A1 (de) 1994-06-08
EP0600799B1 true EP0600799B1 (de) 1998-10-14

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US (1) US5659322A (de)
EP (1) EP0600799B1 (de)
CA (1) CA2110634C (de)
DE (1) DE69321561T2 (de)
ES (1) ES2125317T3 (de)
FR (1) FR2699008B1 (de)

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CA2110634A1 (fr) 1994-06-05
EP0600799A1 (de) 1994-06-08
ES2125317T3 (es) 1999-03-01
FR2699008A1 (fr) 1994-06-10
CA2110634C (fr) 2000-02-15
DE69321561D1 (de) 1998-11-19
US5659322A (en) 1997-08-19
FR2699008B1 (fr) 1994-12-30
DE69321561T2 (de) 1999-04-01

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