EP0522266A1 - Ballast protégé contre surtension - Google Patents

Ballast protégé contre surtension Download PDF

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Publication number
EP0522266A1
EP0522266A1 EP92108304A EP92108304A EP0522266A1 EP 0522266 A1 EP0522266 A1 EP 0522266A1 EP 92108304 A EP92108304 A EP 92108304A EP 92108304 A EP92108304 A EP 92108304A EP 0522266 A1 EP0522266 A1 EP 0522266A1
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EP
European Patent Office
Prior art keywords
input
voltage
monitoring circuit
ballast according
inverter
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP92108304A
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German (de)
English (en)
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Vossloh Schwabe GmbH
Original Assignee
Vossloh Schwabe GmbH
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Vossloh Schwabe GmbH filed Critical Vossloh Schwabe GmbH
Publication of EP0522266A1 publication Critical patent/EP0522266A1/fr
Withdrawn legal-status Critical Current

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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/295—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps
    • H05B41/298—Arrangements for protecting lamps or circuits against abnormal operating conditions
    • H05B41/2981—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions
    • H05B41/2985—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions against abnormal lamp operating conditions

Definitions

  • the invention relates to a ballast with the features of the preamble of claim 1.
  • the inverter only contains a half bridge made of two power transistors connected in series in order to reduce the outlay on components.
  • the gas discharge lamp is connected to the junction of the two power transistors and its other electrode is connected to one of the two supply voltage connections of the inverter.
  • the maximum voltage to be generated in this way on the gas discharge lamp is too low during mains operation to ignite the gas discharge lamp.
  • the gas discharge lamp is not connected directly to the output of the inverter, but rather via a choke which, together with a capacitor lying parallel to the gas discharge lamp, forms a series resonance circuit forms. When the inverter is operated at the resonance frequency of the series resonance circuit, a voltage rise occurs on the capacitor in accordance with the quality of the series resonance circuit. The excess voltage is sufficient to safely ignite the gas discharge lamp.
  • the transistors of the inverter may be overloaded, because a series resonance circuit may have a very low ohmic loss resistance in response to the quality.
  • the known circuit contains a harmonic filter in the one supply line to the gas discharge lamp, which has the purpose of generating a largely sinusoidal network load.
  • This harmonic filter interacts with the smoothing capacitor, which is connected to the output of the line rectifier, in order to adequately sift the full-wave rectified line voltage. If the fluorescent lamp fails, the harmonic filter acts as a pump circuit, which can overload the smoothing capacitor and thus lead to an overload in terms of voltage. To prevent this, a voltage divider is connected in parallel to the smoothing capacitor.
  • the voltage divided by the voltage divider is fed to the gate of a thyristor, which is also connected in parallel to the smoothing capacitor via a resistor.
  • the base of one of the two power transistors is connected to the connection point between the resistor and the thyristor. If the voltage across the capacitor exceeds a predetermined threshold, which is predetermined by the ignition voltage of the thyristor and the voltage divider ratio, the thyristor ignites and shorts the base of the power transistor in question to ground. The inverter then stops vibrating.
  • the new ballast makes use of the fact that when the gas discharge lamp is not burning, the circuit quality of the series resonant circuit at the output of the inverter is significantly greater than in the burning state and therefore that of the capacitor, which is essentially determined together with the inductance of the resonance frequency, is a significantly higher AC voltage than occurs in normal operation.
  • the AC voltage occurring at the connection between the inductance and the capacitance of the series resonance circuit is therefore monitored to determine whether it exceeds a specified limit value.
  • Exceeding the specified limit corresponds to an impermissibly high current in the series resonance circuit that if it were to flow over a longer period of time, the power transistors in the inverter would cause a power loss that was above the permissible value.
  • the permissible value of the power loss for the power transistors also results, for example, from the cooling surface on which the power transistors are mounted.
  • the voltage can be tapped either from the total capacitance of the series resonance circuit or from a partial capacitance. In the latter case, the voltage amplitude is lower in accordance with the division ratio of the capacitance, which may be advantageous.
  • the power transistors of the inverter are also endangered by overvoltages in the grid. Even in the event of overvoltages in the grid, inadmissibly high power losses can occur during operation of the inverter.
  • the monitoring circuit has a second input into which a signal is fed which is proportional to the supply voltage for the inverter.
  • the monitoring circuit In order to avoid a constant switching back and forth of the monitoring circuit between the blocking signal and no blocking signal at its output, it is expedient to provide the monitoring circuit with a bistable switching characteristic. As a result, it remains in the state with a blocking signal at the output until it is switched off by switching off the supply voltage, i.e. Pressing the light switch is reset to the idle state in which it does not generate a blocking signal at its output.
  • the component-related effort for the new ballasts is reduced if both inputs have separate Drive signal paths to a common threshold-sensitive component.
  • the monitoring circuit can be provided with a delay device, which has the effect that the ballast only emits the blocking signal when one of the Overvoltage conditions occur at the input.
  • each of the two signal paths can contain its own delay element.
  • the required OR combination can be generated either by diodes or by additional electronic components influencing the switching threshold of the respective input, e.g. diacs, because a completely non-reactive combination of the two signal paths is not possible is absolutely necessary.
  • the control input of a switching transistor is expediently connected in series with the threshold-sensitive component.
  • the switching path of the transistor forms the output of the monitoring circuit.
  • a thyristor can be used as the threshold-sensitive component, which also has the advantage of being bistable without additives. Once ignited, it remains in the conductive state until the supply voltage for the monitoring circuit is switched off, which is equivalent to the switching off of the supply voltage for the ballast.
  • the supply voltage for the monitoring circuit can easily be derived from the signal at the second input.
  • the inverter can be prevented from triggering again at the same time.
  • the second input can act as an output at the same time if, for example, the second input is switched to low impedance when the monitoring circuit reaches its output with the blocking signal. If the supply voltage for the trigger device for the inverter is connected to the second input.
  • the figure shows a ballast 1 that can be operated on an AC voltage network and that contains an inverter 2 that operates a gas discharge lamp 4 with two heating filaments 5, 6 on the output side via a series resonance circuit 3.
  • a monitoring circuit 7 serves to protect the inverter 2 against the permissible power loss being exceeded.
  • the inverter 2 is connected as a half-bridge and contains two series-connected power transistors 8 and 9.
  • the emitter of the transistor 9 is connected to a circuit ground 12 via an emitter resistor 11, while its collector is electrically connected to the emitter of the transistor 8 via a further emitter resistor 13 .
  • the connection point between the collector of the transistor 9 and the emitter resistor 13 forms an output 14 of the inverter 2.
  • the collector of the power transistor 8 is finally connected to a power supply output 15 of a power supply 16.
  • the power supply 16 has two input connections 17, via which an AC mains voltage is fed. By full-wave rectification by means of a rectifier 18 and a filter capacitor 19, it generates a largely smoothed DC output voltage between its connection 15 and the circuit ground 12.
  • Two freewheeling diodes 21 and 22 are connected in parallel to the two power transistors 8, 9 including their emitter resistors 11, 12, namely the freewheeling diode 21 lies between the output 14 and the circuit ground 12, while the freewheeling diode 22 is connected between the output 14 and the positive supply voltage connection 15 is.
  • An ohmic resistor 23 finally lying in parallel with the freewheeling diode 22 should, if appropriate, prevent RF oscillations with a further capacitor connected in parallel, which can occur if one of the two heating filaments 5, 6 is broken in the gas discharge lamp 4 or the gas discharge lamp 4 is completely absent.
  • the series resonant circuit 3 contains a primary winding 24 of a saturation transformer 25, which also carries two secondary windings 26 and 28.
  • the secondary winding 26 is connected in parallel to the series connection of the emitter resistor 13 and the base-emitter path of the transistor 8, while the secondary winding 27 is connected in parallel in a corresponding manner to the base-emitter path of the power transistor 9 and the emitter resistor 11 lying in series therewith.
  • the primary winding 24 connects the output 14 via the choke 30 to a capacitor 28, the purpose of which is to decouple the DC voltage present at the output 14. Its capacity is large compared to the capacity of a capacitor 29 to which the capacitor 28 is connected via the heating coil 6.
  • the heating coil 5 finally connects the other end of the capacitor 29 to the positive supply voltage connection 15. Since the capacitor 28 is large compared to the encoder 29, the resonance frequency of the series resonance circuit is formed from the primary winding 24, the choke 30 and the two Capacitors 28 and 29, essentially determined by the inductance of the choke 30 and the capacitance of the capacitor 29.
  • the gas discharge lamp 4 is parallel to this, the current flowing through the two heating filaments 5, 6.
  • the monitoring circuit 7 is provided with a first input 31, a second input 32 and an output 33.
  • the inputs 31, 32 and the output 33 are asymmetrical and receive or carry the signals with respect to the circuit ground 12.
  • the active element of the monitoring circuit 7 is a tyristor 34, the anode of which is connected to the second input 32.
  • Signal paths 35 and 36 lead from both inputs 31, 32 to the gate of the tyristor 34, the cathode of which acts on the base of an NPN transistor 37 which is connected to the circuit ground 12 with its emitter. Its collector represents the output 33 of the monitoring circuit 7.
  • the signal path 35 contains a voltage divider comprising two resistors 38 and 39 connected in series, which connect the input 32 to the circuit ground 12.
  • a capacitor 41 serving as a delay element is connected in parallel with the resistor 39, which is connected to the circuit ground 12.
  • a diac 42 leads from the common junction of the two resistors 38, 39 and the capacitor 41 to the gate of the tyristor 34.
  • the second input 32 receives its signal via a resistor 43, which connects the second input 32 to the connection point between the lamp filament 5 and the capacitor 29.
  • the first input 31 is connected to the connection point between the capacitor 28 and the lamp filament 6 and its signal path 36 contains a voltage divider, connected against the circuit ground 12, of two resistors 44 and 45. From the junction of the two resistors 44 and 45, a diode 46 leads to a parallel connection of a capacitor 47 and a resistor 48, namely the diode 46 with its cathode on the parallel connection, which is connected at the other end to the circuit ground 12.
  • a diac 49 likewise leads from the common connection point of the capacitor 47 with the resistor 48 and the diode 46 to the gate of the tyristor 34.
  • the output 33 of the monitoring circuit 7 is finally connected to the base of the power transistor 9.
  • a trigger circuit 51 is provided. Starting from the circuit ground 12, this has, in series, a capacitor 52, a current limiting resistor 53 and a charging resistor 54, the hot end of which is connected to the second input 32 of the monitoring circuit 7.
  • a diac 55 leads from the junction of the two resistors 53 and 54 to the base of the power transistor 9 and also a diode 56 to the output 14, the cathode being connected to the output 14 from the diode 56.
  • the power supply 16 After the mains voltage has been applied to the two input connections 17, the power supply 16 outputs an essentially smoothed DC voltage of approximately 340 V at its output 15 with respect to ground 12. This tension is on the one hand directly connected to the series circuit of the two power transistors 8 and 9 and on the other hand via the lamp filament 5, the resistor 43 also on the trigger circuit 51.
  • the capacitor 52 is charged in a short time via the resistor 54. As soon as it reaches a charging voltage which is equal to the breakdown voltage of the diac 55, the diac 55 generates a current pulse by allowing the capacitor 52 to be discharged via the base-emitter path of the transistor 9.
  • the transistor 9 is controlled to be conductive, and a collector current is produced which flows through the primary winding 24 and the two capacitors 28 and 29 from the connection 15 of the power supply circuit 16.
  • This exponentially increasing current through the primary winding 24 induces a voltage in the secondary winding 27 with a polarity such that it keeps the transistor 9 open.
  • the current through the winding 24 can no longer rise, or because the iron of the saturation transformer 25 saturates, the induced voltage in the secondary winding 27 disappears, whereupon the transistor 9 switches to the off state.
  • the current in the primary winding 24, which continues to flow via the freewheeling diodes 21 and 22, begins to fall, which induces a voltage in its secondary winding 26 with a polarity that controls the connected transistor 8.
  • the transistor 8 remains on until either the iron core of the transformer 25 comes into saturation or the current 24 cannot continue to rise during the start-up phase due to the increasing charge or discharge of the capacitors 28, 29. As soon as this state is reached, the transistor 8 switches off. The now flowing freewheeling current decays and generates again, now in the primary winding 27, a voltage driving the transistor 9, whereby the initial state is reached again.
  • the capacitor 52 is also discharged via the diode 56 then operated in the forward direction. Since the charging time constant for the capacitor 52 is large compared to the oscillation frequency of the inverter 2 as a result of the two resistors 53 and 54 lying in series, the voltage at the encoder 52 will never reach a level sufficient for the diac 55 to trigger in later operation . This ensures that the later oscillating operation of the inverter is not disturbed or even destroyed by asynchronous current pulses for the transistor 9.
  • the inverter 2 inevitably oscillates at the resonance frequency of the series resonance circuit 3, which, as mentioned, is formed by the inductance of the primary winding 24 and the choke 30 and the capacitors 28 and 29.
  • the operation of the inverter 2 at the resonant frequency of the series resonant circuit 3 results in a voltage surge at the capacitors 28 and 29, the voltage drop across the capacitor 29 being substantially greater than that at the capacitor 28, since it is generally about one or two Powers of ten is smaller, so that the capacitor 28 has no significant influence on the oscillation frequency. It should only keep the DC voltage from the gas discharge lamp 4.
  • the alternating voltage which arises on the capacitor 29 after the inverter 2 has started and the series resonant circuit 3 has settled has such a magnitude that it readily ignites the gas discharge lamp 4, even if both of their heating coils 5, 6 are cold, ie are at room temperature.
  • the operation just described is the normal ignition and burning operation of the gas discharge lamp 4.
  • the voltage from the power supply part 16 also reaches the second input 32 of the monitoring circuit 7 via the resistor 43.
  • the resistors 38, 39 pass through the voltage divider in accordance with the internal resistance given by the voltage divider, the capacitor 41 is charged with a corresponding time constant.
  • the voltage across capacitor 41 remains below the breakdown voltage of diac 42, which consequently remains in the blocked state.
  • the alternating voltage dropping at the gas discharge lamp 4 which is superimposed on the supply voltage, reaches the input 31.
  • the voltage divider following the input 31 from the resistors 44 and 45 divides the voltage down.
  • the divided voltage charges the capacitor 47 via a diode 46. Because of the voltage division, the latter can only be charged to the voltage which is less than the breakdown voltage of the diac 49, so that this too remains in a non-conductive state.
  • the resistance 48 also affects the voltage divider ratio, but is relatively large and has only the task of ensuring that the capacitor 47 is discharged when the AC voltage at the input terminals 17 is switched off.
  • the voltage at the gas discharge lamp 4 increases and, owing to the higher operating voltage, the power loss at the two transistors 8 and 9.
  • the higher supply voltage also leads to the capacitor 41 being on a higher voltage is charged. Because of the high internal resistance of the voltage divider from the resistors 38 and 39, the voltage across the capacitor 41 does not immediately follow the rise in the mains voltage, but rather with a considerable time delay. Only when the overvoltage in the network has lasted long enough or has been high enough will the voltage across the capacitor 41 finally reach a value which is greater than the forward voltage for the diac 42 plus the gate-cathode voltage of the thyristor 34 and the base -Emitter voltage of transistor 37.
  • Diac 42 becomes conductive and generates an ignition pulse for the gate of thyristor 34, which then switches on.
  • a base current is created for the transistor 37, which becomes conductive and the base of the transistor via its collector-emitter path 9 shorts to the circuit ground 12.
  • the vibrations of the inverter 2 break off because one of the two transistors, namely the transistor 9 can no longer be turned on by the associated control voltage from the saturation transformer 25.
  • the current through thyristor 34 into the base of transistor 37 is limited by resistor 43 and held at values that do not destroy the base of transistor 37.
  • the trigger circuit 51 is also connected to the second input 32 in terms of power supply, the necessary voltage for the trigger circuit 51 is missing as soon as the thyristor 34 has ignited.
  • the voltage at the input 32 drops immediately after the firing of the thyristor 34 to the forward voltage of the thyristor 34 plus the base-emitter voltage of the transistor 37.
  • the capacitor 52 can no longer be charged to the voltage required to turn on the diac 55 and is missing consequently the ignition pulses, which could otherwise lead to the inverter 2 starting.
  • the low-resistance state of the transistor 37 thus represents a blocking signal that the monitoring circuit 7 outputs at its output 33 as soon as the voltage at the input 32 reaches a value which is above the threshold value typical for this input 32.
  • the threshold value results from the voltage divider ratio of the resistors 38 and 39, as well as the forward voltage of the diac 42 and the downstream components 34 and 37.
  • the blocking signal at the output 33 does not appear immediately if there is a brief increase in the mains voltage, since such a process is not dangerous for the two power transistors 8 and 9.
  • the Capacitor 41 suppresses such brief input signals due to its integrating effect.
  • the thyristor 34 remains conductive until the mains voltage has been switched off by the input terminals 17. An automatic restart is thus effectively prevented.
  • An overload of the two power transistors 8 and 9 of the inverter 2 can also occur if the gas discharge lamp 4 does not ignite after an appropriate time.
  • the non-ignited gas discharge lamp 4 represents practically no load on the capacitor 29, so that the quality of the series resonant circuit 3 is high.
  • a series resonance circuit with high quality shows a correspondingly low internal resistance, which in turn results in a large active current through the series resonance circuit. If this state were to last too long, the power loss of the two transistors 8 and 9 would be exceeded and they would be irreversibly destroyed. Such a dangerous operating state is therefore monitored with the aid of the input 31, because in the case of a non-igniting gas discharge lamp 4, the voltage across the capacitor 47 gradually rises to the forward voltage of the diac 49.
  • the rise in the voltage across the capacitor 47 takes place with a time delay, so that the gas discharge lamp is properly ignited 4 is made possible. Only when sufficient time has elapsed during which the gas discharge lamp 4 should have ignited does the voltage at the capacitor 47 reach the forward voltage of the diac 49, which then generates an ignition pulse for the thyristor 34 via the capacitor 47. This, in turn, turns on, drives the transistor 37, as previously described, which, via its collector-emitter path, forms the base of the Short-circuits transistor 9 to the circuit ground 12 and switches off the inverter 2.
  • the control voltage for the other power transistor 8 also fails and both transistors 8, 9 remain blocked.
  • the thyristor 34 automatically remains in the conductive state until the supply voltage is switched off. A non-igniting gas discharge lamp 4 cannot damage the ballast 1.
  • the transistor 37 has a high resistance and therefore does not load the base of the transistor 9.
  • the inverter 2 then operates as if there were no monitoring circuit 7.
  • each of the two operating states can be monitored, which leads to an inadmissible power loss at the two power transistors 8 and 9. It is not necessary to actually measure the current flowing through the inverter 2, so that an additional current sensor, which would increase the power loss, is unnecessary.
  • the two signals which are fed into the inputs 31 and 32 are of the same order of magnitude, so that simple voltage dividers and diacs and / or diodes are sufficient to control one and the same thyristor 34. In the case of a current sensor, on the other hand, additional reinforcing elements would be required, which would drive up the component expenditure.

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  • Circuit Arrangements For Discharge Lamps (AREA)
EP92108304A 1991-06-22 1992-05-16 Ballast protégé contre surtension Withdrawn EP0522266A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE4120649 1991-06-22
DE19914120649 DE4120649A1 (de) 1991-06-22 1991-06-22 Ueberspannungsgeschuetztes vorschaltgeraet

Publications (1)

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EP0522266A1 true EP0522266A1 (fr) 1993-01-13

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DE (1) DE4120649A1 (fr)

Cited By (20)

* Cited by examiner, † Cited by third party
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EP0659037A2 (fr) * 1993-12-15 1995-06-21 General Electric Company Ballast avec indicateur de son fonctionnement pour lampe à décharge
WO1996035318A1 (fr) * 1995-05-05 1996-11-07 Bailey Arthur R Circuit haute frequence de tube fluorescent a ballast de protection
WO1998023135A1 (fr) * 1996-11-19 1998-05-28 Electro-Mag International, Inc. Circuit d'adaptation a ballast magnetique
US5877926A (en) * 1997-10-10 1999-03-02 Moisin; Mihail S. Common mode ground fault signal detection circuit
US6020688A (en) * 1997-10-10 2000-02-01 Electro-Mag International, Inc. Converter/inverter full bridge ballast circuit
US6028399A (en) * 1998-06-23 2000-02-22 Electro-Mag International, Inc. Ballast circuit with a capacitive and inductive feedback path
US6069455A (en) * 1998-04-15 2000-05-30 Electro-Mag International, Inc. Ballast having a selectively resonant circuit
US6091288A (en) * 1998-05-06 2000-07-18 Electro-Mag International, Inc. Inverter circuit with avalanche current prevention
US6100648A (en) * 1999-04-30 2000-08-08 Electro-Mag International, Inc. Ballast having a resonant feedback circuit for linear diode operation
US6100645A (en) * 1998-06-23 2000-08-08 Electro-Mag International, Inc. Ballast having a reactive feedback circuit
US6107750A (en) * 1998-09-03 2000-08-22 Electro-Mag International, Inc. Converter/inverter circuit having a single switching element
US6127786A (en) * 1998-10-16 2000-10-03 Electro-Mag International, Inc. Ballast having a lamp end of life circuit
US6137233A (en) * 1998-10-16 2000-10-24 Electro-Mag International, Inc. Ballast circuit with independent lamp control
US6153410A (en) * 1997-03-25 2000-11-28 California Institute Of Technology Recombination of polynucleotide sequences using random or defined primers
US6160358A (en) * 1998-09-03 2000-12-12 Electro-Mag International, Inc. Ballast circuit with lamp current regulating circuit
US6169375B1 (en) 1998-10-16 2001-01-02 Electro-Mag International, Inc. Lamp adaptable ballast circuit
US6181083B1 (en) 1998-10-16 2001-01-30 Electro-Mag, International, Inc. Ballast circuit with controlled strike/restart
US6181082B1 (en) 1998-10-15 2001-01-30 Electro-Mag International, Inc. Ballast power control circuit
US6188553B1 (en) 1997-10-10 2001-02-13 Electro-Mag International Ground fault protection circuit
US6222326B1 (en) 1998-10-16 2001-04-24 Electro-Mag International, Inc. Ballast circuit with independent lamp control

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE19819671B4 (de) * 1998-05-02 2008-04-10 Insta Elektro Gmbh Schaltungsanordnung zum Schutz von Leuchtstofflampen und elektronischem Vorschaltgerät
DE10046443A1 (de) * 2000-09-18 2002-03-28 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Elektronische Schaltung zur Detektion des Wandelbruchs bei Gasentladungslampen
DE10206731B4 (de) * 2002-02-18 2016-12-22 Tridonic Gmbh & Co Kg Lampensensor für ein Vorschaltgerät zum Betrieb einer Gasentladunslampe

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DD257535A1 (de) * 1984-11-07 1988-06-15 Akad Wissenschaften Ddr Elektronisches vorschaltgeraet fuer leuchtstofflampen
DE3805510A1 (de) * 1988-02-22 1989-08-31 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Schaltungsanordnung zum betrieb einer niederdruckentladungslampe

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AT390156B (de) * 1985-05-14 1990-03-26 Zumtobel Ag Schutzschaltung fuer eine wechselrichterschaltung
DE3743422A1 (de) * 1987-12-21 1989-06-29 Zumtobel Ag Schaltungsanordnung zum betreiben einer oder mehrerer niederdruckentladungslampen
DE3925899A1 (de) * 1989-08-04 1991-02-07 Zumtobel Ag Elektronisches vorschaltgeraet fuer gasentladungslampen

Patent Citations (2)

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Publication number Priority date Publication date Assignee Title
DD257535A1 (de) * 1984-11-07 1988-06-15 Akad Wissenschaften Ddr Elektronisches vorschaltgeraet fuer leuchtstofflampen
DE3805510A1 (de) * 1988-02-22 1989-08-31 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Schaltungsanordnung zum betrieb einer niederdruckentladungslampe

Cited By (24)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0659037A3 (fr) * 1993-12-15 1997-03-26 Gen Electric Ballast avec indicateur de son fonctionnement pour lampe à décharge.
EP0659037A2 (fr) * 1993-12-15 1995-06-21 General Electric Company Ballast avec indicateur de son fonctionnement pour lampe à décharge
WO1996035318A1 (fr) * 1995-05-05 1996-11-07 Bailey Arthur R Circuit haute frequence de tube fluorescent a ballast de protection
WO1998023135A1 (fr) * 1996-11-19 1998-05-28 Electro-Mag International, Inc. Circuit d'adaptation a ballast magnetique
US6011362A (en) * 1996-11-19 2000-01-04 Electro-Mag International, Inc. Magnetic ballast adaptor circuit
US6153410A (en) * 1997-03-25 2000-11-28 California Institute Of Technology Recombination of polynucleotide sequences using random or defined primers
US6020688A (en) * 1997-10-10 2000-02-01 Electro-Mag International, Inc. Converter/inverter full bridge ballast circuit
US6281638B1 (en) 1997-10-10 2001-08-28 Electro-Mag International, Inc. Converter/inverter full bridge ballast circuit
US5877926A (en) * 1997-10-10 1999-03-02 Moisin; Mihail S. Common mode ground fault signal detection circuit
US6188553B1 (en) 1997-10-10 2001-02-13 Electro-Mag International Ground fault protection circuit
US6069455A (en) * 1998-04-15 2000-05-30 Electro-Mag International, Inc. Ballast having a selectively resonant circuit
US6236168B1 (en) 1998-04-15 2001-05-22 Electro-Mag International, Inc. Ballast instant start circuit
US6091288A (en) * 1998-05-06 2000-07-18 Electro-Mag International, Inc. Inverter circuit with avalanche current prevention
US6028399A (en) * 1998-06-23 2000-02-22 Electro-Mag International, Inc. Ballast circuit with a capacitive and inductive feedback path
US6100645A (en) * 1998-06-23 2000-08-08 Electro-Mag International, Inc. Ballast having a reactive feedback circuit
US6107750A (en) * 1998-09-03 2000-08-22 Electro-Mag International, Inc. Converter/inverter circuit having a single switching element
US6160358A (en) * 1998-09-03 2000-12-12 Electro-Mag International, Inc. Ballast circuit with lamp current regulating circuit
US6181082B1 (en) 1998-10-15 2001-01-30 Electro-Mag International, Inc. Ballast power control circuit
US6169375B1 (en) 1998-10-16 2001-01-02 Electro-Mag International, Inc. Lamp adaptable ballast circuit
US6181083B1 (en) 1998-10-16 2001-01-30 Electro-Mag, International, Inc. Ballast circuit with controlled strike/restart
US6137233A (en) * 1998-10-16 2000-10-24 Electro-Mag International, Inc. Ballast circuit with independent lamp control
US6222326B1 (en) 1998-10-16 2001-04-24 Electro-Mag International, Inc. Ballast circuit with independent lamp control
US6127786A (en) * 1998-10-16 2000-10-03 Electro-Mag International, Inc. Ballast having a lamp end of life circuit
US6100648A (en) * 1999-04-30 2000-08-08 Electro-Mag International, Inc. Ballast having a resonant feedback circuit for linear diode operation

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Publication number Publication date
DE4120649A1 (de) 1992-12-24

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