CN116488476B - Flyback switching power supply for realizing power supply protection based on secondary side feedback - Google Patents
Flyback switching power supply for realizing power supply protection based on secondary side feedback Download PDFInfo
- Publication number
- CN116488476B CN116488476B CN202310751004.2A CN202310751004A CN116488476B CN 116488476 B CN116488476 B CN 116488476B CN 202310751004 A CN202310751004 A CN 202310751004A CN 116488476 B CN116488476 B CN 116488476B
- Authority
- CN
- China
- Prior art keywords
- circuit
- power supply
- signal
- secondary side
- output
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
- 238000001514 detection method Methods 0.000 claims abstract description 37
- 230000002093 peripheral effect Effects 0.000 claims abstract description 23
- 239000003990 capacitor Substances 0.000 claims description 68
- 238000004804 winding Methods 0.000 claims description 34
- 101100464782 Saccharomyces cerevisiae (strain ATCC 204508 / S288c) CMP2 gene Proteins 0.000 claims description 14
- 230000002441 reversible effect Effects 0.000 claims description 14
- 238000007599 discharging Methods 0.000 claims description 13
- 102100029469 WD repeat and HMG-box DNA-binding protein 1 Human genes 0.000 claims description 12
- 101710097421 WD repeat and HMG-box DNA-binding protein 1 Proteins 0.000 claims description 12
- 101100464779 Saccharomyces cerevisiae (strain ATCC 204508 / S288c) CNA1 gene Proteins 0.000 claims description 11
- 102100040844 Dual specificity protein kinase CLK2 Human genes 0.000 claims description 7
- 101000749291 Homo sapiens Dual specificity protein kinase CLK2 Proteins 0.000 claims description 7
- 230000006698 induction Effects 0.000 claims description 6
- 102100040856 Dual specificity protein kinase CLK3 Human genes 0.000 claims description 5
- 101000749304 Homo sapiens Dual specificity protein kinase CLK3 Proteins 0.000 claims description 5
- 102100040862 Dual specificity protein kinase CLK1 Human genes 0.000 claims description 4
- 101000749294 Homo sapiens Dual specificity protein kinase CLK1 Proteins 0.000 claims description 3
- 238000000034 method Methods 0.000 abstract description 6
- 230000000630 rising effect Effects 0.000 description 6
- 102100031033 CCR4-NOT transcription complex subunit 3 Human genes 0.000 description 5
- 101000919663 Homo sapiens CCR4-NOT transcription complex subunit 3 Proteins 0.000 description 5
- 238000001914 filtration Methods 0.000 description 5
- 238000010586 diagram Methods 0.000 description 4
- 102100031025 CCR4-NOT transcription complex subunit 2 Human genes 0.000 description 3
- 101100113692 Caenorhabditis elegans clk-2 gene Proteins 0.000 description 3
- 101001092183 Drosophila melanogaster Regulator of gene activity Proteins 0.000 description 3
- 101000919667 Homo sapiens CCR4-NOT transcription complex subunit 2 Proteins 0.000 description 3
- 238000006243 chemical reaction Methods 0.000 description 3
- 238000012545 processing Methods 0.000 description 3
- 230000008054 signal transmission Effects 0.000 description 3
- 238000013461 design Methods 0.000 description 2
- 230000000694 effects Effects 0.000 description 2
- 102100031024 CCR4-NOT transcription complex subunit 1 Human genes 0.000 description 1
- 102100032981 CCR4-NOT transcription complex subunit 4 Human genes 0.000 description 1
- 101000919674 Caenorhabditis elegans CCR4-NOT transcription complex subunit let-711 Proteins 0.000 description 1
- 101100003180 Colletotrichum lindemuthianum ATG1 gene Proteins 0.000 description 1
- 101000919672 Homo sapiens CCR4-NOT transcription complex subunit 1 Proteins 0.000 description 1
- 101000942594 Homo sapiens CCR4-NOT transcription complex subunit 4 Proteins 0.000 description 1
- 230000003044 adaptive effect Effects 0.000 description 1
- 230000002411 adverse Effects 0.000 description 1
- 230000009286 beneficial effect Effects 0.000 description 1
- 230000005540 biological transmission Effects 0.000 description 1
- 238000004891 communication Methods 0.000 description 1
- 238000005265 energy consumption Methods 0.000 description 1
- 230000006870 function Effects 0.000 description 1
- 238000012986 modification Methods 0.000 description 1
- 230000004048 modification Effects 0.000 description 1
- 238000006467 substitution reaction Methods 0.000 description 1
- 230000001360 synchronised effect Effects 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
- H02H7/00—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions
- H02H7/10—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers
- H02H7/12—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers
- H02H7/1213—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers for DC-DC converters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The application relates to the field of switching power supplies, in particular to a flyback switching power supply for realizing power supply protection based on secondary side feedback, which comprises a main circuit, a peripheral circuit and a detection circuit, wherein the peripheral circuit is used for acquiring electric energy from a secondary side and supplying power to the main circuit; the detection circuit comprises a switch control unit, a reference unit and a mirror image unit, wherein the switch control unit controls the reference unit to pass current based on the short circuit working state of the secondary side of the flyback working circuit, and the mirror image unit copies the current of the reference unit and outputs the current to the main circuit to correspondingly generate a control signal; the main circuit controls the flyback working circuit to work or triggers the main circuit to protect based on the control signal. The method has the advantage of realizing under-voltage protection in a low-voltage scene.
Description
Technical Field
The application relates to the field of switching power supplies, in particular to a flyback switching power supply for realizing power supply protection based on secondary side feedback.
Background
The flyback switching power supply is a power electronic device with small volume and low power, and is widely applied to the fields of household appliances, communication power supplies, notebook adapters and the like. Their compact size and efficient energy conversion characteristics make them an integral part of modern electronic devices. For example, in the home, flyback switching power supplies are widely used in various electronic products such as televisions, audio systems, game machines, etc., to provide stable and reliable power supply to these devices.
The output short-circuit protection in the traditional sense is to turn off the switching signal and enter the under-voltage protection mode after detecting that the output voltage is lower than the design value. However, in some applications, it is required that the switching power supply still works properly under the condition of low output (e.g., 0.1V), so that the conventional under-voltage protection circuit is no longer applicable. If the detection module is directly used for detecting the rising edge or the falling edge of the secondary side current, when a short circuit occurs, the signal obtained by the detection module continuously oscillates at a low potential, and the switching power supply is also suitable for a low-voltage working state, so that the short circuit state is difficult to accurately detect.
Disclosure of Invention
In order to realize under-voltage protection in a low-voltage scene, the application provides a flyback switching power supply for realizing power supply protection based on secondary side feedback.
The application provides a flyback switching power supply based on secondary side feedback realizes power protection adopts following technical scheme:
a flyback switching power supply for implementing power protection based on secondary side feedback, comprising:
the flyback working circuit is used for providing electric energy for the primary side and outputting electric energy at the secondary side;
the control circuit comprises a main circuit, a peripheral circuit and a detection circuit, wherein the peripheral circuit is used for acquiring induction electric energy from the secondary side and supplying power to the main circuit; the detection circuit comprises a switch control unit, a short-circuit discharge unit and an input unit, wherein the short-circuit discharge unit is connected with an output unit and a ground wire, the switch control unit controls the on-off of the short-circuit discharge unit based on the working state of the secondary side of the flyback working circuit, and the output unit is used for outputting current or voltage to the main circuit to correspondingly generate a control signal; the main circuit controls the flyback working circuit to work or triggers the main circuit to protect based on the control signal.
Optionally, the flyback working circuit comprises a primary working circuit and a secondary working circuit, wherein the primary working circuit is used for passing power current, and the secondary working circuit obtains electric energy based on intermittent conduction of the primary working circuit.
Optionally, the main circuit is used for controlling the primary working circuit to be intermittently conducted periodically; the peripheral circuit is used for periodically and intermittently obtaining induction power supply from the secondary side output circuit and supplying power to the main circuit, and the power supply voltage to the main circuit is gradually reduced in the half cycle of secondary side power supply interruption.
Optionally, the main circuit controls the primary side working circuit to be conducted when the power-off half cycle of the primary side working circuit detects that the control signal reaches a first threshold value; in any one of the power-off half cycles of the peripheral circuit, when the power supply of the peripheral circuit to the main circuit is reduced to be lower than the working time of the lowest working voltage of the main circuit by the moment when the control signal reaches the first threshold value, the main circuit is powered off and the conduction of the primary working circuit is not controlled any more.
Optionally, the peripheral circuit includes an auxiliary coil NA, a second resistor R2, a third resistor R3, a fifth diode D5, and a third capacitor C3, where the auxiliary coil NA is coupled to the secondary coil NS, one end of the auxiliary coil NA is connected to a ground line and the third resistor R3, the other end is connected to the second resistor R2, one end of the third resistor R3 away from the ground line is connected to one end of the second resistor R2 away from the auxiliary coil NA, an anode of the fifth diode D5 is connected to one end of the NA away from the ground line, a cathode of the fifth diode D5 is connected to a power supply end of the main circuit, an anode of the third capacitor C3 is connected to a cathode of the fifth diode D5, and a cathode of the third capacitor C3 is connected to the ground line, where a connection node between the second resistor R2 and the third resistor R3 is used for outputting the feedback detection signal VS.
Optionally, the main circuit includes a first flip-flop DFFR1, a second flip-flop DFFR2, a third flip-flop DFFR3, a first AND gate AND1, a first comparator CMP1, a sixth capacitor C6, a third switching tube Q3, AND a set signal output unit, a signal whose initial value is low is set as a zero-crossing timing anti-shake signal, AND the first AND gate AND1 is used for inputting a reverse signal AND a set signal of the zero-crossing timing anti-shake signal; the CLK1 pin of the first trigger DFFR1 is connected to the output end of the first AND gate AND1, the D1 pin of the first trigger DFFR1 is connected to VDD, the RB1 pin of the first trigger DFFR1 is used for inputting a signal representing the on-off state of a primary working circuit, AND the Q1 pin of the first trigger DFFR1 is used for outputting a switching signal SW; the CLK2 pin of the second trigger DFFR2 is used for inputting a reverse signal of the switching signal SW, the D2 pin of the second trigger DFFR2 is connected to VDD, and the RB2 pin of the second trigger DFFR2 is used for inputting a reverse signal of the zero crossing timing anti-shake signal; the CLK3 pin of the third trigger DFFR3 is connected with the Q2 pin of the second trigger DFFR2, the D3 pin of the third trigger DFFR3 is connected with VDD, and the output signal of the Q3 pin of the third trigger DFFR3 is used as a new zero-crossing timing anti-shake signal; the control end of the third switching tube Q3 is used for inputting a reverse signal of the zero crossing timing anti-shake signal, the input end is connected with the positive electrode of the sixth capacitor C6, the output end is connected with the negative electrode of the sixth capacitor C6 and the ground wire, the positive electrode of the sixth capacitor C6 is used for obtaining the output current of the mirror image unit, the non-inverting input end of the first comparator CMP1 is used for inputting the reference voltage VREF1, and the inverting input end is connected with the positive electrode of the sixth capacitor C6;
the setting signal output unit is used for outputting PWM setting signals, and the switch signal SW is used for controlling the on-off of the primary working circuit.
Optionally, the primary working circuit includes a primary coil NP, a second switching tube M2, and a fourth resistor R4, two ends of the primary coil NP are respectively connected to an input end of the second switching tube M2 and one connection end of an external input, two ends of the fourth resistor R4 are respectively connected to an output end of the second switching tube M2 and the other connection end of the external input, and a control end of the second switching tube M2 is connected to the main circuit to obtain the switching signal SW.
Optionally, the switch control unit includes a second comparator CMP2 and an inverter, where an in-phase input end of the second comparator CMP2 is used to obtain a feedback detection signal VS, an inverting input end is connected to a ground line, an output end is connected to an input end of the inverter, and an output end of the inverter is connected to the short-circuit discharge unit to perform switch control on the short-circuit discharge unit, where the feedback detection signal VS is used to characterize a secondary side working state of the flyback working circuit.
Optionally, the switch control unit includes a second comparator CMP2, an in-phase input end of the second comparator CMP2 is connected to a ground line, an opposite-phase input end is used for obtaining a feedback detection signal VS, and an output end is connected to the short-circuit discharging unit to perform switch control on the short-circuit discharging unit, where the feedback detection signal VS is used for characterizing a secondary side working state of the flyback working circuit.
Optionally, the output unit outputs the supply current Ich outwards, the short-circuit discharging unit includes a fourth switching tube Q4, a control end of the fourth switching tube Q4 is connected to the switch control unit, an input end is connected to the output unit, and an output end is connected to the ground wire.
In summary, the present application includes at least one of the following beneficial technical effects:
1. the flyback switching power supply is suitable for a discontinuous mode, can detect a short circuit state when the secondary side output circuit is short-circuited, and distinguishes the short circuit state from the discontinuous mode so as to control the primary side working circuit to prolong the interrupt duration in the discontinuous mode, thereby entering power supply protection. Compared with the prior art, the method can be suitable for the condition that the output of the switching power supply is low.
2. Because the requirements on the circuit state are different in different practical scenes, and the low-voltage output threshold value of the switching power supply is also different, in the application, the detection circuit is used for controlling the short-circuit state, and the internal resistance value of the detection circuit is used for adjusting, or the number of current mirrors is adjusted to be started, or the capacitor is used for charging and discharging, so that the charging time is directly adjusted, and the workload of the adaptive adjustment required by applying the flyback switching power supply to different products is effectively reduced.
Drawings
Fig. 1 is a schematic diagram of a flyback switching power supply implementing power protection based on secondary side feedback according to an embodiment of the present invention.
FIG. 2 is a schematic diagram of a portion of a main circuit according to an embodiment of the invention.
FIG. 3 is a schematic circuit diagram of a detection circuit according to an embodiment of the invention.
Reference numerals illustrate:
1. a primary side working circuit; 2. a secondary side output circuit; 3. a main circuit; 4. a peripheral circuit; 5. and a rectifying and filtering circuit.
Detailed Description
The present application is described in further detail below with reference to the accompanying drawings. It should be understood that the specific embodiments described herein are for purposes of illustration only and are not intended to limit the present application.
In the following description, for purposes of explanation, numerous specific details are set forth in order to provide a thorough understanding of the inventive concepts. As part of this specification, some of the drawings of the present disclosure represent structures and devices in block diagram form in order to avoid obscuring the principles of the disclosure. In the interest of clarity, not all features of an actual implementation are necessarily described. Furthermore, the language used in the present disclosure has been principally selected for readability and instructional purposes, and may not have been selected to delineate or circumscribe the inventive subject matter, resort to the requisite claims to determine such inventive subject matter. Reference in the present disclosure to "one embodiment" or "an embodiment" means that a particular feature, structure, or characteristic described in connection with the embodiment is included in at least one embodiment, and multiple references to "one embodiment" or "an embodiment" should not be understood as necessarily all referring to the same embodiment.
The terms "a," "an," and "the" are not intended to refer to a singular entity, but rather include the general class of which a particular example may be used for illustration, unless clearly defined. Thus, the use of the terms "a" or "an" may mean any number of at least one, including "one", "one or more", "at least one", and "one or more than one". The term "or" means any of the alternatives and any combination of alternatives, including all alternatives, unless alternatives are explicitly indicated as mutually exclusive. The phrase "at least one of" when combined with a list of items refers to a single item in the list or any combination of items in the list. The phrase does not require all of the listed items unless specifically so defined.
The application discloses flyback switching power supply based on secondary side feedback realizes power protection, and with reference to fig. 1, this flyback switching power supply includes flyback work circuit and control circuit, and flyback work circuit is used for from switch-on external power source and export the electric energy through the conversion of former secondary side, and control circuit is used for controlling the break-make of primary side, breaks primary side work when the secondary side takes place the short circuit to enter under-voltage protection.
The flyback working circuit comprises a primary working circuit 1 and a secondary output circuit 2, wherein the primary working circuit is used for obtaining electric energy through power current, and the secondary output circuit is based on intermittent conduction of the primary working circuit.
Specifically, in one embodiment, the primary working circuit includes a primary coil NP, a second switching tube M2, and a fourth resistor R4, two ends of the primary coil NP are respectively connected to an input end of the second switching tube M2 and one connection end of an external input, two ends of the fourth resistor R4 are respectively connected to an output end of the second switching tube M2 and the other connection end of the external input, and a control end of the second switching tube M2 is connected to the control circuit to obtain the switching signal SW. Of course, the arrangement sequence of the primary winding NP, the second switching tube M2 and the fourth resistor R4 may be different in different embodiments, for example, two connection ends of external input are taken as positive and negative poles, so that the primary winding NP, the second switching tube M2 and the fourth resistor R4 may be sequentially connected from positive pole to negative pole, or may be sequentially connected from negative pole to positive pole, or other electronic elements such as resistors are added in the middle, and if the second switching tube M2 is enabled to control on/off of the circuit after receiving the switching signal SW, and the current of the primary winding NP changes when the circuit is on/off, and the voltage drop at both ends of the fourth resistor R4 changes in the state of a path and a short circuit.
In addition, in different embodiments, the second switching tube M2 can be different, for example, the second switching tube M2 is a PMOS tube or an NMOS tube, but any switching tube having a low leakage current and capable of fast responding to the switching signal SW input to the control terminal can be used. As an example, in the above embodiment, the second switching tube M2 is an NMOS tube, two ends of the primary winding NP are respectively connected to the drain of the second switching tube M2 and the positive electrode of the external input, two ends of the fourth resistor R4 are respectively connected to the source of the second switching tube M2 and the negative electrode of the external input, the negative electrode of the external input is connected to the ground, and the gate of the second switching tube M2 is connected to the control circuit to obtain the switching signal SW. When the second switching transistor M2 receives the switching signal SW at a high level, i.e., sw=1, the primary side operating circuit is turned on, hereinafter referred to as a turn-on half cycle of the primary side operating circuit. In the on half period, the end of the fourth resistor R4 distant from the ground is used to output the operation detection signal CS, and cs=1. When the second switching transistor M2 receives the switching signal SW at a low level, i.e., sw=0, the primary side operating circuit is turned off, hereinafter referred to as a power-off half cycle of the primary side operating circuit. In the power-off half cycle, the end of the fourth resistor R4 distant from the ground is used to output the operation detection signal CS, and cs=0.
In order to reduce the adverse effect on the circuit element caused by the abrupt current change when the second switching tube M2 is rapidly switched, and improve the working quality of the primary side working circuit, in some embodiments, the primary side working circuit further includes a spike absorbing unit, where the spike absorbing unit includes a first resistor R1, a fourth capacitor C4, and a sixth diode D6. The positive pole of the sixth diode D6 is connected to the primary winding NP, the negative pole of the sixth diode D6 is connected to the negative pole of the fourth capacitor C4 and the first resistor R1, one end of the first resistor R1 away from the sixth diode D6 is connected to one end of the primary winding NP away from the sixth diode D6, and the positive pole of the fourth capacitor C4 is connected to one end of the primary winding NP away from the sixth diode D6. In these embodiments, the connection manners of the first resistor R1, the fourth capacitor C4 and the sixth diode D6 can be different, but the fourth capacitor C4 can absorb the pulse generated by the primary winding NP, the first resistor R1 can consume the discharge of the primary winding NP and the fourth capacitor C4, the sixth diode D6 can conduct the current generated by the primary winding unidirectionally when the second switching tube M2 is turned off, and the first resistor R1 and the fourth capacitor C4 can be prevented from shorting the primary winding NP when the second switching tube M2 is turned on.
The secondary side output circuit comprises a secondary side coil NS, a seventh diode D7 and a fifth capacitor C5, wherein the secondary side coil NS is coupled to the primary side coil NP, two ends of the secondary side coil NS are respectively connected to two ends of the fifth capacitor C5, the seventh diode D7 is positioned on any connecting line of the secondary side coil NS and the fifth capacitor C5, and two ends of the fifth capacitor C5 serve as output ends of the secondary side output circuit. The secondary winding NS is coupled to the primary winding NP, and when the primary winding NP changes current, the secondary winding NS generates a corresponding induced electromotive force in the forward direction or the reverse direction. Also, in these embodiments, the connection manner of the secondary winding NS, the seventh diode D7 and the fifth capacitor C5 can be different, but the seventh diode D7 can prevent the output of the half cycle of the secondary winding NS, and the fifth capacitor C5 can output in the half cycle. For example, one end of the secondary winding NS is connected to the positive electrode of the seventh diode D7, and the other end is connected to the negative electrode of the fifth capacitor C5 and serves as the negative output end of the secondary output circuit, and the negative electrode of the seventh diode D7 is connected to the positive electrode of the fifth capacitor C5 and serves as the positive output end of the secondary output circuit. It should be noted that, in this embodiment, the end of the primary winding NP far from the positive electrode input is the same-name end as the end of the secondary winding NS connected to the positive electrode of the fifth capacitor C5.
The primary working circuit can directly take direct current input as external input, and can also process alternating current input to indirectly obtain direct current input. Specifically, in some embodiments, the flyback working circuit further includes a rectifying and filtering circuit 5, where the rectifying and filtering circuit includes a first diode D1, a second diode D2, a third diode D3, a fourth diode D4, a first capacitor C1, and a second capacitor C2, and the first diode D1, the second diode D2, the third diode D3, and the fourth diode D4 form a rectifying bridge. For example, the positive pole and the negative pole of the first capacitor C1 are respectively connected to the live wire and the zero line, the positive pole of the first diode D1 and the negative pole of the third diode D3 are connected to the live wire, the positive pole of the second diode D2 and the negative pole of the fourth diode D4 are connected to the zero line, the negative poles of the first diode D1 and the second diode D2 are connected to the positive pole of the second capacitor C2, the positive pole of the second capacitor C2 is used as the positive pole output of the rectifying and filtering circuit, and the positive poles of the third diode D3 and the fourth diode D4 are connected to the negative pole of the second capacitor C2 and are used as the negative pole output of the rectifying and filtering circuit.
The control circuit comprises a main circuit 3, a peripheral circuit 4 and a detection circuit, wherein the main circuit is used for outputting a switching signal SW to control the primary side working circuit to be periodically conducted and disconnected, the peripheral circuit is used for periodically and intermittently obtaining induction power supply from the secondary side output circuit and supplying power to the main circuit, the power supply voltage of the main circuit is gradually reduced in the half period of power interruption, the duration of the half period of power interruption is variable, and the longer the duration is, the lower the power supply voltage of the peripheral circuit to the main circuit is, until the power supply voltage is lower than the lowest working voltage of the main circuit. By setting the detection circuit, when the secondary side output voltage is in a normal fluctuation range, the detection circuit outputs current/voltage to the main circuit, and the generated control signal can enable the peripheral circuit to still provide high enough power supply voltage to the main circuit when the power-off half cycle is finished. In other words, when the main circuit detects that the control signal reaches the first threshold value in the power-off half cycle of the primary side working circuit, the primary side working circuit is controlled to be conducted; in any one of the power-off half cycles of the peripheral circuit, when the power supply of the peripheral circuit to the main circuit is reduced to be lower than the working time of the lowest working voltage of the main circuit by the moment when the control signal reaches the first threshold value, the main circuit is powered off and the conduction of the primary working circuit is not controlled any more. It should be noted that, since there is a delay in the transmission of the signal, the setting of the preset time threshold corresponds to the delay being present. For example, when the control signal reaches the first threshold, that is, through a series of signal transmission and processing, the primary working circuit will be turned on, and in the process that the primary working circuit is turned on to the main circuit to start charging, there is still a series of signal transmission and processing, and the signal transmission and processing will generate time consumption, that is, the time difference exists between the control signal reaching the first threshold and the main circuit to start charging, and the time difference is the preset time threshold. In various embodiments, the implementation structure of the main circuit may be different, AND the main circuit includes, as an example, a first flip-flop DFFR1, a second flip-flop DFFR2, a third flip-flop DFFR3, a first AND gate AND1, a first comparator CMP1, a sixth capacitor C6, a third switching tube Q3, AND a set signal output unit, a signal whose initial value is low is set as the zero-crossing timing anti-shake signal s_tdmin, AND the first AND gate AND1 is used to input the inverse of the set signal AND the zero-crossing timing anti-shake signal s_tdmin. Specifically, one input end of the first AND gate AND1 is connected to the set signal output unit, AND is configured to obtain a PWM set signal, AND the other input end of the first AND gate AND1 receives the zero-crossing timing anti-shake signal s_tdmin through the first NOT gate NOT 1.
The CLK1 pin of the first trigger DFFR1 is connected to the output end of the first AND gate AND1, the D1 pin of the first trigger DFFR1 is connected to VDD, the RB1 pin of the first trigger DFFR1 is used for inputting a signal representing the on-off state of a primary working circuit, AND the Q1 pin of the first trigger DFFR1 is used for outputting a switching signal SW. Specifically, the RB1 pin of the first flip-flop DFFR1 is used for inputting a reverse signal of the digital signal corresponding to the operation detection signal CS, and it should be noted that, because the operation detection signal CS is an analog signal, it needs to be converted into the digital signal by a certain conversion and threshold judgment method, and the scheme is not limited in detail. In addition, in the embodiment provided in the present application, the first flip-flop DFFR1, the second flip-flop DFFR2 and the third flip-flop DFFR3 all adopt synchronous reset D flip-flops, in other embodiments, asynchronous reset D flip-flops may be adopted, and only an inverter needs to be added to the RB pin in relation to the present solution, or other types of flip-flops or electronic elements may also be adopted, so that the function implementation logic is the same as the present solution.
It should be noted that VDD in the main circuit in fig. 2 is usually converted from VCC in fig. 1, so that when VCC has an input under voltage, VDD in the main circuit will also have an under voltage. At present, when a power supply is started, a high-voltage starting module is designed for a switching power supply, and many implementation manners of the high-voltage starting module are provided, for example, when the power supply is powered on, a primary coil charges a third capacitor C3, and when the VCC voltage reaches the starting voltage of a main circuit, various references of the main circuit are established. After the main circuit starts to work, the high-voltage starting is completed, the power supply of the third capacitor C3 is provided by the auxiliary coil NA, and the high-voltage starting module is disconnected.
The CLK2 pin of the second flip-flop DFFR2 is used for inputting the reverse signal of the switching signal SW, the D2 pin of the second flip-flop DFFR2 is connected to VDD, and the RB2 pin of the second flip-flop DFFR2 is used for inputting the reverse signal of the zero-crossing timing anti-shake signal s_tdmin. Specifically, the CLK2 pin of the second flip-flop DFFR2 is connected to the Q1 pin of the first flip-flop DFFR1 through the second NOT gate NOT2, and the RB2 pin of the second flip-flop DFFR2 receives the zero-crossing timing anti-shake signal s_tdmin through the third NOT gate NOT 3.
The CLK3 pin of the third flip-flop DFFR3 is connected to the Q2 pin of the second flip-flop DFFR2, the D3 pin of the third flip-flop DFFR3 is connected to VDD, and the output signal of the Q3 pin of the third flip-flop DFFR3 is used as the new zero-crossing timing anti-shake signal s_tdmin. The control end of the third switching tube Q3 is used for inputting a reverse signal of the zero crossing timing anti-shake signal S_tdmin, the input end is connected to the positive electrode of the sixth capacitor C6, the output end is connected to the negative electrode of the sixth capacitor C6 and the ground wire, and the positive electrode of the sixth capacitor C6 is used for obtaining the charging current ICh. The non-inverting input terminal of the first comparator CMP1 is used for inputting the reference voltage VREF1, and the inverting input terminal is connected to the positive electrode of the sixth capacitor C6. In addition, in different embodiments, the third switching tube Q3 can be different, for example, the third switching tube Q3 is a PMOS tube or an NMOS tube, but any switching tube having a low leakage current and capable of fast responding to the control signal input to the control terminal can be used. As an example, in the above embodiment, the third switching tube Q3 is an NMOS tube, the gate of the third switching tube Q3 is used for inputting the reverse signal of the zero-crossing timing anti-shake signal s_tdmin, the drain is connected to the positive electrode of the sixth capacitor C6, and the source is connected to the negative electrode of the sixth capacitor C6 and the ground.
The peripheral circuit comprises an auxiliary coil NA, a second resistor R2, a third resistor R3, a fifth diode D5 and a third capacitor C3, wherein the auxiliary coil NA is coupled to the secondary coil NS, one end of the auxiliary coil NA is connected to a ground wire and the third resistor R3, the other end of the auxiliary coil NA is connected to the second resistor R2, one end of the third resistor R3, which is far away from the ground wire, is connected to one end of the second resistor R2, which is far away from the auxiliary coil NA, the positive electrode of the fifth diode D5 is connected to one end of the NA, which is far away from the ground wire, the negative electrode of the fifth diode D5 is connected to the power supply end of the main circuit, the positive electrode of the third capacitor C3 is connected to the negative electrode of the fifth diode D5, the negative electrode of the third capacitor C3 is connected to the ground wire, the connection node of the second resistor R2 and the third resistor R3 is used for outputting a feedback detection signal VS, the feedback detection signal VS is used for representing the condition of the secondary load, the capacitor C3 obtains the electric energy of the auxiliary coil NA, and the main circuit is powered when the primary coil is turned on for half a circumference. In addition, the end of the auxiliary winding NA far from the ground line is the same name as the end of the primary winding NP far from the positive electrode input.
The principle of operation of the main circuit and peripheral circuit is as follows:
in the initial stage, the initial value of s_tdmin is low (hereinafter, 0 refers to low level AND1 refers to high level, where s_tdmin=0), AND s_tdmin is output as 1 through the first NOT gate NOT1 AND is input to the input terminal of the first AND gate AND 1. When the SET signal set_sw output by the SET signal output unit goes high, the first and gate output goes high, i.e., clk1=1 at this time. Since the primary winding is not yet on, cs=0, rb1=1. The output Q1 of the first flip-flop DFFR1 goes high, i.e. sw=1. At this time, the primary working circuit is conducted, the power-off half cycle is ended, the current of the primary coil starts to rise, and the conductive half cycle is started.
After being input to the second NOT gate NOT2, the switch signal SW, CLK2 goes low, i.e., clk2=0. S_tdmin after input to the third NOT gate NOT3, the output goes high, and RB2 goes high, i.e., rb2=1. Therefore, the output Q2 of the second flip-flop DFFR2 is low, i.e. q2=clk3=0.
Since the third switching transistor Q3 is turned on and the sixth capacitor C6 is discharged when rb2=1, the level VC6 at the end of the sixth capacitor C6 far from the ground is less than VREF1, and the first comparator CMP1 outputs high, that is, rb3=1. Since CLK3 does not occur a rising edge, s_tdmin=0. Since the primary working circuit is continuously turned on, that is, the passing current of the primary coil NP continuously rises to a stable value until the current of the primary working circuit rises to a design value, the working detection signal CS turns high, and correspondingly, rb1=0. Because of the characteristics of the first flip-flop DFFR1, the output Q1 of the first flip-flop DFFR1 is reset to 0, i.e., sw=0, and thus the primary operating circuit is turned off, the conductive half cycle ends, and the power-off half cycle starts. At the moment when the primary working circuit is disconnected, the primary coil NP is rapidly discharged through the spike absorbing unit, and accordingly, the secondary coil NS generates an induced current and is conducted, and the secondary coil NS charges and supplies power to the fifth capacitor C5.
Accordingly, the auxiliary winding NA generates an induced electromotive force and charges the third capacitor C3 while supplying power to the main circuit. Since sw=0, CLK2 goes high, i.e., a rising edge is input to CLK 2. At this time, rb2=1, so that the output Q2 of the second flip-flop DFFR2 goes high, i.e., is the rising edge input to CLK 3. At this time, rb3=1, so that the output of the third flip-flop DFFR3 turns high by the third switching tube Q3, s_tdmin turns high, i.e., s_tdmin=1.
Since s_tdmin=1, the output of s_tdmin is low after passing through the third NOT gate NOT3, rb2=0, and the output Q2 of the second flip-flop DFFR2 is reset, that is, q2=0. Note that, since rb2=0, the third switching transistor Q3 stops conducting, ich starts charging the sixth capacitor C6, and VC6 continuously rises during charging, so as to exceed VREF1. When VC6 > VREF1, then rb3=0. Therefore, when VC6 < VREF1, since Q2 is reset and a falling edge occurs, the output of the third flip-flop DFFR3 and the third switching transistor Q3 remain the same, i.e., s_tdmin=1 is still at a high level. When the charge of the sixth capacitor C6 by Ich continues for a period of time, VC6 > VREF1, then rb3=0, the output of the third flip-flop DFFR3 is reset by the third switching transistor Q3, i.e., s_tdmin=0, until sw=1, and the power-off half cycle is completed. Thus, the on half cycle and the off half cycle of the original working circuit are completed, the next cycle is entered, and the process is repeated.
In summary, the period of time s_tdmin being high is determined by the charging period of the sixth capacitor C6, and the charging period of the sixth capacitor C6 depends on the size of Ich, so controlling the size of Ich can control the period of time s_tdmin being high, that is, the period of time the second switch tube M2 is turned off.
In the embodiment of the present application, the charging of the Ich is performed by the detection circuit, and in different embodiments, the detection circuit may control the size of the Ich, or may control the charging duration of the sixth capacitor C6 by controlling whether the Ich is output or not. Specifically, in this embodiment of the present application, the detection circuit includes a switch control unit, a short-circuit discharging unit and an input unit, where the short-circuit discharging unit connects an output unit and a ground wire, the switch control unit controls the on-off of the short-circuit discharging unit based on the working state of the secondary side of the flyback working circuit, the output unit is used to output current or voltage to the sixth capacitor C6 to generate a control signal accordingly, and as an example, the output unit selects a dc output source for outputting the supply current Ich.
In one embodiment, the switch control unit includes a second comparator CMP2 and an inverter, where the non-inverting input end of the second comparator CMP2 is used to obtain the feedback detection signal VS, the inverting input end is connected to the ground, the output end is connected to the input end of the inverter, and the output end of the inverter is connected to the short-circuit discharge unit to perform switch control on the short-circuit discharge unit.
In another embodiment, the switch control unit includes a second comparator CMP2, where a non-inverting input terminal of the second comparator CMP2 is connected to a ground line, an inverting input terminal is used to obtain the feedback detection signal VS, and an output terminal is connected to the short-circuit discharge unit to perform switch control on the short-circuit discharge unit.
The short-circuit discharging unit comprises a fourth switching tube Q4, the control end of the fourth switching tube Q4 is connected with the switch control unit, the input end of the fourth switching tube Q4 is connected with the output unit, and the output end of the fourth switching tube Q4 is connected with the ground wire. In different embodiments, the fourth switching tube Q4 can be different, for example, the fourth switching tube Q4 is a PMOS tube or an NMOS tube, but any switching tube having a low leakage current and capable of fast responding to the switching signal SW of the input control terminal can be used. As an example, in the above embodiment, the fourth switching tube Q4 is an NMOS tube, the gate of Q4 is connected to the signal output end of the switching control unit, the drain is connected to the output unit, the source is connected to the ground, and when the gate of Q4 receives the high level signal, Q4 is turned on and the output unit is grounded.
The detection circuit works as follows:
when the main side operation circuit is turned on, sw=1, and clk2=0. Since s_tdmin=0 at this time, rb2=1, the Q2 pin of the second flip-flop DFRR2 maintains an initial value q2=0.
Because the main side working circuit is conducted, the secondary side coil NS and the auxiliary coil NA generate negative induction voltage, VS is less than or equal to 0, the output of the second comparator CMP2 is low, the fourth switching tube Q4 is conducted, the sixth capacitor C6 is short-circuited, VC6 is less than VREF1, and the output of the first comparator CMP1 is high.
Since s_tdmin=0, the output of NOT3 is 1, and the third switching transistor Q3 is turned on. The output of the first comparator CMP1 is high, then rb3=1. Again, since clk3=0, s_tdmin continues to remain low until the primary operating circuit continues to be on for a period of time, so that CS is turned to a level.
When cs=1, then rb1=0, and q1=sw=0 of the first flip-flop DFFR1, then the primary side operation circuit is turned off. Since sw=0, the output of the second NOT gate NOT2 is high, CLK2 receives the rising edge, and since s_tdmin has NOT changed at this time and remains low, the output of the third NOT gate NOT3 is high, CLK3 receives the rising edge. Since the sixth capacitor C6 is not yet charged at this time, VC6 < VREF1, and the output of the first comparator CMP1 is high, then rb3=1, and therefore s_tdmin goes high, and correspondingly, the third switching transistor Q3 is turned off; meanwhile, since sw=0, the secondary winding and the output winding are turned on, VS is greater than 0, the output of the second comparator CMP2 is high, the fourth switching tube Q4 is turned off, the sixth capacitor C6 is turned on to start charging with the Ich current value, when VC6 is greater than VREF1, the output of the first comparator CMP1 is low, rb3=0, s_tdmin is reset to low level, the output of the third NOT3 is high, Q3 is turned on, the sixth capacitor C6 is discharged, SW is turned high after the SET signal SET_SW is turned high, and the cycle is thus repeated.
When the output is short-circuited, the VS signal oscillates about 0V, so that the output of the second comparator continuously oscillates between high and low levels, the high-frequency switching on and off of the fourth switching tube Q4 are controlled after NOT4, and although the third switching tube Q3 is already switched off, the high-frequency switching of the fourth switching tube Q4 still enables the sixth capacitor C6 to be continuously charged and discharged, so that VC6 cannot rise.
Therefore, s_tdmin will not be reset until s_tdmin is high, the switch signal SW will not be turned high, the primary winding NP will not store energy, the secondary winding NS will not supply power to VCC and the third capacitor C3 after the energy consumption of the secondary winding NS is completed, the VCC voltage drops, and after the VCC voltage drops to the under-voltage protection point, the main circuit stops working, and the system is protected.
The above embodiments are only for illustrating the technical solution of the present invention, and are not limiting; although the invention has been described in detail with reference to the foregoing embodiments, it will be understood by those of ordinary skill in the art that: the technical scheme described in the foregoing embodiments can be modified or some technical features thereof can be replaced by equivalents; such modifications and substitutions do not depart from the spirit and scope of the technical solutions of the embodiments of the present invention, and are intended to be included in the scope of the present invention.
Claims (9)
1. A flyback switching power supply for realizing power supply protection based on secondary side feedback is characterized by comprising:
the flyback working circuit is used for providing electric energy for the primary side and outputting electric energy at the secondary side;
the control circuit comprises a main circuit, a peripheral circuit and a detection circuit, wherein the peripheral circuit is used for acquiring induction electric energy from the secondary side and supplying power to the main circuit; the detection circuit comprises a switch control unit, a short-circuit discharge unit and an input unit, wherein the short-circuit discharge unit is connected with an output unit and a ground wire, the switch control unit controls the on-off of the short-circuit discharge unit based on the working state of the secondary side of the flyback working circuit, and the output unit is used for outputting current or voltage to the main circuit to correspondingly generate a control signal; the main circuit controls the flyback working circuit to work or triggers the main circuit to protect based on the control signal;
the main circuit comprises a first trigger DFFR1, a second trigger DFFR2, a third trigger DFFR3, a first AND gate AND1, a first comparator CMP1, a sixth capacitor C6, a third switching tube Q3 AND a set signal output unit, wherein a signal with an initial value of low level is set as a zero-crossing timing anti-shake signal, AND the first AND gate AND1 is used for inputting a reverse signal AND a set signal of the zero-crossing timing anti-shake signal; the CLK1 pin of the first trigger DFFR1 is connected to the output end of the first AND gate AND1, the D1 pin of the first trigger DFFR1 is connected to VDD, the RB1 pin of the first trigger DFFR1 is used for inputting a signal representing the on-off state of a primary working circuit, AND the Q1 pin of the first trigger DFFR1 is used for outputting a switching signal SW; the CLK2 pin of the second trigger DFFR2 is used for inputting a reverse signal of the switching signal SW, the D2 pin of the second trigger DFFR2 is connected to VDD, and the RB2 pin of the second trigger DFFR2 is used for inputting a reverse signal of the zero crossing timing anti-shake signal; the CLK3 pin of the third trigger DFFR3 is connected with the Q2 pin of the second trigger DFFR2, the D3 pin of the third trigger DFFR3 is connected with VDD, and the output signal of the Q3 pin of the third trigger DFFR3 is used as a new zero-crossing timing anti-shake signal; the control end of the third switching tube Q3 is used for inputting a reverse signal of the zero crossing timing anti-shake signal, the input end is connected with the positive electrode of the sixth capacitor C6, the output end is connected with the negative electrode of the sixth capacitor C6 and the ground wire, the positive electrode of the sixth capacitor C6 is used for obtaining the output current of the mirror image unit, the non-inverting input end of the first comparator CMP1 is used for inputting the reference voltage VREF1, and the inverting input end is connected with the positive electrode of the sixth capacitor C6;
the setting signal output unit is used for outputting PWM setting signals, and the switch signal SW is used for controlling the on-off of the primary working circuit.
2. The flyback switching power supply for power supply protection based on secondary side feedback according to claim 1, wherein the flyback operation circuit comprises a primary side operation circuit and a secondary side output circuit, the primary side operation circuit is used for passing power current, and the secondary side output circuit obtains electric energy based on intermittent conduction of the primary side operation circuit.
3. The flyback switching power supply for achieving power supply protection based on secondary side feedback according to claim 2, wherein the main circuit is configured to control the primary side working circuit to be intermittently turned on periodically; the peripheral circuit is used for periodically and intermittently obtaining induction power supply from the secondary side output circuit and supplying power to the main circuit, and the power supply voltage to the main circuit is gradually reduced in the half cycle of secondary side power supply interruption.
4. The flyback switching power supply for power protection based on secondary side feedback according to claim 3, wherein the main circuit controls the primary side working circuit to be turned on when the power-off half cycle of the primary side working circuit detects that the control signal reaches a first threshold; in any one of the power-off half cycles of the peripheral circuit, when the power supply of the peripheral circuit to the main circuit is reduced to be lower than the working time of the lowest working voltage of the main circuit by the moment when the control signal reaches the first threshold value, the main circuit is powered off and the conduction of the primary working circuit is not controlled any more.
5. The flyback switching power supply for power protection based on secondary feedback according to claim 4, wherein the peripheral circuit comprises an auxiliary winding NA, a second resistor R2, a third resistor R3, a fifth diode D5 and a third capacitor C3, the auxiliary winding NA is coupled to the secondary winding NS, one end of the auxiliary winding NA is connected to ground and the third resistor R3, the other end is connected to the second resistor R2, one end of the third resistor R3 far from ground is connected to one end of the second resistor R2 far from the auxiliary winding NA, the positive electrode of the fifth diode D5 is connected to one end of NA far from ground, the negative electrode of the fifth diode D5 is connected to the power supply end of the main circuit, the positive electrode of the third capacitor C3 is connected to the negative electrode of the fifth diode D5, the negative electrode of the third capacitor C3 is connected to ground, and the connection node of the second resistor R2 and the third resistor R3 is used for outputting the feedback detection signal VS.
6. The flyback switching power supply for realizing power protection based on secondary side feedback according to claim 1 or 2, wherein the primary side working circuit comprises a primary side coil NP, a second switching tube M2 and a fourth resistor R4, two ends of the primary side coil NP are respectively connected to an input end of the second switching tube M2 and one connection end of an external input, two ends of the fourth resistor R4 are respectively connected to an output end of the second switching tube M2 and the other connection end of the external input, and a control end of the second switching tube M2 is connected to the main circuit to obtain the switching signal SW.
7. The flyback switching power supply for realizing power supply protection based on secondary side feedback according to claim 1, wherein the switching control unit comprises a second comparator CMP2 and an inverter, wherein the non-inverting input end of the second comparator CMP2 is used for acquiring a feedback detection signal VS, the inverting input end is connected to a ground wire, the output end is connected to the input end of the inverter, and the output end of the inverter is connected to the short-circuit discharging unit to perform switching control on the short-circuit discharging unit, wherein the feedback detection signal VS is used for representing the secondary side working state of the flyback working circuit.
8. The flyback switching power supply for realizing power supply protection based on secondary side feedback according to claim 1, wherein the switching control unit comprises a second comparator CMP2, the non-inverting input end of the second comparator CMP2 is connected to a ground line, the inverting input end is used for obtaining a feedback detection signal VS, and the output end is connected with the short-circuit discharging unit to perform switching control on the short-circuit discharging unit, wherein the feedback detection signal VS is used for representing a secondary side working state of the flyback working circuit.
9. The flyback switching power supply for realizing power supply protection based on secondary side feedback according to claim 7 or 8, wherein the output unit outputs a supply current Ich outwards, the short-circuit discharging unit comprises a fourth switching tube Q4, a control end of the fourth switching tube Q4 is connected to the switching control unit, an input end is connected to the output unit, and an output end is connected to a ground line.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202310751004.2A CN116488476B (en) | 2023-06-25 | 2023-06-25 | Flyback switching power supply for realizing power supply protection based on secondary side feedback |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202310751004.2A CN116488476B (en) | 2023-06-25 | 2023-06-25 | Flyback switching power supply for realizing power supply protection based on secondary side feedback |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN116488476A CN116488476A (en) | 2023-07-25 |
| CN116488476B true CN116488476B (en) | 2024-01-23 |
Family
ID=87212341
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202310751004.2A Active CN116488476B (en) | 2023-06-25 | 2023-06-25 | Flyback switching power supply for realizing power supply protection based on secondary side feedback |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN116488476B (en) |
Citations (9)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2009065266A1 (en) * | 2007-11-20 | 2009-05-28 | System General Corp. | Synchronous regulation circuit |
| CN101997423A (en) * | 2010-10-29 | 2011-03-30 | 广州金升阳科技有限公司 | Self-oscillating flyback converter with function of output short circuit protection |
| CN102364859A (en) * | 2011-05-31 | 2012-02-29 | 杭州士兰微电子股份有限公司 | Switching power supply control device and flyback switching power supply with same |
| CN202309527U (en) * | 2011-11-09 | 2012-07-04 | 深圳市同洲电子股份有限公司 | Flyback switching power supply output short-circuit protection circuit |
| CN107453628A (en) * | 2016-05-25 | 2017-12-08 | 戴洛格半导体公司 | Short-circuit and soft short-circuit protection for data-interface charging |
| CN107612334A (en) * | 2017-09-11 | 2018-01-19 | 广州金升阳科技有限公司 | A kind of primary side detects circuit |
| CN108173434A (en) * | 2018-01-15 | 2018-06-15 | 昂宝电子（上海）有限公司 | Switching power circuit |
| US10362644B1 (en) * | 2017-07-28 | 2019-07-23 | Universal Lighting Technologies, Inc. | Flyback converter with load condition control circuit |
| CN213213347U (en) * | 2020-10-30 | 2021-05-14 | 苏州力生美半导体有限公司 | Flyback switching power supply resonance EMI optimization circuit |
-
2023
- 2023-06-25 CN CN202310751004.2A patent/CN116488476B/en active Active
Patent Citations (9)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2009065266A1 (en) * | 2007-11-20 | 2009-05-28 | System General Corp. | Synchronous regulation circuit |
| CN101997423A (en) * | 2010-10-29 | 2011-03-30 | 广州金升阳科技有限公司 | Self-oscillating flyback converter with function of output short circuit protection |
| CN102364859A (en) * | 2011-05-31 | 2012-02-29 | 杭州士兰微电子股份有限公司 | Switching power supply control device and flyback switching power supply with same |
| CN202309527U (en) * | 2011-11-09 | 2012-07-04 | 深圳市同洲电子股份有限公司 | Flyback switching power supply output short-circuit protection circuit |
| CN107453628A (en) * | 2016-05-25 | 2017-12-08 | 戴洛格半导体公司 | Short-circuit and soft short-circuit protection for data-interface charging |
| US10362644B1 (en) * | 2017-07-28 | 2019-07-23 | Universal Lighting Technologies, Inc. | Flyback converter with load condition control circuit |
| CN107612334A (en) * | 2017-09-11 | 2018-01-19 | 广州金升阳科技有限公司 | A kind of primary side detects circuit |
| CN108173434A (en) * | 2018-01-15 | 2018-06-15 | 昂宝电子（上海）有限公司 | Switching power circuit |
| CN213213347U (en) * | 2020-10-30 | 2021-05-14 | 苏州力生美半导体有限公司 | Flyback switching power supply resonance EMI optimization circuit |
Also Published As
| Publication number | Publication date |
|---|---|
| CN116488476A (en) | 2023-07-25 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN108712062B (en) | Switch control circuit, chip, adapter and switch control method | |
| EP3136114A1 (en) | Method and device for detecting current of inductor of pfc circuit | |
| CN108933529B (en) | Power supply control device and power supply control system | |
| CN213846230U (en) | Overcurrent protection circuit | |
| US11329569B2 (en) | Power conversion system | |
| KR102600908B1 (en) | Converter and power adapter | |
| CN115085302A (en) | Double-battery charging and discharging circuit, control method and electronic equipment | |
| CN217445265U (en) | Current limit control circuit | |
| CN116488476B (en) | Flyback switching power supply for realizing power supply protection based on secondary side feedback | |
| CN107508456B (en) | Switching power supply control circuit, switching power supply circuit and starting method | |
| CN217931786U (en) | Phase compensation sampling circuit | |
| CN114527407B (en) | Capacitance detection circuit, device and equipment | |
| US11831238B2 (en) | Power conversion system | |
| CN116581984A (en) | Control method, control device, control chip and switching power supply | |
| CN116885949A (en) | Ultralow output switching power supply with power supply protection function | |
| CN116885948A (en) | Flyback switching power supply with short-circuit protection function | |
| CN112467976B (en) | Switch converter and control circuit and control method thereof | |
| CN214205328U (en) | Electronic equipment and soft start circuit thereof | |
| CN108847771A (en) | Extend the power supply circuit and Expander backboard in PMC chip service life | |
| CN215263706U (en) | Zero-crossing detection circuit, control circuit and household appliance | |
| TW202222022A (en) | Active clamp flyback converter | |
| CN113206494A (en) | Input voltage's detection circuitry and charger | |
| CN217134168U (en) | Transformer circuit and transformer system | |
| CN108880234B (en) | Charge pump | |
| CN217445049U (en) | Power-on protection circuit and electronic equipment |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |