CN110927686A - Modulation frequency deviation mapping device for linear frequency modulation signal - Google Patents
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- 238000013507 mapping Methods 0.000 title claims abstract description 21
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- 238000003199 nucleic acid amplification method Methods 0.000 claims abstract description 9
- 230000015572 biosynthetic process Effects 0.000 claims abstract description 8
- 238000003786 synthesis reaction Methods 0.000 claims abstract description 8
- 238000010408 sweeping Methods 0.000 claims abstract description 6
- 239000013078 crystal Substances 0.000 claims description 12
- 239000003990 capacitor Substances 0.000 claims description 2
- 238000005259 measurement Methods 0.000 abstract description 16
- 238000000034 method Methods 0.000 abstract description 3
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- 238000010586 diagram Methods 0.000 description 6
- 238000001514 detection method Methods 0.000 description 5
- 230000007613 environmental effect Effects 0.000 description 4
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
- G01S7/40—Means for monitoring or calibrating
- G01S7/4004—Means for monitoring or calibrating of parts of a radar system
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
- G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
- G01S13/06—Systems determining position data of a target
- G01S13/08—Systems for measuring distance only
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Abstract
The invention discloses a linear frequency modulation signal modulation frequency offset mapping device, which mainly solves the problems of inaccurate mapping and large error of the conventional linear frequency modulation signal modulation frequency offset mapping device due to the influence of factors such as environment temperature change, vibration impact and the like. The frequency synthesizer comprises a frequency synthesis source module, a filtering amplification module, a frequency sweeping voltage-controlled oscillator, a broadband power divider and a frequency mixer. The frequency sweeping voltage-controlled oscillator generates a linear frequency modulation signal under the control of an external sawtooth wave signal FM, the frequency modulation signal is divided into two paths through a broadband power divider, one path is transmitted to an antenna transmitting port through a transmitting channel, the other path and a dot frequency signal output by the frequency comprehensive source module are subjected to frequency mixing in a frequency mixer to generate an intermediate frequency signal, and the intermediate frequency signal is processed by a filtering and amplifying module to generate a frequency standard signal CAV. The method can accurately measure and measure the modulation frequency offset of the linear frequency modulation signal in real time, is not influenced by the ambient temperature and vibration impact, and can be used for distance measurement of a radar linear frequency modulation continuous wave system.
Description
Technical Field
The invention belongs to the technical field of distance measurement, and particularly relates to a modulation frequency offset mapping device which can be used for accurately calculating a target distance under the condition of modulation frequency offset change.
Background
The modulation waveform of the linear frequency modulation continuous wave radar is sawtooth wave, the sawtooth wave signal period is T, the frequency modulation bandwidth is B, the sawtooth wave signal regulates and controls a voltage-controlled oscillator of the radar to generate linear frequency modulation continuous wave to be transmitted, the transmitted signal is reflected by a target to generate an echo signal after time delay and is received by the radar, the radar carries out frequency mixing on the echo signal and a replica of the transmitted signal, then filtering, coherent detection and sampling are carried out in sequence, finally, a group of narrow-band filters are adopted to carry out frequency spectrum analysis by an FFT method, and frequency information, namely difference frequency f is extractedbThen according to the light speed c, the sawtooth wave signal period T and the difference frequency fbRelation between the target distance R and the bandwidth B: r ═ c × T × fb) Dividing (2 × B), calculating to obtain target distance, and obtaining distance measurement error △ R/R- △ fb/fb+ △ T/T- △ B/B. wherein fbThe error of (2) is related to the number of FFT processing points, and f can be reduced by selecting a large number of pointsbAn error of (2); the high-stability crystal oscillator and the high-speed digital clock are adopted for counting, so that the quantization error of T can be reduced; the error of B is related to the stability of the voltage-controlled oscillator, the frequency fluctuation of the voltage-controlled oscillator causes a modulation frequency offset error, and the modulation frequency offset error is the first factor for restricting the improvement of the radar ranging precision. The modulation frequency deviation of the output frequency of the voltage-controlled oscillator can be changed under the influence of power supply ripples or the influence of environment temperature change or the influence of high working frequency of the radar, if the modulation frequency deviation of the output frequency of the voltage-controlled oscillator is mapped, the actual value of the modulation frequency deviation is obtained, the actually measured modulation frequency deviation value is used for calculating the frequency modulation bandwidth B and then is substituted into the distance measuring formula, and the target distance can be accurately calculated.
The existing device for mapping the modulation frequency deviation of the linear frequency modulation signal is shown in fig. 1, and two medium resonators are adopted, the resonance center frequency of the medium resonators is respectively arranged at the starting frequency point and the ending frequency point of the linear frequency modulation signal, the linear frequency modulation signal is coupled in before entering a transmitting channel, and two video pulses are formed through medium resonator resonance, wave detector envelope detection and operational amplifier amplification, the rising edges of the two video pulses correspond to the frequency sweep voltage of a sawtooth wave, and the frequency sweep voltage forms a linear relation with the modulation frequency deviation of the linear frequency modulation signal, so that the frequency sweep voltage corresponding to the modulation frequency deviation is accurately measured, the frequency modulation bandwidth B can be calculated, and the distance from a target to a radar is calculated. The existing modulation frequency offset mapping method has the following defects: the working frequency point of the dielectric resonator is the radar emission frequency, and along with the increasing radar emission frequency, the engineering realization difficulty is increased; the resonant frequency points of the dielectric resonator are easily drifted under the influence of the environment temperature or the vibration impact, so that the two detection frequency points are changed, the detection amplitude is reduced, the slope of the rising edge of the video pulse is gentle, the accuracy of the determination moment is reduced, the inaccurate modulation frequency offset measurement value is finally caused, and the distance measurement precision of the radar is reduced.
Disclosure of Invention
The invention aims to provide a modulation frequency offset mapping device of linear frequency modulation signals aiming at the defects of the prior art, so as to realize real-time accurate mapping of modulation frequency offset of the linear frequency modulation signals, improve the environmental adaptability of a radar and further ensure the real-time performance and the accuracy of radar distance measurement and calculation.
In order to achieve the purpose, the technical scheme of the invention comprises the following steps:
a modulation frequency offset mapping device of a linear frequency modulation signal is characterized by comprising a frequency synthesis source module, a filtering amplification module, a frequency scanning voltage-controlled oscillator, a broadband power divider and a frequency mixer.
The frequency sweeping voltage-controlled oscillator generates a linear frequency modulation signal under the control of an external sawtooth wave signal FM, the frequency modulation signal is divided into two paths through a broadband power divider, one path is transmitted to an antenna transmitting port through a transmitting channel, the other path and a dot frequency signal output by the frequency comprehensive source module are subjected to frequency mixing in a frequency mixer to generate an intermediate frequency signal, and the intermediate frequency signal is processed by a filtering and amplifying module to generate a frequency standard signal CAV.
Preferably, the frequency synthesizer source module includes: a point frequency voltage-controlled oscillator, a narrow-band power divider, a frequency divider, a phase discriminator, a loop filter and a crystal oscillator. The output end of the crystal oscillator is connected with the second input end of the phase discriminator, the output end of the phase discriminator is connected with the input end of the point frequency voltage-controlled oscillator through the loop filter, the output end of the point frequency voltage-controlled oscillator is divided into two paths of output through the narrow-band power divider, the first path of output enters the second input end of the frequency mixer, and the second path of output is fed back to the first input end of the phase discriminator through the frequency divider to form a phase-locked loop; when the phase difference between the 100MHz signal output by the frequency divider and the 100MHz signal output by the crystal oscillator is constant, the phase discriminator outputs a direct current voltage signal with a constant value, so that the output frequency of the point frequency voltage-controlled oscillator is locked on the point frequency of 4300MHz, and the direct current voltage signal is input into the frequency mixer through the first output end of the narrow-band power divider.
Preferably, the filtering and amplifying module includes an LC band-pass filter, a logarithmic amplifier, and a reverse amplifier, the LC band-pass filter is formed by cascading discrete capacitors and inductors, band-pass filtering is performed on the intermediate frequency signal output from the mixer to generate two 41MHz intermediate frequency points, the two 41MHz intermediate frequency points correspond to the start frequency and the end frequency of the linear frequency modulation signal modulation frequency offset mapping, the logarithmic amplifier performs logarithmic amplification on the signal output from the LC band-pass filter and inputs the signal into the reverse amplifier for reverse amplification to form two pulse signals, and the two pulse signals are the frequency standard signal CAV.
Compared with the prior art, the invention has the following advantages:
1. modulation frequency offset mapping accuracy
In the prior art, the resonance frequency points of two dielectric resonators adopted are influenced by environmental temperature change and vibration impact factors to change, so that the modulation frequency offset mapping of linear frequency modulation signals is inaccurate; the invention adopts a point frequency source as a reference source signal, down-converts a linear frequency modulation signal to an intermediate frequency, uses an LC band-pass filter to generate two frequency measurement pulses with a relative frequency difference of B, and can accurately measure and map the modulation frequency offset of the linear frequency modulation signal because the corresponding difference frequency B has a small change quantity, even if the modulation frequency offset is changed under the influence of environmental temperature and vibration impact factors, the modulation frequency offset can still be accurately measured and mapped;
2. is not limited by working frequency
In the prior art, the higher the working frequency of the radar is, the more difficult the engineering realization of the dielectric resonator under the higher working frequency is, and the poorer the environmental adaptability is; the invention adopts the LC band-pass filter working at the intermediate frequency to generate the frequency measuring pulse because of down-converting the linear frequency modulation signal to the intermediate frequency, thereby being free from the limit of higher and higher working frequency.
3. Steep rising edge of frequency measurement pulse
In the prior art, two dielectric resonators are adopted, because of the characteristics of dielectric materials and the difference of rectangular coefficients, the slopes of the rising edges of two frequency measurement signals generated respectively are gentle, and the frequency of frequency measurement is changed into a video frequency measurement pulse signal from a radio frequency signal through envelope detection, so that the rising edges of the frequency measurement signals are further gentle; the LC band-pass filter adopted by the invention has good rectangular coefficient, the rising edge slopes of two frequency measuring pulses generated successively are steep, the steeper the rising edge is, the more accurate the measuring time is, and further, the measuring precision of the modulation frequency offset is higher.
Drawings
Fig. 1 is a block diagram of a conventional linear frequency modulation signal modulation frequency offset mapping apparatus;
FIG. 2 is a block diagram of the present invention;
FIG. 3 is a block diagram of the frequency synthesis source module of the present invention
FIG. 4 is a block diagram of a filtering and amplifying module according to the present invention
Fig. 5 is an overall schematic block diagram of the present invention.
Detailed Description
The following detailed description of the embodiments of the invention refers to the accompanying drawings.
Referring to fig. 2, an example of the present invention includes an integrated frequency source module 1, a filtering and amplifying module 2, a swept frequency voltage controlled oscillator 3, a wideband power divider 4, and a mixer 5. The frequency sweeping voltage-controlled oscillator 3 is connected with an input end of a broadband power divider 4, a first output end of the broadband power divider 4 is connected with an input end of a transmitting channel, a second output end of the broadband power divider 4 is connected with a first input end of a mixer 5, an output end of a frequency synthesis source module 1 is connected with a second input end of the mixer 5, an output end of the mixer 5 is connected with an input end of a filtering and amplifying module 2, and an output end of the filtering and amplifying module 2 is connected with an input end of a system.
Referring to fig. 3, the frequency synthesis source module 1 includes a point-frequency voltage-controlled oscillator 11, a narrow-band power divider 12, a frequency divider 13, a phase discriminator 14, a loop filter 15, and a crystal oscillator 16; the output end of the crystal oscillator 16 is connected with the second input end of the phase detector 14, the output end of the phase detector 14 is connected with the input end of the point frequency voltage-controlled oscillator 11 through the loop filter 15, the output end of the point frequency voltage-controlled oscillator 11 is divided into two paths of output through the narrow-band power divider 12, the first path of output enters the second input end of the frequency mixer 5, and the second path of output is fed back to the first input end of the phase detector 14 through the frequency divider 13, so that a phase-locked loop is formed.
Referring to fig. 4, the filtering and amplifying module 2 includes an LC band-pass filter 21, a logarithmic amplifier 22, and an inverting amplifier 23. The input of LC band-pass filter 21 is connected to the output of mixer 5, and the output of LC band-pass filter 21 is connected in turn to logarithmic amplifier 22 and inverting amplifier 23.
The devices in each module of the above structural block diagram can be implemented by using existing devices or existing built mature circuits.
Referring to fig. 5, the working principle of the present invention is as follows:
the output frequency of the sweep vco 3 is controlled by the input voltage, the output frequency is linear with the input voltage, and when the input voltage is V, the output frequency is f (V) ═ K × V + f0Wherein K is the intrinsic parameter value of the sweep frequency voltage-controlled oscillator 3, i.e. the electric tuning sensitivity, f0Is the initial output frequency of the sweep frequency voltage-controlled oscillator 3 when no voltage is input; the sweep frequency voltage-controlled oscillator 3 generates a linear frequency modulation signal under the control of an external sawtooth wave FM, the output frequency of the frequency modulation signal is linearly changed along with the sawtooth wave voltage, and the sawtooth wave voltage is VMThe frequency of the output of the sweep VCO 3 is f (V)M) 4300MHz, when the sawtooth voltage is from VM-VTLinear change to VM+VTWhen, VTThe output frequency of the sweep VCO 3 is from 4300MHz-f (V) for the sawtooth voltage sweep offsetT) To 4300MHz + f (V)T) Linear variation, namely generating a linear frequency modulation signal, the linear frequency modulation signal is divided into two paths to be output through a broadband power divider 4, the first path is output to an antenna transmitting port in a transmitting channel through a low-pass filter, a power amplifier and a coupler in sequence and is transmitted out, the transmitted linear frequency modulation signal is reflected by a target to form an echo signal to enter a receiving channel, and at the moment, the transmitting signal coupled by the coupler in the transmitting channel is mixed with the echo signal to generate a constant difference frequency signal fbAnd the distance between the target and the system can be calculated according to the sawtooth wave signal parameter information at the moment. The other output signal of the broadband power divider 4 enters a first input end of a mixer 5. Adding different voltages to the tuning input end of the point frequency voltage controlled oscillator 11 to output signals with different frequencies, dividing the output signal of the point frequency voltage controlled oscillator 11 into two paths of output by a narrow-band power divider 12, inputting one path of output into the second input end of the mixer 5, dividing the frequency of the other path of output signal by a frequency divider 13 by a frequency division coefficient N of 43, inputting the divided signal and the 100MHz signal output by the crystal oscillator 16 into the input end of a phase discriminator 14 at the same time, detecting the phase difference of the two paths of signals by the phase discriminator 14 to output a dc voltage signal related to the phase difference, filtering the dc voltage signal by a loop filter 15 and inputting the dc voltage signal into the input end of the point frequency voltage controlled oscillator 11 to control the frequency of the output signal of the point frequency voltage controlled oscillator 11, and controlling the frequency of the output signal of the point frequency voltage controlled oscillator 11 by the narrow-band power divider 12 and the frequency divider 13, The phase is fed back to the phase detector 14 to form a phase locked loop. When the phase difference between the 100MHz signal output by the frequency divider 13 and the 100MHz signal output by the crystal oscillator 16 is constant, the phase detector 14 outputs a dc voltage signal with a constant value, so that the output frequency of the dot frequency voltage-controlled oscillator 11 is locked to the dot frequency of 4300MHz, and when the 100MHz signal output by the crystal oscillator 16 is a dot frequency signal with high frequency stability and low phase noise, the dot frequency voltage-controlled oscillator 11 outputs a dot frequency signal with high frequency stability and low phase noise through the phase-locked loop. The 4300MHz dot frequency signal output by the narrow-band power divider 12 is output by the mixer 5 and (V4300 MHz-f (V) output by the second output terminal of the wide-band power divider 4T))～(4300MHz+f(VT) Mixing the chirp signals to generate f (V)T)～0 and 0 to f (V)T) Two intermediate frequency chirp signals are filtered by an LC band-pass filter 21 having a center frequency of 41MHz, f (V)T) The two pulse signals are subjected to logarithmic amplification by the logarithmic amplifier 22 and then subjected to reverse amplification by the reverse amplifier 23 to form two pulse signals, wherein the two pulse signals are frequency standard signals CAV.
The modulation frequency offset mapping device of the linear frequency modulation signal can accurately map the modulation frequency offset of the linear frequency modulation signal under the environment temperature and vibration impact, improves the ranging precision, and specifically analyzes the following steps:
the rising edge of the first 41MHz frequency point in the frequency standard signal CAV corresponds to the modulation frequency deviation of 4300MHz-41MHz ═ 4289MHz output by the sweep frequency voltage-controlled oscillator 3, and the modulation frequency deviation of 4289MHz corresponds to the medium voltage V of the sawtooth wave1The rising edge of the second 41MHz frequency point in the frequency standard signal CAV corresponds to the 4300MHz +41MHz 4341MHz modulation frequency offset output by the sweep-frequency voltage-controlled oscillator 3, and the 4341MHz modulation frequency offset corresponds to the voltage V in the sawtooth wave2Because the modulation frequency deviation frequency is high, the frequency value of the modulation frequency deviation to be accurately measured is complex to realize, the frequency value is simple to realize by measuring the corresponding sawtooth voltage, the bandwidth of the band pass filter 21 of the LC band pass filter is narrow and less than 2MHz, so that the rising edges of two pulses of a frequency standard signal CAV are steep, and the measurement of the corresponding sawtooth voltage by the mapping of the rising edges of the two pulses is more accurate. LC band-pass filter adopts discrete electric capacity, inductance cascade to form, capacitance value and inductance value variation are little under ambient temperature, and under the vibration impact, capacitance value and inductance value do not change, LC band-pass filter central frequency is 41MHz, the variation is very little under ambient temperature and vibration impact, and frequency synthesis source module 1 locks the output on 4300MHz spot frequency through the phase-locked loop, the frequency stability of the spot frequency signal is high under ambient temperature and vibration impact, the frequency variation is little, because in the frequency standard signal CAV that produces, 4300MHz-41MHz that two 41MH frequency points correspond is ═ asThe variation of modulation frequency deviation of 4289MHz and 4300MHz +41MHz 4341MHz is small under the environment temperature and vibration impact, so that sawtooth wave voltage V corresponding to mapping1And V2The variation amount is small at the ambient temperature, and the distance measurement formula R is (c multiplied by T multiplied by f)b)÷(2×B)＝(c×T×fb)÷(2×K×(V2-V1) Known as the sawtooth voltage V obtained by mapping1And V2The target distance can be accurately calculated and measured without being influenced by the ambient temperature and vibration impact, so that the distance measurement error is reduced, and the distance measurement precision is improved.
The foregoing description is only an example of the present invention and is not intended to limit the invention, so that it will be apparent to those skilled in the art that various changes and modifications in form and detail may be made therein without departing from the spirit and scope of the invention.
Claims (3)
1. The modulation frequency offset mapping device of the linear frequency modulation signal is characterized by comprising a frequency synthesis source module (1), a filtering amplification module (2), a frequency sweeping voltage-controlled oscillator (3), a broadband power divider (4) and a frequency mixer (5).
The frequency sweeping voltage-controlled oscillator (3) generates a linear frequency modulation signal under the control of an external sawtooth wave signal FM, the frequency modulation signal is divided into two paths through a broadband power divider (4), one path is transmitted to an antenna transmitting port through a transmitting channel, the other path is mixed with a dot frequency signal output by the frequency synthesis source module (1) in a mixer (5) to generate an intermediate frequency signal, and the intermediate frequency signal is processed by a filtering and amplifying module (2) to generate a frequency standard signal CAV.
2. The apparatus of claim 1, wherein the frequency synthesizer source module (1) comprises: the device comprises a point frequency voltage-controlled oscillator (11), a narrow-band power divider (12), a frequency divider (13), a phase discriminator (14), a loop filter (15) and a crystal oscillator (16); the output end of the crystal oscillator (16) is connected with the second input end of the phase discriminator (14), the output end of the phase discriminator (14) is connected with the input end of the point frequency voltage-controlled oscillator (11) through a loop filter (15), the output end of the point frequency voltage-controlled oscillator (11) is divided into two paths of output through a narrow-band power divider (12), the first path of output enters the second input end of the mixer (5), and the second path of output is fed back to the first input end of the phase discriminator (14) through a frequency divider (13) to form a phase-locked loop; when the phase difference between the output signal of the frequency divider (13) and the output signal of the crystal oscillator (16) is constant, the phase discriminator (14) outputs a direct current voltage signal with a constant value, so that the output frequency of the point frequency voltage controlled oscillator (11) is locked on the point frequency of 4300MHz, and the direct current voltage signal is input to the second input end of the frequency mixer (5) through the first output end of the narrow-band power divider (12).
3. The device according to claim 1, wherein the filtering and amplifying module (2) comprises an LC band-pass filter (21), a logarithmic amplifier (22) and a reverse amplifier (23), the LC band-pass filter is formed by cascading discrete capacitors and inductors, the LC band-pass filter filters the intermediate frequency signal output from the mixer (5) to generate two 41MHz intermediate frequency points, the two intermediate frequency points correspond to the start frequency and the end frequency of the modulation frequency offset mapping of the chirp signal, the logarithmic amplifier (22) logarithmically amplifies the signal output from the LC band-pass filter (21) and inputs the signal into the reverse amplifier (23) for reverse amplification to form two pulse signals, and the two pulse signals are the frequency standard signal CAV.
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN111835342A (en) * | 2020-07-24 | 2020-10-27 | 中国人民解放军海军航空大学 | Millimeter wave radar signal generator |
| CN114531327A (en) * | 2022-01-26 | 2022-05-24 | 小唐科技（上海）有限公司 | Frequency deviation self-tracking device |
Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4610030A (en) * | 1983-11-04 | 1986-09-02 | Thomson-Lgt | Frequency modulated transmitter applicable to MF broadcasting |
| CN101666874A (en) * | 2009-09-07 | 2010-03-10 | 北京科技大学 | Measuring device for accurate correction by FMCW radar distance measurement and compensation correction method |
| CN203632644U (en) * | 2013-10-25 | 2014-06-04 | 海华电子企业(中国)有限公司 | Novel X wave band frequency synthesizer based on DDS and PLL |
| CN104865567A (en) * | 2015-03-12 | 2015-08-26 | 零八一电子集团有限公司 | Missile-borne frequency modulated continuous wave miss distance measurement radar system |
| CN107979388A (en) * | 2017-12-29 | 2018-05-01 | 陕西烽火电子股份有限公司 | A kind of wave filter group device of ultrashort wave broadband transceiver |
| CN109444833A (en) * | 2018-10-19 | 2019-03-08 | 陕西长岭电子科技有限责任公司 | Contactless Doppler radar analogue system |
| CN209497453U (en) * | 2019-02-26 | 2019-10-15 | 河北鸿捷电子科技有限公司 | A kind of linear frequency sweep local oscillator |
-
2019
- 2019-12-17 CN CN201911304538.0A patent/CN110927686A/en active Pending
Patent Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4610030A (en) * | 1983-11-04 | 1986-09-02 | Thomson-Lgt | Frequency modulated transmitter applicable to MF broadcasting |
| CN101666874A (en) * | 2009-09-07 | 2010-03-10 | 北京科技大学 | Measuring device for accurate correction by FMCW radar distance measurement and compensation correction method |
| CN203632644U (en) * | 2013-10-25 | 2014-06-04 | 海华电子企业(中国)有限公司 | Novel X wave band frequency synthesizer based on DDS and PLL |
| CN104865567A (en) * | 2015-03-12 | 2015-08-26 | 零八一电子集团有限公司 | Missile-borne frequency modulated continuous wave miss distance measurement radar system |
| CN107979388A (en) * | 2017-12-29 | 2018-05-01 | 陕西烽火电子股份有限公司 | A kind of wave filter group device of ultrashort wave broadband transceiver |
| CN109444833A (en) * | 2018-10-19 | 2019-03-08 | 陕西长岭电子科技有限责任公司 | Contactless Doppler radar analogue system |
| CN209497453U (en) * | 2019-02-26 | 2019-10-15 | 河北鸿捷电子科技有限公司 | A kind of linear frequency sweep local oscillator |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN111835342A (en) * | 2020-07-24 | 2020-10-27 | 中国人民解放军海军航空大学 | Millimeter wave radar signal generator |
| CN114531327A (en) * | 2022-01-26 | 2022-05-24 | 小唐科技（上海）有限公司 | Frequency deviation self-tracking device |
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