CN109975768B - Ka wave band frequency synthesizer based on radar - Google Patents
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- CN109975768B CN109975768B CN201910400810.9A CN201910400810A CN109975768B CN 109975768 B CN109975768 B CN 109975768B CN 201910400810 A CN201910400810 A CN 201910400810A CN 109975768 B CN109975768 B CN 109975768B
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- 230000010355 oscillation Effects 0.000 claims abstract description 40
- 239000013078 crystal Substances 0.000 claims abstract description 17
- 230000005284 excitation Effects 0.000 claims abstract description 15
- 229910005538 GaSn Inorganic materials 0.000 claims description 21
- 230000003321 amplification Effects 0.000 claims description 12
- 238000003199 nucleic acid amplification method Methods 0.000 claims description 12
- JBRZTFJDHDCESZ-UHFFFAOYSA-N AsGa Chemical compound [As]#[Ga] JBRZTFJDHDCESZ-UHFFFAOYSA-N 0.000 description 18
- 229910001218 Gallium arsenide Inorganic materials 0.000 description 18
- 101100455646 Homo sapiens LAMTOR1 gene Proteins 0.000 description 10
- 102100022151 Ragulator complex protein LAMTOR1 Human genes 0.000 description 10
- BTCSSZJGUNDROE-UHFFFAOYSA-N gamma-aminobutyric acid Chemical compound NCCCC(O)=O BTCSSZJGUNDROE-UHFFFAOYSA-N 0.000 description 8
- 230000006872 improvement Effects 0.000 description 8
- 238000001228 spectrum Methods 0.000 description 8
- 238000010586 diagram Methods 0.000 description 4
- 238000000034 method Methods 0.000 description 4
- 230000004044 response Effects 0.000 description 4
- 238000012986 modification Methods 0.000 description 3
- 230000004048 modification Effects 0.000 description 3
- 238000005516 engineering process Methods 0.000 description 2
- 238000012360 testing method Methods 0.000 description 2
- 238000004458 analytical method Methods 0.000 description 1
- 230000009286 beneficial effect Effects 0.000 description 1
- 230000015572 biosynthetic process Effects 0.000 description 1
- 238000004364 calculation method Methods 0.000 description 1
- 239000003990 capacitor Substances 0.000 description 1
- 230000015556 catabolic process Effects 0.000 description 1
- 230000008859 change Effects 0.000 description 1
- 230000001427 coherent effect Effects 0.000 description 1
- 230000007547 defect Effects 0.000 description 1
- 238000006731 degradation reaction Methods 0.000 description 1
- 238000013461 design Methods 0.000 description 1
- 238000001514 detection method Methods 0.000 description 1
- 230000005611 electricity Effects 0.000 description 1
- 239000000463 material Substances 0.000 description 1
- 230000001105 regulatory effect Effects 0.000 description 1
- 238000012216 screening Methods 0.000 description 1
- 230000006641 stabilisation Effects 0.000 description 1
- 238000011105 stabilization Methods 0.000 description 1
- 238000003786 synthesis reaction Methods 0.000 description 1
- XLYOFNOQVPJJNP-UHFFFAOYSA-N water Substances O XLYOFNOQVPJJNP-UHFFFAOYSA-N 0.000 description 1
Classifications
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
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- Engineering & Computer Science (AREA)
- Computer Networks & Wireless Communication (AREA)
- Physics & Mathematics (AREA)
- General Physics & Mathematics (AREA)
- Radar, Positioning & Navigation (AREA)
- Remote Sensing (AREA)
- Stabilization Of Oscillater, Synchronisation, Frequency Synthesizers (AREA)
Abstract
The invention relates to a Ka wave band frequency synthesizer based on radar, which comprises a signal source input circuit, a first local oscillation input signal and a second local oscillation input signal, wherein the signal source input circuit is formed by connecting an 80MHz crystal oscillator and a coupler in series, the 80MHz crystal oscillator is used for generating an 80MHz signal, and the coupler is used for dividing frequency to obtain the first local oscillation input signal and the second local oscillation input signal; the two-stage local oscillator circuit is used for outputting a local oscillator 16.8GHz signal, the two-stage local oscillator circuit is used for outputting a two-stage local oscillator 1.54GHz signal, the excitation signal circuit comprises a primary amplifying circuit and a secondary amplifying circuit which are connected in series, the output end of the two-stage local oscillator circuit is connected with the input end of the primary amplifying circuit after being mixed with a 60MHz intermediate frequency signal, the output end of the one-stage local oscillator circuit 2 is connected with the output end of the primary amplifying circuit to the input end of the secondary amplifying circuit after being multiplied by frequency, and the secondary amplifying circuit is used for generating a 35.2GHz excitation signal.
Description
Technical Field
The invention relates to the field of radars, in particular to a Ka-band frequency synthesizer based on radar.
Background
The frequency source is the heart of the radar system, wherein the most important indicator of the frequency source is phase noise. If the phase noise of the frequency source is poor, the reflected wave of the radar is submerged under the noise, the detection distance of the radar is greatly shortened, and the phenomenon is more obvious in the Doppler radar. In the millimeter wave band, the minimum required index of the radar, namely 105dBc@1KHz, is difficult to achieve by the phase noise of the frequency source, and the phase noise of the SIN-KaTRX5-T is 8dBc worse than the phase noise index required by the radar by taking the SIN-KaTRX5-T as an example of a product of the SiYing. The index of the frequency source scheme is up to-105dBc@[email protected] from the new design, and the lowest phase noise index used by the radar is met; and this index may be further optimized.
Improvement factor I (1000 Hz) of emission excitation source and limit improvement factor calculation formula。
Wherein: i is a limit improvement factor (dB), S/N is a signal-to-noise ratio (dB), B is an analysis bandwidth (Hz) of the spectrum analyzer,
PRF is the transmit pulse repetition frequency (Hz).
The common similar products in the market are I (1000 Hz) is more than or equal to 45dB.
The conventional frequency source in this frequency band of 35GHz has poor far-end phase noise. about-110dBc@[email protected], -110dBc@[email protected], -110dBc@[email protected].
The millimeter wave receiving component in the market usually uses a harmonic mixer, the input and output standing waves of the harmonic mixer are very poor, and in practical engineering application, the input power stability requirement of the harmonic mixer on the local oscillator is very high: 1. the harmonic mixer outputs spurious signals, intermodulation is very difficult to control, and the harmonic mixer can work normally only when local oscillation power is fixed to a certain value (about 13 dBm); 2. for the radar, the working environment is in the field, the air temperature is changed to (-40 ℃ to 70 ℃), and in the severe temperature change, the power of the microwave local oscillator also changes along with the environment temperature, so that the harmonic mixer is not suitable for radar products.
Disclosure of Invention
The invention aims to overcome the defects of the prior art and provides a Ka-band frequency synthesizer based on radar, which is used for outputting excitation signals suitable for radar products.
The aim of the invention is realized by the following technical scheme:
a Ka band frequency synthesizer based on radar usage, comprising:
the signal source input circuit is formed by connecting an 80MHz crystal oscillator and a coupler in series, wherein the 80MHz crystal oscillator is used for generating an 80MHz signal, and a local oscillator input signal and two local oscillator input signals are obtained by frequency division of the coupler;
the input end of the local oscillation circuit is connected with the first output port of the coupler, and the output end of the local oscillation circuit outputs a local oscillation 16.8GHz signal;
the input end of the two local oscillation circuits is connected with the second output port of the coupler, and the output end of the two local oscillation circuits outputs a two local oscillation 1.54GHz signal;
the excitation signal circuit comprises a primary amplification circuit and a secondary amplification circuit which are connected in series, wherein the output end of the secondary local oscillation circuit is connected with the input end of the primary amplification circuit after being mixed with a 60MHz intermediate frequency signal, the output end of the primary amplification circuit is connected to the input end of the secondary amplification circuit after frequency multiplication of the primary local oscillation circuit 2, and the secondary amplification circuit is used for generating 35.2GHz excitation signals.
Furthermore, the local oscillation circuit is formed by sequentially connecting a medium phase-locked oscillator, a 2 frequency multiplier A, an amplifier A, a frequency modulator and a power divider A in series, and the input end of the medium phase-locked oscillator is connected with the output port I of the coupler.
Further, the two local oscillator circuits are composed of an amplifier B, a power divider B, a coaxial medium oscillator and a power divider C which are sequentially connected in series with the coupler, and the input end of the amplifier B is connected with the output port II of the coupler.
Further, the primary amplifying circuit is formed by sequentially connecting a primary mixer, a primary frequency modulator and a primary amplifying tube in series, and the output end of a local oscillation circuit is connected with the input end of the primary mixer;
the secondary amplifying power is formed by sequentially connecting a secondary mixer, a secondary frequency modulator, a secondary amplifying tube and a coupler in series, and a 2 frequency multiplier B is connected between the output end of the local oscillation circuit and the secondary mixer in series.
Furthermore, the structural parameters of the 2 frequency multiplier A and the 2 frequency multiplier B are completely the same, and the 2 frequency multiplier A and the 2 frequency multiplier B consist of a primary amplifying tube, a secondary amplifying tube and a tertiary amplifying tube;
the primary amplifying tube, the secondary amplifying tube and the tertiary amplifying tube share drain voltage VD;
the secondary amplifying tube and the tertiary amplifying tube share the grid voltage Vg;
the grid electrode of the primary amplifying tube is connected with a frequency multiplication voltage Vg1, wherein the input P1 of the primary amplifying tube is smaller than-10 dBm to-5 dBm.
Furthermore, the models of the primary amplifying tube, the secondary amplifying tube and the tertiary amplifying tube are GaSn amplifying tubes.
Further, the power divider C also outputs:
one path of 80M clock signal;
one path is sequentially connected with a frequency modulator A, a frequency multiplier 3, a frequency modulator B and an amplifier B in series to output 240M clocks.
The clock signal of 80MHz is sent to a clock distribution circuit of an external radar signal processor; 240MHz is sent to the radar DDS array as a reference clock.
Further, the front end of the primary mixer is connected with an intermediate frequency digital module, and the 60MHz intermediate frequency signal is generated by the intermediate frequency digital module.
The beneficial effects of the invention are as follows:
1) According to the scheme, the phase noise of a 35.2GHz frequency source is greatly improved, the theoretical limit value can be optimized to be-111 dBc@[email protected], the actual prototype test value is-105dBc@[email protected], and the actual prototype test value is far higher than the conventional millimeter wave frequency source index-97dBc@[email protected] in the market.
2) The phase noise and the limit improvement factor of the millimeter wave radar system are improved, so that the phase noise of the millimeter wave water floating plant radar system reaches-105dBc@[email protected]; the limit improvement factor of the radar system is optimized to be I (1000 Hz) not less than 51dB, which is higher than the index of the conventional millimeter wave radar under the same condition in the market.
3) The radar echo is made more coherent and interference resistant.
4) The harmonic mixer is improved to be a frequency multiplier and a GaSn (gallium arsenide) mixer, so that the output of the frequency source system always has stable pure signals.
5) The invention improves a GaSn (gallium arsenide) amplifier by Cheng Beipin: 1. the frequency of the input GaSn (gallium arsenide) amplifier is not in the working frequency band of the amplifier; 2. the frequency of the frequency multiplication output is screened through the working frequency section of the GaSn (gallium arsenide) amplifier, and the frequency multiplication output can be used as a pure local oscillation signal without a filter after frequency multiplication; 3. the number of devices used for the frequency source frequency multiplication channel is reduced, so that the phase noise of the frequency source is optimized to a certain extent.
6) The far-end phase noise of the frequency spectrum is greatly improved, and the far-end phase noise of the frequency spectrum is better than-119dBc@[email protected], -144dBc@[email protected] and-153dBc@[email protected].
7) CRO (coaxial dielectric oscillator) technology is used to improve the phase noise of the phase locked loop output.
8) The limit improvement factor I (1000 Hz) of the radar is optimized to be more than or equal to 52dB.
Drawings
FIG. 1 is a system block diagram of the present invention;
FIG. 2 is a circuit diagram of an improved 2-frequency multiplier A/2-frequency multiplier B;
FIG. 3 is a schematic diagram of a GaSn (gallium arsenide) cascode amplifier
Fig. 4 is a graph of the frequency response of a two-stage amplifier and a three-stage amplifier.
Detailed Description
The technical scheme of the present invention is described in further detail below in connection with specific embodiments, but the scope of the present invention is not limited to the following.
As shown in fig. 1, a Ka band frequency synthesizer based on radar use, comprising:
the signal source input circuit is formed by connecting an 80MHz crystal oscillator and a coupler in series, wherein the 80MHz crystal oscillator is used for generating an 80MHz signal, and a local oscillator input signal and two local oscillator input signals are obtained by frequency division of the coupler;
the input end of the local oscillation circuit is connected with the first output port of the coupler, and the output end of the local oscillation circuit outputs a local oscillation 16.8GHz signal;
the input end of the two local oscillation circuits is connected with the second output port of the coupler, and the output end of the two local oscillation circuits outputs a two local oscillation 1.54GHz signal;
the excitation signal circuit comprises a primary amplifying circuit and a secondary amplifying circuit which are connected in series, wherein the output end of the secondary local oscillator circuit is connected with the input end of the primary amplifying circuit after being mixed with a 60MHz intermediate frequency signal, the output end of the primary amplifying circuit is connected to the input end of the secondary amplifying circuit after being multiplied by frequency of the primary local oscillator circuit 2, and the secondary amplifying circuit is used for generating a 35.2GHz excitation signal.
The local oscillation circuit is formed by sequentially connecting a medium phase-locked oscillator, a 2 frequency multiplier A, an amplifier A, a frequency modulator and a power divider A in series, and the input end of the medium phase-locked oscillator is connected with the output port I of the coupler.
The two local oscillation circuits are composed of an amplifier B, a power divider B, a coaxial medium oscillator and a power divider C which are sequentially connected in series by a coupler, and the input end of the amplifier B is connected with the output port II of the coupler.
The primary amplifying circuit is formed by sequentially connecting a primary mixer, a primary frequency modulator and a primary amplifying tube in series, and the output end of a local oscillation circuit is connected with the input end of the primary mixer;
the secondary amplifying electricity is composed of a secondary mixer, a secondary frequency modulator, a secondary amplifying tube and a coupler which are sequentially connected in series, and a 2 frequency multiplier B is connected between the output end of a local oscillation circuit and the secondary mixer in series.
The 80MHz crystal oscillator generates 80MHz pure frequency to be sent to a PDRO (medium phase locked oscillator), the PDRO (medium phase locked oscillator) medium phase locked oscillator generates a very high reference frequency of 8.4GHz, and a local oscillator of 16.8GHz is generated by a 2 frequency multiplier A; and a path of 80MHz is used as a reference to be sent to a PLL+CRO (coaxial medium oscillator) to generate a two-local oscillator 1.54GHz.60MHz is an intermediate frequency signal generated by an intermediate frequency digital module, the 60MHz is mixed with two local oscillators sequentially to obtain 1.6GHz, and a 2 frequency multiplier B of the 1.6GHz and the local oscillator is used to obtain a 35.2GHz excitation signal with high phase noise.
The 35.2GHz excitation signal is obtained by a 2-frequency multiplier B of 60MHz intermediate frequency mixing with two local oscillators and one local oscillator in sequence, and the phase noise index of the excitation signal depends on the worst phase noise in the 2-frequency multipliers of the 60MHz intermediate frequency, the two local oscillators and the one local oscillator. 60MHz has digital module generation, its phase noise is about-130 dBc@1KHz; the two local oscillators 1.54GHz are generated by pll+cro (coaxial dielectric oscillator).
Its phase noise is about = -221+10lg (80 MHz) +20lg (19.25) = -221+79+26 = -116dbc@1khz; the indexes of the former 2 indexes are far higher than-105 dBc@1KHz, so that one of the core indexes of the product can be realized as long as the 2-frequency multiplication phase noise of a local oscillator is better than-105 dBc@1KHz: output excitation signal phase noise-105dBc@[email protected]. This index is inseparable from many details of the overall scheme, which are described in detail below.
The 80MHz crystal oscillator output adopts a coupler frequency division mode, and the reason is that: 1) The crystal oscillator is the period with the lowest phase noise in the world, and the phase noise can only be deteriorated and never becomes good after any period; 2) The crystal oscillator transmits a reference signal to a PDRO (medium phase-locked oscillator) through a main path of the coupler, so that the minimum loss of phase noise transmitted to the PDRO (medium phase-locked oscillator) on the main path can be ensured, and if the influence of a secondary path of the power divider is relatively large; 3) The coupler has high main circuit power, so that an amplifier is not needed to stabilize the power of the phase demodulation frequency of the PDRO (medium phase-locked oscillator) on the main circuit at high and low temperatures, and the phase noise of the frequency output by the crystal oscillator is certainly deteriorated after the frequency output by the crystal oscillator passes through the amplifier.
A PDRO (dielectric phase locked oscillator) mode is used instead of a comb spectrum (step diode) mode: 1) The step diode is very high in base low noise (high in far-end phase noise) at a high frequency band of 16.8GHz, the root cause is that far-end noise output by all devices (including crystal oscillator) is mainly white noise, the value of the far-end noise is a constant (normally, the far-end noise of the crystal oscillator is= -170 dBc), the theoretical degradation value of the noise after frequency multiplication through the step diode is= lgN =46.5 dBc, and the theoretical value of the base noise is= -123.5dBc when the comb spectrum outputs 16.8GHz (because an amplifier is added in a link, the value is generally smaller); 2) PDRO (dielectric phase locked oscillator) is an indirect frequency synthesis whose far-end noise has a relation to DRO only, whereas DRO is far-end noise=white noise (which has a value of about-155 dBc) during this period; 3) The near-spectrum phase noise is because the loop filter largely suppresses the noise power, so the near-spectrum phase noise PDRO (dielectric phase locked oscillator) is also far superior to the step diode. Summarizing: the phase noise of PDRO (dielectric phase-locked oscillator) is far superior to that of step diode, and when the phase noise of frequency source is greatly raised, the limit improvement factor of radar is optimized to I (1000 Hz) and is more than or equal to 52dB.
As shown in fig. 2, the structural parameters of the 2 frequency multiplier A and the 2 frequency multiplier B are completely the same, and the 2 frequency multiplier A and the 2 frequency multiplier B consist of a primary amplifying tube, a secondary amplifying tube and a tertiary amplifying tube; the primary amplifying tube, the secondary amplifying tube and the tertiary amplifying tube share drain voltage VD; the secondary amplifying tube and the tertiary amplifying tube share the grid voltage Vg; the grid electrode of the primary amplifying tube is connected with a frequency multiplication voltage Vg1, wherein the input P1 of the primary amplifying tube is smaller than-10 dBm to-5 dBm, and the models of the 2 frequency multipliers A and 2 frequency multiplier B are GaSn amplifiers.
The schematic diagram of a common GaSn (gallium arsenide) cascade amplifier is shown in fig. 3, and the GaSn (gallium arsenide) cascade amplifier chip needs to be loaded with a gate voltage Vg and a drain voltage VD to work, so that the GaSn (gallium arsenide) cascade amplifier chip is modified, a gate voltage line of a first-stage amplifying tube of a bare chip is cut off, then Vg1 is newly led out, the Vg1 is adjusted to enable the voltage to enable the first-stage amplifying tube to work in a nonlinear distortion state (and the P1 of the first-stage amplifying tube is adjusted to enable the input P1 to be smaller than-10 dBm to-5 dBm), and therefore the first-stage amplifying tube can generate a plurality of N frequency multiplication signals, and the frequency multiplication purpose is achieved, wherein v1=1.25v.
Meanwhile, the frequency multiplication of the amplifier is carried out, and meanwhile, the screening of the frequency multiplication signal is also needed, and here, the stray is filtered by using the characteristic that the gain curve of the 2-stage (namely a second-stage amplifying tube and a third-stage amplifying tube) GaSn (gallium arsenide) amplifier only works in the frequency range of 30-40 GHz; the frequency response curve of the latter 2-stage GaSn (gallium arsenide) amplifier is shown in fig. 4.
The method is equivalent to cutting off a grid voltage wire of a first-stage amplifying tube of a GaSn (gallium arsenide) cascade amplifier chip, then newly leading out Vg1, and regulating the Vg1 to enable the voltage to enable the first-stage amplifying tube to work in a nonlinear distortion state; 2) Inputting 16.8GHz signals to a GaSn (gallium arsenide) cascade amplifier chip, wherein the 16.8GHz signals are not in the frequency response range of the GaSn (gallium arsenide) cascade amplifier, but the first-stage amplifying tube works in a nonlinear distortion state, and the energy of the excessive input signals cannot be completely disappeared and can only be released by the energy of the frequency multiplication signals, so that the frequency multiplication power of 2 is very high; 3) The output signals after frequency multiplication mainly comprise: 16.8GHz,33.6GHz,50.4GHz; 4) The output frequency multiplication signal only has 33.6GHz response in the following 2-stage GaSn (gallium arsenide) amplifier, so other stray back amplifiers are filtered; 5) The method utilizes the characteristics of long millimeter wave frequency multiplication stray distance and narrow relative frequency bandwidth of GaSn (gallium arsenide) amplifier materials in millimeter wave bands.
Use of CRO (coaxial dielectric oscillator) improves phase noise of the phase locked loop output: CRO (coaxial dielectric oscillator) =dielectric voltage controlled oscillator, which has advantages in much higher power consumption, lower power consumption, better far-end phase noise, smaller volume than the transistor VCO phase noise. The internal part adopts CR (mixed circuit of resistor and capacitor) and varactor with high Q value to conduct frequency stabilization and frequency tuning
In summary, the greatest characteristics of the present project are:
1. adopting 80MHz reference frequency; 2. the method is in accordance with the use index of the water-float plant radar; 3. outputting an excitation frequency of 35.2GHz point frequency; 4. limit theoretical phase noise is better than-111 dBc@[email protected]; 5. prototype phase noise is better than-105dBc@[email protected],; 6. the limit improvement factor is optimized to be I (1000 Hz) more than or equal to 51dB; 7. the invention improves the GaSn (gallium arsenide) amplifier into a frequency multiplier, thereby optimizing the phase noise of a microwave link (note that the frequency of the input GaSn (gallium arsenide) amplifier is not in the working frequency band of the amplifier, so that the frequency of the frequency multiplication output can be screened through the working frequency band of the GaSn (gallium arsenide) amplifier), and the frequency multiplication can be used as a pure local oscillation signal without a filter. 8. A PDRO (dielectric phase locked oscillator) phase lock technique is used. 9. The far-end phase noise of the spectrum is better than-119dBc@[email protected], -144dBc@[email protected] and-153dBc@[email protected]. 10. CRO (coaxial dielectric oscillator) technology is used to improve system phase noise. 11. The output of the crystal oscillator adopts a coupler mode, thereby ensuring that the phase noise loss on the main circuit is minimum. 12. While satisfying the above conditions.
The foregoing is merely a preferred embodiment of the invention, and it is to be understood that the invention is not limited to the form disclosed herein but is not to be construed as excluding other embodiments, but is capable of numerous other combinations, modifications and environments and is capable of modifications within the scope of the inventive concept, either as taught or as a matter of routine skill or knowledge in the relevant art. And that modifications and variations which do not depart from the spirit and scope of the invention are intended to be within the scope of the appended claims.
Claims (5)
1. A Ka band frequency synthesizer for use with radar, comprising:
the signal source input circuit is formed by connecting an 80MHz crystal oscillator and a coupler in series, wherein the 80MHz crystal oscillator is used for generating an 80MHz signal, and a local oscillator input signal and two local oscillator input signals are obtained by frequency division of the coupler;
the input end of the local oscillation circuit is connected with the first output port of the coupler, and the output end of the local oscillation circuit outputs a local oscillation 16.8GHz signal;
the input end of the two local oscillation circuits is connected with the second output port of the coupler, and the output end of the two local oscillation circuits outputs a two local oscillation 1.54GHz signal;
the excitation signal circuit comprises a primary amplification circuit and a secondary amplification circuit which are connected in series, wherein the output end of the secondary local oscillation circuit is connected with the input end of the primary amplification circuit after being mixed with a 60MHz intermediate frequency signal, the output end of the primary amplification circuit is connected to the input end of the secondary amplification circuit after being multiplied by frequency of the primary local oscillation circuit 2, and the secondary amplification circuit is used for generating a 35.2GHz excitation signal;
the local oscillation circuit is formed by sequentially connecting a medium phase-locked oscillator, a 2 frequency multiplier A, an amplifier A, a frequency modulator and a power divider A in series, and the input end of the medium phase-locked oscillator is connected with the output port I of the coupler;
the two local oscillation circuits are composed of an amplifier B, a power divider B, a coaxial medium oscillator and a power divider C which are sequentially connected in series by the coupler, and the input end of the amplifier B is connected with the output port II of the coupler;
the primary amplifying circuit is formed by sequentially connecting a primary mixer, a primary frequency modulator and a primary amplifying tube in series, and the output end of a local oscillation circuit is connected with the input end of the primary mixer;
the secondary amplifying power is formed by sequentially connecting a secondary mixer, a secondary frequency modulator, a secondary amplifying tube and a coupler in series, and a 2 frequency multiplier B is connected between the output end of the local oscillation circuit and the secondary mixer in series.
2. The Ka-band frequency synthesizer based on radar use according to claim 1, wherein the 2-multiplier a and 2-multiplier B are identical in structural parameters and consist of a primary amplifier tube, a secondary amplifier tube and a tertiary amplifier tube;
the primary amplifying tube, the secondary amplifying tube and the tertiary amplifying tube share drain voltage VD;
the secondary amplifying tube and the tertiary amplifying tube share the grid voltage Vg;
the grid electrode of the primary amplifying tube is connected with the frequency multiplication voltage Vg1, wherein the input P1 of the primary amplifying tube is smaller than-10 dBm to-5 dBm.
3. The Ka-band frequency synthesizer based on radar usage according to claim 2, wherein the primary amplifier, the secondary amplifier, and the tertiary amplifier are GaSn amplifier types.
4. A Ka-band frequency synthesizer based on radar use according to claim 3 wherein the power divider C further outputs:
one path of 80M clock signal;
one path is sequentially connected with a frequency modulator A, a frequency multiplier 3, a frequency modulator B and an amplifier B in series to output 240M clocks.
5. The Ka-band frequency synthesizer based on radar usage according to claim 1, wherein said primary mixer front end is connected to an intermediate frequency digital module from which said 60MHz intermediate frequency signal is generated.
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