CN104184357A - Storage battery charging and discharging control system and method - Google Patents

Abstract

The invention relates to a storage battery charging and discharging control system and method. The system comprises a rectifier and a load. The two ends of the load are connected with a capacitor C in parallel, the rectifier is connected with an inductor L and a resistor Rs in series, an AC-DC converter is additionally arranged between the rectifier and the load, the AC-DC converter is a full-bridge circuit with a half bridge composed of insulated gate bipolar transistors V and diodes VD in a parallel connection mode, each two-phase circuit of the full-bridge circuit comprises two boost chopping circuits which are formed by the insulated gate bipolar transistors V, the diodes VD and inductors Ls. The direct-current side voltage of the system is controlled through the duty ratio of the insulated gate bipolar transistors V. According to the storage battery charging and discharging control system and method, the AC-DC converter is additionally arranged between the rectifier and the load, the current feedback technology is used, current tracking input voltage is input, therefore, total harmonic distortion (THD) of currents of an input end is made to be less than 5%, and the power factor can be improved to 0.99 or higher. Active devices are adopted in the storage battery charging and discharging control system and method, and therefore active power factor correction is achieved.

Description

A kind of storage battery charge-discharge control system and method

Technical field

The present invention relates to a kind of storage battery charge-discharge control system based on two-way inversion transformation technique, belong to vehicle product test technical field.

Background technology

Current accumulator charging/discharging system adopts industrial computer as controlling hinge, is a kind of centralized management mode, once industrial computer is out of joint, large quantities of storage batterys of being controlled by it are just all scrapped, and to producer, bring very large economic loss.

Summary of the invention

In order to overcome the deficiencies in the prior art, the invention provides a kind of storage battery charge-discharge control system based on two-way inversion transformation technique, by add AC-DC converter between rectifier and load, solve industrial computer centralized management mode and easily produce the problem that large quantities of storage batterys are scrapped, applied current feedback technique, input current is followed the tracks of input voltage, thereby makes input electric current total harmonic distortion THD be less than 5%, and power factor can bring up to 0.99 or higher.

Technical scheme of the present invention is: a kind of storage battery charge-discharge control system, this comprises rectifier and load, load two ends are parallel with capacitor C, rectifier series inductance L and resistance R s, between described rectifier and load, add AC-DC converter, AC-DC converter is the full-bridge circuit that half-bridge is composed in parallel by insulated gate bipolar transistor V and diode VD, and the every quarter-phase circuit of full-bridge circuit comprises by insulated gate bipolar transistor V, diode VD, diode VD and inductance L _stwo boost choppers that form.The DC voltage of this system is by insulated gate bipolar transistor V Duty ratio control.In every quarter-phase circuit, work as u _sduring >0, by insulated gate bipolar transistor V ₂, diode VD ₄, diode VD ₁, inductance L _swith insulated gate bipolar transistor V ₃, diode VD ₁, diode VD ₄, inductance L _sform two boost choppers; Work as u _sduring <0, by insulated gate bipolar transistor V ₁, diode VD ₃, diode VD ₂, inductance L _swith insulated gate bipolar transistor V ₄, diode VD ₂, diode VD ₃, inductance L _sform two boost choppers, as insulated gate bipolar transistor V ₂during conducting, u _spass through V ₂, VD ₄to L _senergy storage, works as V ₂during shutoff, L _sthe energy storing passes through VD ₁, VD ₄to DC bus capacitor C charging, separate by two loops of chopper circuit.

An accumulator charging and discharging control method, is characterized in that, the method comprises the following steps: step 1, the voltage equation to reversible three phase static coordinate system $\begin{array}{c}{e}_a=L\frac{{\mathrm{di}}_a}{\mathrm{dt}}+v_a\\ e_b=L\frac{{\mathrm{di}}_b}{\mathrm{dt}}+v_b\\ e_c=L\frac{{\mathrm{di}}_c}{\mathrm{dt}}+v_c\end{array}$ Carrying out Clark conversion obtains $\left[\begin{array}{c}{e}_x\\ e_y\end{array}\right]=\frac{2}{3}\left[\begin{array}{ccc}1& -\frac{1}{2}& -\frac{1}{2}\\ \frac{\sqrt{3}}{2}& \sqrt{3}& 0\end{array}\right]\left[\begin{array}{c}{e}_a\\ e_b\\ e_c\end{array}\right],$ Wherein, i _afor reversible convertor A phase input current, i _bfor reversible convertor B phase input current, i _cfor reversible convertor C phase input current, v _afor reversible convertor A phase input voltage, v _bfor reversible convertor B phase input voltage, it is reversible convertor C phase input voltage; Step 2, three-phase mains voltage $\begin{array}{c}{e}_a=E\cos \left(\mathrm{wt}\right)\\ e_b=E\cos (\mathrm{wt}-\frac{2}{3}\mathrm{\&pi;})\\ e_c=E\cos (\mathrm{wt}+\frac{2}{3}\mathrm{\&pi;})\end{array}$ Substitution Clark conversion obtains the expression formula of input voltage under x-y static coordinate $\begin{array}{c}{e}_x=E\cos \left(\mathrm{wt}\right)\\ e_y=E\sin \left(\mathrm{wt}\right)\end{array},$ Wherein, e _afor reversible convertor A phase input voltage, e _bfor reversible convertor B phase input voltage, e _cfor reversible convertor C phase input voltage, E is the peak value of power supply phase voltage, the angular frequency that w is supply voltage;

Step 3, the equation by reversible convertor in static x-y coordinate system $\begin{array}{c}{e}_x=L\frac{{\mathrm{di}}_x}{\mathrm{dt}}+v_x\\ e_y=L\frac{{\mathrm{di}}_y}{\mathrm{dt}}+v_y\end{array}$ Static coordinate system in voltage equation be transformed in the d-q two-phase synchronous coordinate system with the rotation of w angular frequency, adopt PARK transformation matrix $\left[\begin{array}{c}{e}_d\\ e_q\end{array}\right]=\left[\begin{array}{cc}\cos \left(\mathrm{wt}\right)& \sin \left(\mathrm{wt}\right)\\ -\sin \left(\mathrm{wt}\right)& \cos \left(\mathrm{wt}\right)\end{array}\right]\left[\begin{array}{c}{e}_x\\ e_y\end{array}\right]$ Obtain $\left[\begin{array}{c}{e}_d\\ e_q\end{array}\right]=L\frac{d}{\mathrm{dt}}\left[\begin{array}{c}{i}_d\\ i_q\end{array}\right]+\mathrm{wL}\left[\begin{array}{c}-i_q\\ i_d\end{array}\right]+\left[\begin{array}{c}{v}_d\\ v_q\end{array}\right];$ Step 4, the expression formula by input voltage under x-y static coordinate $\begin{array}{c}{e}_x=E\cos \left(\mathrm{wt}\right)\\ e_y=E\sin \left(\mathrm{wt}\right)\end{array}$ Substitution PARK transformation matrix obtains the expression formula of input voltage in synchronous d-q coordinate system $\begin{array}{c}{e}_d=E\\ e_q=0\end{array};$ Step 5, from $\begin{array}{c}{e}_d=E\\ e_q=0\end{array}$ Can find out that d axle is useful work amount, q shaft type idle work amount, if realize unity power factor transmission, the reference current of q axle the active power of input is $P=\frac{3}{2}(e_d{i}_d+e_q{i}_q)=\frac{3}{2}{\mathrm{Ei}}_d.$ By $\begin{array}{c}[k_p(I_d^{*}-i_d)+k_i\&Integral;(I_d^{*}-i_d)\mathrm{dt}+L\frac{{\mathrm{di}}_d}{d_t}=0\\ [k_p(I_q^{*}-i_q)+k_i\&Integral;I_q^{*}-i_q)\mathrm{dt}+L\frac{{\mathrm{di}}_q}{d_t}=0\end{array}$ Realizing the decoupling zero of electric current controls.

The present invention has following good effect: between control rectifier of the present invention and load, add DC-DC converter, applied current feedback technique, input current is followed the tracks of input voltage, thereby makes input electric current total harmonic distortion THD be less than 5%, and power factor can bring up to 0.99 or higher.This scheme becomes Active Power Factor Correction (APFC) because having applied active device.Can obtain high power factor, THD is little; Can under wider input voltage range, work; Volume, weight are little; It is constant that output voltage can keep, or be regulated to command value; The PWM rectifier of employing full-bridge and half-bridge structure can also be realized the two-way flow of electric energy.

Accompanying drawing explanation

Fig. 1 is specific embodiment of the invention single phase rectifier circuit schematic diagram;

Fig. 2 is specific embodiment of the invention rectified three-phase circuit schematic diagram;

Fig. 3 be specific embodiment of the invention system model in simulink AC the schematic diagram of DC part;

Fig. 4 is specific embodiment of the invention system model main control module schematic diagram in simulink;

Embodiment

Contrast accompanying drawing below, by the description to embodiment, the specific embodiment of the present invention is as the effect of the mutual alignment between the shape of each related member, structure, each several part and annexation, each several part and operation principle, manufacturing process and operation using method etc., be described in further detail, to help those skilled in the art to have more complete, accurate and deep understanding to inventive concept of the present invention, technical scheme.

As shown in Figure 1, work as u _sduring >0, by V ₂, VD ₄, VD ₁, L _sand V ₃, VD ₁, VD ₄, L _stwo boost choppers have been formed respectively.To comprise V ₂boost chopper be example, work as V ₂during conducting, u _spass through V ₂, VD ₄to L _senergy storage, works as V ₂during shutoff, L _sthe energy storing passes through VD ₁, VD ₄to DC bus capacitor C, charge.By V ₃the chopper circuit forming also can be analyzed by same mode, and working alone in two loops, can regard shunt circuit as.

Work as u _sduring <0, by V ₁, VD ₃, VD ₂, L _sand V ₄, VD ₂, VD ₃, L _stwo boost choppers have been formed respectively, operation principle and u _ssimilar during >0.

Circuit is pressed boost chopper work from the above analysis, and the voltage of DC side can be by IGBT Duty ratio control.

As shown in Figure 2, the operation principle of rectified three-phase circuit is similar with single-phase full bridge circuit, we if every two-phase as a loop line voltage analysis, situation is with regard to single-phase just the same like this.So the voltage of DC side also can be by the Duty ratio control of IGBT.

V at a time for example ₃conducting is (with V ₃relevant have AB phase and a BC phase), if at this moment the line voltage of AB phase is at positive half cycle, AC power is passed through V ₃, VD ₁to L _s(inductance that comprises A phase and B phase) energy storage, V ₃l during shutoff _sthe energy storing passes through VD ₁, VD ₆to DC bus capacitor C charging, if in negative half period AB phase line current, depending on V ₁and V ₆break-make situation and determining.The line current of the line voltage of BC phase BC phase when positive half cycle is looked V ₅and V ₄break-make situation and determining, if the line voltage of BC phase at negative half period; AC power is passed through V ₃, VD ₅to L _s(inductance that comprises B phase and C phase) energy storage, V ₃l during shutoff _sthe energy storing passes through VD ₅, VD ₆to DC bus capacitor C, charge.

If the three-phase mains voltage of input is

$\begin{array}{c}{e}_a=E\cos \left(\mathrm{wt}\right)\\ e_b=E\cos (\mathrm{wt}-\frac{2}{3}\mathrm{\&pi;})\\ e_c=E\cos (\mathrm{wt}+\frac{2}{3}\mathrm{\&pi;})\end{array}---\left(1\right)$

E in formula _a--reversible convertor A phase input voltage; e _b--reversible convertor B phase input voltage

E _c--reversible convertor C phase input voltage; The peak value of E-power supply phase voltage

The angular frequency of w-supply voltage;

The voltage equation of reversible three phase static coordinate system

$\begin{array}{c}{e}_a=L\frac{{\mathrm{di}}_a}{\mathrm{dt}}+v_a\\ e_b=L\frac{{\mathrm{di}}_b}{\mathrm{dt}}+v_b\\ e_c=L\frac{{\mathrm{di}}_c}{\mathrm{dt}}+v_c\end{array}---\left(2\right)$

I in formula _a---reversible convertor A phase input current; i _b---reversible convertor B phase input current

I _c---reversible convertor C phase input current; v _a---reversible convertor A phase input voltage

V _b---reversible convertor B phase input voltage; v _c---reversible convertor C phase input voltage

Three phase static voltage equation is converted through Clark

$\left[\begin{array}{c}{e}_x\\ e_y\end{array}\right]=\frac{2}{3}\left[\begin{array}{ccc}1& -\frac{1}{2}& -\frac{1}{2}\\ \frac{\sqrt{3}}{2}& \sqrt{3}& 0\end{array}\right]\left[\begin{array}{c}{e}_a\\ e_b\\ e_c\end{array}\right]---\left(3\right)$

The equation of reversible convertor in static x-y coordinate system is:

$\begin{array}{c}{e}_x=L\frac{{\mathrm{di}}_x}{\mathrm{dt}}+v_x\\ e_y=L\frac{{\mathrm{di}}_y}{\mathrm{dt}}+v_y\end{array}---\left(4\right)$

Now the voltage equation in the static coordinate system in (4) formula is transformed in the d-q two-phase synchronous coordinate system with the rotation of w angular frequency, adopts PARK transformation matrix:

$\left[\begin{array}{c}{e}_d\\ e_q\end{array}\right]=\left[\begin{array}{cc}\cos \left(\mathrm{wt}\right)& \sin \left(\mathrm{wt}\right)\\ -\sin \left(\mathrm{wt}\right)& \cos \left(\mathrm{wt}\right)\end{array}\right]\left[\begin{array}{c}{e}_x\\ e_y\end{array}\right]---\left(5\right)$

By (4) formula substitution (5) Shi Ke get

$\left[\begin{array}{c}{e}_d\\ e_q\end{array}\right]=L\frac{d}{\mathrm{dt}}\left[\begin{array}{c}{i}_d\\ i_q\end{array}\right]+\mathrm{wL}\left[\begin{array}{c}-i_q\\ i_d\end{array}\right]+\left[\begin{array}{c}{v}_d\\ v_q\end{array}\right]---\left(6\right)$

(1) formula substitution (3) formula can be obtained to the expression formula of input voltage under x-y static coordinate

$\begin{array}{c}{e}_x=E\cos \left(\mathrm{wt}\right)\\ e_y=E\sin \left(\mathrm{wt}\right)\end{array}---\left(7\right)$

Formula (7) substitution formula (5) can be obtained to the expression formula of input voltage in synchronous d-q coordinate system

$\begin{array}{c}{e}_d=E\\ e_q=0\end{array}---\left(8\right)$

Formula (8) is updated in formula (6) and can be obtained

$\begin{array}{c}E=L\frac{{\mathrm{di}}_d}{\mathrm{dt}}-w{\mathrm{Li}}_q+v_d\\ 0=L\frac{{\mathrm{di}}_q}{\mathrm{dt}}+w{\mathrm{Li}}_d+v_q\end{array}---\left(9\right)$

From (8) formula, can find out that d axle is useful work amount, q shaft type idle work amount, so will realize unity power factor transmission, wishes the reference current of q axle the active power of input is

$P=\frac{3}{2}(e_d{i}_d+e_q{i}_q)=\frac{3}{2}{\mathrm{Ei}}_d---\left(10\right)$

Visible input active power is directly proportional to d shaft current.The reference current of d axle to be obtained by the voltage regulator output of DC side.

From (9) formula, also can find out that this is a coupled system, the curent change of q axle has impact to the electric current of d axle, and the variation of the electric current of same d axle also has impact to q axle, so want reality need to realize decoupling zero to the control of electric current, controls.

In order to realize the decoupling zero of electric current, control, adopt control program below, voltage given instruction is

$\begin{array}{c}{V}_d^{*}=E_d+\mathrm{wL}{I}_q-[k_p(I_d^{*}-i_d)+k_i\&Integral;(I_d^{*}-i_d)\mathrm{dt}\\ V_q^{*}=E_q-\mathrm{wL}{I}_d-[k_p(I_q^{*}-i_q)+k_i\&Integral;I_q^{*}-i_q)\mathrm{dt}\end{array}---\left(11\right)$

To in (11) formula substitution (6) formula, can obtain

$\begin{array}{c}[k_p(I_d^{*}-i_d)+k_i\&Integral;(I_d^{*}-i_d)\mathrm{dt}+L\frac{{\mathrm{di}}_d}{d_t}=0\\ [k_p(I_q^{*}-i_q)+k_i\&Integral;I_q^{*}-i_q)\mathrm{dt}+L\frac{{\mathrm{di}}_q}{d_t}=0\end{array}---\left(12\right)$

Above formula has been realized the decoupling zero of electric current as seen.

Fig. 3 middle controller DC voltage of having sampled, the electric current and voltage of three-phase alternating current side.

The given voltage U dc of direct current ^*=650V, the supply voltage of DC side is zero, by net side ABC phase voltage current simulations waveform, can find out that voltage is finally stabilized in given 650V.The given voltage U dc of DC side ^*=650V, the supply voltage of DC side is 800V, and by net side A phase voltage current simulations waveform, circuit working is in inverter mode, and DC voltage still maintains 650V.

PWM rectifier net side presents the characteristic of current source, thereby this characteristic makes PWM rectifier and control technology acquisition thereof further develop and widen, and obtained application more widely, as static reactive (SVG), active power filtering (APF), unified trend are controlled generating electricity by way of merging two or more grid systems of the regenerative resources such as (UPFC), superconducting energy storage (SMES), high voltage direct current transmission (HVDC), electrical equipment transmission (ED), novel UPS and solar energy, wind energy.

By reference to the accompanying drawings the present invention is exemplarily described above; obviously specific implementation of the present invention is not subject to the restrictions described above; as long as adopted the improvement of the various unsubstantialities that method of the present invention design and technical scheme carry out; or without improving, design of the present invention and technical scheme are directly applied to other occasion, all within protection scope of the present invention.

Claims (5)

1. a storage battery charge-discharge control system, it is characterized in that: this comprises rectifier and load, load two ends are parallel with capacitor C, rectifier series inductance L and resistance R s, between described rectifier and load, add AC-DC converter, AC-DC converter is the full-bridge circuit that half-bridge is composed in parallel by insulated gate bipolar transistor V and diode VD, and the every quarter-phase circuit of full-bridge circuit comprises by insulated gate bipolar transistor V, diode VD, diode VD and inductance L _stwo boost choppers that form.

2. storage battery charge-discharge control system according to claim 1, is characterized in that: the DC voltage of this system is by insulated gate bipolar transistor V Duty ratio control.

3. according to the accumulator charging and discharging control method described in claim 1 or 2 any one, it is characterized in that: in every quarter-phase circuit, work as u _sduring >0, by insulated gate bipolar transistor V ₂, diode VD ₄, diode VD ₁, inductance L _swith insulated gate bipolar transistor V ₃, diode VD ₁, diode VD ₄, inductance L _sform two boost choppers; Work as u _sduring <0, by insulated gate bipolar transistor V ₁, diode VD ₃, diode VD ₂, inductance L _swith insulated gate bipolar transistor V ₄, diode VD ₂, diode VD ₃, inductance L _sform two boost choppers, as insulated gate bipolar transistor V ₂during conducting, u _spass through V ₂, VD ₄to L _senergy storage, works as V ₂during shutoff, L _sthe energy storing passes through VD ₁, VD ₄to DC bus capacitor C charging, separate by two loops of chopper circuit.

4. according to accumulator charging and discharging control method described in claims 1 to 3 any one, it is characterized in that, the method comprises the following steps: step 1, the voltage equation to reversible three phase static coordinate system $\begin{array}{c}{e}_a=L\frac{{\mathrm{di}}_a}{\mathrm{dt}}+v_a\\ e_b=L\frac{{\mathrm{di}}_b}{\mathrm{dt}}+v_b\\ e_c=L\frac{{\mathrm{di}}_c}{\mathrm{dt}}+v_c\end{array}$ Carrying out Clark conversion obtains $\left[\begin{array}{c}{e}_x\\ e_y\end{array}\right]=\frac{2}{3}\left[\begin{array}{ccc}1& -\frac{1}{2}& -\frac{1}{2}\\ \frac{\sqrt{3}}{2}& \sqrt{3}& 0\end{array}\right]\left[\begin{array}{c}{e}_a\\ e_b\\ e_c\end{array}\right],$ Wherein, i _afor reversible convertor A phase input current, i _bfor reversible convertor B phase input current, i _cfor reversible convertor C phase input current, v _afor reversible convertor A phase input voltage, v _bfor reversible convertor B phase input voltage, it is reversible convertor C phase input voltage;

Step 2, three-phase mains voltage $\begin{array}{c}{e}_a=E\cos \left(\mathrm{wt}\right)\\ e_b=E\cos (\mathrm{wt}-\frac{2}{3}\mathrm{\&pi;})\\ e_c=E\cos (\mathrm{wt}+\frac{2}{3}\mathrm{\&pi;})\end{array}$ Substitution Clark conversion obtains the expression formula of input voltage under x-y static coordinate $\begin{array}{c}{e}_x=E\cos \left(\mathrm{wt}\right)\\ e_y=E\sin \left(\mathrm{wt}\right)\end{array},$ Wherein, e _afor reversible convertor A phase input voltage, e _bfor reversible convertor B phase input voltage, e _cfor reversible convertor C phase input voltage, E is the peak value of power supply phase voltage, the angular frequency that w is supply voltage;

Step 3, the equation by reversible convertor in static x-y coordinate system $\begin{array}{c}{e}_x=L\frac{{\mathrm{di}}_x}{\mathrm{dt}}+v_x\\ e_y=L\frac{{\mathrm{di}}_y}{\mathrm{dt}}+v_y\end{array}$ Static coordinate system in voltage equation be transformed in the d-q two-phase synchronous coordinate system with the rotation of w angular frequency, adopt PARK transformation matrix $\left[\begin{array}{c}{e}_d\\ e_q\end{array}\right]=\left[\begin{array}{cc}\cos \left(\mathrm{wt}\right)& \sin \left(\mathrm{wt}\right)\\ -\sin \left(\mathrm{wt}\right)& \cos \left(\mathrm{wt}\right)\end{array}\right]\left[\begin{array}{c}{e}_x\\ e_y\end{array}\right]$ Obtain $\left[\begin{array}{c}{e}_d\\ e_q\end{array}\right]=L\frac{d}{\mathrm{dt}}\left[\begin{array}{c}{i}_d\\ i_q\end{array}\right]+\mathrm{wL}\left[\begin{array}{c}-i_q\\ i_d\end{array}\right]+\left[\begin{array}{c}{v}_d\\ v_q\end{array}\right];$

Step 4, the expression formula by input voltage under x-y static coordinate $\begin{array}{c}{e}_x=E\cos \left(\mathrm{wt}\right)\\ e_y=E\sin \left(\mathrm{wt}\right)\end{array}$ Substitution PARK transformation matrix obtains the expression formula of input voltage in synchronous d-q coordinate system $\begin{array}{c}{e}_d=E\\ e_q=0\end{array};$

Step 5, from $\begin{array}{c}{e}_d=E\\ e_q=0\end{array}$ Can find out that d axle is useful work amount, q shaft type idle work amount, if realize unity power factor transmission, the reference current of q axle the active power of input is $P=\frac{3}{2}(e_d{i}_d+e_q{i}_q)=\frac{3}{2}{\mathrm{Ei}}_d.$

5. accumulator charging and discharging control method according to claim 4, is characterized in that: by $\begin{array}{c}[k_p(I_d^{*}-i_d)+k_i\&Integral;(I_d^{*}-i_d)\mathrm{dt}+L\frac{{\mathrm{di}}_d}{d_t}=0\\ [k_p(I_q^{*}-i_q)+k_i\&Integral;I_q^{*}-i_q)\mathrm{dt}+L\frac{{\mathrm{di}}_q}{d_t}=0\end{array}$ Realizing the decoupling zero of electric current controls.