WO2022229457A1 - Accord de résonance parasite pour une oscillation de nœud de commutation réduite dans des convertisseurs de puissance - Google Patents

Accord de résonance parasite pour une oscillation de nœud de commutation réduite dans des convertisseurs de puissance Download PDF

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Publication number
WO2022229457A1
WO2022229457A1 PCT/EP2022/061625 EP2022061625W WO2022229457A1 WO 2022229457 A1 WO2022229457 A1 WO 2022229457A1 EP 2022061625 W EP2022061625 W EP 2022061625W WO 2022229457 A1 WO2022229457 A1 WO 2022229457A1
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WO
WIPO (PCT)
Prior art keywords
state
switch
controller
controlling
current
Prior art date
Application number
PCT/EP2022/061625
Other languages
English (en)
Inventor
Elmar Peters
Original Assignee
Elmar Solar
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Publication date
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Publication of WO2022229457A1 publication Critical patent/WO2022229457A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/125—Avoiding or suppressing excessive transient voltages or currents
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present disclosure is directed to power converters and, more specifically, to a commutation cell for connecting a first power element to a second power element wherein said commutation cell is arranged for reducing oscillations occurring in a current caused by switching of a switch in said commutation cell.
  • Zero voltage switching, ZVS, operation schemes are used to eliminates turn on losses associated with the capacitive discharge of the parasitic capacitance’s of the switches at turn-on. ZVS operation allows for a further increase in switching frequency while maintaining high efficiency.
  • parasitic power loop inductance introduced by, for example, the output capacitor, semiconductor switches, interconnections and packaging can lead to undesired large voltage spikes during turn-off transients of active switches.
  • the undesired voltage spikes can potentially exceed the device’s voltage ratings and have significant impact on the safe operation of fast switching devices.
  • the parasitic power loop inductance becomes critical to high efficiency. It has been identified that the power loop inductance may be of importance. Conventionally, people have tried to reduce the loop inductance as much as possible, making all kinds of compromises. When the loop inductance can’t be reduced enough, switch turn-off and turn-on speed are typically limited to reduce ringing, i.e. oscillation, but this increases losses.
  • One of the drawbacks of the power converters in the prior art is related to oscillation that occurs when switching from the ON-state of the switch to the OFF- state of the switch.
  • a commutation cell for connecting a first power element to a second power element comprising:
  • a switch arranged for, in an ON-state, enabling a first current path in said commutation cell, and, in an OFF-state, enabling a second current path in said commutation cell, wherein said first current path is different to said second current path;
  • a controller for controlling said switch between said ON-state and said OFF- state; wherein a resonance circuit is provided in said commutation cell, said resonance circuit being formed by at least any of: o parasitic capacitance in any of said switch and said rectifier element; o parasitic inductance of any of said second power element, said switch, said rectifier element and interconnections provided in said commutation cell; such that, when said controller controls said switch from said ON-state to said OFF-state, said resonance circuit causes a current in said resonance circuit to oscillate; characterized in that a relationship exists between o an amplitude of said oscillation of said current in said resonance circuit, and o an amount of current in said first current path when said controller controls said switch from said ON-state to said OFF-state, said relationship having a plurality of local maxima in said amplitude for given amount of current, said controller is arranged for controlling said switch from said ON-state to said OFF-state based on said local maxima in said relationship.
  • the amount of current flowing through the switch at the moment that the controller controls the switch from the ON-state to the OFF-state is an aspect that determines the amplitude of the oscillation that will occur in the current in resonance circuit. It is noted that the oscillation above is provided with respect to the oscillation occurring in the current. The oscillation may also be provided with respect to the voltage, for example the voltage over the switch.
  • the inventor has found that the relationship between these two is not random.
  • the relationship has a plurality of local maxima in the amplitude for given amount of current. That is, the relationship may not be strictly monotone increasing, i.e. the amplitude of the oscillation may not strictly increase by increasing amount of current in the first current path, when switching from ON-state to OFF-state of the switch.
  • the amplitude of the oscillation is thus a function of the amount of current when switching from the ON-state to the OFF-state of the switch, and the function has multiple local maxima.
  • the moving average of the function may be strictly monotone increasing, but the function itself is not.
  • the function itself itself has multiple local maxima.
  • the inventor has found that it may be undesirable to set the controller in such a way that the switch is switched OFF when the current trough the switch is such that the amplitude would be in a local maximum. This would lead to an undesired oscillating effect.
  • the controller may therefore be wise to set the controller based on the local maxima in the relationship. That is, the controller may be tuned to a particular set point based on the location of the local maxima in the relationship.
  • the switch is arranged to be in an ON-state or in an OFF-state.
  • the switch is, for example, a Field Effect Transistor, FET, like a N-Metal Oxide Semiconductor, NMOS, a PMOS FET, GaN FETs, SiC MOSFETs, HEMTs or anything alike.
  • the switch is a GaN transistor which is very suitable for high frequency switching.
  • the rectifier element may, for example, be a diode or anything alike.
  • the rectifier may also be encompassed by a further switch or a further switch may be placed in parallel over the rectifier element.
  • the further switch may be turned on once the current crosses zero amperes, or anything close to that.
  • the controller may, for example, be an integrated circuit, IC, a Field Programmable Gate Array, FPGA, an Application Specific IC, ASIC, micro controller, or anything alike.
  • the controller may thus control the switch with a control signal having a particular frequency and a particular duty cycle.
  • the control signal determines when the switch is turned ON, i.e. conducting, and when the switch is turned OFF, i.e. non conducting.
  • the switch may not behave perfectly ideal in the sense that the transition between the ON state and the OFF state is infinitely small.
  • the switch may be a semiconductor device, the transition between the states may take sever nano-seconds, but is at least much smaller compared to the time period of the oscillation signal.
  • the resonance circuit may be identified by a plurality of parasitic capacitances and parasitic inductances of the different elements. In addition to the parasitic capacitances and parasitic inductances, additional capacitance and/or inductance may be incorporated. In any case, the presence of the resonance circuit causes the current the current in the resonance circuit to oscillate, and thus also a output voltage to oscillate, for example the voltage over the switch.
  • the parasitic inductance as referenced to in this particular disclosure may be considered as the inductance formed by the magnetic flux that flows through the corresponding element.
  • the inventor has found that there is a relationship between the amplitude of the oscillation of the current in the resonance circuit and the amount of current in the first current path at the moment when the controller controls the switch from the ON-state to the OFF-state, and that the relationship has a plurality of local maxima in the amplitude for given amount of current.
  • SMPS Switched Mode Power Supply
  • an electrical engineer may use the knowledge of the relationship for determining one, or more, points in the relationship at which the controller is to be operated.
  • Another option is that there is provided a feedback loop to the controller for feeding back information with respect to the amplitude of the oscillation, for example a voltage or anything alike, and that this information is used for adjusting the setpoint of the controller.
  • the controller may adjust the setpoint in such a way that it is searching for the most promising minima.
  • the controller may thus know that, for example, even though the set point is currently in a local minimum, another local minimum exists which may be suitable as well.
  • the average current is measured and fed back to the controller. Using the average current, it is possible to calculate the actual current through the switch.
  • the controller is arranged for controlling said switch from said ON-state to said OFF-state such that said plurality of local maxima are substantially avoided.
  • the advantage hereof is that the controller is set such that oscillations having a maximum amplitude are avoided as much as possible. This, thus, does not necessarily mean that the controller is set such that no oscillations in the output current occur, but that at least the controller is set such that oscillations witch a maximum amplitude are avoided as much as possible.
  • the controller may be set to fully avoid the local maxima. This could mean that although it is preferred to set the controller such that the switch turns OFF at a particular set point, which setpoint is actually located in a local maxima, the controller is set to a different set point to avoid the local maxima.
  • the controller may, for example, interpolate between two local minima, surround the local maxima, in such a way that the average current at which the switch is turned OFF is actually substantially equal to the average current at the local maxima, but due to the fact that the switch is controller in two local minima the oscillations at the output current, and the output voltage, are maintained to a minimum.
  • the controller is arranged for controlling said switch from said ON-state to said OFF-state such that said amplitude of said oscillation is below a predefined threshold.
  • the advantage hereof is that it may occur that certain components used for building a Switch Mode Power Supply, SMPS, may have a voltage or current rating.
  • the predefined threshold may be used during the development phase for assuring that the components are not substantially used outside their voltage or current rating.
  • the relationship has a plurality of local minima, and wherein said controller is arranged for controlling said switch from said ON-state to said OFF-state in any of said local minima.
  • the above described example may be considered a preferred example as, in this case, the amplitude of the oscillation signal at the output is contained to a minimum.
  • the controller is arranged for controlling said switch from ON-states to OFF-states at different amount of currents.
  • the controller may switch the switch to the OFF-state at different amounts of currents, i.e. using interpolation, for obtaining a desired or minimum oscillation signal.
  • a method for operating a commutation cell in accordance with any of the previous examples, wherein said method comprises the steps of: controlling, by said controller, said switch from said ON-state to said OFF-state based on said local maxima in said relationship.
  • the step of controlling further comprises: controlling, by said controller, said switch from said ON-state to said OFF-state such that said plurality of local maxima are substantially avoided.
  • the step of controlling further comprises: avoiding, by said controller, said local maxima.
  • the step of controlling further comprises: controlling, by said controller, said switch from said ON-state to said OFF-state such that said amplitude of said oscillation is below a predefined threshold.
  • the relationship has a plurality of local minima
  • said step of controlling further comprises: controlling, by said controller, said switch from said ON-state to said OFF-state in any of said local minima.
  • the step of controlling further comprises: controlling, by said controller, said switch from ON-states to OFF- states at different amount of currents.
  • a Switched Mode Power Supply comprises a commutation cell in accordance with any of the previous examples. It is noted that the advantages as explained with respect to the first aspect, being the commutation cell, correspond to the advantages as explained with respect to the third aspect, being the SMPS.
  • a controller arranged for operating in a commutation cell in accordance with any of the examples as provided above.
  • a computer program product comprising a computer readable medium having instructions stored thereon which, when executed by a controller, cause said controller to implement a method in accordance with any of the method examples as provided above.
  • Figure 1 discloses an example of a commutation cell in accordance with the present disclosure
  • Figures 2a-2d disclose examples of current paths in the commutation cell in accordance with figure 1 ;
  • Figure 3a discloses an example of a timing diagram of the voltage over the switch as well as the voltage over the rectifier element
  • Figure 3b discloses an example of a timing diagram of the voltage over the switch over time when the switch is turned from the ON-state to the OFF-state;
  • Figure 4 discloses the voltage over the switch over time for different amounts of current through the switch when the switch is being switched to the OFF- state
  • Figure 5 discloses the overshoot voltage as function of input current
  • FIG. 6 discloses an example of a Switched Mode Power Supply, SMPS, in accordance with the present disclosure
  • Figure 7a - 7c disclose another examples of current paths in a commutation cell in accordance with the present disclosure. Detailed description
  • Figure 1 discloses an example of a commutation cell 1 in accordance with the present disclosure.
  • the commutation cell 1 is arranged for connecting a first power element
  • the first power element 3 may be any of a voltage source, a current source, an inductor, a capacitor, a load or anything alike.
  • the second power element 2 may be any of a voltage source, a current source, a capacitor, a load or anything alike.
  • Ground is indicated with reference numeral 4.
  • a switch 8 is provided in the commutation cell 1 that is controlled by the controller 9.
  • the switch 8 may be switched ON in which the switch provides for a conducting path and may be switched OFF in which the switch does not provide for a conducting path. Of course, some sort of transition time may exist when turning the switch ON and OFF.
  • the switch 8 may, for example, be a Metal Oxide Semiconductor, MOS,
  • FET Field Effect Transistor
  • GaN transistor GaN transistor
  • the switch 8 may have a parasitic capacitance as indicated with reference numeral 5. Such a parasitic capacitance is typically an undesired capacitance as it may put upper limits to the speed of the switch 8.
  • the switch 8 is arranged for, in an ON-state, enable a first current path in the commutation cell, and, in an OFF-state, enable a second current path in the commutation cell, wherein the first current path is different to the second current path. This is explained in more detail with respect to figures 2a - 2d.
  • a rectifier element 7 is provided in the second current path.
  • the rectifier element may comprise a PN-junction, for example a diode.
  • the rectifier element 7 may also be encompassed by a switch, or a switch may be placed in parallel over said rectifier element 7.
  • the rectifier element 7 allows the current to flow in one direction, i.e. from the anode to the cathode.
  • the rectifier element 7 may also comprise a parasitic capacitance as indicated with reference numeral 6.
  • a resonance circuit may be provided in the mutation cell 1 , wherein the resonance circuit may be formed by at least any of the parasitic capacitance 5 in any of the switch 8 and the parasitic capacitance 6 in the rectifier element 7 as well as the parasitic inductance in any of the second power element 2, the switch 8, the rectifier element 7 and interconnections provided in the commutation cell 1.
  • the interconnections may be modelled by an inductance as indicated with reference numeral 10.
  • the resonance circuit may not necessarily equal any of the first current path and the second current path as the parasitic capacitances and the parasitic inductances play a role as well. This is explained in more detail when referring to figures 2a - 2d.
  • the present disclosure describes the relationship between the amplitude of the oscillation of the current in the resonance circuit and the amount of current in the first current path when the controller controls the switch from the ON-state to the OFF-state.
  • the inventor has noted that the relationship has a plurality of local maxima in the amplitude for given amount of current, and has found that this knowledge may be used by the controller 9 in controlling the switch 8.
  • the controller 9 is arranged for controlling the switch 8 from the ON-state to the OFF-state based on the local maxima in the relationship.
  • the parasitic capacitance of the switch 8 equals the parasitic capacitance of the rectifier element 7.
  • the rectifier element 7 is provided in a further switch, for example the body diode of the further switch. In that case, it would be beneficial if the two switches are of the same type.
  • Figures 2a-2d disclose examples of current paths in the commutation cell in accordance with figure 1.
  • Figure 2a discloses an example of the commutation cell 1 of figure 1 wherein the first current path in the commutation cell 1 is highlighted.
  • the first current path is indicated with reference numeral 11.
  • Figure 2b discloses an example of the commutation cell 1 of figure 1 , wherein the second current path in the commutation cell 1 is highlighted.
  • the second current path is indicated with reference numeral 12.
  • Figure 2c discloses an example of a third current path in the commutation cell 1 of figure 1 , wherein the third current path in the commutation cell 1 is highlighted.
  • the third current path is indicated with reference numeral 13.
  • Figure 2d discloses an example of the first and second current path in the commutation cell 1 of figure 1 , wherein the first and second current path in the commutation cell 1 are highlighted.
  • the first and second current path are indicated with reference numerals 15 and 14, respectively.
  • Figure 2d may be considered the power loop that oscillates in section B as well as section C of figure 3.
  • oscillation may occur in the third current path as indicated with reference numeral 13.
  • Reference numeral 13 may also be used for indicating the resonance circuit in the commutation cell 1.
  • Figure 3a discloses an example of a timing diagram of the voltage over the switch as well as the voltage over the rectifier element.
  • the X-axis indicates the time, for example in nanoseconds or milliseconds or anything alike and the Y-axis resembled to voltage.
  • the switch 8 is controlled such that it switches from the ON- state to the OFF-state.
  • a switch placed in parallel over the rectifier element 7 may be switched from the OFF-state to the ON-state.
  • the line having reference numeral 26 indicates the voltage over the switch 8 and the line having reference numeral 28 indicates the voltage over the rectifier element 7.
  • the amplitude of the current of the oscillation relates to the amplitude of the voltage of the oscillation and is indicated with reference numeral 27.
  • the switch 8 is closed. This is indicated with the reference numeral “A”. Then, the switch 8 opens, i.e. switches to the OFF-state, and the switch node voltage, i.e. the voltage over the switch 8, begins to rise as the parasitic capacitance 5 begins to charge. The parasitic capacitance 6 of the rectifier element shifts the voltage on the cathode of the rectifier element above the output voltage, the current through the inductance 10 rises and the oscillation is initiated. The above is indicated with reference numeral “B”.
  • Figure 3b discloses an example of a timing diagram of the voltage over the switch over time when the switch is turned from the ON-state to the OFF-state.
  • Figure 4 discloses the voltages 31 over the switch over time for different amounts of current through the switch when the switch is being switched to the OFF- state.
  • the line having reference numeral 34 shows the oscillation behaviour of the voltage over the switch 8 for a first current.
  • the line having reference numeral 35 shows the oscillation behaviour of the voltage over the switch 8 for a second current.
  • the line having reference numeral 36 shows the oscillation behaviour of the voltage over the switch 8 for a third current.
  • the line having reference numeral 37 shows the oscillation behaviour of the voltage over the switch 8 for a fourth current. In this particular case the first current > the second current > the third current > the fourth current.
  • Figure 5 is an example of the relationship 41 between the amplitude of said oscillation of said current in said resonance circuit, and an amount of current in said first current path when said controller controls said switch from said ON-state to said OFF-state.
  • the above identified amount of current is provided on the horizontal axis 43, the above identified amplitude of the oscillation is provided on the vertical axis 42.
  • sweet spots i.e. local minima, in which the amplitude is relatively low.
  • sweet spots are, amongst other, indicated with reference numerals 44, 46 and 48. IN these sweet sports the oscillation reaches a local minimum.
  • worst-case spots i.e. local maxima, in which the amplitude is relatively high.
  • worst-case sports are, amongst other, indicated with reference numerals 45, 47 and 49.
  • FIG. 6 discloses a Switched Mode Power Supply, SMPS, 51 in accordance with the present disclosure.
  • the method as described in the appended claims may be provided in the controller 52.
  • Figure 6 is just an example of many possible topologies, i.e. many possible SMPSs.
  • the inductor without the core is the power loop induction.
  • the inductor with the core may be considered the first power element.
  • the voltage sources combined may be considered the second power element.
  • boost converter being the commutation cell. It is however noted that the advantages of the present disclosure are applicable for all kinds of converters, for example buck converters as well as isolated converters like a flyback converter, and may be applicable for an N-phase inverter.
  • Figure 7a - 7c disclose another examples of current paths in a commutation cell in accordance with the present disclosure.
  • the switch and the rectifier element are switched from position to clarify that the commutation cell may also operate in a different manner.
  • the present disclosure is directed to both options, such that both options are covered by the commutation cell in accordance with the claims of the present disclosure.
  • Figure 7 and figure 2 are commutations that an both be implemented on the invertor, depending on the directions of the current through the inductor and, to chose one of the switches as active rectification, or synchronous rectification.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Dc-Dc Converters (AREA)

Abstract

La présente divulgation concerne une cellule de commutation pour connecter un premier élément de puissance à un deuxième élément de puissance, ladite cellule de commutation comprenant un commutateur agencé pour, dans un état MARCHE, permettre un premier trajet de courant dans ladite cellule de commutation, et, dans un état ARRÊT, permettre un deuxième trajet de courant dans ladite cellule de commutation, ledit premier trajet de courant étant différent dudit deuxième trajet de courant, un élément redresseur disposé dans ledit deuxième trajet de courant, un dispositif de commande pour commander ledit commutateur entre ledit état MARCHE et ledit état ARRÊT, un circuit de résonance étant disposé dans ledit deuxième trajet de courant, ledit circuit de résonance étant formé par au moins une capacité parasite quelconque parmi l'un quelconque dudit commutateur et dudit élément redresseur, et une inductance parasite de l'un quelconque dudit deuxième élément de puissance, ledit commutateur, ledit élément redresseur et les interconnexions étant disposés dans ladite cellule de commutation, de telle sorte que, lorsque ledit dispositif de commande commande ledit commutateur dudit état MARCHE vers l'état ARRÊT, ledit circuit de résonance provoque l'oscillation d'un courant dans ledit deuxième trajet de courant, une relation existant entre une amplitude de ladite oscillation dudit courant dans ledit deuxième trajet de courant, et une quantité de courant dans ledit premier trajet de courant lorsque ledit dispositif de commande commande ledit commutateur dudit état MARCHE vers l'état ARRÊT, ladite relation ayant une pluralité de maxima locaux dans ladite amplitude pour une quantité de courant donnée, ledit dispositif de commande étant conçu pour commander ledit commutateur de l'état MARCHE vers l'état ARRÊT sur la base desdits maxima locaux dans ladite relation.
PCT/EP2022/061625 2021-04-29 2022-04-29 Accord de résonance parasite pour une oscillation de nœud de commutation réduite dans des convertisseurs de puissance WO2022229457A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
NLNL2028098 2021-04-29
NL2028098A NL2028098B1 (en) 2021-04-29 2021-04-29 Parasitic resonant tuning for reduced switching node ringing in power converters.

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EP3512085A1 (fr) * 2018-01-12 2019-07-17 Fraunhofer-Gesellschaft zur Förderung der angewandten Forschung e.V. Convertisseur cc/cc avec circuits résonnants et pentes commutations ultra-abrupts

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EP3512085A1 (fr) * 2018-01-12 2019-07-17 Fraunhofer-Gesellschaft zur Förderung der angewandten Forschung e.V. Convertisseur cc/cc avec circuits résonnants et pentes commutations ultra-abrupts

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