WO2022110274A1 - Procédé de suppression et d'analyse de perte pour moteur électrique à aimant permanent modulé par champ magnétique - Google Patents

Procédé de suppression et d'analyse de perte pour moteur électrique à aimant permanent modulé par champ magnétique Download PDF

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Publication number
WO2022110274A1
WO2022110274A1 PCT/CN2020/133832 CN2020133832W WO2022110274A1 WO 2022110274 A1 WO2022110274 A1 WO 2022110274A1 CN 2020133832 W CN2020133832 W CN 2020133832W WO 2022110274 A1 WO2022110274 A1 WO 2022110274A1
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permanent magnet
rotor
magnetic
harmonics
magnetic field
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PCT/CN2020/133832
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English (en)
Chinese (zh)
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徐亮
赵文祥
蒋婷婷
刘国海
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江苏大学
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Priority to GB2200824.7A priority Critical patent/GB2599611B/en
Publication of WO2022110274A1 publication Critical patent/WO2022110274A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K21/00—Synchronous motors having permanent magnets; Synchronous generators having permanent magnets
    • H02K21/02—Details
    • H02K21/021—Means for mechanical adjustment of the excitation flux
    • H02K21/028—Means for mechanical adjustment of the excitation flux by modifying the magnetic circuit within the field or the armature, e.g. by using shunts, by adjusting the magnets position, by vectorial combination of field or armature sections
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/64—Electric machine technologies in electromobility

Definitions

  • the invention relates to a loss analysis and suppression method of a magnetic field modulation permanent magnet motor, belongs to the field of motors, and is particularly suitable for motor systems requiring high torque and high efficiency, such as electric vehicles, ship propulsion and wind power generation.
  • the direct-drive permanent magnet motor can save the intermediate transmission mechanism such as gearbox and has the advantages of high reliability, high efficiency and low vibration and noise.
  • direct-drive permanent magnet motors have been used in various industries including electric vehicle in-wheel motors, large wind turbines and ship propulsion systems.
  • the rapid development of electric vehicles, ship propulsion and wind power generation also requires higher and higher performance of motor systems.
  • miniaturization and light weight are the development trends of electric vehicle drive motors.
  • the torque density of the drive motor is the key.
  • the in-wheel motor drive method installs the drive motor in the wheel, which can omit a large number of transmission components, make the vehicle structure simpler, and realize the advantages of a complex electric vehicle drive method.
  • the narrow space in the wheel requires the motor to have a high torque density.
  • various new permanent magnet motor structures such as double stator permanent magnet motors, double rotor permanent magnet motors, axial flux permanent magnet motors, and transverse flux permanent magnet motors.
  • the magnetic field modulation permanent magnet motor is a new type of permanent magnet motor, and its working principle is different from that of the conventional permanent magnet motor.
  • Traditional permanent magnet motors only use a single magnetic field harmonic to generate torque, and there are a large number of useless magnetic field harmonics in the air gap that cannot be used to generate torque.
  • the magnetic field modulated permanent magnet motor operates on the basis of the magnetic gear effect and can take advantage of various magnetic field harmonic components in the air gap, thus having the advantage of high torque density.
  • the research results show that the torque density of the magnetic field modulated permanent magnet motor has obvious advantages compared with the conventional permanent magnet motor under the same conditions, and the structure of the magnetic field modulated permanent magnet motor adopts the torque boosting technology such as double rotor, double stator and axial magnetic flux.
  • the structure of the permanent magnet motor is relatively simple, so it has received extensive attention in the direct drive permanent magnet motor system.
  • the magnetic field harmonic content of the magnetic field modulation permanent magnet motor is rich, among which various magnetic field harmonics can generate torque. Under the cooperative work of various magnetic field harmonic magnetic fields, the average torque of the motor can be greatly improved. But it is worth noting that the harmonic magnetic field of the magnetic field modulation permanent magnet motor is rich, which will lead to the increase of the electromagnetic loss of the motor. The high loss of the motor will cause the temperature of the motor to rise, which will reduce the performance of the motor and shorten the service life of the motor. The rich magnetic field harmonics and the magnetic gear effect of the magnetic field modulated permanent magnet motor make it very difficult to carry out accurate loss analysis. On the other hand, simply suppressing the magnetic field harmonic content will result in a reduction in motor torque, losing the advantages of field-modulated permanent magnet motors.
  • the rich magnetic field harmonics improve its torque density, but at the same time it will cause high losses to affect the performance and operation of the motor. Therefore, in addition to considering the torque density when designing a magnetic field modulated permanent magnet motor, its loss also needs to be studied.
  • the purpose of the present invention is to propose a loss analysis and suppression method of the magnetic field modulation permanent magnet motor in view of the deficiencies in the loss analysis and suppression of the existing magnetic field modulation permanent magnet motor.
  • the stator, rotor, permanent magnet and winding structure of the magnetic field modulated permanent magnet motor the magnetomotive force and permeance model are established, and the magnetic field harmonic distribution of the armature winding and the permanent magnet air gap is deduced; the order, frequency and magnetic field harmonics are analyzed.
  • Rotation characteristics determine whether each magnetic field harmonics can contribute to torque and loss; calculate the contribution of each magnetic field harmonics to torque and loss, and find out the high-hazard magnetic field harmonics that generate loss but not torque .
  • the invention analyzes the action mechanism of the magnetic field harmonics of the magnetic field modulation permanent magnet motor on the loss, can quantitatively calculate the contribution value of the magnetic field harmonics to the loss and torque, and at the same time can directionally suppress the high-harm magnetic field harmonics, so as to ensure the high torque of the motor Loss suppression effect under the premise of density.
  • the motor of the present invention is realized by adopting the following technical solutions: a loss analysis and suppression method of a magnetic field modulation permanent magnet motor, comprising the following steps:
  • Step 1 Ignore the magnetic field generated by the armature winding on the stator and the cogging structure on the stator, and only consider the magnetic flux path formed by the permanent magnetic field generated by the permanent magnet on the rotor; according to the symmetry and periodicity of the rotor magnetic circuit, select the rotor structure
  • the basic unit establishes the permanent magnet magnetomotive force expression
  • Step 2 Ignore the permanent magnet magnetic field on the rotor, only consider the cogging structure on the stator and the connection and energization mode of the armature windings, establish the magnetomotive force expression of the armature windings of each phase in turn, and calculate the magnetomotive force of the armature windings of each phase.
  • the mathematical expressions are added together to obtain the synthetic armature winding magnetomotive force expression considering the stator cogging effect;
  • Step 3 Considering the unequal magnetic permeability of the teeth and slots on the stator on the circumference of the motor air gap, select the basic unit of the tooth and slot structure on the stator, and establish the stator permeability expression;
  • Step 4 The permanent magnets on the rotor are attached to the rotor core, and the permeance of the rotor core does not change with time and space as a constant, and the stator and rotor permeance expressions can be obtained by multiplying the stator permeance and the rotor permeance;
  • Step 5 Multiply the permanent magnet magnetomotive force, the stator and rotor permeability and the permeability coefficient to obtain the permanent magnet air gap flux density expression
  • Step 6 Multiply the magnetomotive force of the synthetic armature winding considering the stator cogging effect and the permeance of the rotor to obtain the expression of the air-gap flux density of the armature winding;
  • Step 7 Identify the harmonics of the air gap flux density that can contribute to the average torque and those that cannot contribute to the average torque; analyze and compare the order and rotational speed of the harmonic components of the permanent magnet air gap flux density and the armature winding air gap flux density, When the speed and order of the two magnetic density harmonics are equal, the magnetic density harmonic can contribute to the average torque for the working wave, otherwise it cannot contribute to the average torque for the non-working wave;
  • Step 8 Identify the air-gap flux density harmonics that contribute to the average torque and those that cannot contribute to the average torque; analyze the permanent magnet air-gap flux density and the armature winding air-gap flux density harmonics relative to the rotor rotational speed, which is equal to the rotor rotational speed The magnetic density harmonics do not generate rotor loss, and the magnetic density harmonics that are not equal to the rotation speed of the rotor generate rotor loss; the rotor loss is calculated by the calculation formula of rotor core loss and permanent magnet eddy current loss;
  • Step 9 For the air-gap flux density harmonics that generate losses but do not contribute to the average torque, design several magnetic flux barriers on the motor rotor to increase the reluctance on the magnetic flux path of the armature windings that generate high-hazard magnetic field harmonics, so that Reduce the content of high-hazard harmonics to ensure that the air-gap flux density harmonics contributing to the average torque are not affected.
  • F PMn is the Fourier coefficient
  • ⁇ is the circumferential position of the motor air gap
  • P r is the number of pole pairs of the rotor permanent magnet
  • n is a positive odd number.
  • step 2 if it is a five-phase centralized winding, the five-phase windings are successively passed into sinusoidal currents with a mutual difference of ⁇ /5 electrical angle, and the synthetic armature winding magnetomotive force F aq ( ⁇ , t considering the stator cogging effect) ) expression is:
  • F aq is the magnitude of the magnetomotive force of the armature winding
  • N is the number of turns of each set of windings
  • I max is the amplitude of the alternating current
  • ⁇ PM is the rotational speed of the stator relative to the rotor and the permanent magnet
  • q is the magnetic force of the armature winding.
  • Potential harmonic order P r is the number of pole pairs of the rotor permanent magnet
  • r is a positive integer
  • ⁇ 1 and ⁇ 2 are the coordinate positions 1 and 2 on both sides of the first stator split tooth of phase A, the difference between ⁇ 1 and ⁇ 2 The value is the width of a split tooth
  • t is the time.
  • step 3 the expression of the stator permeance ⁇ s ( ⁇ , t) is:
  • ⁇ 0 and ⁇ k are the Fourier coefficients, k is a positive integer, ⁇ PM is the rotational speed of the stator relative to the rotor and the permanent magnet, ⁇ 0 is the initial position of the rotor, and N s is the number of stator teeth;
  • step 4 the permanent magnets on the rotor are attached to the rotor core, and the rotor magnetic permeability ⁇ or ( ⁇ , t) is expressed as:
  • ⁇ r1 is the rotor flux
  • step 5 the permanent magnetic air gap flux density B PM ( ⁇ , t) is expressed as:
  • F PMn is the Fourier coefficient
  • g is the equivalent air gap thickness
  • ⁇ 0 is the vacuum permeability
  • step 6 the armature winding air gap flux density B or ( ⁇ , t) is expressed as:
  • step 7 is:
  • Step 7.1 The permanent magnet air gap flux density contains two types of flux density harmonics: the order is nP r , the rotational speed is 0, the angular frequency is 0, the order is
  • , and the rotational speed is kN s ⁇ PM / (P r ⁇ kN s ), angular frequency kN s f_ PM ; the armature winding flux density contains two types of flux density harmonics: order is q 10r-9, rotational speed is (qP r ) ⁇ PM /q, angular frequency is
  • f_ PM , the order is q 10r-1, the rotational speed is (q+P r ) ⁇ PM /q, and the angular frequency is
  • Step 7.2 The average torque contributed by harmonics with the same order and rotational speed is calculated as:
  • B v is the magnetic density amplitude of the permanent magnet air gap of the v order
  • a Wv is the electric load harmonic amplitude of the v order
  • D ri is the diameter of the air gap
  • a is the axial length of the motor
  • ⁇ v is The phase angle between the v-order permanent magnet air-gap flux density harmonics and the electrical load harmonics, the average torque of the magnetic field-modulated permanent magnet motor can be obtained by adding the average torques contributed by the air-gap flux density harmonics;
  • the electrical load harmonic A Wv can be expressed as:
  • m is the number of phases of the motor armature winding
  • kwv is the winding factor of the v order
  • N is the number of turns of the motor winding
  • I max is the amplitude of the alternating current passing through the armature winding.
  • step 8 select the representative points on the rotor core and the permanent magnet, use the finite element method to calculate the change of the magnetic density of the representative point with time, and determine the representative point according to the change period of the armature current and the space change period of the permanent magnet.
  • the period of the point magnetic density changing with time, the harmonic analysis is performed on the representative point magnetic density, and the amplitude, order and angular frequency of each magnetic density harmonic are calculated:
  • Step 8.1 Calculate the permanent magnet eddy current loss and rotor core loss of the motor according to the amplitude, order and angular frequency of each magnetic density harmonic at the representative point.
  • the calculation formula of the permanent magnet eddy current loss is:
  • a, b and d are the axial length, width and thickness of the permanent magnet, respectively, ⁇ is the electrical conductivity of the permanent magnet, ⁇ k is the magnetic density harmonic rotation speed of order k, and B PMk is the order of The magnetic density harmonic amplitude of k;
  • Step 8.2 The core loss calculation formula is:
  • a e is the core eddy current loss coefficient
  • a h is the core hysteresis loss coefficient
  • f k is the alternating frequency of the k-order magnetic density harmonic
  • B Corek is the k-order rotor core magnetic density amplitude.
  • step 9 compare the angular frequency of the magnetic density harmonics of the permanent magnet and the rotor core with the angular frequency of the armature winding and the air gap magnetic density of the permanent magnet, and determine the permanent magnet and the The rotor core magnetic density is generated by which air-gap magnetic density harmonics, and then calculate the permanent magnet and iron core losses generated by each air-gap magnetic density harmonic, and identify the air-gap magnetic density harmonics that generate a lot of losses without contributing to the average torque Wave Components:
  • Step 9.1 Design P r magnetic flux barriers on the motor rotor.
  • the calculation formula of the motor rotor magnetic permeability ⁇ pr ( ⁇ , t) is:
  • ⁇ is the width of the magnetic flux barrier
  • ⁇ 1 is the rotor permeability amplitude
  • T is twice the pole pitch of the permanent magnet
  • Step 9.2 After designing P r magnetic flux barriers on the rotor, the calculation formula of the air gap flux density harmonics of the armature winding is:
  • the present invention establishes a magnetomotive force and a magnetic permeability model according to the stator, rotor, permanent magnet and winding structure of a magnetic field modulation permanent magnet motor, and derives the harmonic distribution of the armature winding and the permanent magnetic air gap magnetic field; by analyzing the magnetic field harmonics
  • the order, frequency and rotation characteristics can quickly determine whether each magnetic field harmonic can contribute to the torque loss. It avoids the blindness of the traditional parameter scanning analysis and design method, points out the direction for the loss analysis and suppression of the magnetic field modulation permanent magnet motor, reduces the workload of motor design, and shortens the optimization design cycle of the motor.
  • the present invention constructs the conversion mechanism of air gap flux density harmonics and permanent magnet and rotor core harmonic flux density, establishes an analysis and calculation model based on the harmonic angle of permanent magnet and rotor core loss, and can analyze and calculate each air gap flux density.
  • the contribution value of the dense harmonics to the loss can be determined, and the high-hazard magnetic field harmonics that only generate loss but do not contribute to the torque can be identified, which lays a solid foundation for realizing the loss suppression under the premise of ensuring the motor torque density.
  • the present invention establishes a rotor permeability model considering the rotor magnetic flux barrier, analyzes the action mechanism of the magnetic flux barrier on the rotor on the harmonics of the armature winding, and proposes an optimal design method for the rotor magnetic flux barrier, which can be used without affecting the contribution torque.
  • the harmonics of the motor it can effectively suppress the harmonics of the armature winding with high hazard, so as to reduce the loss while ensuring the high torque density of the motor.
  • the magnetic field modulation permanent magnet motor designed by the loss analysis and suppression method of the present invention has better torque performance and lower loss.
  • FIG. 1 is a cross-sectional view of an object of an embodiment of the present invention.
  • FIG. 2 is a schematic diagram of a basic unit of a rotor structure and a permanent magnet magnetomotive force without a magnetic flux barrier according to an embodiment of the present invention
  • Fig. 3 is the connection schematic diagram of the armature winding of the embodiment of the present invention.
  • FIG. 4 is a schematic diagram of the magnetomotive force of each phase armature winding according to an embodiment of the present invention
  • FIG. 5 is a schematic diagram of a basic unit of a stator cogging structure and a stator flux guide according to an embodiment of the present invention
  • FIG. 6 is a schematic diagram of a rotor flux permeance without a magnetic flux barrier according to an embodiment of the present invention.
  • Fig. 7 is the harmonic analysis of the magnetic density of the permanent magnetic air gap without the magnetic flux barrier according to the embodiment of the present invention.
  • Fig. 8 is the harmonic analysis of the air gap magnetic density of the armature winding without the magnetic flux barrier according to the embodiment of the present invention.
  • FIG. 9 is the contribution of the air gap magnetic density harmonics to the average torque without the magnetic flux barrier according to the embodiment of the present invention.
  • FIG. 13 is a schematic diagram of the basic unit of the rotor structure and the rotor magnetic permeability under the magnetic flux barrier according to the embodiment of the present invention.
  • FIG. 16 is a comparison of average torque and torque ripple with or without a flux barrier according to an embodiment of the present invention.
  • the object of the embodiment of the present invention is a five-phase magnetic field modulation permanent magnet motor, including a motor stator 1 and a motor rotor 2.
  • An air gap 4 is provided between the motor stator 1 and the motor rotor 2, and the motor stator 1 is wound on the top.
  • the armature winding 3 is made; the motor stator 1 contains 20 stator teeth 11, each stator tooth 11 is split into 2 split teeth 13, and each split tooth 13 has split slots 12 on both sides, and there are a total of 40 on the motor stator 1.
  • a method for analyzing and suppressing loss of a magnetic field modulation permanent magnet motor characterized in that it includes the following steps:
  • Step 1 Ignore the magnetic field generated by the armature winding on the stator and the cogging structure on the stator, and only consider the magnetic flux path formed by the permanent magnetic field generated by the permanent magnet on the rotor; according to the symmetry and periodicity of the rotor magnetic circuit, select the rotor structure
  • the basic unit establishes the permanent magnet magnetomotive force expression
  • Step 2 Ignore the permanent magnet magnetic field on the rotor, only consider the cogging structure on the stator and the connection and energization mode of the armature windings, establish the magnetomotive force expression of the armature windings of each phase in turn, and calculate the magnetomotive force of the armature windings of each phase.
  • the mathematical expressions are added together to obtain the synthetic armature winding magnetomotive force expression considering the stator cogging effect;
  • Step 3 Considering the unequal magnetic permeability of the teeth and slots on the stator on the circumference of the motor air gap, select the basic unit of the tooth and slot structure on the stator, and establish the stator permeability expression;
  • Step 4 The permanent magnets on the rotor are attached to the rotor core, and the permeance of the rotor core does not change with time and space as a constant.
  • the rotor permeance is shown in Figure 6.
  • the stator and rotor permeance can be expressed by multiplying the stator and rotor permeance. Mode;
  • Step 5 Multiply the permanent magnet magnetomotive force, the stator and rotor permeability and the permeability coefficient to obtain the permanent magnet air gap flux density expression:
  • Step 6 Multiply the magnetomotive force of the synthetic armature winding considering the stator cogging effect and the permeance of the rotor to obtain the expression of the air-gap flux density of the armature winding;
  • Step 7 Identify the harmonics of the air gap flux density that can contribute to the average torque and those that cannot contribute to the average torque; analyze and compare the order and rotational speed of the harmonic components of the permanent magnet air gap flux density and the armature winding air gap flux density, When the speed and order of the two magnetic density harmonics are equal, the magnetic density harmonic can contribute to the average torque for the working wave, otherwise it cannot contribute to the average torque for the non-working wave;
  • Step 8 Identify the air-gap flux density harmonics that contribute to the average torque and those that cannot contribute to the average torque; analyze the permanent magnet air-gap flux density and the armature winding air-gap flux density harmonics relative to the rotor rotational speed, which is equal to the rotor rotational speed
  • the magnetic density harmonics of 2000 do not produce rotor loss, and the magnetic density harmonics that are not equal to the rotation speed of the rotor produce rotor loss; the rotor loss is calculated by the calculation formula of rotor core loss and permanent magnet eddy current loss.
  • Step 9 For the air-gap flux density harmonics that generate losses but do not contribute to the average torque, design several magnetic flux barriers on the motor rotor to increase the reluctance on the magnetic flux path of the armature windings that generate high-hazard magnetic field harmonics, so that Reduce the content of high-hazard harmonics to ensure that the air-gap flux density harmonics contributing to the average torque are not affected.
  • Step 1 The expression of permanent magnet magnetomotive force F PM ( ⁇ ) is:
  • F PMn is the Fourier coefficient
  • ⁇ is the circumferential position of the motor air gap
  • P r is the number of pole pairs of the rotor permanent magnet
  • n is a positive odd number.
  • Step 2 It is a five-phase centralized winding, and the A, B, C, D, E five-phase windings are sequentially passed into sinusoidal currents with a mutual difference of ⁇ /5 electrical angle as follows:
  • N is the number of turns of each set of windings
  • I max is the amplitude of the alternating current
  • ⁇ PM is the rotational speed of the stator relative to the rotor and the permanent magnet
  • q is the armature winding magnetomotive force harmonic order
  • r is a positive integer
  • ⁇ 1 and ⁇ 2 are the coordinate positions 1 and 2 on both sides of the first stator split tooth of phase A
  • the difference between ⁇ 1 and ⁇ 2 is the width of one split tooth
  • ⁇ 0 is the initial position of the rotor
  • t is the time.
  • Step 3 As shown in Figure 5, the stator permeability expression is:
  • ⁇ 0 and ⁇ k are the Fourier coefficients, k is a positive integer, ⁇ PM is the rotational speed of the stator relative to the rotor and the permanent magnet, ⁇ 0 is the initial position of the rotor, and N s is the number of stator teeth;
  • Step 4 The permanent magnets on the rotor are attached to the rotor core.
  • the rotor magnetic permeability ⁇ or ( ⁇ , t) is expressed as:
  • ⁇ r1 is the rotor permeance.
  • Step 5 The permanent magnetic air gap flux density B PM ( ⁇ , t) is expressed as:
  • F PMn is the Fourier coefficient
  • g is the equivalent air gap thickness
  • ⁇ 0 is the vacuum permeability
  • Step 6 The expression of the armature winding air gap flux density B or ( ⁇ , t) is:
  • step 7 is:
  • the permanent magnet air gap flux density contains two types of flux density harmonics: the order is nP r , the rotational speed is 0, the angular frequency is 0, the order is
  • , the rotational speed is is kN s ⁇ PM /(P r ⁇ kN s ), the angular frequency kN s f_ PM ; as shown in Figure 8, the armature winding flux density includes two types of flux density harmonics: the order is q 10r-9, the rotational speed is (qP r ) ⁇ PM /q, the angular frequency is
  • f_ PM , the order is q 10r-1, the rotational speed is (q+P r ) ⁇ PM /q, and the angular frequency is
  • f_PM is the permanent magnet frequency
  • Step 7.2 The average torque contributed by harmonics with the same order and rotational speed is calculated as:
  • B v is the magnetic density amplitude of the permanent magnet air gap of the v order
  • a Wv is the electric load harmonic amplitude of the v order
  • D ri is the diameter of the air gap
  • a is the axial length of the motor
  • ⁇ v is The phase angle between the v-order permanent magnet air-gap flux density harmonics and the electrical load harmonics.
  • the average torque of the magnetic field-modulated permanent magnet motor can be obtained by summing the average torques contributed by the harmonics of the air-gap flux density, as shown in Figure 9.
  • the electrical load harmonic A Wv can be expressed as:
  • m is the number of phases of the motor armature winding
  • kwv is the winding factor of the v order
  • N is the number of turns of the motor winding
  • I max is the amplitude of the alternating current passing through the armature winding.
  • step 8 is as follows. Select the representative points on the rotor core and permanent magnet, and use the finite element method to calculate the variation of the magnetic density of the representative points with time, as shown in Figures 10(a) and 11(a). According to the change period of the armature current and the space change period of the permanent magnet, the period of the magnetic density of the representative point changing with time is determined, and the harmonic analysis of the magnetic density of the representative point is carried out to calculate the amplitude, order and angular frequency of the harmonics of each magnetic density. As shown in Figures 10(b) and 11(b).
  • Step 8.1 The calculation formula of permanent magnet eddy current loss is:
  • a, b and d are the axial length, width and thickness of the permanent magnet, respectively, ⁇ is the electrical conductivity of the permanent magnet, ⁇ k is the magnetic density harmonic rotation speed of order k, and B PMk is the order of The magnetic density harmonic amplitude of k.
  • the eddy current loss of the permanent magnet of the motor can be calculated by substituting the amplitude, order and angular frequency of each magnetic density harmonic at the representative point of the permanent magnet, as shown in Figure 12(a).
  • Step 8.2 The core loss calculation formula is:
  • a e is the core eddy current loss coefficient
  • a h is the core hysteresis loss coefficient
  • f k is the alternating frequency of the k-order magnetic density harmonic
  • B Corek is the k-order rotor core magnetic density amplitude.
  • the rotor core loss of the motor can be calculated by substituting the amplitude, order and angular frequency of each magnetic density harmonic at the representative point of the rotor core, as shown in Figure 12(b).
  • step 9 the specific calculation method of step 9 is as follows. Compare the angular frequency of the magnetic density harmonics of the permanent magnet and rotor core with the angular frequency of the magnetic density harmonics of the armature winding and the permanent magnet air gap, and determine which air gaps the magnetic density of the permanent magnet and the rotor core is composed of by the difference of the angular frequency of each harmonic. The magnetic density harmonics are generated, and then the permanent magnet and iron core losses generated by the air gap magnetic density harmonics are calculated. Identify the harmonic components of the air gap flux density that generate significant losses without contributing to the average torque.
  • Step 9.1 Design P r magnetic flux barriers on the rotor of the motor (Fig. 13). At this time, the calculation formula of the magnetic permeability of the rotor of the motor is:
  • ⁇ 1 is the rotor permeability amplitude
  • T is twice the pole pitch of the permanent magnet.
  • Step 9.2 After designing P r magnetic flux barriers on the rotor, the calculation formula of the air gap flux density harmonics of the armature winding is:
  • FIG. 14 is the harmonic analysis of the air-gap flux density of the armature winding with or without the magnetic flux barrier according to the embodiment of the present invention.
  • the designed rotor flux barrier structure effectively suppresses the generation of high-harm harmonics (1st harmonic), while other harmonics are basically unaffected.
  • FIG. 15 is a comparison of the loss of the permanent magnet and the rotor core with or without the magnetic flux barrier in the embodiment of the present invention.
  • FIG. 16 is a comparison of average torque and torque ripple with or without a flux barrier according to an embodiment of the present invention.
  • the embodiment of the present invention can suppress the loss on the premise of ensuring the torque density of the motor.
  • the present invention discloses a loss analysis and suppression method of a magnetic field modulation permanent magnet motor.
  • the stator, rotor, permanent magnet and winding structure of the magnetic field modulated permanent magnet motor According to the stator, rotor, permanent magnet and winding structure of the magnetic field modulated permanent magnet motor, the magnetomotive force and permeance model are established, and the magnetic field harmonic distribution of the armature winding and the permanent magnet air gap is deduced; the order, frequency and magnetic field harmonics are analyzed.
  • Rotation characteristics determine whether each magnetic field harmonic can contribute to torque and loss; calculate the contribution value of each magnetic field harmonic to torque and loss, and find out the high-hazard magnetic field harmonic that only produces loss but not torque Wave.
  • the invention analyzes the action mechanism of the magnetic field harmonics of the magnetic field modulation permanent magnet motor on the loss, can quantitatively calculate the contribution value of the magnetic field harmonics to the loss and torque, and at the same time can directionally suppress the high-harm magnetic field harmonics, so as to ensure the high torque of the motor Loss suppression effect under the premise of density.

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  • Power Engineering (AREA)
  • Permanent Field Magnets Of Synchronous Machinery (AREA)
  • Permanent Magnet Type Synchronous Machine (AREA)

Abstract

Procédé de suppression et d'analyse de perte pour un moteur électrique à aimant permanent modulé par champ magnétique. Un modèle de force magnétomotrice et de conduction magnétique est établi en fonction des structures d'un stator (1), d'un rotor (2), d'aimants permanents (21) et d'enroulements d'induit (3) d'un moteur électrique à aimant permanent modulé par champ magnétique, et des distributions harmoniques de champ magnétique d'entrefer des enroulements d'induit (3) et des aimants permanents sont dérivés ; les caractéristiques d'ordre, de fréquence et de rotation d'une onde harmonique de champ magnétique sont analysées, et si chaque ordre d'onde harmonique de champ magnétique peut contribuer à un couple et à une perte ; et des valeurs de contribution de chaque ordre d'onde harmonique de champ magnétique au couple et à la perte sont calculées, et une onde harmonique de champ magnétique à risque élevé qui génère la perte mais ne génère pas le couple est mesurée. Une structure de barrière au flux magnétique de rotor est conçue, l'effet de réglage d'une barrière au flux magnétique sur une onde harmonique de champ magnétique est analysé, la résistance magnétique sur un trajet de flux magnétique où les enroulements d'induit (3) génèrent des ondes harmoniques de champ magnétique à risque élevé est augmentée, et des composantes harmoniques de champ magnétique d'enroulements d'induit à risque élevé (3) sont réduites de manière ciblée sans toucher à une composante harmonique de champ magnétique qui génère le couple. Grâce au procédé, une onde harmonique de champ magnétique à risque élevé peut être supprimée de manière directionnelle, ce qui permet d'obtenir un effet de suppression de perte sur le principe de la garantie d'une densité de couple élevée d'un moteur électrique.
PCT/CN2020/133832 2020-11-24 2020-12-04 Procédé de suppression et d'analyse de perte pour moteur électrique à aimant permanent modulé par champ magnétique WO2022110274A1 (fr)

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