WO2020228818A1 - 准谐振反激变换器的同步整流控制***及方法 - Google Patents
准谐振反激变换器的同步整流控制***及方法 Download PDFInfo
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- 238000004804 winding Methods 0.000 claims description 13
- 230000002441 reversible effect Effects 0.000 claims description 6
- 238000005457 optimization Methods 0.000 claims description 4
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- 230000005284 excitation Effects 0.000 description 8
- 230000003044 adaptive effect Effects 0.000 description 3
- 230000007423 decrease Effects 0.000 description 3
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- 238000005516 engineering process Methods 0.000 description 3
- 238000012360 testing method Methods 0.000 description 2
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
- H02M1/007—Plural converter units in cascade
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0009—Devices or circuits for detecting current in a converter
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
- H02M1/15—Arrangements for reducing ripples from dc input or output using active elements
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/38—Means for preventing simultaneous conduction of switches
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33515—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with digital control
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/06—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- This application relates to a flyback converter, and more particularly to a synchronous rectification control system and method for a quasi-resonant flyback converter.
- Switching power supply also known as switching converter, is a power supply that uses modern power electronic technology to make the output voltage constant by adjusting the conduction ratio or frequency of the switching device.
- the conduction loss of the rectifier diode (DR) due to its forward conduction voltage drop is an important component of the system loss.
- the conduction loss will account for more than 50% of the total power loss.
- synchronous rectification technology In order to improve efficiency and reduce loss, the use of synchronous rectification technology has become a necessary means. It uses a Metal-Oxide-Semiconductor Field-Effect Transistor (MOSFET) with extremely low on-resistance to replace traditional rectifier diodes or Schottky diodes to reduce output rectification losses. Compared with the traditional Schottky diode, the synchronous rectifier has low on-resistance and small forward voltage drop, so the rectification loss is low. In addition, the synchronous rectifier tube also has the advantages of high cut-off voltage and small reverse current.
- MOSFET Metal-Oxide-Semiconductor Field-Effect Transistor
- the flyback converter includes a transformer primary side and a transformer secondary side.
- the primary side includes a primary winding and a switching tube
- the secondary side includes A secondary winding, a synchronous rectifier tube, and a resonant capacitor.
- the method includes: sampling the output terminal voltage of the switching tube to obtain a switching tube sampling voltage; and obtaining the dead time according to the switching tube sampling voltage and a preset relationship
- the preset relationship is the corresponding relationship between the time period during which the sampling voltage of the switch tube is lower than the first preset value and the dead time of the switch tube during the conduction time of one switching cycle, the dead zone
- the time is the time from when the switching tube is turned off to when the synchronous rectifier tube is turned on; the switching control of the synchronous rectifier tube is performed according to the dead time.
- a synchronous rectification control system for a quasi-resonant flyback converter includes a transformer primary side and a transformer secondary side.
- the primary side includes a primary winding and a switch tube, and the secondary side includes The secondary winding, the synchronous rectifier and the resonant capacitor.
- the system includes: a switching tube voltage sampling circuit for sampling the output terminal voltage of the switching tube to obtain the switching tube sampling voltage; a sampling calculation module for calculating The switching tube sampling voltage and the preset relationship are used to obtain the dead time; the predetermined relationship is the duration of the switching tube's on-time of one switching cycle when the switching tube sampling voltage is lower than the first preset value Corresponding to the dead time, the dead time is the time from when the switch tube is turned off to when the synchronous rectifier tube is turned on; the control module receives the dead time and adjusts the time according to the dead time The synchronous rectifier tube performs switching control.
- FIG. 1 is a circuit topology diagram of a synchronous rectification control system of a quasi-resonant flyback converter in an embodiment
- Figure 2 is the single-tube quasi-resonant flyback converter efficiency ⁇ and excitation current starting point Im(t0);
- Figure 3 is a steady-state waveform diagram of a quasi-resonant flyback converter
- FIG. 4 is a schematic diagram of the structure of a sampling circuit in an embodiment
- Fig. 5 is a control flow chart of a synchronous rectifier tube in an embodiment
- Fig. 6 is a circuit topology diagram of a synchronous rectification control system of a quasi-resonant flyback converter in another embodiment.
- Fig. 1 is a circuit topology diagram of a synchronous rectification control system of a quasi-resonant flyback converter in an embodiment.
- the converter is a single-tube quasi-resonant flyback converter, including the primary side of the transformer and the secondary side of the transformer.
- the primary side includes the primary winding Np, the resonant inductor Lr, the switching tube Q1, and the sampling resistor Rs.
- the secondary side includes the secondary winding Ns, the resonant capacitor Cr, the output capacitor C L , and the synchronous rectifier Q2.
- the resonant inductor Lr is connected in series with the primary winding Np
- the synchronous rectifier Q2 is connected in series with the secondary winding Ns.
- the switch tube Q1 and the synchronous rectifier tube Q2 are N-channel MOS tubes.
- Figure 3 is a steady-state waveform diagram of the quasi-resonant flyback converter.
- the synchronous rectification control system and method of the quasi-resonant flyback converter adopts valley-bottom conduction technology (that is, the switch is between the input end and the output end).
- valley-bottom conduction technology that is, the switch is between the input end and the output end.
- n is an integer greater than 0
- the output voltage when the nth valley is turned on is less than the required output voltage
- the output voltage when the n+1th valley is turned on is greater than all If the output voltage is needed, the switch tube Q1 can be turned on at the two valley bottoms by reasonable distribution, which can not only meet the requirements of the output voltage, but also achieve valley turn-on to reduce losses.
- i 1 be the lowest value of the primary current during the conduction period when the switching tube Q1 is fixed at the nth valley bottom
- i 2 is the corresponding conduction when the switching tube Q1 is fixed at the n+1th valley bottom. The lowest value of the primary current during the on period.
- the on-time of the switch Q1 is determined by the resonant inductance Lr and the resonant voltage, and the period of each valley in the drain-source voltage Vds waveform is determined by the resonant inductor Lr and the drain-source voltage Vds of the switch Q1; those skilled in the art According to the switching frequency of the specific application of the quasi-resonant flyback converter, an appropriate inductance/capacitance value can be reasonably selected for the resonant inductor Lr and the resonant capacitor Cr.
- the single switching cycle of a quasi-resonant flyback converter can be divided into four working states:
- the synchronous rectification control system of the quasi-resonant flyback converter includes a sampling circuit 10, a sampling calculation module 20 and a control module 30.
- the sampling circuit 10 includes a switching tube voltage sampling circuit for sampling the output terminal voltage of the switching tube Q1 to obtain the switching tube sampling voltage Vp.
- the switch Q1 is an N-channel MOSFET, the output terminal is the drain, the input terminal is the source, and the control terminal is the gate.
- the sampling calculation module 20 is used to obtain the dead time according to the sampling voltage of the switch tube and the preset relationship.
- the dead time is the time from when the switch Q1 is turned off to when the synchronous rectifier Q2 is turned on.
- the preset relationship refers to the corresponding relationship between the time period Ta during which the sampling voltage Vp of the switch tube Q1 is lower than the first preset value and the dead time Tb during the on time of the switch tube Q1 (that is, the value of Ta and the value of Tb Correspondence between values).
- the first preset value is the time period when the primary current is less than i 1 , that is, the time period from t5 to t2 in FIG. 3, and Ta and Tb correspond one-to-one non-linearly.
- the control module 30 receives the dead time Tb calculated by the sampling calculation module 20, and performs switching control on the switching tube Q1 and the synchronous rectifier Q2 according to the dead time Tb.
- the charging time of the resonant capacitor (the time required to charge the output voltage) is the same as The magnitude of the excitation current is related, and the synchronous rectifier turns on when the resonant capacitor is charged to the output voltage (ie, t3 in Figure 3). Therefore, the time Ta when the sampling voltage of the switching tube is lower than the first preset value determines the dead time Tb, and each Tb value corresponds to a Ta value. According to the sampling voltage of the switching tube and the preset relationship, it is determined that the switching tube is turned off to synchronous rectification. The dead time of tube opening realizes the adaptive control of the dead time.
- the synchronous rectification control system of the quasi-resonant flyback converter includes a driving module 40 for driving the switching tube Q1 and the synchronous rectifying tube Q2 to work according to the output of the control module 30.
- a corresponding table of Ta and Tb values can be established, and the Tb value corresponding to Ta can be obtained by looking up the table during control.
- the corresponding table may be stored in the control module 30, and the control module 30 can look up the table according to the sampling voltage Vp of the switch tube to obtain the dead time Tb.
- the correspondence table can be obtained through actual testing of a quasi-resonant flyback converter.
- the sampling circuit 10 further includes a synchronous rectifier tube voltage sampling circuit for sampling the input terminal of the synchronous rectifier tube Q2 to obtain the rectifier tube sampling voltage Vds1.
- the synchronous rectifier Q2 is an NMOSFET, the output terminal of which is a drain, the input terminal is a source, and the control terminal is a gate.
- the sampling calculation module 20 obtains the forward conduction duration of the parasitic diode of the synchronous rectifier tube according to the rectifier tube sampling voltage Vds1.
- the parasitic diode of the synchronous rectifier Q2 will be turned on, and the drain-source voltage of the synchronous rectifier Q2 will have a small voltage spike. Is the on-voltage drop of the parasitic diode of the synchronous rectifier, and the length is the on-time of the parasitic diode of the synchronous rectifier. Therefore, we can obtain the length of the small spike according to the sampling voltage Vds1 of the rectifier tube, and also obtain the forward conduction time of the parasitic diode of the synchronous rectifier tube Q2.
- the control module 30 also includes a dead time optimization unit 34, configured to adjust the foregoing preset relationship according to the forward conduction time length, so that the forward conduction time length tends to zero.
- a dead time optimization unit 34 configured to adjust the foregoing preset relationship according to the forward conduction time length, so that the forward conduction time length tends to zero.
- each switching cycle is controlled by looking up the table, and according to the sampling voltage Vds1 of the rectifier tube, it is judged whether the parasitic diode of the synchronous rectifier tube Q2 is forward conducting.
- the rectifier sampling voltage Vds1 obtains the conduction time, and then corrects the value in the table to make the conduction time tend to zero. If it is not turned on, keep the value in the table unchanged and wait for the next switching cycle to arrive.
- the dead time optimizing unit 34 is further configured to delay the safety time before the synchronous rectifier Q2 is turned off, so as to prevent the synchronous rectifier Q2 from conducting reversely. Specifically, if the actual conduction time of the synchronous rectifier Q2 is greater than the ideal synchronous rectifier conduction time, the synchronous rectifier tube will be reversely conducted, so that the linear rise time of the primary current is prolonged, the primary current and the primary voltage increase, and the switch Tube Q1 will be burned out. Therefore, a minimum on-time Tc of the parasitic diode can be preset, and the synchronous rectifier Q2 can be turned off after delaying Tc based on the on-time of the ideal synchronous rectifier to ensure that the synchronous rectifier will not conduct reversely. For the same reason, in another embodiment, the safety time may be delayed before the synchronous rectifier Q2 is turned on; the safety time delayed before turning on and turning off may be both Tc or different.
- the sampling circuit 10 further includes an output voltage sampling circuit for sampling the output voltage of the flyback converter to obtain the output voltage sampling value Vo.
- the control module 30 also includes a forced shutdown unit 32, which is used to control the switching tube Q1 and the synchronous rectifier Q2 to be turned off when the output voltage sample value Vo rises to a preset upper limit, and when the output voltage sample value Vo drops to a preset upper limit At the lower limit, the control switch Q1 and the synchronous rectifier Q2 enter the normal working state. That is, a forced shutdown state is added to the aforementioned control method.
- the sampled output voltage value Vo is a voltage of the output capacitor C L is obtained by sampling.
- control module 30 is provided with a switch-off upper limit value and a switch-off lower limit value of the sampling voltage Vp of the switch tube, and the control module 30 performs a control on the switch tube Q1 according to the switch-off upper limit value and the switch-off lower limit value.
- the turn-off control is used to limit the output terminal voltage of the switch tube Q1 when it is turned off, and to control the on time of the switch tube Q1 when it is turned off.
- the upper limit of the turn-off value is V 0
- the lower limit of the turn-off is V 2
- V 0 is the Vp value corresponding to the aforementioned i 0
- V 2 is the Vp value corresponding to the aforementioned i 2 ;
- V 0 and V 2 determine the upper and lower limits of the aforementioned correspondence table.
- the sampling circuit 10 includes an analog-to-digital converter ADC and four comparators comp.
- the output voltage sampling value Vo undergoes analog-to-digital conversion processing to obtain V OIN and output to the sampling calculation module 20; the rectifier sampling voltage Vds1 is input to the non-inverting input terminal of the first comparator, and the inverting input terminal of the first comparator inputs zero potential,
- the Vds_comp output from the output terminal is also sent to the sampling calculation module 20;
- the non-inverting input terminals of the other three comparators all input the switching tube sampling voltage Vp, and the inverting input terminals are respectively input V 1 , V 2 and V 0 , three comparisons
- the Vp1_comp, Vp2_comp, and Vp0_comp output from the output terminal of the device are also given to the sampling calculation module 20, where V 1 is the Vp value corresponding to the aforementioned i 1 , V 2 is the Vp value corresponding to
- control module 30 includes an MCU.
- an MCU equipped with a comparator, a register, a counter, and an adder, and having an addition and subtraction function can be used to form the control module 30.
- the two comparators inputting V 0 and V 2 are used to set the upper and lower limits of the correspondence table. Therefore, after the initial setting of the correspondence table, these two comparator settings can no longer be used. form.
- the upper and lower limits of the table can be directly called (first use the comparator open-loop test to obtain the upper and lower limits for subsequent use), so the two comparators can be used in actual use. Set up the correspondence table.
- Fig. 6 is a circuit topology diagram of a synchronous rectification control system of a quasi-resonant flyback converter in another embodiment.
- the inductance Lm in Fig. 6 represents the inductance of an ideal transformer, and the parasitic inductance of the switch Q1 is represented by Coss.
- the working principle of the circuit structure of FIG. 6 can be referred to FIG. 1, where the dead time optimization unit 234 of FIG. 6 corresponds to the dead time optimization unit 34 of FIG. 1.
- the output voltage sampling circuit 212 is used to sample the output voltage of the flyback converter, and the state judgment module is used to control the switching tube Q1 and the synchronous rectifier Q2 to be forced to turn off when the output voltage sampling value rises to the preset upper limit.
- the driving circuit 242 and the driving circuit 244 correspond to the driving module 40 in FIG. 1, and are used to drive the switching tube Q1 and the synchronous rectifier Q2 to work, respectively.
- the synchronous rectification control system of the quasi-resonant flyback converter in FIG. 6 also includes a delay compensation module 252 connected to the drive circuit 242 and a delay compensation module 254 connected to the drive circuit 244 to compensate for the delay of the drive circuit.
- the application also correspondingly provides a synchronous rectification control method for a quasi-resonant flyback converter, including:
- the dead time is obtained according to the sampling voltage of the switch tube and the preset relationship; the preset relationship is that the sampling voltage of the switch tube is lower than the first preset value during the on time of the switch tube.
- the switching control of the synchronous rectifier tube is performed according to the dead time.
- control method further includes:
- the preset relationship is adjusted according to the forward conduction duration, so that the forward conduction duration tends to zero.
- control method further includes a step of delaying a safety time before the synchronous rectifier is turned on to avoid reverse conduction of the synchronous rectifier.
- the safety time can be delayed before the synchronous rectifier is turned off.
- control method further includes:
- the switch tube and the synchronous rectifier tube are controlled to enter a normal working state.
- the method further includes the step of outputting a switching tube control signal to the control terminal of the switching tube to control the on and off of the switching tube, and the switching tube control signal is at the input terminal of the switching tube.
- the switching tube is controlled to be turned on.
- a preset value is the voltage value of the sampling voltage of the switching tube when the primary current of the flyback converter is the first current value
- the first current value is the value of the switching tube when the switching tube is fixed at the nth valley and turned on.
- the control method further includes setting a turn-off upper limit value and a turn-off lower limit value of the sampling voltage of the switch tube, and controlling the switch according to the turn-off upper limit value and the turn-off lower limit value.
- the transistor performs turn-off control to limit the output terminal voltage of the switch tube when the switch tube is turned off, and to control the on-time of the switch tube.
- the turn-off lower limit is the voltage value of the switching tube sampling voltage when the primary current of the flyback converter is the second current value, and the second current value is the fixed value of the switching tube.
- the third current value is the lowest value of the primary current during the conduction period corresponding to when the switching tube is turned on at the optimal efficiency of the flyback converter.
- control method further includes the step of obtaining a correspondence table between the duration and the dead time.
- the step of obtaining the dead time according to the sampling voltage of the switch tube and a preset relationship is to check Table to get the dead time.
- the synchronous rectification control system and method of the quasi-resonant flyback converter described above determines the magnitude of the excitation current according to Ta, thereby determining the dead time Tb before the synchronous rectifier is turned on.
- the dead-time adaptation is realized, the switching information of multiple working cycles is used to recursively look-up the table to control the operation of the synchronous rectifier in this cycle, and according to the voltage difference that exists when the parasitic diode of the synchronous rectifier is turned on, The on-point and off-point of the synchronous rectifier are determined, so the optimal switching time of the synchronous rectifier can be determined, and the dead time adaptive of the synchronous rectifier can be realized.
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Abstract
Description
Claims (15)
- 一种准谐振反激变换器的同步整流控制方法,所述反激变换器包括变压器原边侧和变压器副边侧,所述原边侧包括原边绕组和开关管,所述副边侧包括副边绕组、同步整流管及谐振电容,所述方法包括:对所述开关管的输出端电压进行采样,得到开关管采样电压;根据所述开关管采样电压和预设关系,得到死区时间;所述预设关系是所述开关管在一个开关周期的导通时间内,所述开关管采样电压低于第一预设值的时长与所述死区时间的对应关系,所述死区时间是所述开关管关断到所述同步整流管打开的时间;及根据所述死区时间对所述同步整流管进行开关控制。
- 根据权利要求1所述的方法,其特征在于,还包括:对所述同步整流管的输入端进行采样,得到整流管采样电压;根据所述整流管采样电压得到所述同步整流管的寄生二极管的正向导通时长;及根据所述正向导通时长对所述预设关系进行调整,以使所述正向导通时长趋向于零。
- 根据权利要求1所述的方法,其特征在于,还包括在所述同步整流管导通前延时安全时间,以避免所述同步整流管反向导通的步骤。
- 根据权利要求1所述的方法,其特征在于,还包括在所述同步整流管关断前延时安全时间,以避免所述同步整流管反向导通的步骤。
- 根据权利要求1所述的方法,其特征在于,还包括在所述同步整流管导通前和关断前延时安全时间,以避免所述同步整流管反向导通的步骤。
- 根据权利要求1所述的方法,其特征在于,还包括:对反激变换器的输出电压进行采样,得到输出电压采样值;当所述输出电压采样值上升到预设上限值时,控制所述开关管和同步整流管关断;及当所述输出电压采样值下降到预设下限值时,控制所述开关管和同步整流管进入正常工作状态。
- 根据权利要求1所述的方法,其特征在于,还包括向所述开关管的控制端输出开关管控制信号以控制所述开关管的导通和关断的步骤,所述开关管控制信号在所述开关管的输入端和输出端之间的电压到达谷底时控制所述开关管导通,在所述开关管的一个开关周期中,所述输入端和输出端之间的电压出现一次以上所述谷底;所述第一预设值是所述反激变换器的原边电流为第一电流值时开关管采样电压的电压值,所述第一电流值是所述开关管固定在第n个谷底导通时所对应的导通期间所述原边电流的最低值,反激变换器效率最优点的开关管导通时间在当前开关周期的第n个谷底和第n+1个谷底之间,n为大于0的整数。
- 根据权利要求7所述的方法,其特征在于,还包括设置所述开关管采样电压的关断上限值和关断下限值,并根据所述关断上限值和关断下限值对所述开关管进行关断控制,以限制所述开关管关断时开关管的输出端电压、并控制所述开关管的导通时间的步骤。
- 根据权利要求8所述的方法,其特征在于,所述关断下限值是所述反激变换器的原边电流为第二电流值时开关管采样电压的电压值,所述第二电流值是所述开关管固定在第n+1个谷底导通时所对应的导通期间所述原边电流的最低值;所述关断上限值是所述反激变换器的原边电流为第三电流值时开关管采样电压的电压值,所述第三电流值是所述开关管在反激变换器效率最优点导通时所对应的导通期间所述原边电流的最低值。
- 一种准谐振反激变换器的同步整流控制***,所述反激变换器包括变压器原边侧和变压器副边侧,所述原边侧包括原边绕组和开关管,所述副边侧包括副边绕组、同步整流管及谐振电容,所述***包括:开关管电压采样电路,用于对所述开关管的输出端电压进行采样,得到开关管采样电压;采样计算模块,用于根据所述开关管采样电压和预设关系,得到死区时 间;所述预设关系是所述开关管在一个开关周期的导通时间内,所述开关管采样电压低于第一预设值的时长与所述死区时间的对应关系,所述死区时间是所述开关管关断到所述同步整流管打开的时间;及控制模块,接收所述死区时间,并根据所述死区时间对所述同步整流管进行开关控制。
- 根据权利要求10所述的同步整流控制***,其特征在于,还包括同步整流管电压采样电路,用于对所述同步整流管的输入端进行采样,得到整流管采样电压;所述采样计算模块还用于根据所述整流管采样电压得到所述同步整流管的寄生二极管的正向导通时长;所述控制模块还包括死区时间优化单元,用于根据所述正向导通时长对所述预设关系进行调整,以使所述正向导通时长趋向于零。
- 根据权利要求10所述的同步整流控制***,其特征在于,还包括输出电压采样电路,用于对反激变换器的输出电压进行采样,得到输出电压采样值;所述控制模块还包括强制关断单元,用于在所述输出电压采样值上升到预设上限值时,控制所述开关管和同步整流管关断,在所述输出电压采样值下降到预设下限值时,控制所述开关管和同步整流管进入正常工作状态。
- 根据权利要求10所述的同步整流控制***,其特征在于,所述控制模块是向所述开关管的控制端输出开关管控制信号以控制所述开关管的导通和关断,所述开关管控制信号在所述开关管的输入端和输出端之间的电压到达谷底时控制所述开关管导通,在所述开关管的一个开关周期中,所述输入端和输出端之间的电压出现一次以上所述谷底;所述第一预设值是所述反激变换器的原边电流为第一电流值时开关管采样电压的电压值,所述第一电流值是所述开关管固定在第n个谷底导通时所对应的导通期间所述原边电流的最低值,反激变换器效率最优点的开关管导通时间在当前开关周期的第n个谷底和第n+1个谷底之间,n为大于0的整数。
- 根据权利要求10所述的同步整流控制***,其特征在于,还包括:驱动电路,连接于所述控制模块和同步整流管之间,用于根据所述控制 模块的输出驱动所述同步整流管工作;延迟补偿模块,连接所述驱动电路,用于对驱动电路的延迟进行补偿。
- 根据权利要求10所述的同步整流控制***,其特征在于,所述开关管和同步整流管是N沟道MOS管,N沟道MOS管的源端为输入端,漏端为输出端。
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