WO2018126720A1 - 数控振荡器和基于数控振荡器的全数字锁频环和锁相环 - Google Patents

数控振荡器和基于数控振荡器的全数字锁频环和锁相环 Download PDF

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WO2018126720A1
WO2018126720A1 PCT/CN2017/099965 CN2017099965W WO2018126720A1 WO 2018126720 A1 WO2018126720 A1 WO 2018126720A1 CN 2017099965 W CN2017099965 W CN 2017099965W WO 2018126720 A1 WO2018126720 A1 WO 2018126720A1
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Prior art keywords
frequency
digital
clock signal
period
control word
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PCT/CN2017/099965
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English (en)
French (fr)
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修黎明
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京东方科技集团股份有限公司
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Priority to US15/761,708 priority Critical patent/US10715154B2/en
Priority to EP17849897.8A priority patent/EP3567725A4/en
Publication of WO2018126720A1 publication Critical patent/WO2018126720A1/zh

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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03L—AUTOMATIC CONTROL, STARTING, SYNCHRONISATION OR STABILISATION OF GENERATORS OF ELECTRONIC OSCILLATIONS OR PULSES
    • H03L7/00—Automatic control of frequency or phase; Synchronisation
    • H03L7/06—Automatic control of frequency or phase; Synchronisation using a reference signal applied to a frequency- or phase-locked loop
    • H03L7/08—Details of the phase-locked loop
    • H03L7/099—Details of the phase-locked loop concerning mainly the controlled oscillator of the loop
    • H03L7/0991—Details of the phase-locked loop concerning mainly the controlled oscillator of the loop the oscillator being a digital oscillator, e.g. composed of a fixed oscillator followed by a variable frequency divider
    • H03L7/0992—Details of the phase-locked loop concerning mainly the controlled oscillator of the loop the oscillator being a digital oscillator, e.g. composed of a fixed oscillator followed by a variable frequency divider comprising a counter or a frequency divider
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03L—AUTOMATIC CONTROL, STARTING, SYNCHRONISATION OR STABILISATION OF GENERATORS OF ELECTRONIC OSCILLATIONS OR PULSES
    • H03L7/00—Automatic control of frequency or phase; Synchronisation
    • H03L7/06—Automatic control of frequency or phase; Synchronisation using a reference signal applied to a frequency- or phase-locked loop
    • H03L7/08—Details of the phase-locked loop
    • H03L7/085—Details of the phase-locked loop concerning mainly the frequency- or phase-detection arrangement including the filtering or amplification of its output signal
    • H03L7/087—Details of the phase-locked loop concerning mainly the frequency- or phase-detection arrangement including the filtering or amplification of its output signal using at least two phase detectors or a frequency and phase detector in the loop
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03L—AUTOMATIC CONTROL, STARTING, SYNCHRONISATION OR STABILISATION OF GENERATORS OF ELECTRONIC OSCILLATIONS OR PULSES
    • H03L7/00—Automatic control of frequency or phase; Synchronisation
    • H03L7/06—Automatic control of frequency or phase; Synchronisation using a reference signal applied to a frequency- or phase-locked loop
    • H03L7/08—Details of the phase-locked loop
    • H03L7/085—Details of the phase-locked loop concerning mainly the frequency- or phase-detection arrangement including the filtering or amplification of its output signal
    • H03L7/093—Details of the phase-locked loop concerning mainly the frequency- or phase-detection arrangement including the filtering or amplification of its output signal using special filtering or amplification characteristics in the loop
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03L—AUTOMATIC CONTROL, STARTING, SYNCHRONISATION OR STABILISATION OF GENERATORS OF ELECTRONIC OSCILLATIONS OR PULSES
    • H03L7/00—Automatic control of frequency or phase; Synchronisation
    • H03L7/06—Automatic control of frequency or phase; Synchronisation using a reference signal applied to a frequency- or phase-locked loop
    • H03L7/08—Details of the phase-locked loop
    • H03L7/099—Details of the phase-locked loop concerning mainly the controlled oscillator of the loop
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03L—AUTOMATIC CONTROL, STARTING, SYNCHRONISATION OR STABILISATION OF GENERATORS OF ELECTRONIC OSCILLATIONS OR PULSES
    • H03L7/00—Automatic control of frequency or phase; Synchronisation
    • H03L7/06—Automatic control of frequency or phase; Synchronisation using a reference signal applied to a frequency- or phase-locked loop
    • H03L7/16—Indirect frequency synthesis, i.e. generating a desired one of a number of predetermined frequencies using a frequency- or phase-locked loop
    • H03L7/18—Indirect frequency synthesis, i.e. generating a desired one of a number of predetermined frequencies using a frequency- or phase-locked loop using a frequency divider or counter in the loop
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03L—AUTOMATIC CONTROL, STARTING, SYNCHRONISATION OR STABILISATION OF GENERATORS OF ELECTRONIC OSCILLATIONS OR PULSES
    • H03L2207/00—Indexing scheme relating to automatic control of frequency or phase and to synchronisation
    • H03L2207/50—All digital phase-locked loop

Definitions

  • the present disclosure relates to very large scale VLSI integrated circuit designs, and more particularly to time averaged frequency direct cycle synthesis (TAF-DPS) digitally controlled oscillators and TAF-DPS digitally controlled oscillator based all digital frequency locked loops and phase locks Loop.
  • TAF-DPS time averaged frequency direct cycle synthesis
  • analog direct frequency synthesis digital direct synthesis
  • DDS digital direct synthesis
  • PLL phase-locked loop
  • VCO oscillator
  • ADPLL All Digital Phase-Locked Loop
  • a prominent feature of the ADPLL is its internal digital oscillator, which is capable of controlling the frequency of the clock signal generated by the digital oscillator by digital values.
  • the all-digital phase-locked loop (ADPLL) reduces the complexity of the analog design compared to traditional phase-locked loops, making it suitable for digital processing.
  • the "digital oscillator" in this ADPLL is not a digital circuit, it still includes a large number of analog circuits, and it is called a digital oscillator simply because its frequency tuning is achieved by digital control.
  • Time-Average-Frequency Direct Period Synthesis (TAF-DPS) is used as an all-digital frequency oscillator. Therefore, an oscillator such as its digitally controlled oscillator (DCO) is used to construct an all digital frequency locked loop and a phase locked loop.
  • DCO digitally controlled oscillator
  • a key issue to be addressed in this disclosure is the use of pure digital circuitry to construct a frequency locked loop (FLL) and a phase locked loop (PLL).
  • the FLL and PLL are designed using standard cells from any given ASIC library. Therefore, no analog circuitry is required in the FLL and PLL.
  • the design method is Verilog coding ⁇ simulation ⁇ synthesis ⁇ actual circuit. No transistor-level custom circuit design skills are required.
  • the TAF-DPS synthesizer consists entirely of digital standard cells from the ASIC library. Then, a frequency-locked loop (FLL) is constructed from the all-digital TAF-DPS DCO.
  • the frequency detector used in this loop is a digital detector. Therefore, the entire loop is constructed digitally, where the loop response time is fully computable based on the DCO period.
  • the design goal is to make the loop delay as small as possible so that the input frequency of the FLL can be tracked (followed) as quickly as possible.
  • the TAF-DPS also has phase synthesis capability, which enables the construction of a PLL from the DCO.
  • the present disclosure provides a digitally controlled oscillator comprising: a frequency divider chain configured to divide an input clock signal to generate K basic clock signals, wherein the K basic clock signals have the same frequency and period, And a time difference between two adjacent basic clock signals is a basic time unit; and a TAF-DPS frequency synthesizer configured to receive the K basic clock signals from the frequency divider chain and according to a basic time unit and The frequency control word determines a first period and a second period and generates a synthesized clock signal based on the K basic clock signals, wherein the synthesized clock signal uses the first period and the second period in an alternating manner.
  • the frequency control word is equal to I+r, where I is an integer, 0 ⁇ r ⁇ 1, wherein the first period is equal to I* ⁇ , and the second period is equal to (I+1) * ⁇ , r is the probability of occurrence of the second period, and the period of the synthesized clock signal is equal to (1-r) * first period + r * second period.
  • the frequency synthesizer is a TAF-DPS frequency synthesizer.
  • the present disclosure also provides an all-digital frequency-locked loop, comprising: the above-mentioned digitally controlled oscillator; a frequency divider configured to: divide the synthesized clock signal output by the digitally controlled oscillator to obtain feedback a clock signal, wherein the frequency dividing ratio is N, N is an integer greater than or equal to 1; and the digital frequency detector is configured to: detect a feedback clock frequency of the feedback clock signal, and input a reference frequency and the feedback clock The frequencies are compared and the frequency control word is updated based on the frequency difference.
  • the all-digital frequency-locked loop further includes: a low-pass filter configured to filter high-frequency components and noise in an output signal of the digital-type frequency detector, and to filter the signal The updated frequency control word is output to the digitally controlled oscillator.
  • the devices in the all digital frequency locked loop are digital devices.
  • the present disclosure also provides an all-digital phase-locked loop, comprising: the above-mentioned digitally controlled oscillator; a frequency divider configured to: divide the synthesized clock signal output by the digitally controlled oscillator to obtain feedback a clock signal, wherein the frequency dividing ratio is N, N is an integer greater than or equal to 1; the digital frequency detector is configured to: detect a feedback clock frequency of the feedback clock signal, and input a reference frequency and the feedback clock frequency Comparing and updating the frequency control word according to a frequency difference; and a digital phase detector configured to: detect a feedback clock phase of the feedback clock signal, compare an input reference phase with the feedback clock phase, and A phase control word is generated based on the phase difference, wherein the digitally controlled oscillator further receives the phase control word and adds the phase control word to the updated frequency control word as an updated frequency control word.
  • the all-digital phase-locked loop further includes: a first low-pass filter configured to filter high-frequency components and noise in an output signal of the digital-type frequency detector, and to filter The signal is output to the digitally controlled oscillator as an updated frequency control word.
  • the all-digital phase-locked loop further includes: a second low-pass filter configured to filter high-frequency components and noise in an output signal of the digital phase detector, and to filter The signal is output as a phase control word to the digitally controlled oscillator.
  • the devices in the all digital phase locked loop are digital devices.
  • FIG. 1 schematically illustrates the operation of a time averaged frequency direct cycle synthesis (TAF-DPS) clock generator.
  • TAF-DPS time averaged frequency direct cycle synthesis
  • FIG. 2 is a block diagram showing an exemplary circuit of the TAF-DPS frequency synthesizer shown in FIG. 1.
  • FIG. 3 is an exemplary circuit diagram of an exemplary circuit block diagram of the TAF-DPS frequency synthesizer shown in FIG. 2.
  • Figure 4 shows the phase adjustment mechanism of the TAF-DPS clock generator.
  • FIG. 5 illustrates an all digital phase locked loop FLL using TAF-DPS as its DCO (upper right) and an all digital phase locked loop PLL using TAF-DPS as its DCO (bottom right), in accordance with an embodiment of the present disclosure.
  • TAF-DPS Time-Average-Frequency Direct Period Synthesis
  • DCO Digitally Controlled Oscillator
  • FIG. 1 schematically illustrates the operation of a time averaged frequency direct cycle synthesis (TAF-DPS) clock generator.
  • TAF-DPS time averaged frequency direct cycle synthesis
  • the TAF-DPS clock generator includes a TAF-DPS frequency synthesizer 110 configured to determine a first period and a second period based on the basic time unit and the frequency control word, and based on the K basic clock signals A composite clock signal is generated, wherein the composite clock signal uses the first period and the second period in an alternating manner.
  • the output of the TAF-DPS frequency synthesizer 110 is configured to output a composite clock signal.
  • the composite clock signal is a synthesized time averaged frequency clock signal.
  • the frequency control word F is determined according to the target clock frequency input by the user, and according to the circuit design
  • the basic time unit ⁇ is designed as needed.
  • the patent is not limited thereto, and the first period and the second period may be determined in other manners.
  • the TAF-DPS frequency synthesizer 110 determines the synthesis period by using the first period T A and the second period T B , and generates a synthesized clock signal with the synthesis period as a clock cycle, and then outputs the synthesized clock signal through its output terminal.
  • F is an integer (i.e., r is zero)
  • the first weight W A is 1
  • FIG. 2 is a block diagram showing an exemplary circuit of the TAF-DPS frequency synthesizer shown in FIG. 1.
  • the Flying-Adder frequency synthesis architecture shown in FIG. 2 can be utilized as an all-digital circuit implementation of the TAF-DPS frequency synthesizer shown in FIG. 1.
  • the TAF-DPS frequency synthesizer includes a first multiplexer 210, a first selection control circuit 220, a second multiplexer 230, a second selection control circuit 240, and a third multiplexer 250. And an output circuit 260.
  • the first selection controller 220 generates a first selection control signal according to the first frequency control word
  • the second selection controller 240 generates a second selection control signal according to the second frequency control word, the first frequency control word and
  • the second frequency control word is determined based on the frequency control word F.
  • the first frequency control word is equal to the frequency control word F
  • the second frequency control word is half of the frequency control word F.
  • the first selection controller 220 outputs the first selection control signal to the first multiplexer 210, and the second selection controller 240 outputs the second to the second multiplexer 230 Select the control signal.
  • the first multiplexer 210 receives a plurality of basic clock signals, and selects one of the plurality of basic clock signals as a first selected clock signal according to the first selection control signal; the second multiplexer 230 receiving the plurality of basic clock signals, and selecting one of the plurality of basic clock signals as the second selected clock signal according to the second selection control signal.
  • the third multiplexer 250 selects one of the first selection clock signal and the second selection clock signal as a selection clock signal.
  • the output circuit 260 generates a synthesized clock signal CLK1 and an intermediate clock signal CLK2 based on the selected clock signal, and the phase of the synthesized clock signal CLK1 and the intermediate clock signal CLK2 are different by 180°.
  • the plurality of basic clock signals may be K basic clock signals, K is an integer greater than 1, and each of the K basic clock signals has a frequency of f div and a period of T div , and The K basic clock signals are sequentially delayed by T div /K and have a phase lag of 360°/K.
  • the TAF-DPS frequency synthesizer controls the frequency of the synthesized clock signal whose output is based on the first frequency control word and the second frequency control word.
  • FIG. 3 is an exemplary circuit diagram of an exemplary circuit block diagram of the TAF-DPS frequency synthesizer shown in FIG. 2.
  • the first selection controller 220 has a first input end and a second input end, and the first input end receives a first frequency control word, and the value of the first frequency control word is equal to the frequency control word F The value is the same; the second input receives the intermediate clock signal CLK2.
  • the first selection controller 220 generates the first selection control signal according to the first frequency control word F and the intermediate clock signal CLK2, and according to the first frequency control word F and the intermediate clock signal CLK2 Generate a control word adjustment signal.
  • the first selection controller 220 has a first output terminal that outputs the first selection control signal and a second output terminal that outputs the control word adjustment signal.
  • the second selection controller 240 has a first input terminal, a second input terminal, a third input terminal and a fourth input terminal, the first input terminal receiving a second frequency control word, the second frequency control word
  • the value F/2 is half of the value of the frequency control word F
  • the second input receives the synthesis
  • the clock signal CLK1 the third input terminal receives the intermediate clock signal CLK2, and the fourth input terminal receives the control word adjustment signal.
  • the first selection controller 220 generates the second selection control signal according to the second frequency control word F/2, the synthesized clock signal CLK1, the intermediate clock signal CLK2, and the control word adjustment signal.
  • the first selection control circuit 220 includes a first adder, a first register, and a second register. a first input of the first adder as a first input of the first selection control circuit 220 to receive the first frequency control word, and a second input of the first adder receives the Control word adjustment signal.
  • a first input of the first register is coupled to an output of the first adder, a second input of the first register receives the intermediate clock signal CLK2, and an output of the first register serves as a second output of the first selection controller 220 and outputting the control word adjustment signal;
  • a first input of the second register is coupled to an output of the first register, and a second input of the second register
  • the intermediate clock signal CLK2 is received, and an output of the second register serves as a first output of the first selection controller 220 and outputs the first selection control signal.
  • the second selection controller 240 includes a second adder, a third register, and a fourth register.
  • the two input ends of the second adder respectively serve as a first input terminal and a fourth input terminal of the second selection controller 240 to receive the second frequency control word and the control word adjustment signal.
  • a first input end of the third register is connected to an output end of the second adder, a second input end of the third register receives the intermediate clock signal CLK2, and a first input end of the fourth register is connected
  • An output of the third register, a second input of the fourth register receives the synthesized clock signal CLK1, and an output of the fourth register serves as an output of the second selection controller 240 and outputs The second selection control signal.
  • the TAF-DPS frequency synthesizer controls the frequency of the synthesized clock signal of the output according to the first frequency control word F and the second frequency control word F/2, that is, the synthesis of the TAF-DPS frequency synthesizer output.
  • the frequency control word F I + r, where I is an integer, r is a fraction, and 0 ⁇ r ⁇ 1.
  • the TAF-DPS frequency synthesizer outputs a signal of a single frequency.
  • the TAF-DPS frequency synthesizer uses the time-averaged frequency concept in its output pulse signal.
  • a TAF-DPS frequency synthesizer can be used as the circuit block 110 in FIG.
  • Signal F is used as the frequency control word F in FIG.
  • the synthesized synthesized clock signal is used as the synthesized clock signal in FIG.
  • Figure 4 shows a schematic diagram of the phase synthesis principle of the TAF-DPS clock generator.
  • the TAF-DPS clock generator shown in Figure 1 has a direct cycle synthesis capability that can be used not only for synthesizing frequency/period, but also for adjusting the phase of the synthesized clock signal of its output.
  • Figure 4 illustrates this phase adjustment mechanism by adjusting the period of the corresponding pulse by a single change in the frequency control word F, specifically extending or shortening the period of the corresponding pulse, which will result in a phase advance of the synthesized clock signal or Back.
  • the output burst will have an extended or shortened period.
  • This function will be used in the embodiments of the present disclosure to construct an all digital PLL.
  • an all-digital frequency-locked loop and a phase-locked loop in an integrated circuit can be constructed using TAF-DPS.
  • FIG. 5 illustrates an all digital phase locked loop FLL using TAF-DPS as its DCO (upper right) and an all digital phase locked loop PLL using TAF-DPS as its DCO (bottom right), in accordance with an embodiment of the present disclosure.
  • the all-digital frequency-locked loop FLL includes a digital frequency detector (FD) 402, a time-averaged frequency direct-cycle synthesized digitally controlled oscillator (TAF-DPS DCO) 404, and a frequency divider 405.
  • the all-digital frequency-locked loop FLL may also include a low pass filter (LPF) 403.
  • a digital frequency detector (FD) 402, a low pass filter 403 (LPF), a time average frequency direct cycle synthesis digitally controlled oscillator (TAF-DPS DCO) 404, and a frequency divider 405 are sequentially connected in series to form a loop.
  • the TAF-DPS DCO 404 is composed of a frequency divider chain 401 and a TAF-DPS frequency synthesizer as shown in FIG.
  • the input divider chain 401 receives an input clock signal, the frequency of the input clock signal is f i.
  • the divider chain 401 is configured to divide the input clock signal to generate K basic clock signals and feed the K basic clock signals to a TAF-DPS frequency synthesizer, where K is greater than one An integer of which each of the K basic clock signals has a frequency of f div and a period of T div , and the K basic clock signals are sequentially delayed by T div /K and the phase is delayed by 360/K.
  • the input end of the TAF-DPS frequency synthesizer receives the frequency control word F output by the low pass filter (LPF) 403, and generates a synthesized clock according to the received frequency control word F and the K basic clock signals.
  • the signal, the frequency of the synthesized clock signal is f o .
  • An output of the TAF-DPS frequency synthesizer serves as an output of the all-digital frequency-locked loop FLL, and outputs the synthesized clock signal.
  • An input of the frequency divider 405 receives the synthesized clock signal and divides the synthesized clock signal to generate a feedback clock signal.
  • the first input of the digital frequency detector 402 serves as an input of the all-digital frequency-locked loop FLL and receives an input reference frequency fr .
  • the second input of the digital frequency detector 402 receives the feedback clock signal output from the frequency divider 405, the frequency of the feedback clock signal being f b .
  • the digital frequency detector 402 is configured to detect a feedback clock frequency f b of the feedback clock signal and generate or update a frequency control word F based on the input reference frequency f r and the feedback clock frequency f b .
  • the digital frequency detector 402 can be configured to compare the input reference frequency f r and the feedback clock frequency f b to obtain a first control signal related to the frequency difference and generate according to the first control signal The first control word F.
  • the first control signal and the first control word are both digital values.
  • the low pass filter 403 is configured to filter out high frequency components and noise in the first control word output by the digital frequency detector 402, and output the filtered first control word as a frequency control word. Go to TAF-DPS DCO 404.
  • the digital frequency detector 402 can directly output the first control word as the frequency control word to the TAF-DPS DCO 404.
  • the TAF-DPS DCO 404 then generates a composite clock signal based on the frequency control word F. Thereby, a closed loop operation of the all digital frequency locked loop FLL is formed.
  • the input reference frequency is compared with the frequency of the synthesized clock signal generated by the TAF-DPS DCO 404, and is gradually adjusted according to the comparison result to be input to the TAF-
  • the frequency of the DPS DCO 404 controls the word F until the frequency of the generated synthesized clock signal coincides with the input reference frequency, thereby implementing the frequency locking function of the all digital frequency locked loop FLL.
  • the all-digital phase-locked loop PLL includes: a digital frequency detector (FD) 402, a time-averaged frequency direct-cycle synthesized digitally controlled oscillator (TAF-DPS DCO) 404, a frequency divider 405, and Digital phase detector (PD) 406.
  • the all-digital phase-locked loop PLL is also Low pass filters (LPF) 403 and 407 may be included.
  • a digital frequency detector (FD) 402, a low pass filter (LPF) 403, a TAF-DPS DCO 404, and a frequency divider 405 are sequentially connected in series.
  • the frequency detector 406, the low pass filter 407, the TAF-DPS DCO 404, and the frequency divider 405 are sequentially connected in series.
  • the first input of the TAF-DPS frequency synthesizer receives the frequency control word F
  • the second input of the TAF-DPS frequency synthesizer receives the phase control word P, and controls the word F, according to the frequency
  • the phase control word P and the K basic clock signals generate a composite clock signal having a frequency f o and a phase p o .
  • An output of the TAF-DPS frequency synthesizer serves as an output of the all-digital phase-locked loop PLL and outputs the synthesized clock signal.
  • An input of the frequency divider 405 receives the synthesized clock signal, the synthesized clock signal has a frequency of f o and a phase of p o , and divides the synthesized clock signal to generate a feedback clock signal.
  • a first input of the digital phase detector (PD) 406 acts as an input to the all digital phase locked loop PLL and receives an input reference phase pr .
  • the second input of the digital frequency detector 402 receives the feedback clock signal output from the frequency divider 405, and the feedback clock signal has a feedback clock phase of p b .
  • the digital phase detector (PD) 406 is configured to detect a feedback clock phase p b of the feedback clock signal and generate or update a second based on the input reference phase p r and the feedback clock phase p b Control word P.
  • the digital phase detector (PD) 406 can be configured to compare the input reference phase p r and the feedback clock phase p b to obtain a second control signal related to the phase difference and according to the second The control signal generates a second control word P.
  • the second control signal and the second control word are both digital values.
  • the low pass filter 407 is configured to filter out high frequency components and noise in the second control word output by the digital phase detector 406, and use the filtered second control word as the phase control word P. Output to TAF-DPS DCO 404.
  • the digital phase detector 406 can directly output the second control word as the phase control word to the TAF-DPS DCO 404.
  • the TAF-DPS DCO 404 then generates a composite clock signal based on the frequency control word F and the phase control word P. Thus, a closed loop operation of the all digital phase locked loop PLL is formed.
  • the phase control word P may be added to the frequency control word F to obtain a new frequency control word F, thereby adjusting the corresponding output pulse by a single adjustment of the frequency control word F.
  • the period of the pulse is extended or shortened to achieve the effect of adjusting the phase of the output signal.
  • the input reference frequency can be compared with the frequency of the synthesized clock signal generated by the TAF-DPS DCO 404, but also the input reference phase can be compared with the TAF.
  • the phase of the synthesized clock signal generated by the -DPS DCO 404 is compared, and the frequency control word F and the phase control word P to be input to the TAF-DPS DCO 404 are gradually adjusted according to the comparison result until the frequency of the generated synthesized clock signal is The phase is consistent with the input reference frequency and phase, thereby implementing the phase lock function of the all-digital frequency-locked loop FLL.

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Abstract

一种数字控制振荡器，包括：分频器链，被配置以对输入时钟信号进行分频以产生K个基本时钟信号，并将该K个基本时钟信号馈送到时间平均频率直接周期合成TAF-DPS频率合成器，其中所述K个基本时钟信号的频率与周期均相同，并且相邻两个基本时钟信号之间的时间差为基本时间单元；和TAF-DPS频率合成器，被配置以根据基本时间单元和频率控制字确定第一周期和第二周期，并基于所述K个基本时钟信号生成合成时钟信号，其中所述合成时钟信号以交替方式使用第一周期和第二周期。本公开还提供一种全数字锁频环和全数字锁相环，包括上述的数字控制振荡器。在本公开中，TAF-DPS频率合成器完全由来自ASIC库的数字标准单元构成。然后，从该TAF-DPS频率合成器构成的全数字TAF-DPS DCO来构建锁频环和锁相环。

Description

数控振荡器和基于数控振荡器的全数字锁频环和锁相环
本申请要求2017年01月04日提交的申请号为201710004456.9且发明名称为“数控振荡器和基于数控振荡器的全数字锁频环和锁相环”的中国优先申请的优先权，通过引用将其全部内容并入于此。
技术领域
本公开涉及超大规模VLSI集成电路设计，更具体地说，涉及时间平均频率直接周期合成(TAF-DPS)数字控制振荡器和基于TAF-DPS数字控制振荡器的全数字锁频环路和锁相环路。
背景技术
在频率合成领域，存在三种主要技术：模拟直接频率合成、数字直接合成(DDS)和基于锁相环路(PLL)的间接频率合成。对于片上时钟生成，PLL是设计人员的首选，因为它易于与芯片上的其他电路集成。然而，在大多数PLL设计中，是以模拟数字混合信号风格来实现的，即需要大量的模拟电路，这主要是由于在设计中使用的振荡器(VCO)，其是模拟组件。
近年来，全数字锁相环路(ADPLL)已经成为锁相环路PLL系列中的常用成员。ADPLL的显著特征是其内部包含的数字振荡器，能够通过数字值控制该数字振荡器所产生的时钟信号的频率。全数字锁相环路(ADPLL)相对于传统锁相环路来讲，降低了模拟设计的复杂性，使其适用于数字处理。然而，这种ADPLL中的“数字振荡器”并不是数字电路，它仍包括大量的模拟电路，并且它被称为数字振荡器，仅仅是因为它的频率调谐是通过数字控制来实现的。
因此，需要一种全数字锁相环路和锁频环路。
发明内容
本公开的另外方面和优点部分将在后面的描述中阐述，还有部分可从描述中明显地看出，或者可以在本公开的实践中得到。
在本公开中，时间平均频率直接周期合成(TAF-DPS,Time-Average-Frequency Direct Period Synthesis)被用作全数字频率振荡器。 因此，使用诸如其数字控制振荡器(DCO)的振荡器来构造全数字锁频环路和锁相环路。
要在本公开中解决的关键问题是：使用纯数字电路来构造锁频环路(FLL)和锁相环路(PLL)。换句话说，使用来自任何给定ASIC库的标准单元来设计FLL和PLL。因此，在FLL和PLL中不需要模拟电路。此外，设计方法是Verilog编码→模拟→合成→实际电路。无需晶体管级定制电路设计技能。
在本公开中，TAF-DPS合成器完全由来自ASIC库的数字标准单元构成。然后，从该全数字TAF-DPS DCO来构建锁频环路(FLL)。该环路中使用的频率检测器是数字型检测器。因此，整个环路以数字方式构造，其中环路响应时间以DCO周期为基准是完全可计算的。设计目标是使环路延迟尽可能小，以便能够尽可能快地跟踪(跟随)FLL的输入频率。TAF-DPS还具有相位合成能力，这使得能够从该DCO构建PLL。
由于数字电路对环境干扰更加鲁棒，因此设计具有更高的工作可靠性。
本公开提供一种数字控制振荡器，包括：分频器链，被配置以对输入时钟信号进行分频以产生K个基本时钟信号，其中所述K个基本时钟信号的频率与周期均相同，并且相邻两个基本时钟信号之间的时间差为基本时间单元；和TAF-DPS频率合成器，被配置以从所述分频器链接收所述K个基本时钟信号，并根据基本时间单元和频率控制字确定第一周期和第二周期，并基于所述K个基本时钟信号生成合成时钟信号，其中所述合成时钟信号以交替方式使用第一周期和第二周期。
在一个实施例中，所述合成时钟信号的频率和周期通过如下公式计算：1/f＝T＝F*Δ，其中F为所述频率控制字，Δ为所述基本时间单元，f是所述合成时钟信号的频率，T是所述合成时钟信号的周期。
在一个实施例中，所述频率控制字等于I+r，其中I是整数，0≤r<1，其中，所述第一周期等于I*△，所述第二周期等于(I+1)*△，r是第二周期的发生可能性，所述合成时钟信号的周期等于(1-r)*第一周期+r*第二周期。
在一个实施例中，基本时间单元的值△＝Tdiv/K＝1/(K·fdiv)，fdiv＝fi/K，其中，Tdiv是K个基本时钟信号的周期，fdiv是K个基本时钟信号的频率，fi是分频器链的输入时钟信号的频率。
在一个实施例中，所述频率合成器为TAF-DPS频率合成器。
本公开还提供一种全数字锁频环，包括：上述的数字控制振荡器；分频器，被配置为：对所述数字控制振荡器输出的所述合成时钟信号进行分频，以得到反馈时钟信号，其中，分频比为N，N为大于等于1的整数；以及数字型频率检测器，被配置为：检测所述反馈时钟信号的反馈时钟频率，对输入参考频率与所述反馈时钟频率进行比较，并根据频率差更新所述频率控制字。
在一个实施例中，所述全数字锁频环还包括：低通滤波器，被配置以滤除所述数字型频率检测器的输出信号中的高频分量和噪声，并将滤波后的信号作为更新后的频率控制字输出到所述数字控制振荡器。
在一个实施例中，所述全数字锁频环中的器件均为数字器件。
本公开还提供一种全数字锁相环，包括：上述的数字控制振荡器；分频器，被配置为：对所述数字控制振荡器输出的所述合成时钟信号进行分频，以得到反馈时钟信号，其中，分频比为N，N为大于等于1的整数；数字型频率检测器，被配置为：检测所述反馈时钟信号的反馈时钟频率，对输入参考频率与所述反馈时钟频率进行比较，并根据频率差更新所述频率控制字；以及数字型相位检测器，被配置为：检测所述反馈时钟信号的反馈时钟相位，对输入参考相位与所述反馈时钟相位进行比较，并根据相位差生成相位控制字，其中，所述数字控制振荡器还接收所述相位控制字，并将所述相位控制字与所述更新的频率控制字相加作为更新的频率控制字。
在一个实施例中，所述全数字锁相环还包括：第一低通滤波器，被配置以滤除所述数字型频率检测器的输出信号中的高频分量和噪声，并将滤波后的信号作为更新后的频率控制字输出到所述数字控制振荡器。
在一个实施例中，所述全数字锁相环还包括：第二低通滤波器，被配置以滤除所述数字型相位检测器的输出信号中的高频分量和噪声，并将滤波后的信号作为相位控制字输出到数字控制振荡器。
在一个实施例中，所述全数字锁相环中的器件均为数字器件。
附图说明
通过结合附图对本公开的优选实施例进行详细描述，本公开的上述和其他目的、特性和优点将会变得更加清楚，其中相同的标号指定相同结构的单元，并且在其中：
图1示意性地示出了时间平均频率直接周期合成(TAF-DPS)时钟发生器的工作原理。
图2是图1所示的TAF-DPS频率合成器的示例性电路框图。
图3是图2所示的TAF-DPS频率合成器的示例性电路框图的示例性电路图。
图4示出了TAF-DPS时钟发生器的相位调整机制。
图5示出了根据本公开实施例的使用TAF-DPS作为其DCO(右上)的全数字锁频环FLL和使用TAF-DPS作为其DCO(右下)的全数字锁相环PLL。
具体实施方式
下面将参照示出本公开实施例的附图充分描述本公开。然而，本公开可以以许多不同的形式实现，而不应当认为限于这里所述的实施例。相反，提供这些实施例以便使本公开透彻且完整，并且将向本领域技术人员充分表达本公开的范围。在附图中，为了清楚起见放大了组件。
时间平均频率直接周期合成(TAF-DPS,Time-Average-Frequency Direct Period Synthesis)的频率合成架构基于新的时间平均频率概念。TAF-DPS的显著特征包括小频率粒度(也称为任意频率生成)和快速频率切换(也称为瞬时频率切换)。更重要的是，其频率切换速度是可量化的。换句话说，从接收频率控制字更新的时刻到频率切换的时刻的响应时间可以根据时钟周期来计算。这些特性使TAF-DPS成为用作数字控制振荡器(DCO)的理想电路块。
图1示意性地示出了时间平均频率直接周期合成(TAF-DPS)时钟发生器的工作原理。
如图1所示，TAF-DPS时钟发生器包括TAF-DPS频率合成器110，被配置以根据基本时间单元和频率控制字确定第一周期和第二周期，并基于所述K个基本时钟信号生成合成时钟信号，其中所述合成时钟信号以交替方式使用第一周期和第二周期。
如图1所示，TAF-DPS频率合成器110具有第一和第二输入参数，所述第一输入参数为基本时间单元Δ，第二输入参数为频率控制字F＝I+r，其中I是整数，r是分数，并且0≤r<1。TAF-DPS频率合成器110的输出端被配置为输出合成时钟信号。该合成时钟信号是合成的时间平均频率时钟信号。通常，根据用户输入的目标时钟频率确定频率控制字F，并且根据电路设计 的需要而设计基本时间单元Δ。
具体地，TAF-DPS频率合成器110根据基本时间单元Δ和频率控制字F，确定具有不同时间长度的第一周期和第二周期。例如，第一周期TA＝I*△和第二周期TB＝(I+1)*△。然而，本专利不限于此，可以以其他方式确定第一周期和第二周期。
然后，TAF-DPS频率合成器110通过使用第一周期TA和第二周期TB确定合成周期，并且以该合成周期为时钟周期生成合成时钟信号，然后通过其输出端输出该合成时钟信号。例如，可以基于第一周期TA和第二周期TB按照加权的方式计算合成周期TTAF，第一周期TA的权重为第一权重WA，第二周期的权重TB为第二权重WB，则TTAF＝WA*TA+WB*TB。例如，第一周期TA以及第二周期TB发生的可能性可以由分数r的值控制，换言之第一权重WA和第二权重WB可以由分数r的值决定，第一权重WA可以为(1-r)，第二权重WB可以为r，在此情况下，TTAF＝(1-r)*TA+r*TB。在F为整数(即r为零)的情况下，第一权重WA为1，第二权重WB为0，并且合成周期TTAF＝TA。
在确定了合成周期TTAF之后，TAF-DPS频率合成器110可以通过1/fTAF＝TTAF＝F*Δ来计算合成频率，即fTAF＝1/(F*Δ)。给定足够的资源(即，给予频率控制字F中的I和r足够的位的数目)，则TAF-DPS频率合成器110可以生成任何频率(任意频率生成)。此外，由于直接根据输入的基本时间单元Δ和频率控制字F生成每个单独的脉冲，所以可以立即改变输出频率/周期，也即可以实现快速频率切换。
图2是图1所示的TAF-DPS频率合成器的示例性电路框图。可以利用图2示出的飞加法器(Flying-Adder)频率合成架构作为图1所示的TAF-DPS频率合成器的全数字电路实现。
如图2所示，TAF-DPS频率合成器包括第一多路选择器210、第一选择控制电路220、第二多路选择器230、第二选择控制电路240、第三多路选择器250、输出电路260。
所述第一选择控制器220根据第一频率控制字产生第一选择控制信号，所述第二选择控制器240根据第二频率控制字产生第二选择控制信号，所述第一频率控制字和第二频率控制字是根据所述频率控制字F确定的。可选地，所述第一频率控制字与所述频率控制字F相等，所述第二频率控制字是所述频率控制字F的一半。
所述第一选择控制器220向所述第一多路选择器210输出所述第一选择控制信号，所述第二选择控制器240向所述第二多路选择器230输出所述第二选择控制信号。
所述第一多路选择器210接收多个基本时钟信号，并且根据所述第一选择控制信号选择所述多个基本时钟信号之一作为第一选择时钟信号；所述第二多路选择器230接收所述多个基本时钟信号，并且根据所述第二选择控制信号选择所述多个基本时钟信号之一作为第二选择时钟信号。
接下来，所述第三多路选择器250选择所述第一选择时钟信号和所述第二选择时钟信号之一作为选择时钟信号。
最后，所述输出电路260基于所述选择时钟信号产生合成时钟信号CLK1和中间时钟信号CLK2，所述合成时钟信号CLK1和所述中间时钟信号CLK2的相位相差180°。作为示例，所述多个基本时钟信号可以为K个基本时钟信号，K为大于1的整数，所述K个基本时钟信号中每个基本时钟信号的频率为fdiv且周期为Tdiv，并且所述K个基本时钟信号依次时间滞后Tdiv/K且相位滞后360°/K。相邻两个基本时钟信号之间的时间差即为基本时间单元Δ＝Tdiv/K＝1/(K·fdiv)。
根据本公开实施例，TAF-DPS频率合成器根据所述第一频率控制字和第二频率控制字控制其输出的合成时钟信号的频率。
图3是图2所示的TAF-DPS频率合成器的示例性电路框图的示例性电路图。
所述第一选择控制器220具有第一输入端和第二输入端，所述第一输入端接收第一频率控制字，所述第一频率控制字的取值等于所述频率控制字F的取值相同；所述第二输入端接收中间时钟信号CLK2。所述第一选择控制器220根据所述第一频率控制字F和所述中间时钟信号CLK2生成所述第一选择控制信号，并且根据所述第一频率控制字F和所述中间时钟信号CLK2生成控制字调整信号。所述第一选择控制器220具有第一输出端和第二输出端，所述第一输出端输出所述第一选择控制信号，所述第二输出端输出所述控制字调整信号。
所述第二选择控制器240具有第一输入端、第二输入端、第三输入端和第四输入端，所述第一输入端接收第二频率控制字，所述第二频率控制字的取值F/2为所述频率控制字F的取值的一半，所述第二输入端接收所述合成 时钟信号CLK1，所述第三输入端接收所述中间时钟信号CLK2，所述第四输入端接收所述控制字调整信号。所述第一选择控制器220根据所述第二频率控制字F/2、所述合成时钟信号CLK1、所述中间时钟信号CLK2和所述控制字调整信号，生成所述第二选择控制信号。
所述第一选择控制电路220包括第一加法器、第一寄存器和第二寄存器。所述第一加法器的第一输入端作为所述第一选择控制电路220的第一输入端，以接收所述第一频率控制字，所述第一加法器的第二输入端接收所述控制字调整信号。所述第一寄存器的第一输入端连接所述第一加法器的输出端，所述第一寄存器的第二输入端接收所述中间时钟信号CLK2，所述第一寄存器的输出端作为所述第一选择控制器220的第二输出端并且输出所述控制字调整信号；所述第二寄存器的第一输入端连接所述第一寄存器的输出端，所述第二寄存器的第二输入端接收所述中间时钟信号CLK2，并且所述第二寄存器的输出端作为所述第一选择控制器220的第一输出端并且输出所述第一选择控制信号。
所述第二选择控制器240包括第二加法器、第三寄存器和第四寄存器。所述第二加法器的两个输入端分别作为所述第二选择控制器240的第一输入端和第四输入端，以接收所述第二频率控制字和所述控制字调整信号。所述第三寄存器的第一输入端连接所述第二加法器的输出端，所述第三寄存器的第二输入端接收所述中间时钟信号CLK2，所述第四寄存器的第一输入端连接所述第三寄存器的输出端，所述第四寄存器的第二输入端接收所述合成时钟信号CLK1，并且所述第四寄存器的输出端作为所述第二选择控制器240的输出端并且输出所述第二选择控制信号。
如图3所示，TAF-DPS频率合成器根据所述第一频率控制字F和第二频率控制字F/2控制其输出的合成时钟信号的频率，即TAF-DPS频率合成器输出的合成时钟信号的频率fTAF满足：1/fTAF＝TTAF＝F*Δ。如上所述，频率控制字F＝I+r，其中I是整数，r是分数，并且0≤r<1。当在控制字F中仅使用整数时(即r＝0时)，TAF-DPS频率合成器输出单一频率的信号。当控制字F包含小数部分时(即0<r<1时)，TAF-DPS频率合成器在其输出脉冲信号中使用了时间平均频率概念。TAF-DPS频率合成器可以用作图1中的电路块110。信号F用作图1中的频率控制字F。输出的合成时钟信号用作图1中的合成时钟信号。
图4示出了TAF-DPS时钟发生器的相位合成原理的示意图。
如图1所示的TAF-DPS时钟发生器，其直接周期合成能力不仅可用于合成频率/周期，而且可用于调整其输出的合成时钟信号的相位。图4示出了这种相位调整机制，通过给定的频率控制字F的单次变化来调整对应脉冲的周期，具体地延长或缩短对应脉冲的周期，这将导致合成时钟信号的相位提前或后退。
如图4所示，通过将调整值加入到频率控制字F，从而输出脉冲串将具有延长或缩短的周期。此功能将用于本公开实施例中用于构建全数字PLL。
根据本公开实施例，可以利用TAF-DPS构造集成电路(例如超大规模VLSI集成电路)中的全数字锁频环路和锁相环路。
图5示出了根据本公开实施例的使用TAF-DPS作为其DCO(右上)的全数字锁频环FLL和使用TAF-DPS作为其DCO(右下)的全数字锁相环PLL。
下面将具体描述根据本公开实施例的全数字锁频环FLL和全数字锁相环PLL的操作。
如图5右上图所示，全数字锁频环FLL包括：数字型频率检测器(FD)402、时间平均频率直接周期合成数字控制振荡器(TAF-DPS DCO)404和分频器405。可选地，全数字锁频环FLL还可以包括低通滤波器(LPF)403。数字型频率检测器(FD)402、低通滤波器403(LPF)、时间平均频率直接周期合成数字控制振荡器(TAF-DPS DCO)404和分频器405顺次串联，形成环路。
所述TAF-DPS DCO 404由分频器链401和如图2所示的TAF-DPS频率合成器构成。
所述分频器链401的输入端接收输入时钟信号，该输入时钟信号的频率为fi。所述分频器链401被配置为对所述输入时钟信号进行分频以产生K个基本时钟信号，并将该K个基本时钟信号馈送到TAF-DPS频率合成器，其中，K为大于1的整数，所述K个基本时钟信号中每个基本时钟信号的频率为fdiv且周期为Tdiv，并且所述K个基本时钟信号依次时间滞后Tdiv/K且相位滞后360/K。相邻两个基本时钟信号之间的时间差即为基本时间单元Δ＝Tdiv/K＝1/(K·fdiv)。
所述TAF-DPS频率合成器的输入端接收低通滤波器(LPF)403输出的频率控制字F，并且根据所接收到的所述频率控制字F与所述K个基本时钟 信号产生合成时钟信号，所述合成时钟信号的频率为fo。所述TAF-DPS频率合成器的输出端作为所述全数字锁频环FLL的输出端，并且输出所述合成时钟信号。
所述分频器405的输入端接收所述合成时钟信号，并且对所述合成时钟信号进行分频以产生反馈时钟信号。所述分频器405的输出端输出所述反馈时钟信号，所述反馈时钟信号的反馈时钟频率为fb＝fo/N，其中N为分频器405的分频比并且N为大于1的整数。
所述数字型频率检测器402的第一输入端作为所述全数字锁频环FLL的输入端，并且接收输入参考频率fr。所述数字型频率检测器402的第二输入端接收从所述分频器405输出的反馈时钟信号，该反馈时钟信号的频率为fb。所述数字型频率检测器402被配置为检测所述反馈时钟信号的反馈时钟频率fb，并且基于所述输入参考频率fr和所述反馈时钟频率fb，产生或更新频率控制字F。例如，所述数字型频率检测器402可以被配置为将所述输入参考频率fr和所述反馈时钟频率fb进行比较，得到与频率差相关的第一控制信号并根据第一控制信号生成第一控制字F。其中，第一控制信号和第一控制字都是数字值。
可选地，低通滤波器403被配置以滤除所述数字型频率检测器402输出的第一控制字中的高频分量和噪声，并将滤波后的第一控制字作为频率控制字输出到TAF-DPS DCO 404。在不存在低通滤波器403的情况下，所述数字型频率检测器402可以直接将所述第一控制字作为所述频率控制字输出到TAF-DPS DCO 404。然后，所述TAF-DPS DCO 404再基于所述频率控制字F产生合成时钟信号。由此，形成了全数字锁频环FLL的闭环操作。
根据本公开实施例，在所述全数字锁频环FLL中，将输入参考频率与由TAF-DPS DCO 404生成的合成时钟信号的频率进行比较，并且根据比较结果逐步地调整将要输入到TAF-DPS DCO 404的频率控制字F，直至所生成的合成时钟信号的频率与所述输入参考频率一致，从而实现全数字锁频环FLL的锁频功能。
在图5右下图中，与图5右上图中相同的部件采用了相同的标记。
如图5右下图所示，全数字锁相环PLL包括：数字型频率检测器(FD)402、时间平均频率直接周期合成数字控制振荡器(TAF-DPS DCO)404、分频器405和数字型相位检测器(PD)406。可选地，全数字锁相环PLL还 可以包括低通滤波器(LPF)403和407。数字型频率检测器(FD)402、低通滤波器(LPF)403、TAF-DPS DCO 404和分频器405顺次串联。频率检测器406、低通滤波器407、TAF-DPS DCO 404和分频器405顺次串联。
与图5右上图相同的部件其功能和原理与图5右上图的相同，在此不再赘述。
所述TAF-DPS频率合成器的第一输入端接收所述频率控制字F，所述TAF-DPS频率合成器的第二输入端接收相位控制字P，并且根据所述频率控制字F、所述相位控制字P与所述K个基本时钟信号产生合成时钟信号，所述合成时钟信号的频率为fo且相位为po。所述TAF-DPS频率合成器的输出端作为所述全数字锁相环PLL的输出端，并且输出所述合成时钟信号。
所述分频器405的输入端接收所述合成时钟信号，所述合成时钟信号的频率为fo且相位为po，并且对所述合成时钟信号进行分频以产生反馈时钟信号。所述分频器405的输出端输出所述反馈时钟信号，所述反馈时钟信号的反馈时钟频率为fb＝fo/N，并且所述反馈时钟信号的反馈时钟相位为pb＝po/N，其中N为分频器405的分频比并且N为大于1的整数。
所述数字型相位检测器(PD)406的第一输入端作为所述全数字锁相环PLL的输入端，并且接收输入参考相位pr。所述数字型频率检测器402的第二输入端接收从所述分频器405输出的反馈时钟信号，该反馈时钟信号的反馈时钟相位为pb。所述数字型相位检测器(PD)406被配置为检测所述反馈时钟信号的反馈时钟相位pb，并且基于所述输入参考相位pr和所述反馈时钟相位pb，产生或更新第二控制字P。例如，所述数字型相位检测器(PD)406可以被配置为将所述输入参考相位pr和所述反馈时钟相位pb进行比较，得到与相位差相关的第二控制信号并根据第二控制信号生成第二控制字P。其中，第二控制信号和第二控制字都是数字值。
可选地，低通滤波器407被配置以滤除所述数字型相位检测器406输出的第二控制字中的高频分量和噪声，并将滤波后的第二控制字作为相位控制字P输出到TAF-DPS DCO 404。在不存在低通滤波器407的情况下，所述数字型相位检测器406可以直接将所述第二控制字作为所述相位控制字输出到TAF-DPS DCO 404。然后，所述TAF-DPS DCO 404再基于所述频率控制字F和所述相位控制字P产生合成时钟信号。由此，形成了全数字锁相环PLL的闭环操作。
根据本公开实施例，如上所述，可以将所述相位控制字P与所述频率控制字F相加得到新的频率控制字F，从而通过频率控制字F的单次调整来调整对应输出脉冲的周期，从而使得对应脉冲的周期延长或缩短，以达到调整输出信号的相位的效果。
根据本公开实施例，在所述全数字锁相环PLL中，不仅可以将输入参考频率与由TAF-DPS DCO 404生成的合成时钟信号的频率进行比较，而且还可以将输入参考相位与由TAF-DPS DCO 404生成的合成时钟信号的相位进行比较，并且根据比较结果逐步地调整将要输入到TAF-DPS DCO 404的频率控制字F和相位控制字P，直至所生成的合成时钟信号的频率和相位均与所述输入参考频率和相位一致，从而实现全数字锁频环FLL的锁相功能。
除非另有定义，这里使用的所有术语(包括技术和科学术语)具有与本公开所属领域的普通技术人员共同理解的相同含义。还应当理解，诸如在通常字典里定义的那些术语应当被解释为具有与它们在相关技术的上下文中的含义相一致的含义，而不应用理想化或极度形式化的意义来解释，除非这里明确地这样定义。
上面是对本公开的说明，而不应被认为是对其的限制。尽管描述了本公开的若干示例性实施例，但本领域技术人员将容易地理解，在不背离本公开的新颖教学和优点的前提下可以对示例性实施例进行许多修改。因此，所有这些修改都意图包含在权利要求书所限定的本公开范围内。应当理解，上面是对本公开的说明，而不应被认为是限于所公开的特定实施例，并且对所公开的实施例以及其他实施例的修改意图包含在所附权利要求书的范围内。本公开由权利要求书及其等效物限定。

Claims (12)

  1. 一种数字控制振荡器，包括：
    分频器链，被配置以对输入时钟信号进行分频以产生K个基本时钟信号，其中所述K个基本时钟信号的频率与周期均相同，并且相邻两个基本时钟信号之间的时间差为基本时间单元；和
    频率合成器，被配置以从所述分频器链接收所述K个基本时钟信号，并根据基本时间单元和频率控制字确定第一周期和第二周期，并基于所述K个基本时钟信号生成合成时钟信号，其中所述合成时钟信号以交替方式使用第一周期和第二周期。
  2. 如权利要求1所述的数字控制振荡器，其中，所述合成时钟信号的频率和周期通过如下公式计算：
    1/f＝T＝F*Δ，
    其中F为所述频率控制字，Δ为所述基本时间单元，f是所述合成时钟信号的频率，T是所述合成时钟信号的周期。
  3. 如权利要求2所述的数字控制振荡器，其中，所述频率控制字等于I+r，其中I是整数，0≤r<1，
    其中，所述第一周期等于I*△，所述第二周期等于(I+1)*△，r是第二周期的发生可能性，
    所述合成时钟信号的周期等于(1-r)*第一周期+r*第二周期。
  4. 如权利要求1所述的数字控制振荡器，其中，基本时间单元的值△＝Tdiv/K＝1/(K·fdiv)，fdiv＝fi/K，其中，Tdiv是K个基本时钟信号的周期，fdiv是K个基本时钟信号的频率，fi是分频器链的输入时钟信号的频率。
  5. 如权利要求1所述的数字控制振荡器，其中，所述频率合成器为TAF-DPS频率合成器。
  6. 一种全数字锁频环，包括：
    如权利要求1-5的任何一项所述的数字控制振荡器；
    分频器，被配置为：对所述数字控制振荡器输出的所述合成时钟信号进行分频，以得到反馈时钟信号，其中，分频比为N，N为大于等于1的整数；以及
    数字型频率检测器，被配置为：检测所述反馈时钟信号的反馈时钟频率， 对输入参考频率与所述反馈时钟频率进行比较，并根据频率差更新所述频率控制字。
  7. 如权利要求6所述的全数字锁频环，还包括：
    低通滤波器，被配置以滤除所述数字型频率检测器的输出信号中的高频分量和噪声，并将滤波后的信号作为更新后的频率控制字输出到所述数字控制振荡器。
  8. 如权利要求6所述的全数字锁频环，其中，所述全数字锁频环中的器件均为数字器件。
  9. 一种全数字锁相环，包括：
    如权利要求1-5的任何一项所述的数字控制振荡器；
    分频器，被配置为：对所述数字控制振荡器输出的所述合成时钟信号进行分频，以得到反馈时钟信号，其中，分频比为N，N为大于等于1的整数；
    数字型频率检测器，被配置为：检测所述反馈时钟信号的反馈时钟频率，对输入参考频率与所述反馈时钟频率进行比较，并根据频率差更新所述频率控制字；以及数字型相位检测器，被配置为：检测所述反馈时钟信号的反馈时钟相位，对输入参考相位与所述反馈时钟相位进行比较，并根据相位差生成相位控制字，
    其中，所述数字控制振荡器还接收所述相位控制字，并将所述相位控制字与所述更新的频率控制字相加作为更新的频率控制字。
  10. 如权利要求9所述的全数字锁相环，还包括：
    第一低通滤波器，被配置以滤除所述数字型频率检测器的输出信号中的高频分量和噪声，并将滤波后的信号作为更新后的频率控制字输出到所述数字控制振荡器。
  11. 如权利要求9所述的全数字锁相环，还包括：
    第二低通滤波器，被配置以滤除所述数字型相位检测器的输出信号中的高频分量和噪声，并将滤波后的信号作为相位控制字输出到数字控制振荡器。
  12. 如权利要求9所述的全数字锁相环，其中，所述全数字锁相环中的器件为数字器件。
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US10715154B2 (en) 2020-07-14
EP3567725A1 (en) 2019-11-13
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CN108270437B (zh) 2023-04-14
US20190123749A1 (en) 2019-04-25

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