WO2017185856A1 - 一种谐振功率变换器及其频率跟踪方法 - Google Patents
一种谐振功率变换器及其频率跟踪方法 Download PDFInfo
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- WO2017185856A1 WO2017185856A1 PCT/CN2017/073988 CN2017073988W WO2017185856A1 WO 2017185856 A1 WO2017185856 A1 WO 2017185856A1 CN 2017073988 W CN2017073988 W CN 2017073988W WO 2017185856 A1 WO2017185856 A1 WO 2017185856A1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/01—Resonant DC/DC converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0025—Arrangements for modifying reference values, feedback values or error values in the control loop of a converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33571—Half-bridge at primary side of an isolation transformer
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0009—Devices or circuits for detecting current in a converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
- H02M1/007—Plural converter units in cascade
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0095—Hybrid converter topologies, e.g. NPC mixed with flying capacitor, thyristor converter mixed with MMC or charge pump mixed with buck
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33573—Full-bridge at primary side of an isolation transformer
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/4815—Resonant converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/483—Converters with outputs that each can have more than two voltages levels
- H02M7/487—Neutral point clamped inverters
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- Embodiments of the present invention relate to the field of communications, and in particular, to a resonant power converter and a frequency tracking method thereof.
- the resonant power converter is a power electronic converter based on soft switching technology.
- soft switching technology With the birth of high frequency switching devices, resonant power converters are moving toward high frequency, integration and modularization.
- the soft switch is a switching process using soft switching technology.
- the ideal soft switching process is that the current or voltage first drops to zero, and the current or voltage gradually rises to the rated value, so the switching loss is approximately zero, so that the power converter can be realized. High frequency.
- Commonly used soft switches include: ZVS (Zero Voltage Switching), ZCS (Zero Current Switching), ZCT (Zero Current Transition), ZCT (Zero Voltage Transition), etc. .
- LLC that is, a series circuit composed of two inductors L and one capacitor C in series
- DC Direct Current
- the DC characteristic curve of the LLC resonant power converter is shown in Figure 1, where Q in Figure 1 is the quality factor of the LLC resonant power converter.
- the LLC resonant power converter may operate at the resonant frequency point, the ZVS region, or the ZCS region.
- the LLC resonant power converter operates at the resonant frequency point with the highest efficiency, but in actual operation, the LLC resonant power converter may operate in different regions due to changes in parameters such as load and voltage.
- the LLC resonant power converter should be guaranteed to operate at the resonant frequency point or the first region in Figure 1 in all load ranges, generally not working in the second region, and not working in the third region. region.
- the LLC resonant power converter Because if the LLC resonant power converter operates in the second region, when the load becomes large, the LLC resonant power converter may enter the third region from the second region, and the monotonicity of the voltage gain changes (ie, under a certain load) As the frequency increases, the voltage gain decreases, and the voltage gain increases as the frequency increases under a certain load. There is a hidden danger of the bomber. Therefore, the LLC resonant power converter needs to judge whether the LLC resonant power converter operates at the resonance frequency point, the first region, the second region or the third region by judging the resonance state of the LLC resonant power converter, thereby adjusting the resonance according to the resonance state. The switching frequency of the switching tube in the power converter.
- the existing resonant power converter mostly determines the resonance state of the resonant power converter by detecting the phase difference between the primary current flowing into the resonant network and the square wave voltage applied to the resonant network.
- the resonance state of the resonant power converter cannot be judged by the existing method.
- the embodiment of the invention provides a resonant power converter and a frequency tracking method thereof, which can determine the resonance state of the resonant power converter by sampling the secondary current, thereby controlling the frequency of the driving signal to achieve the frequency tracking resonant power of the driving signal.
- the purpose of the resonant frequency of the converter is to determine the resonance state of the resonant power converter by sampling the secondary current, thereby controlling the frequency of the driving signal to achieve the frequency tracking resonant power of the driving signal.
- an embodiment of the present invention provides a resonant power converter including an inverter branch, a resonant branch connected to the inverter branch, a transformer connected to the resonant branch, and a rectifying and filtering branch connected to the transformer.
- the primary end of the transformer is connected to the resonant branch, and the secondary end of the transformer is connected to the rectifying and filtering branch;
- the resonant power converter further includes: a detecting branch connected to the secondary end of the transformer and the rectifying and filtering branch, a judging branch connected to the detecting branch and a control branch connected to the judging branch and the inverting branch;
- the detecting branch is configured to obtain a secondary current of the transformer, generate a pulse signal corresponding to the secondary current according to the secondary current, and send a pulse signal corresponding to the secondary current to the determining branch;
- control branch for generating a driving signal, and transmitting a driving signal to the inverter branch and the determining branch, wherein the driving signal is used to drive the inverter branch;
- the determining branch is configured to receive a pulse signal corresponding to the secondary current sent by the detecting branch and a driving signal sent by the control branch, and generate and send the first information to the control branch according to the pulse signal and the driving signal corresponding to the secondary current
- the first information is used to indicate the resonant state of the resonant power converter
- the control branch is further configured to receive the first information sent by the determining branch, and control the frequency of the driving signal according to the first information.
- the determining branch can receive the pulse signal corresponding to the secondary current sent by the detecting branch, and generate the indicating resonant power according to the pulse signal and the driving signal corresponding to the secondary current.
- the first information of the resonant state of the converter is such that the control branch controls the frequency of the driving signal according to the first information, and the resonant state of the resonant power converter is determined by sampling the secondary current, and the frequency of the driving signal is controlled. The purpose of tracking the resonant frequency of the resonant power converter.
- the resonant power converter further includes:
- a sampling circuit connected to the detection branch, the secondary side of the transformer, and the rectifying and filtering branch is used to sample the secondary current.
- the sampling circuit is specifically configured to sample the secondary current through the Hall effect, or sample the secondary current by sampling the voltage across the diode in the rectifier branch.
- the sampling circuit specifically includes: a comparator, a first resistor, a second resistor, a third resistor, and a capacitor;
- the output end of the comparator is connected to one end of the third resistor, one end of the capacitor is connected to the other end of the third resistor, and the other end of the third resistor is connected to the detecting branch, and the positive input end of the comparator and the first resistor are One end is connected, the negative input end of the comparator is connected to one end of the second resistor, and the other end of the first resistor is connected to the transformer and the rectifying and filtering branch, and the other end of the second resistor and the other end of the capacitor Ground.
- the sampling circuit specifically includes: a comparator, a first resistor, a second resistor, a third resistor, a fourth resistor, a fifth resistor, and a sixth resistor;
- the output end of the comparator is connected to the detection branch
- the negative input end of the comparator is connected to one end of the first resistor
- the other end of the first resistor is connected to one end of the second resistor
- the other end of the second resistor is connected to the transformer and
- the rectifying and filtering branches are connected, one end of the third resistor is connected to the output end of the comparator, the other end of the third resistor is connected to the negative input end of the comparator, and the positive input end of the comparator is connected to one end of the fourth resistor,
- the other end of the fourth resistor is connected to one end of the fifth resistor, the other end of the fifth resistor is connected to the rectifying and filtering branch, the positive input end of the comparator is connected to one end of the sixth resistor, and the other end of the sixth resistor is grounded.
- the inverter branch is any one of a half bridge inverter circuit structure, a full bridge inverter circuit structure, and a three-level inverter circuit structure;
- the resonant branch is an LLC resonant circuit structure composed of a series combination of a magnetizing inductance, a resonant inductor and a resonant capacitor;
- the rectification filter branch is a half-wave rectification filter circuit structure or a full-wave rectification filter circuit structure.
- an embodiment of the present invention provides a frequency tracking method for a resonant power converter, which is applied to a resonant power converter according to any one of the first aspects, the frequency tracking method of the resonant power converter includes:
- the resonant power converter acquires a pulse signal and a driving signal corresponding to the secondary current; secondly, the resonant power converter generates a first indicating the resonant state of the resonant power converter according to the pulse signal and the driving signal corresponding to the secondary current. Information; finally, the resonant power converter controls the frequency of the drive signal based on the first information.
- the resonant power converter can generate the first information for indicating the resonant state of the resonant power converter according to the pulse signal and the driving signal corresponding to the secondary current, Therefore, according to the first information, the frequency of the driving signal is controlled, and the resonance state of the resonant power converter is determined by sampling the secondary current, and the frequency of the driving signal is controlled to track the resonant frequency of the resonant power converter.
- the method for the resonant power converter to obtain the pulse signal corresponding to the secondary current includes:
- the resonant power converter first acquires the secondary current, and then generates a pulse signal corresponding to the secondary current according to the secondary current.
- the method for generating the first information by the resonant power converter according to the pulse signal and the driving signal corresponding to the secondary current includes:
- the resonant power converter confirms that the rising edge of the pulse signal corresponding to the secondary current is synchronized with the rising edge of the driving signal, and the falling edge of the pulse signal corresponding to the secondary current is synchronized with the falling edge of the driving signal; and generates the first information, first The information is used to indicate that the resonant power converter is operating at the resonant frequency point.
- the resonant power converter according to the first information, the method for controlling the frequency of the driving signal includes:
- the resonant power converter maintains the frequency of the drive signal unchanged according to the first information.
- the frequency tracking method of the resonant power converter provided by the embodiment of the present invention, if the rising edge of the pulse signal corresponding to the secondary current is synchronized with the rising edge of the driving signal, and the pulse signal corresponding to the secondary current The falling edge of the number is synchronized with the falling edge of the drive signal, indicating that the resonant power converter operates at the resonant frequency point. At this time, it is not necessary to adjust the frequency of the driving signal, and it is only necessary to maintain the frequency of the driving signal.
- the method for generating the first information by the resonant power converter according to the pulse signal and the driving signal corresponding to the secondary current includes:
- the resonant power converter confirms that the rising edge of the pulse signal corresponding to the secondary current is synchronized with the rising edge of the driving signal, and the falling edge of the pulse signal corresponding to the secondary current lags behind the falling edge of the driving signal; and generates the first information, first The information is used to indicate that the resonant power converter is operating in the first region.
- the resonant power converter according to the first information, the method for controlling the frequency of the driving signal includes:
- the resonant power converter reduces the frequency of the drive signal based on the first information.
- the frequency tracking method of the resonant power converter provided by the embodiment of the present invention, if the rising edge of the pulse signal corresponding to the secondary current is synchronized with the rising edge of the driving signal, and the falling edge of the pulse signal corresponding to the secondary current lags behind the driving signal The falling edge indicates that the resonant power converter operates in the first region, in which case the frequency of the drive signal needs to be reduced so that the resonant power converter operates at the resonant frequency point.
- the method for generating the first information by the resonant power converter according to the pulse signal and the driving signal corresponding to the secondary current includes:
- the resonant power converter confirms that the rising edge of the pulse signal corresponding to the secondary current is synchronized with the rising edge of the driving signal, and the falling edge of the pulse signal corresponding to the secondary current leads the falling edge of the driving signal; and generates the first information, first The information is used to indicate that the resonant power converter is operating in the second region.
- the resonant power converter according to the first information, the method for controlling the frequency of the driving signal includes:
- the resonant power converter increases the frequency of the drive signal based on the first information.
- the frequency tracking method of the resonant power converter provided by the embodiment of the present invention, if the rising edge of the pulse signal corresponding to the secondary current is synchronized with the rising edge of the driving signal, and the falling edge of the pulse signal corresponding to the secondary current leads the driving signal The falling edge indicates that the resonant power converter operates in the second region, and it is necessary to increase the frequency of the driving signal so that the resonant power converter operates at the resonant frequency point.
- the method for generating the first information by the resonant power converter according to the pulse signal and the driving signal corresponding to the secondary current includes:
- the resonant power converter confirms that the rising edge of the pulse signal corresponding to the secondary current leads the rising edge of the driving signal, and the falling edge of the pulse signal corresponding to the secondary current leads the falling edge of the driving signal; and generates the first information, first The information is used to indicate that the resonant power converter is operating in the third region.
- the resonant power converter according to the first information, the method for controlling the frequency of the driving signal includes:
- the resonant power converter first stops generating the driving signal according to the first information; and after increasing the frequency of the driving signal, continues to generate the driving signal.
- the rising edge of the pulse signal corresponding to the secondary current exceeds the rising edge of the driving signal, and the falling edge of the pulse signal corresponding to the secondary current leads the driving signal The falling edge indicates that the resonant power converter operates in the third region.
- the resonant power converter Control branch continues to generate drive And transmitting a driving signal to the inverter branch of the resonant power converter, and then determining whether the resonant power converter is still operating in the third region, and if the resonant power converter is still operating in the third region, continuing to stop generating the driving signal, improving The frequency of the drive signal ultimately reaches the goal of allowing the resonant power converter to operate at the resonant frequency point.
- Embodiments of the present invention provide a resonant power converter and a frequency tracking method thereof, and a resonant power converter including an inverter branch, a resonant branch connected to the inverter branch, a transformer connected to the resonant branch, and a transformer a connected rectifying and filtering branch, wherein the original end of the transformer is connected to the resonant branch, the secondary end of the transformer is connected to the rectifying and filtering branch; the detecting branch connected to the secondary end of the transformer and the rectifying and filtering branch, and the detecting branch a judging branch connected to the road, and a control branch connected to the judging branch and the inverting branch; wherein the detecting branch is used for acquiring the secondary current of the transformer, and generating a pulse corresponding to the secondary current according to the secondary current Signal, and send a pulse signal corresponding to the secondary current to the determining branch; the control branch is used to generate the driving signal, and send the driving signal to the inverter branch and the determining branch,
- the determination branch can receive the pulse signal corresponding to the secondary current transmitted by the detection branch, and generate the resonance state for indicating the resonance state of the resonant power converter according to the pulse signal and the drive signal corresponding to the secondary current. a message that causes the control branch to control the frequency of the drive signal according to the first information, to determine the resonance state of the resonant power converter by sampling the secondary current, and to control the frequency of the drive signal to track the resonance of the resonant power converter The purpose of the frequency.
- FIG. 2 is a waveform diagram of a conventional LLC resonant power converter operating in an inductive mode and a capacitive mode;
- FIG. 3 is a schematic structural diagram 1 of a resonant power converter according to an embodiment of the present invention.
- FIG. 4 is a schematic structural diagram 2 of a resonant power converter according to an embodiment of the present invention.
- FIG. 5 is a schematic structural diagram 3 of a resonant power converter according to an embodiment of the present disclosure
- FIG. 6 is a schematic structural diagram 4 of a resonant power converter according to an embodiment of the present disclosure.
- FIG. 7 is a schematic structural diagram 5 of a resonant power converter according to an embodiment of the present disclosure.
- FIG. 8 is a schematic structural diagram 6 of a resonant power converter according to an embodiment of the present invention.
- FIG. 9 is a schematic structural diagram 7 of a resonant power converter according to an embodiment of the present disclosure.
- FIG. 10 is a schematic structural diagram 8 of a resonant power converter according to an embodiment of the present invention.
- FIG. 11 is a schematic structural diagram IX of a resonant power converter according to an embodiment of the present disclosure.
- FIG. 12 is a schematic structural diagram 10 of a resonant power converter according to an embodiment of the present invention.
- FIG. 13 is a schematic structural diagram 1 of a DC/DC converter according to an embodiment of the present invention.
- FIG. 14 is a schematic structural diagram 2 of a DC/DC converter according to an embodiment of the present disclosure.
- FIG. 15 is a schematic structural diagram 3 of a DC/DC converter according to an embodiment of the present disclosure.
- 16 is a schematic structural diagram 4 of a DC/DC converter according to an embodiment of the present invention.
- FIG. 17 is a schematic flowchart 1 of a frequency tracking method for a resonant power converter according to an embodiment of the present invention
- FIG. 18 is a second schematic flowchart of a frequency tracking method for a resonant power converter according to an embodiment of the present disclosure
- FIG. 19 is a schematic flowchart 3 of a frequency tracking method for a resonant power converter according to an embodiment of the present disclosure
- FIG. 20 is a waveform diagram of a resonant power converter operating at a resonant frequency point according to an embodiment of the present invention
- FIG. 21 is a schematic flowchart diagram 4 of a frequency tracking method for a resonant power converter according to an embodiment of the present disclosure
- FIG. 22 is a waveform diagram of a resonant power converter operating in a first region according to an embodiment of the present invention
- FIG. 23 is a schematic flowchart 5 of a frequency tracking method for a resonant power converter according to an embodiment of the present invention
- FIG. 24 is a waveform diagram of a resonant power converter operating in a second region according to an embodiment of the present invention.
- 25 is a schematic flowchart 6 of a frequency tracking method for a resonant power converter according to an embodiment of the present invention
- FIG. 26 is a waveform diagram of a resonant power converter operating in a third region according to an embodiment of the present invention.
- the technology described in the embodiments of the present invention is mainly used in an LLC resonant power converter, and the LLC resonant power converter provided by the embodiment of the present invention is an open loop structure control circuit, wherein the open loop structure refers to a control that is not to be controlled. The results are fed back to influence the structure of the current control.
- the primary current Ip flowing through the detection of the inflow resonant network and the application to the resonant circuit are employed in the prior art.
- the phase difference of the square wave voltage Vd is used to determine the inductive/capacitive mode.
- the primary current Ip leads the square wave voltage Vd
- the primary current Ip lags behind the square wave voltage Vd.
- FIG. 2 and (b) in FIG. 2 are waveform diagrams when the LLC resonant power converter operates in an inductive mode and a capacitive mode, respectively. As shown in Fig.
- the primary current Ip lags behind the square wave voltage Vd, and the LLC resonant power converter operates in an inductive mode; as shown in Fig. 2(b), the primary current Ip leads the square wave voltage Vd,
- the LLC resonant power converter operates in a capacitive mode.
- the LLC resonant power converter adjusts the switching frequency of the switching tube in the resonant power converter according to its working mode. That is, when the LLC resonant power converter operates in the inductive mode, it is necessary to reduce the switching frequency of the switching tube in the resonant power converter. When the LLC resonant power converter operates in the capacitive mode, it is necessary to increase the switching frequency of the switching transistor in the resonant power converter.
- the resonant power converter provided by the embodiment of the invention can By sampling the secondary current, determining the resonant state of the resonant power converter, controlling the frequency of the driving signal, and achieving the frequency of the driving signal to track the resonant frequency of the resonant power converter.
- association relationship describing an association object, indicating that there may be three relationships, for example, A and/or B, which may indicate that A exists separately, and A exists at the same time. And B, there are three cases of B alone.
- the character "/" in this article generally indicates that the contextual object is an "or" relationship.
- the embodiment of the present invention provides a resonant power converter, as shown in FIG. 3, including an inverter branch 101, a resonant branch 102 connected to the inverter branch 101, a transformer 103 connected to the resonant branch 102, and The rectifier filter branch 104 is connected to the transformer 103.
- the primary end of the transformer 103 is connected to the resonant branch 102, and the secondary end of the transformer 103 is connected to the rectifying and filtering branch 104.
- the inverter branch 101, the resonant branch 102, and the transformer are connected.
- 103, and a circuit comprising a rectifying and filtering branch 104 may be referred to as a main power circuit 10 (the portion indicated by the dashed box in FIG.
- the resonant power converter further includes: a secondary end of the transformer 103 and a rectifying and filtering branch 104
- the detection branch 11 connected to each other, the determination branch 12 connected to the detection branch 11 and the control branch 13 connected to both the determination branch 12 and the inverter branch 101.
- the detection branch 11 is configured to acquire the secondary current of the transformer 103, generate a pulse signal corresponding to the secondary current according to the secondary current, and transmit a pulse signal corresponding to the secondary current to the determination branch 12.
- the control branch 13 is configured to generate a drive signal and transmit a drive signal to the inverter branch 101 and the determination branch 12, and the drive signal is used to drive the inverter branch 101.
- the determining branch 12 is configured to receive a pulse signal corresponding to the secondary current sent by the detecting branch 11 and a driving signal sent by the control branch 13, and generate and transmit the first information according to the pulse signal and the driving signal corresponding to the secondary current. To the control branch 13, wherein the first information is used to indicate the resonant state of the resonant power converter.
- the control branch 13 is further configured to receive the first information sent by the determining branch 12 and control the frequency of the driving signal according to the first information.
- the pulse signal corresponding to the driving signal and the secondary current may not be the signals in the same switching cycle.
- the driving signal sent by the control branch 13 obtained by the branch 12 may be the driving signal of the previous switching cycle, or may be the driving signal of the first few switching cycles, which is not limited in the embodiment of the present invention.
- the driving signal mentioned in the embodiment of the present invention is a signal for driving the switching tube in the inverter branch 101. Therefore, the switching frequency of the switching tube in the inverter branch 101 is equal to the frequency of the driving signal.
- the resonant power converter further includes:
- the sampling circuit 14 generally samples the secondary current by two methods: one is to sample the secondary current by using the Hall effect, and the Hall effect is when the current is perpendicular to the external magnetic field through the conductor. The carrier is deflected, and an additional charge is generated perpendicular to the direction of the current and the magnetic field. Field, thereby creating a potential difference across the conductor; another way is to sample the secondary current by sampling the voltage across the diode in the rectifier filter branch 104, because the unidirectional conductivity of the diode determines the current flow in the diode When passing, the forward voltage drop is only a few tenths of a volt. For example, a typical silicon diode is about 0.7V.
- the diode When the diode is turned off, the diode is subjected to a reverse voltage. When the voltage across the diode in the sampling rectifier circuit 104 is sampled, the voltage is sampled. When the secondary current is current, it is only necessary to judge the positive and negative of the diode voltage, that is, the output voltage is high when the diode voltage is positive, and the low level is output when the diode voltage is negative.
- the inverter branch 101 is any one of a half bridge inverter circuit structure, a full bridge inverter circuit structure, and a three-level inverter circuit structure.
- the resonant branch 102 is an LLC resonant circuit structure in which the LLC resonant circuit structure is composed of a series combination of a magnetizing inductance Lm, a resonant inductor Lr and a resonant capacitor Cr.
- the rectifying and filtering branch 104 is a half-wave rectifying and filtering circuit structure or a full-wave rectifying and filtering circuit structure.
- the inverter branch 101 is a half bridge circuit structure
- the resonance branch 102 is an LLC resonant circuit structure
- the rectification filter branch 104 is a half wave rectification filter circuit structure as an example, which is implemented by the present invention.
- the example provides a resonant power converter for detailed description:
- embodiments of the present invention provide a resonant power converter that includes a DC power source for supplying power to the inverter branch 101.
- the inverter branch 101 (the portion indicated by the broken line frame in FIG. 5 ) specifically includes a first switch tube Q1 and a second switch tube Q2 , and the gate of the first switch tube Q1 is connected to the control branch 13 , first The drain of the switch Q1 is connected to the positive pole of the power supply, the source of the first switch Q1 is connected to the drain of the second switch Q2, the gate of the second switch Q2 is connected to the control branch 13, and the second switch Q2 The source is connected to the negative pole of the power source; the resonant branch 102 (as indicated by the dashed box in FIG.
- the resonant inductor Lr specifically includes a magnetizing inductance Lm, a resonant inductor Lr and a resonant capacitor Cr connected in series, wherein one end of the resonant capacitor Cr and the first The drain of the second switch Q2 is connected, the other end of the resonant capacitor Cr is connected to one end of the resonant inductor Lr, the other end of the resonant inductor Lr is connected to one end of the exciting inductor Lm, and the other end of the exciting inductor Lm is connected to the negative pole of the power supply, and the magnetizing inductance One end of the Lm is connected to one end of the original end of the transformer 103, and the other end of the exciting inductance Lm is connected to the other end of the original end of the transformer 103; the rectifying and filtering branch 104 (as indicated by the dotted line in FIG.
- the 5) specifically includes the first two Polar tube D1, second diode D2 and a filter capacitor Cf, wherein the input end of the first diode D1 is connected to one end of the secondary end of the transformer 103, the output end of the first diode D1 is connected to one end of the filter capacitor Cf, and the second diode D2 is connected The input terminal is connected to the other end of the secondary terminal of the transformer 103, and the output terminal of the second diode D2 is connected to the other end of the filter capacitor Cf.
- one end of the filter capacitor Cf is usually connected to one end of the output end, and the other end of the filter capacitor Cf is connected to the other end of the output end, and the output end is usually a resistor.
- the current directions of the primary and secondary ends of the transformer 103 are the same.
- the control branch 13 respectively sends a driving signal to the gate of the first switching transistor Q1 and the gate of the second switching transistor Q2, wherein the driving signal sent to the first switching transistor Q1 and the driving signal sent to the second switching transistor Q2
- the phase is reversed and the frequency is the same. Therefore, when the first switching transistor Q1 is turned on, the first diode D1 is turned on. At this time, it is determined that the branch 12 compares the driving signal of the first switching transistor Q1 with the secondary current.
- the branch circuit 12 compares the positional relationship between the driving signal of the second switching transistor Q2 and the rising edge of the pulse signal corresponding to the secondary current and the driving signal of the second switching transistor Q2 and the secondary current. The positional relationship of the falling edge of the pulse signal.
- the branch circuit 12 determines that the rising edge of the pulse signal corresponding to the secondary current is synchronized with the rising edge of the driving signal, and the falling edge of the pulse signal corresponding to the secondary current is synchronized with the falling edge of the driving signal, the resonance is indicated.
- the power converter operates at a resonant frequency point and the control branch 13 maintains the frequency of the drive signal unchanged.
- the branch circuit 12 determines that the rising edge of the pulse signal corresponding to the secondary current is synchronized with the rising edge of the driving signal, and the falling edge of the pulse signal corresponding to the secondary current lags behind the falling edge of the driving signal, the resonant power converter is illustrated. Operating in the first region, the control branch 13 needs to reduce the frequency of the drive signal.
- the branch circuit 12 determines that the rising edge of the pulse signal corresponding to the secondary current is synchronized with the rising edge of the driving signal, and the falling edge of the pulse signal corresponding to the secondary current leads the falling edge of the driving signal, the resonant power converter is illustrated. Operating in the second region, the control branch 13 needs to increase the frequency of the drive signal.
- the branch circuit 12 determines that the rising edge of the pulse signal corresponding to the secondary current exceeds the rising edge of the driving signal, and the falling edge of the pulse signal corresponding to the secondary current leads the falling edge of the driving signal, the resonant power converter is illustrated.
- the inverter branch 101 is a half bridge inverter circuit structure
- the resonance branch 102 is an LLC resonant circuit structure
- the rectification filter branch 104 is a half wave rectification filter circuit structure, for example, sampling.
- the circuit 14 may specifically include: a comparator, a first resistor R1, a second resistor R2, a third resistor R3, and a capacitor C;
- the output end of the comparator is connected to one end of the third resistor R3, one end of the capacitor C is connected to the other end of the third resistor R3, and the other end of the third resistor R3 is connected to the detecting branch 11, the positive input end of the comparator Connected to one end of the first resistor R1, the negative input end of the comparator is connected to one end of the second resistor R2, and the other end of the first resistor R1 is connected to the secondary end of the transformer 103 and the rectifying and filtering branch 104, and the second resistor R2 The other end is grounded to the other end of the capacitor C.
- first resistor R1, the second resistor R2, and the third resistor R3 included in the sampling circuit 14 may be resistors in which a plurality of resistors are connected in parallel, and the capacitor C may be a plurality of capacitors in series and the like.
- the effective capacitance is not limited in the embodiment of the present invention.
- the inverter branch 101 is a half bridge inverter circuit structure
- the resonance branch 102 is an LLC resonant circuit structure
- the rectification filter branch 104 is a half wave rectification filter circuit structure, for example, sampling.
- the circuit 14 specifically includes: a comparator, a first resistor R1, a second resistor R2, a third resistor R3, a fourth resistor R4, a fifth resistor R5 and a sixth resistor R6;
- the output end of the comparator is connected to the detecting branch 11, the negative input end of the comparator is connected to one end of the first resistor R1, the other end of the first resistor R1 is connected to one end of the second resistor R2, and the second resistor R2 is connected.
- the other end is connected to the secondary end of the transformer 103 and the rectifying and filtering branch 104.
- One end of the third resistor R3 is connected to the output end of the comparator, and the other end of the third resistor R3 is connected to the negative input end of the comparator.
- the positive input terminal is connected to one end of the fourth resistor R4, the other end of the fourth resistor R4 is connected to one end of the fifth resistor R5, and the other end of the fifth resistor R5 is connected to the rectifying and filtering branch 104, and the positive input terminal of the comparator is One end of the sixth resistor R6 is connected, and the other end of the sixth resistor R6 is grounded.
- first resistor R1, the second resistor R2, the third resistor R3, the fourth resistor R4, the fifth resistor R5, and the sixth resistor R6 included in the sampling circuit 14 may be a plurality of resistors connected in series and in parallel.
- the electrical resistance of the present invention is not limited in the embodiment of the present invention.
- the structure of the two sampling circuits 14 provided by the embodiments of the present invention is only a manner that the sampling circuit 14 can be implemented.
- Other structures that can achieve the purpose of sampling the secondary current can be the sampling circuit 14 mentioned in the embodiment of the present invention.
- the embodiment of the present invention does not limit this.
- the inverter branch 101 is a half bridge circuit structure
- the resonance branch 102 is an LLC resonant circuit structure
- the rectification filter branch 104 is a full wave rectification filter circuit structure as an example, and the present invention is implemented.
- the example provides a resonant power converter for detailed description:
- embodiments of the present invention provide a resonant power converter that includes a DC power source for supplying power to the inverter branch 101.
- the inverter branch 101 (the portion indicated by the broken line frame in FIG. 8 ) specifically includes a first switch tube Q1 and a second switch tube Q2 , and the gate of the first switch tube Q1 is connected to the control branch 13 , first The drain of the switch Q1 is connected to the positive pole of the power supply, the source of the first switch Q1 is connected to the drain of the second switch Q2, the gate of the second switch Q2 is connected to the control branch 13, and the second switch Q2 The source is connected to the negative pole of the power source; the resonant branch 102 (as indicated by the dashed box in FIG.
- the resonant inductor Lr specifically includes a magnetizing inductance Lm, a resonant inductor Lr and a resonant capacitor Cr connected in series, wherein one end of the resonant capacitor Cr and the first The drain of the second switch Q2 is connected, the other end of the resonant capacitor Cr is connected to one end of the resonant inductor Lr, the other end of the resonant inductor Lr is connected to one end of the exciting inductor Lm, and the other end of the exciting inductor Lm is connected to the negative pole of the power supply, and the magnetizing inductance One end of the Lm is connected to one end of the original end of the transformer 103, and the other end of the exciting inductance Lm is connected to the other end of the original end of the transformer 103; the rectifying and filtering branch 104 (as indicated by the dotted line in FIG.
- the 8) specifically includes the first two Polar tube D1, second diode D2, a third diode D3, a fourth diode D4 and a filter capacitor Cf, wherein the input end of the first diode D1 is connected to one end of the secondary end of the transformer 103, and the output end of the first diode D1 is One end of the filter capacitor Cf is connected, the output end of the second diode D2 is connected to one end of the secondary end of the transformer 103, the input end of the second diode D2 is connected to the other end of the filter capacitor Cf, and the third diode D3 is connected The input end is connected to the other end of the filter capacitor Cf, the output end of the third diode D3 is connected to one end of the filter capacitor Cf, and the output end of the fourth diode D4 is connected to the other end of the secondary end of the transformer 103, the fourth two The input end of the pole tube D4 is connected to the other end of the filter capacitor Cf.
- one end of the filter capacitor Cf is usually connected to one end of the output end, and the other end of the filter capacitor Cf is connected to the other end of the output end, and the output end is usually a resistor.
- the current directions of the primary and secondary ends of the transformer 103 are the same.
- the control branch 13 respectively sends a driving signal to the gate of the first switching transistor Q1 and the gate of the second switching transistor Q2, wherein the driving signal sent to the first switching transistor Q1 and the driving signal sent to the second switching transistor Q2
- the phase is reversed and the frequency is the same. Therefore, when the first switching transistor Q1 is turned on, the first diode D1 and the second diode D2 are turned on. At this time, it is determined that the branch 12 compares the driving of the first switching transistor Q1.
- the positional relationship between the rising edge of the pulse signal corresponding to the signal and the secondary current is the positional relationship between the falling edge of the pulse signal corresponding to the driving signal of the first switching transistor Q1 and the secondary current; when the second switching transistor Q2 is turned on, the corresponding The third diode D3 and the fourth diode D4 are turned on.
- the branch circuit 12 compares the positional relationship between the driving signal of the second switching transistor Q2 and the rising edge of the pulse signal corresponding to the secondary current and the second switching transistor.
- the positional relationship between the falling edge of the pulse signal corresponding to the drive signal of Q2 and the secondary current is the same as the result corresponding to FIG. 5 above, and details are not described herein again.
- the inverter branch 101 is a full bridge circuit structure
- the resonance branch 102 is an LLC resonant circuit structure
- the rectification filter branch 104 is a half wave rectification filter circuit structure as an example, and the present invention is implemented.
- the example provides a resonant power converter for detailed description:
- embodiments of the present invention provide a resonant power converter that includes a DC power source for supplying power to the inverter branch 101.
- the inverter branch 101 (the portion indicated by the broken line frame in FIG. 9 ) specifically includes a first switch tube Q1 , a second switch tube Q2 , a third switch tube Q3 , and a fourth switch tube Q4 , wherein the first switch
- the gate control branch 13 of the transistor Q1 is connected, the drain of the first switching transistor Q1 is connected to the positive pole of the power supply, the source of the first switching transistor Q1 is connected to the drain of the fourth switching transistor Q4, and the gate of the second switching transistor Q2 is connected.
- the pole is connected to the control branch 13, the drain of the second switch Q2 is connected to the source of the third switch Q3, the source of the second switch Q2 is connected to the negative pole of the power supply, and the gate and control of the third switch Q3
- the branch 13 is connected, the drain of the third switch Q3 is connected to the positive pole of the power supply, the gate of the fourth switch Q4 is connected to the control branch 13, and the source of the fourth switch Q4 is connected to the negative pole of the power supply; the resonant branch 102 (the portion indicated by the dashed box in FIG.
- the rectifying and filtering branch 104 (the portion indicated by the dashed box in FIG.
- 9) specifically includes a first diode D1, a second diode D2, and a filter capacitor Cf, wherein the input end of the first diode D1 and the secondary end of the transformer 103 One end is connected, the output end of the first diode D1 is connected to one end of the filter capacitor Cf, the input end of the second diode D2 is connected to the other end of the secondary end of the transformer 103, and the output end of the second diode D2 is filtered.
- the other end of the capacitor Cf is connected.
- one end of the filter capacitor Cf is usually connected to one end of the output end, and the other end of the filter capacitor Cf is connected to the other end of the output end, and the output end is usually a resistor.
- the current directions of the primary and secondary ends of the transformer 103 are the same.
- the control branch 13 respectively sends driving signals to the gates of the first switching transistor Q1 and the fourth switching transistor Q4, and transmits a driving signal to the gate of the second switching transistor Q2 and the gate of the third switching transistor Q3, wherein
- the driving signals to the first switching transistor Q1 and the fourth switching transistor Q4 are opposite to the phases of the driving signals sent to the second switching transistor Q2 and the third switching transistor Q3, and the frequencies are the same, therefore, when the first switch When the tube Q1 and the fourth switch tube Q4 are turned on, the first diode D1 is turned on.
- the branch circuit 12 compares the driving signal of the first switching transistor Q1 or the fourth switching transistor Q4 with the pulse corresponding to the secondary current.
- the positional relationship of the rising edge of the signal and the positional relationship of the falling edge of the pulse signal corresponding to the driving signal of the first switching transistor Q1 or the fourth switching transistor Q4 and the secondary switching current; when the second switching transistor Q2 and the third switching transistor Q3 are guided The second diode D2 is turned on according to the current time. At this time, it is determined that the branch circuit 12 compares the positional relationship between the driving signal of the second switching transistor Q2 or the third switching transistor Q3 and the rising edge of the pulse signal corresponding to the secondary current. The positional relationship between the driving signal of the second switching transistor Q2 or the third switching transistor Q3 and the falling edge of the pulse signal corresponding to the secondary current. The result of the comparison is the same as the result corresponding to FIG. 5 above, and details are not described herein again.
- the inverter branch 101 is a full bridge circuit structure
- the resonance branch 102 is an LLC resonant circuit structure
- the rectification filter branch 104 is a full wave rectification filter circuit structure, for example, and is implemented by the present invention.
- the example provides a resonant power converter for detailed description:
- embodiments of the present invention provide a resonant power converter that includes a DC power source for supplying power to the inverter branch 101.
- the inverter branch 101 (the portion indicated by the broken line frame in FIG. 10) specifically includes a first switch tube Q1, a second switch tube Q2, a third switch tube Q3, and a fourth switch tube Q4, wherein the first switch
- the gate control branch 13 of the transistor Q1 is connected, the drain of the first switching transistor Q1 is connected to the positive pole of the power supply, the source of the first switching transistor Q1 is connected to the drain of the fourth switching transistor Q4, and the gate of the second switching transistor Q2 is connected.
- the pole is connected to the control branch 13, the drain of the second switch Q2 is connected to the source of the third switch Q3, the source of the second switch Q2 is connected to the negative pole of the power supply, and the gate and control of the third switch Q3
- the branch 13 is connected, the drain of the third switch Q3 is connected to the positive pole of the power supply, the gate of the fourth switch Q4 is connected to the control branch 13, and the source of the fourth switch Q4 is connected to the negative pole of the power supply; the resonant branch 102 (the portion indicated by the dashed box in FIG.
- 10) specifically includes a magnetizing inductance Lm, a resonant inductor Lr, and a resonant capacitor Cr connected in series, wherein one end of the resonant capacitor Cr is connected to the drain of the second switching transistor Q2, and the resonant capacitor Cr The other end is connected to one end of the resonant inductor Lr, and the other end of the resonant inductor Lr is excited.
- the circuit 104 (such as the portion indicated by the dashed box in FIG.
- first diode D1 specifically includes a first diode D1, a second diode D2, a third diode D3, a fourth diode D4, and a filter capacitor Cf, wherein
- the input end of the first diode D1 is connected to one end of the secondary end of the transformer 103, the output end of the first diode D1 is connected to one end of the filter capacitor Cf, and the output end of the second diode D2 is connected to the secondary end of the transformer 103.
- One end is connected, the input end of the second diode D2 is connected to the other end of the filter capacitor Cf, the input end of the third diode D3 is connected to the other end of the filter capacitor Cf, and the output end of the third diode D3 is filtered.
- One end of the capacitor Cf is connected, the output end of the fourth diode D4 is connected to the other end of the secondary end of the transformer 103, and the input end of the fourth diode D4 is connected to the other end of
- one end of the filter capacitor Cf is usually connected to one end of the output end, and the other end of the filter capacitor Cf is connected to the other end of the output end, and the output end is usually a resistor.
- the current directions of the primary and secondary ends of the transformer 103 are the same.
- the control branch 13 respectively sends a driving signal to the gates of the first switching transistor Q1 and the fourth switching transistor Q4. And transmitting a driving signal to the gate of the second switching transistor Q2 and the gate of the third switching transistor Q3, wherein the driving signals sent to the first switching transistor Q1 and the fourth switching transistor Q4 are sent to the second switching transistor
- the driving signals of Q2 and the third switching transistor Q3 are opposite in phase and have the same frequency. Therefore, when the first switching transistor Q1 and the fourth switching transistor Q4 are turned on, the first diode D1 and the second diode D2 are turned on.
- the branch circuit 12 compares the positional relationship between the driving signal of the first switching transistor Q1 or the fourth switching transistor Q4 and the rising edge of the pulse signal corresponding to the secondary current and the first switching transistor Q1 or the fourth switching transistor Q4.
- the branch circuit 12 compares the positional relationship between the driving signal of the second switching transistor Q2 or the third switching transistor Q3 and the rising edge of the pulse signal corresponding to the secondary current and the driving signal of the second switching transistor Q2 or the third switching transistor Q3.
- the bit of the falling edge of the pulse signal corresponding to the secondary current Relations The result of the comparison is the same as the result corresponding to FIG. 5 above, and details are not described herein again.
- the inverter branch 101 is a three-level circuit structure
- the resonant branch 102 is an LLC resonant circuit structure
- the rectifying and filtering branch 104 is a half-wave rectifying and filtering circuit structure as an example.
- the embodiment provides a resonant power converter for detailed description:
- embodiments of the present invention provide a resonant power converter that includes a DC power source for supplying power to the inverter branch 101.
- the inverter branch 101 (the portion indicated by the broken line frame in FIG. 11 ) specifically includes a first switch tube Q1, a second switch tube Q2, a third switch tube Q3, a fourth switch tube Q4, and a fifth diode.
- the gate control branch 13 of the first switch transistor Q1 is connected, the drain of the first switch transistor Q1 is connected to the positive pole of the power source, the source of the first switch transistor Q1 and the second switch transistor Q2 The drains are connected, the gate control branch 13 of the second switch transistor Q2 is connected, the source of the second switch transistor Q2 is connected to the drain of the third switch transistor Q3, and the gate control branch 13 of the third switch transistor Q3 is connected.
- the source of the third switching transistor Q3 is connected to the drain of the fourth switching transistor Q4, the gate control branch 13 of the fourth switching transistor Q4 is connected, and the source of the fourth switching transistor Q4 is connected to the negative pole of the power supply, fifth
- the input end of the diode D5 is connected to the output end of the sixth diode D6, the output end of the fifth diode D5 is connected to the source of the first switch tube Q1, and the input end of the sixth diode D6 is The source of the three-switching tube Q3 is connected; the resonant branch 102 (the portion indicated by the dashed box in FIG. 11) specifically includes the magnetizing inductance Lm and the resonant inductor L connected in series.
- the rectifying and filtering branch 104 (eg The portion indicated by the dashed box in FIG.
- first diode D1 specifically includes a first diode D1, a second diode D2, and a filter capacitor Cf, wherein the input end of the first diode D1 is connected to one end of the secondary end of the transformer 103, The output end of the first diode D1 is connected to one end of the filter capacitor Cf, the input end of the second diode D2 is connected to the other end of the secondary end of the transformer 103, and the output end of the second diode D2 is connected to the filter capacitor Cf. The other end is connected.
- one end of the filter capacitor Cf is usually connected to one end of the output end, and the other end of the filter capacitor Cf is connected to the other end of the output end, and the output end is usually a resistor.
- Transformer 103 original end The current direction is the same as that of the secondary side.
- the control branch 13 respectively sends driving signals to the gates of the first switching transistor Q1 and the second switching transistor Q2, and transmits a driving signal to the gate of the third switching transistor Q3 and the gate of the fourth switching transistor Q4, wherein
- the driving signals to the first switching transistor Q1 and the second switching transistor Q2 are opposite to the phases of the driving signals sent to the gate of the third switching transistor Q3 and the fourth switching transistor Q4, and the frequencies are the same, therefore, when the first switching transistor Q1 When the second switching transistor Q2 is turned on, the first diode D1 is turned on.
- the branch circuit 12 is compared with the driving signal corresponding to the first switching transistor Q1 or the second switching transistor Q2 and the pulse signal corresponding to the secondary current.
- the inverter branch 101 is a three-level circuit structure
- the resonance branch 102 is an LLC resonant circuit structure
- the rectification filter branch 104 is a full-wave rectification filter circuit structure.
- the embodiment provides a resonant power converter for detailed description:
- embodiments of the present invention provide a resonant power converter that includes a DC power source for supplying power to the inverter branch 101.
- the inverter branch 101 (the portion indicated by the broken line frame in FIG. 12 ) specifically includes a first switch tube Q1, a second switch tube Q2, a third switch tube Q3, a fourth switch tube Q4, and a fifth diode.
- the gate control branch 13 of the first switch transistor Q1 is connected, the drain of the first switch transistor Q1 is connected to the positive pole of the power source, the source of the first switch transistor Q1 and the second switch transistor Q2 The drains are connected, the gate control branch 13 of the second switch transistor Q2 is connected, the source of the second switch transistor Q2 is connected to the drain of the third switch transistor Q3, and the gate control branch 13 of the third switch transistor Q3 is connected.
- the source of the third switching transistor Q3 is connected to the drain of the fourth switching transistor Q4, the gate control branch 13 of the fourth switching transistor Q4 is connected, and the source of the fourth switching transistor Q4 is connected to the negative pole of the power supply, fifth
- the input end of the diode D5 is connected to the output end of the sixth diode D6, the output end of the fifth diode D5 is connected to the source of the first switch tube Q1, and the input end of the sixth diode D6 is The source of the three-switching tube Q3 is connected; the resonant branch 102 (as indicated by the dashed box in FIG. 12) specifically includes the magnetizing inductance Lm and the resonant inductor L connected in series.
- the rectifying and filtering branch 104 (eg The portion indicated by the dashed box in FIG.
- first diode D1 specifically includes a first diode D1, a second diode D2, a third diode D3, a fourth diode D4, and a filter capacitor Cf, wherein the first diode
- the input end of the tube D1 is connected to one end of the secondary end of the transformer 103.
- the output end of the first diode D1 is connected to one end of the filter capacitor Cf, and the output end of the second diode D2 is connected to one end of the secondary end of the transformer 103.
- the input end of the diode D2 is connected to the other end of the filter capacitor Cf, and the input end of the third diode D3 is filtered.
- the other end of the capacitor Cf is connected, the output end of the third diode D3 is connected to one end of the filter capacitor Cf, the output end of the fourth diode D4 is connected to the other end of the secondary end of the transformer 103, and the fourth diode D4 is connected.
- the input terminal is connected to the other end of the filter capacitor Cf.
- one end of the filter capacitor Cf is usually connected to one end of the output end, and the other end of the filter capacitor Cf is connected to the other end of the output end, and the output end is usually a resistor.
- the current directions of the primary and secondary ends of the transformer 103 are the same.
- the control branch 13 respectively sends driving signals to the gates of the first switching transistor Q1 and the second switching transistor Q2, and transmits a driving signal to the gate of the third switching transistor Q3 and the gate of the fourth switching transistor Q4, wherein
- the driving signals to the first switching transistor Q1 and the second switching transistor Q2 are opposite to the phases of the driving signals sent to the gate of the third switching transistor Q3 and the fourth switching transistor Q4, and the frequencies are the same, therefore, when the first switching transistor Q1 When the second switch tube Q2 is turned on, the first diode D1 and the second diode D2 are turned on.
- the branch circuit 12 is compared with the driving signal and the pair of the first switch tube Q1 or the second switch tube Q2.
- control branch 13 mentioned in the embodiment of the present invention drives each switch tube in the inverter branch 101, and the control branch 13 may be separately connected to each switch tube, that is, the control branch 13 is separate. Each switch is driven; the control branch 13 is connected to a plurality of switch tubes that need to be turned on at the same time, which is not limited in the embodiment of the present invention.
- Embodiments of the Invention FIG. 5 to FIG. 12 are described by taking the control branch 13 separately from each of the switch tubes as an example.
- the frequency tracking method of the LLC resonant power converter provided by the embodiment of the present invention is applied in an open-loop LLC circuit, and the open-loop LLC resonant power converter can be used in series with a closed-loop DC/DC converter to realize a voltage. Adjustment.
- the LLC resonant power converter can be applied to a DC/DC converter composed of a DC/DC converter structure and an LLC resonant power converter.
- the DC/DC conversion structure is closed-loop controlled by sampling the output voltage of the LLC resonant power converter as a feedback voltage of the DC/DC conversion structure, and adjusting the output voltage of the DC/DC conversion structure to adjust the LLC resonant power converter.
- the switching frequency reaches the frequency of the drive signal to track the resonant frequency of the resonant power converter.
- the DC/DC conversion structure may be any single-phase DC/DC conversion structure
- the LLC resonant power converter may be any one of the LLC resonant power converters described in the above embodiments.
- the DC/DC conversion structure is a buck converter
- the inverter branch 101 of the LLC resonant power converter is a half bridge inverter circuit structure
- the resonance branch 102 is an LLC resonant circuit structure
- the rectification and filtering branch circuit is shown.
- 104 is a half-wave rectification filter circuit structure.
- an LLC resonant power converter can be applied to two DC/DCs.
- the voltage of the LLC resonant power converter can be adjusted by the DC/DC conversion structure on the left side in FIG. 15, or can be adjusted by the DC/DC conversion structure on the right side in FIG.
- the adjustment of the DC/DC conversion structure on the left side of FIG. 15 ensures that the output voltage of the LLC resonant power converter is stabilized at a set value, and the output voltage of the DC/DC conversion structure on the left side of FIG. 15 is changed to achieve the adjustment frequency.
- the output voltage adjustment by the DC/DC conversion structure on the right side in FIG. 15 is to keep the output voltage of the DC/DC conversion structure on the right side in FIG. 15 unchanged by changing the input of the DC/DC conversion structure on the right side in FIG. The voltage reaches the purpose of adjusting the frequency.
- the DC/DC conversion structure may be any single-phase DC/DC conversion structure
- the LLC resonant power converter may be any one of the LLC resonant power converters described in the above embodiments.
- the two DC/DC conversion structures are buck converters
- the inverter branch 101 of the LLC resonant power converter is a half bridge inverter circuit structure
- the resonance branch circuit 102 is an LLC resonant circuit structure
- the rectification is performed.
- the filter branch 104 is a half-wave rectification filter circuit structure.
- the above-mentioned closed-loop controlled DC/DC converter may be a buck converter, or a boost converter or a buck-boost converter, which is not limited in the embodiment of the present invention.
- the switch tube provided by the embodiment of the present invention may be an IGBT (Insulated Gate Bipolar Transistor) or a MOSFET (Metal-Oxide-Semiconductor Field-Effect Transistor).
- IGBT Insulated Gate Bipolar Transistor
- MOSFET Metal-Oxide-Semiconductor Field-Effect Transistor
- the diodes, the triodes, and the like, the diodes provided in the rectifying and filtering branch of the embodiment of the invention may be replaced by a synchronous rectifier, which is not limited in the embodiment of the present invention.
- Embodiments of the present invention provide a resonant power converter including an inverter branch, a resonant branch connected to the inverter branch, a transformer connected to the resonant branch, and a rectifying and filtering branch connected to the transformer, wherein the transformer The primary end is connected to the resonant branch, the secondary end of the transformer is connected to the rectifying and filtering branch; the detecting branch connected to the secondary end of the transformer and the rectifying and filtering branch, the determining branch connected to the detecting branch, and the judgment a control branch connected to the branch circuit and the inverter branch; wherein the detection branch is used for acquiring the secondary current of the transformer, generating a pulse signal corresponding to the secondary current according to the secondary current, and transmitting the pulse corresponding to the secondary current Signal to the judgment branch; control branch for generating the drive signal, and transmitting the drive signal to the inverter branch and the judgment branch, the drive signal is used to drive the inverter branch; and the branch is used for receiving the detection branch The pulse signal
- Branch information indicating the first resonant power converter of a resonant state
- a control branch for receiving further determining a first branch information transmitted, and in accordance with the first information, control driving signal frequency.
- the determination branch can receive the pulse signal corresponding to the secondary current transmitted by the detection branch, and generate the resonance state for indicating the resonance state of the resonant power converter according to the pulse signal and the drive signal corresponding to the secondary current.
- Embodiments of the present invention also provide a frequency tracking method for a resonant power converter, which is applied to the above
- the resonant power converter includes an inverter branch, a resonant branch connected to the inverter branch, a transformer connected to the resonant branch, and a rectifying and filtering branch connected to the transformer, wherein The primary end of the transformer is connected to the resonant branch, the secondary end of the transformer is connected to the rectifying and filtering branch; the detecting branch connected to the secondary end of the transformer and the rectifying and filtering branch; and the determining branch connected to the detecting branch;
- the control branch connecting the branch circuit and the inverter branch is determined, as shown in FIG. 17, the method includes:
- the resonant power converter acquires a pulse signal and a driving signal corresponding to the secondary current.
- the determining branch of the resonant power converter acquires a pulse signal and a driving signal corresponding to the secondary current.
- step S101 may include S101a-S101c:
- the resonant power converter obtains the secondary current.
- the detection branch of the resonant power converter can directly obtain the secondary current of the transformer from the secondary side of the transformer of the main power circuit, or can sample the secondary current of the transformer by the sampling circuit of the resonant power converter, and then send it to the detection branch.
- S101b and the resonant power converter generate a pulse signal corresponding to the secondary current according to the secondary current.
- the method for generating a pulse signal corresponding to the secondary current according to the secondary current of the resonant power converter may include: converting the secondary current into a voltage signal through a resistor, and comparing the voltage signal with 0 to obtain a positive and positive The pulse signal corresponding to the secondary current corresponding to the current time; or, if the sampling circuit samples the diode voltage, it is only necessary to judge the positive and negative of the diode voltage, the output voltage is high when the diode voltage is positive, and the output is negative when the diode voltage is negative. Low level.
- the detection branch of the resonant power converter transmits a pulse signal corresponding to the secondary current to the decision branch.
- the resonant power converter obtains a driving signal.
- the judging branch of the resonant power converter acquires a driving signal sent by the control branch.
- the resonant power converter generates first information according to the pulse signal and the driving signal corresponding to the secondary current, and the first information is used to indicate a resonant state of the resonant power converter.
- the resonant power converter controls the frequency of the driving signal according to the first information.
- step S102 may include S102a and S102b:
- S102a and the resonant power converter confirm that the rising edge of the pulse signal corresponding to the secondary current is synchronized with the rising edge of the driving signal, and the falling edge of the pulse signal corresponding to the secondary current is synchronized with the falling edge of the driving signal.
- the resonant power converter generates first information, and the first information is used to indicate that the resonant power converter operates at a resonant frequency point.
- the decision branch in the resonant power converter performs steps S102a and S102b and transmits the first information to the control branch in the resonant power converter.
- step S103 may include S103a:
- the resonant power converter maintains the frequency of the driving signal unchanged according to the first information.
- control branch in the resonant power converter performs step S103a.
- step S102 may include S102c and S102d:
- S102c and the resonant power converter confirm that the rising edge of the pulse signal corresponding to the secondary current is synchronized with the rising edge of the driving signal, and the falling edge of the pulse signal corresponding to the secondary current lags behind the falling edge of the driving signal.
- the resonant power converter generates first information, where the first information is used to indicate that the resonant power converter operates in the first region.
- the decision branch in the resonant power converter performs steps S102c and S102d and transmits the first information to the control branch in the resonant power converter.
- step S103 may include S103b:
- the resonant power converter reduces the frequency of the driving signal according to the first information.
- control branch in the resonant power converter performs step S103b and transmits the reduced frequency drive signal to the decision branch of the resonant power converter.
- the resonant power converter is illustrated.
- the rising edge of the pulse signal corresponding to the secondary current is synchronized with the rising edge of the driving signal, and the falling edge of the pulse signal corresponding to the secondary current lags behind the falling edge of the driving signal.
- the resonant power converter is illustrated.
- the resonant power converter can gradually reduce the frequency of the driving signal, and the resonant power converter operates at the resonant frequency point after multiple adjustments.
- the resonant power converter reduces the frequency of the drive signal by a preset value each time, and then judges, and adjusts the frequency of the drive signal of the resonant power converter a plurality of times, so that the resonant power converter finally operates at the resonance frequency point.
- step S102 may include S102e and S102f:
- S102e and the resonant power converter confirm that the rising edge of the pulse signal corresponding to the secondary current is synchronized with the rising edge of the driving signal, and the falling edge of the pulse signal corresponding to the secondary current leads the falling edge of the driving signal.
- the resonant power converter generates first information, where the first information is used to indicate that the resonant power converter operates in the second region.
- the decision branch in the resonant power converter performs steps S102e and S102f and transmits the first information to the control branch in the resonant power converter.
- step S103 may include S103c:
- the resonant power converter increases the frequency of the driving signal according to the first information.
- control branch in the resonant power converter performs step S103c and transmits the increased frequency drive signal to the decision branch of the resonant power converter.
- the resonant power converter is illustrated.
- the resonant power converter operates at the resonant frequency point.
- the resonant power converter can gradually increase the frequency of the driving signal, and after repeated adjustments, the resonant power converter operates at the resonant frequency point.
- step S102 may include S102g and S102h:
- S102g and the resonant power converter confirm that the rising edge of the pulse signal corresponding to the secondary current exceeds the rising edge of the driving signal, and the falling edge of the pulse signal corresponding to the secondary current leads the falling edge of the driving signal.
- the resonant power converter generates first information, where the first information is used to indicate that the resonant power converter operates in the third region.
- the decision branch in the resonant power converter performs steps S102g and S102h and transmits the first information to the control branch in the resonant power converter.
- step S103 may include S103d and S103e:
- the resonant power converter stops generating the driving signal according to the first information.
- the resonant power converter generates a drive signal after increasing the frequency of the drive signal.
- control branch in the resonant power converter performs steps S103d and S103e, and transmits the increased frequency drive signal to the decision branch of the resonant power converter.
- the resonant power converter is illustrated.
- the rising edge of the pulse signal corresponding to the secondary current and the rising edge of the driving signal, and the relationship between the falling edge of the pulse signal corresponding to the secondary current and the falling edge of the driving signal can be determined by two methods: It is judged by logical operation, and the second is judged by comparing the data size in the register representing the rising edge of the two pulse signals and the data size in the register representing the falling edge of the two pulse signals, that is, judging between the two quantities. Time difference.
- the driving signal is represented by A
- the pulse signal corresponding to the secondary current is represented by B
- the method of determining by logic operation is: if the result of A and B is equal to A and equal to B, Then A is the same as B, indicating that the resonant power converter is at the resonant frequency point; if the result of A and B is equal to A is not equal to B, it means that the converter is in region 1; if the result of A and B is not equal to A but equal to B, then Indicates that the converter is in zone 2; if the result of A and B is neither equal to A nor equal to B, then the converter is in zone 3.
- the driving signals of the switching transistors in the DSP are: It is generated by comparing the timing register and the comparison register.
- the timer register starts counting every interrupt cycle. When the interrupt cycle ends, the data in the timer register reaches the maximum. When the next interrupt cycle starts, the timer register reset starts counting again.
- the number in the PWM (Pulse Width Modulation) comparison register is equal to the number in the timing register, the PWM signal transitions, and the value in the timing register at the time of signal transition is recorded.
- the pulse signal corresponding to the secondary current is sent to the DSP through the AD port.
- the value in the corresponding timing counter during the pulse transition is recorded in each interrupt cycle, and the drive signal transition is compared (including rising jump and falling).
- the value of the corresponding register and the deviation of the value of the timing register when the pulse signal jumps (including the rising transition and the falling transition) corresponding to the secondary current, if the rising jump and the falling transition are two numbers
- the deviation is less than the preset value (the preset value is related to the clock frequency, resolution, etc., defined by the designer), indicating that both the rising and falling edges of the two signals are synchronized; if the rising transition is two registers
- the deviation of the number is less than the preset value, and the value of the register corresponding to the driving signal when the falling transition is smaller than the value of the pulse signal register indicates that the operation is in the region 1; if the value of the two timing registers is less than the preset when the rising transition occurs Value, while the value of the timing register corresponding to the drive signal during the falling transition is greater than the value of the pulse signal timing register, indicating that
- Embodiments of the present invention provide a frequency tracking method for a resonant power converter, which is applied to a resonant power converter.
- the frequency tracking method of the resonant power converter includes: acquiring a pulse signal corresponding to a secondary current and a driving signal; corresponding to the secondary current.
- the pulse signal and the driving signal generate first information, the first information is used to indicate a resonance state of the resonant power converter; and the frequency of the driving signal is controlled according to the first information.
- the determination branch can receive the pulse signal corresponding to the secondary current transmitted by the detection branch, and generate the resonance state for indicating the resonance state of the resonant power converter according to the pulse signal and the drive signal corresponding to the secondary current.
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Abstract
一种谐振功率变换器及其频率跟踪方法,能够通过对副边电流进行采样,判断谐振功率变换器的谐振状态,进而控制驱动信号的频率,达到驱动信号的频率跟踪谐振功率变换器的谐振频率的目的。谐振功率变换器包括逆变支路(101)、与逆变支路相连的谐振支路(102)、与谐振支路相连的变压器(103),以及与变压器相连的整流滤波支路(104),变压器的原端与谐振支路相连,变压器的副端与整流滤波支路相连;与变压器的副端和整流滤波支路均相连的检测支路(11);与检测支路相连的判断支路(12);与判断支路和逆变支路均相连的控制支路(13)。
Description
本申请要求于2016年04月29日提交中国专利局、申请号为201610281631.4、发明名称为“一种谐振功率变换器及其频率跟踪方法”的中国专利申请的优先权,其全部内容通过引用结合在本申请中。
本发明实施例涉及通信领域,尤其涉及一种谐振功率变换器及其频率跟踪方法。
谐振功率变换器是一种基于软开关技术的电力电子变换装置,随着高频开关器件的诞生,谐振功率变换器正朝着高频化、集成化和模块化的方向发展。其中,软开关是使用软开关技术的开关过程,理想的软开关过程是电流或电压先降到零,电流或电压再逐渐上升到额定值,所以开关损耗近似为零,如此能够实现功率变换器的高频化。常用的软开关包括:ZVS(Zero Voltage Switching,零电压开关)、ZCS(Zero Current Switching,零电流开关)、ZCT(Zero Current Transition,零电流转换)、ZCT(Zero Voltage Transition,零电压转换)等。
LLC(即由两个电感L和一个电容C串联组成的)谐振电路是目前常用的一种高效的DC(Direct Current,直流)/DC变换器结构。为了提高LLC谐振功率变换器的效率,通常需要控制LLC谐振功率变换器工作在软开关的状态,以此减小开关损耗,进而提高LLC谐振功率变换器的功率密度。LLC谐振功率变换器的直流特性曲线如图1所示,其中,图1中的Q为LLC谐振功率变换器的品质因数。LLC谐振功率变换器可能工作在谐振频率点、ZVS区或者ZCS区。LLC谐振功率变换器工作在谐振频率点时的效率是最高的,但是在实际工作时,LLC谐振功率变换器由于负载、电压等参数的变化可能会工作在不同的区域。为了保证LLC谐振功率变换器的安全,应该保证LLC谐振功率变换器在所有负载范围内工作在谐振频率点或者图1中的第一区域,一般不工作在第二区域,更不能工作在第三区域。因为如果LLC谐振功率变换器工作在第二区域,在负载变大时,LLC谐振功率变换器可能会从第二区域进入第三区域,电压增益的单调性改变(即原来是在一定的负载下随着频率增加电压增益下降,变为在一定的负载下随着频率增加电压增益增加),存在炸机的隐患。因此,LLC谐振功率变换器需要通过判断LLC谐振功率变换器的谐振状态来判断LLC谐振功率变换器是工作在谐振频率点、第一区域、第二区域还是第三区域,从而根据谐振状态调整谐振功率变换器中开关管的开关频率。
现有的谐振功率变换器多是通过检测流入谐振网络的原边电流和施加在谐振网络上的方波电压的相位差来判断谐振功率变换器的谐振状态的。然而,
基于副边电流采样的谐振功率变换器由于无法获得谐振网络的原边电流,不能通过现有的方式判断谐振功率变换器的谐振状态。
发明内容
本发明实施例提供一种谐振功率变换器及其频率跟踪方法,能够通过对副边电流进行采样,判断谐振功率变换器的谐振状态,进而控制驱动信号的频率,达到驱动信号的频率跟踪谐振功率变换器的谐振频率的目的。
为达到上述目的,本发明的实施例采用如下技术方案:
第一方面,本发明实施例提供一种谐振功率变换器,包括逆变支路、与逆变支路相连的谐振支路、与谐振支路相连的变压器,以及与变压器相连的整流滤波支路,其中,变压器的原端与谐振支路相连,变压器的副端与整流滤波支路相连;此外,谐振功率变换器还包括:与变压器的副端和整流滤波支路均相连的检测支路,与检测支路相连的判断支路,以及与判断支路和逆变支路均相连的控制支路;
检测支路,用于获取变压器的副边电流,根据副边电流生成副边电流对应的脉冲信号,并发送副边电流对应的脉冲信号至判断支路;
控制支路,用于生成驱动信号,并发送驱动信号至逆变支路和判断支路,驱动信号用于驱动逆变支路;
判断支路,用于接收检测支路发送的副边电流对应的脉冲信号和控制支路发送的驱动信号,并根据副边电流对应的脉冲信号和驱动信号,生成并发送第一信息至控制支路,第一信息用于指示谐振功率变换器的谐振状态;
控制支路,还用于接收判断支路发送的第一信息,并根据第一信息,控制驱动信号的频率。
本发明实施例提供的谐振功率变换器中,由于判断支路可以接收检测支路发送的副边电流对应的脉冲信号,并根据副边电流对应的脉冲信号和驱动信号,生成用于指示谐振功率变换器的谐振状态的第一信息,使得控制支路根据第一信息,控制驱动信号的频率,达到了通过对副边电流进行采样,判断谐振功率变换器的谐振状态,并控制驱动信号的频率跟踪谐振功率变换器的谐振频率的目的。
可选的,谐振功率变换器还包括:
与检测支路、变压器的副边和整流滤波支路均相连的采样电路,用于对副边电流进行采样。
可选的,采样电路具体用于通过霍尔效应对副边电流进行采样,或者通过采样整流滤波支路中二极管两端的电压对副边电流进行采样。
可选的,采样电路具体包括:比较器,第一电阻、第二电阻、第三电阻和电容;
其中,比较器的输出端与第三电阻的一端相连,电容的一端与第三电阻的另一端相连,第三电阻的另一端与检测支路相连,比较器的正输入端与第一电阻的一端相连,比较器的负输入端与第二电阻的一端相连,第一电阻的另一端与变压器和整流滤波支路均相连,第二电阻的另一端和电容的另一端
接地。
可选的,采样电路具体包括:比较器、第一电阻、第二电阻、第三电阻、第四电阻,第五电阻和第六电阻;
其中,比较器的输出端与检测支路相连,比较器的负输入端与第一电阻的一端相连,第一电阻的另一端与第二电阻的一端相连,第二电阻的另一端与变压器和整流滤波支路均相连,第三电阻的一端与比较器的输出端相连,第三电阻的另一端与比较器的负输入端相连,比较器的正输入端与第四电阻的一端相连,第四电阻的另一端与第五电阻的一端相连,第五电阻的另一端与整流滤波支路相连,比较器的正输入端与第六电阻的一端相连,第六电阻的另一端接地。
可选的,逆变支路为半桥逆变电路结构、全桥逆变电路结构、三电平逆变电路结构中的任意一种电路结构;
谐振支路为由励磁电感、谐振电感和谐振电容串联构成的LLC谐振电路结构;
整流滤波支路为半波整流滤波电路结构或者全波整流滤波电路结构。
第二方面,本发明实施例提供一种谐振功率变换器的频率跟踪方法,应用于如第一方面任意一项的谐振功率变换器,该谐振功率变换器的频率跟踪方法包括:
首先,谐振功率变换器获取副边电流对应的脉冲信号和驱动信号;其次,谐振功率变换器根据副边电流对应的脉冲信号和驱动信号,生成用于指示谐振功率变换器的谐振状态的第一信息;最后,谐振功率变换器根据第一信息,控制驱动信号的频率。
本发明实施例提供的谐振功率变换器的频率跟踪方法中,由于谐振功率变换器可以根据副边电流对应的脉冲信号和驱动信号,生成用于指示谐振功率变换器的谐振状态的第一信息,从而根据第一信息,控制驱动信号的频率,达到了通过对副边电流进行采样,判断谐振功率变换器的谐振状态,并控制驱动信号的频率跟踪谐振功率变换器的谐振频率的目的。
可选的,谐振功率变换器获取副边电流对应的脉冲信号的方法包括:
谐振功率变换器先获取副边电流,再根据副边电流,生成副边电流对应的脉冲信号。
可选的,谐振功率变换器根据副边电流对应的脉冲信号和驱动信号,生成第一信息的方法包括:
谐振功率变换器确认副边电流对应的脉冲信号的上升沿和驱动信号的上升沿同步,且副边电流对应的脉冲信号的下降沿和驱动信号的下降沿同步;并生成第一信息,第一信息用于指示谐振功率变换器在谐振频率点工作。
谐振功率变换器根据第一信息,控制驱动信号的频率的方法包括:
谐振功率变换器根据第一信息,维持驱动信号的频率不变。
本发明实施例提供的谐振功率变换器的频率跟踪方法中,若副边电流对应的脉冲信号的上升沿和驱动信号的上升沿同步,且副边电流对应的脉冲信
号的下降沿和驱动信号的下降沿同步,则说明谐振功率变换器在谐振频率点工作,此时不需要调整驱动信号的频率,只需维持驱动信号的频率不变即可。
可选的,谐振功率变换器根据副边电流对应的脉冲信号和驱动信号,生成第一信息的方法包括:
谐振功率变换器确认副边电流对应的脉冲信号的上升沿和驱动信号的上升沿同步,且副边电流对应的脉冲信号的下降沿滞后于驱动信号的下降沿;并生成第一信息,第一信息用于指示谐振功率变换器在第一区域工作。
谐振功率变换器根据第一信息,控制驱动信号的频率的方法包括:
谐振功率变换器根据第一信息,降低驱动信号的频率。
本发明实施例提供的谐振功率变换器的频率跟踪方法中,若副边电流对应的脉冲信号的上升沿和驱动信号的上升沿同步,且副边电流对应的脉冲信号的下降沿滞后于驱动信号的下降沿,则说明谐振功率变换器在第一区域工作,此时需要降低驱动信号的频率,以使得谐振功率变换器在谐振频率点工作。
可选的,谐振功率变换器根据副边电流对应的脉冲信号和驱动信号,生成第一信息的方法包括:
谐振功率变换器确认副边电流对应的脉冲信号的上升沿和驱动信号的上升沿同步,且副边电流对应的脉冲信号的下降沿超前于驱动信号的下降沿;并生成第一信息,第一信息用于指示谐振功率变换器在第二区域工作。
谐振功率变换器根据第一信息,控制驱动信号的频率的方法包括:
谐振功率变换器根据第一信息,提高驱动信号的频率。
本发明实施例提供的谐振功率变换器的频率跟踪方法中,若副边电流对应的脉冲信号的上升沿和驱动信号的上升沿同步,且副边电流对应的脉冲信号的下降沿超前于驱动信号的下降沿,则说明谐振功率变换器在第二区域工作,此时需要提高驱动信号的频率,以使得谐振功率变换器在谐振频率点工作。
可选的,谐振功率变换器根据副边电流对应的脉冲信号和驱动信号,生成第一信息的方法包括:
谐振功率变换器确认副边电流对应的脉冲信号的上升沿超前于驱动信号的上升沿,且副边电流对应的脉冲信号的下降沿超前于驱动信号的下降沿;并生成第一信息,第一信息用于指示谐振功率变换器在第三区域工作。
谐振功率变换器根据第一信息,控制驱动信号的频率的方法包括:
谐振功率变换器首先根据第一信息,停止生成驱动信号;在提高驱动信号的频率后,再继续生成驱动信号。
本发明实施例提供的谐振功率变换器的频率跟踪方法中,若副边电流对应的脉冲信号的上升沿超前于驱动信号的上升沿,且副边电流对应的脉冲信号的下降沿超前于驱动信号的下降沿,则说明谐振功率变换器在第三区域工作,此时为了避免炸机,需要先停止生成驱动信号,在谐振功率变换器的控制支路提高驱动信号的频率后,谐振功率变换器的控制支路再继续生成驱动
信号并发送驱动信号至谐振功率变换器的逆变支路,随后判断谐振功率变换器是否仍在第三区域工作,若谐振功率变换器仍在第三区域工作,则继续停止生成驱动信号,提高驱动信号的频率,最终达到让谐振功率变换器在谐振频率点工作的目的。
本发明实施例提供一种谐振功率变换器及其频率跟踪方法,谐振功率变换器,包括逆变支路、与逆变支路相连的谐振支路、与谐振支路相连的变压器,以及与变压器相连的整流滤波支路,其中,变压器的原端与谐振支路相连,变压器的副端与整流滤波支路相连;与变压器的副端和整流滤波支路均相连的检测支路,与检测支路相连的判断支路,以及与判断支路和逆变支路均相连的控制支路;其中,检测支路,用于获取变压器的副边电流,根据副边电流生成副边电流对应的脉冲信号,并发送副边电流对应的脉冲信号至判断支路;控制支路,用于生成驱动信号,并发送驱动信号至逆变支路和判断支路,驱动信号用于驱动逆变支路;判断支路,用于接收检测支路发送的副边电流对应的脉冲信号和控制支路发送的驱动信号,并根据副边电流对应的脉冲信号和驱动信号,生成并发送第一信息至控制支路,第一信息用于指示谐振功率变换器的谐振状态;控制支路,还用于接收判断支路发送的第一信息,并根据第一信息,控制驱动信号的频率。基于上述的描述,由于判断支路可以接收检测支路发送的副边电流对应的脉冲信号,并根据副边电流对应的脉冲信号和驱动信号,生成用于指示谐振功率变换器的谐振状态的第一信息,使得控制支路根据第一信息,控制驱动信号的频率,达到了通过对副边电流进行采样,判断谐振功率变换器的谐振状态,并控制驱动信号的频率跟踪谐振功率变换器的谐振频率的目的。
图1为现有的LLC谐振功率变换器的直流特性曲线;
图2为现有的LLC谐振功率变换器工作于感性模式和容性模式时的波形图;
图3为本发明实施例提供的一种谐振功率变换器的结构示意图一;
图4为本发明实施例提供的一种谐振功率变换器的结构示意图二;
图5为本发明实施例提供的一种谐振功率变换器的结构示意图三;
图6为本发明实施例提供的一种谐振功率变换器的结构示意图四;
图7为本发明实施例提供的一种谐振功率变换器的结构示意图五;
图8为本发明实施例提供的一种谐振功率变换器的结构示意图六;
图9为本发明实施例提供的一种谐振功率变换器的结构示意图七;
图10为本发明实施例提供的一种谐振功率变换器的结构示意图八;
图11为本发明实施例提供的一种谐振功率变换器的结构示意图九;
图12为本发明实施例提供的一种谐振功率变换器的结构示意图十;
图13为本发明实施例提供的一种DC/DC变换器的结构示意图一;
图14为本发明实施例提供的一种DC/DC变换器的结构示意图二;
图15为本发明实施例提供的一种DC/DC变换器的结构示意图三;
图16为本发明实施例提供的一种DC/DC变换器的结构示意图四;
图17为本发明实施例提供的一种谐振功率变换器的频率跟踪方法的流程示意图一;
图18为本发明实施例提供的一种谐振功率变换器的频率跟踪方法的流程示意图二;
图19为本发明实施例提供的一种谐振功率变换器的频率跟踪方法的流程示意图三;
图20为本发明实施例提供的一种谐振功率变换器在谐振频率点工作的波形图;
图21为本发明实施例提供的一种谐振功率变换器的频率跟踪方法的流程示意图四;
图22为本发明实施例提供的一种谐振功率变换器在第一区域工作的波形图;
图23为本发明实施例提供的一种谐振功率变换器的频率跟踪方法的流程示意图五;
图24为本发明实施例提供的一种谐振功率变换器在第二区域工作的波形图;
图25为本发明实施例提供的一种谐振功率变换器的频率跟踪方法的流程示意图六;
图26为本发明实施例提供的一种谐振功率变换器在第三区域工作的波形图。
本发明实施例所描述技术主要用于LLC谐振功率变换器中,并且本发明实施例提供的LLC谐振功率变换器是一种开环结构的控制电路,其中,开环结构是指不将控制的结果反馈回来影响当前控制的结构。
为了判断LLC谐振功率变换器是工作在图1中的谐振频率点、第一区域、第二区域还是第三区域,现有技术中采用通过检测流入谐振网络的原边电流Ip和施加在谐振电路上的方波电压Vd的相位差来进行感性/容性模式的判断。其中,容性模式时原边电流Ip超前于方波电压Vd,感性模式时原边电流Ip滞后于方波电压Vd。图2中的(a)和图2中的(b)分别为LLC谐振功率变换器工作于感性模式和容性模式时的波形图。如图2(a)所示,原边电流Ip滞后于方波电压Vd,LLC谐振功率变换器工作于感性模式;如图2(b)所示,原边电流Ip超前于方波电压Vd,LLC谐振功率变换器工作于容性模式。LLC谐振功率变换器根据自身工作的模式,对谐振功率变换器中开关管的开关频率进行调整,即当LLC谐振功率变换器工作于感性模式时,需要降低谐振功率变换器中开关管的开关频率;当LLC谐振功率变换器工作于容性模式时,需要提高谐振功率变换器中开关管的开关频率。然而基于副边电流采样的LLC谐振功率变换器由于无法获得原边电流Ip,因此不能通过现有的方式判断LLC谐振功率变换器的谐振状态。本发明实施例提供的谐振功率变换器能
够通过对副边电流进行采样,判断谐振功率变换器的谐振状态,控制驱动信号的频率,达到驱动信号的频率跟踪谐振功率变换器的谐振频率的目的。
需要说明的是,本文中术语“和/或”,仅仅是一种描述关联对象的关联关系,表示可以存在三种关系,例如,A和/或B,可以表示:单独存在A,同时存在A和B,单独存在B这三种情况。另外,本文中字符“/”,一般表示前后关联对象是一种“或”的关系。
本发明实施例提供一种谐振功率变换器,如图3所示,包括逆变支路101、与逆变支路101相连的谐振支路102、与谐振支路102相连的变压器103、以及与变压器103相连的整流滤波支路104,其中,变压器103的原端与谐振支路102相连,变压器103的副端与整流滤波支路104相连,由逆变支路101、谐振支路102、变压器103、以及整流滤波支路104组成的电路可以称为主功率电路10(图3中虚线框所指示的部分);该谐振功率变换器还包括:与变压器103的副端和整流滤波支路104均相连的检测支路11,与检测支路11相连的判断支路12,以及与判断支路12和逆变支路101均相连的控制支路13。
其中,检测支路11,用于获取变压器103的副边电流,根据副边电流生成副边电流对应的脉冲信号,并发送副边电流对应的脉冲信号至判断支路12。
控制支路13,用于生成驱动信号,并发送驱动信号至逆变支路101和判断支路12,驱动信号用于驱动逆变支路101。
判断支路12,用于接收检测支路11发送的副边电流对应的脉冲信号和控制支路13发送的驱动信号,并根据副边电流对应的脉冲信号和驱动信号,生成并发送第一信息至控制支路13,其中,第一信息用于指示谐振功率变换器的谐振状态。
控制支路13,还用于接收判断支路12发送的第一信息,并根据第一信息,控制驱动信号的频率。
需要说明的是,判断支路12在根据驱动信号与副边电流对应的脉冲信号生成第一信息的过程中,驱动信号与副边电流对应的脉冲信号可以不是同一个开关周期内的信号。例如,判断支路12获取的控制支路13发送的驱动信号可以是上一个开关周期的驱动信号,也可以是前几个开关周期的驱动信号,本发明实施例不做限制。
还需要说明的是,本发明实施例中提到的驱动信号是用于驱动逆变支路101中开关管的信号,因此,逆变支路101中开关管的开关频率等于驱动信号的频率。
其中,如图4所示,谐振功率变换器还包括:
与检测支路11、变压器103的副边和整流滤波支路104均相连的采样电路14,用于对副边电流进行采样。
需要说明的是,采样电路14对副边电流进行采样的方法通常包括两种:一种是利用霍尔效应采样副边电流,其中,霍尔效应是指当电流垂直于外磁场通过导体时,载流子发生偏转,垂直于电流和磁场的方向会产生一附加电
场,从而在导体的两端产生电势差的现象;另一种方式是通过采样整流滤波支路104中二极管两端的电压来采样副边电流,因为二极管的单向导电性决定当二极管中有电流流过的时候正向导通压降只有零点几伏,如一般的硅二极管为0.7V左右,当二极管关断的时候二极管承受反向电压,当通过采样整流滤波支路104中二极管两端的电压来采样副边电流时,只需判断二极管电压的正负,即二极管电压为正时输出高电平,二极管电压为负时输出低电平。
具体的,逆变支路101为半桥逆变电路结构、全桥逆变电路结构以及三电平逆变电路结构中的任意一种电路结构。
谐振支路102为LLC谐振电路结构,其中,LLC谐振电路结构由励磁电感Lm、谐振电感Lr和谐振电容Cr依次串联组成。
整流滤波支路104为半波整流滤波电路结构或者全波整流滤波电路结构。
示例性的,如图5所示,以逆变支路101为半桥电路结构,谐振支路102为LLC谐振电路结构,整流滤波支路104为半波整流滤波电路结构为例,对本发明实施例提供谐振功率变换器进行详细说明:
通常的,本发明实施例提供谐振功率变换器包括用于向逆变支路101供电的直流电源。其中,逆变支路101(如图5中虚线框所指示的部分)具体包括第一开关管Q1和第二开关管Q2,第一开关管Q1的栅极与控制支路13相连,第一开关管Q1的漏极与电源正极相连,第一开关管Q1的源极与第二开关管Q2的漏极相连,第二开关管Q2的栅极与控制支路13相连,第二开关管Q2的源极与电源负极相连;谐振支路102(如图5中虚线框所指示的部分)具体包括串联连接的励磁电感Lm、谐振电感Lr和谐振电容Cr,其中,谐振电容Cr的一端与第二开关管Q2的漏极相连,谐振电容Cr的另一端与谐振电感Lr的一端相连,谐振电感Lr的另一端与励磁电感Lm的一端相连,励磁电感Lm的另一端与电源负极相连,励磁电感Lm的一端与变压器103的原端的一端相连,励磁电感Lm的另一端与变压器103的原端的另一端相连;整流滤波支路104(如图5中虚线框所指示的部分)具体包括第一二极管D1、第二二极管D2和滤波电容Cf,其中,第一二极管D1的输入端与变压器103的副端的一端相连,第一二极管D1的输出端与滤波电容Cf的一端相连,第二二极管D2的输入端与变压器103的副端的另一端相连,第二二极管D2的输出端与滤波电容Cf的另一端相连。
还需要说明的是,滤波电容Cf的一端通常和输出端的一端相连,滤波电容Cf的另一端和输出端的另一端相连,输出端通常为电阻。变压器103原端和副端的电流方向一致。
控制支路13分别发送驱动信号至第一开关管Q1的栅极和第二开关管Q2的栅极,其中,发送至第一开关管Q1的驱动信号和发送至第二开关管Q2的驱动信号的相位相反,频率相同,因此,当第一开关管Q1导通时对应第一二极管D1导通,此时,判断支路12比较第一开关管Q1的驱动信号和副边电流对应的脉冲信号的上升沿的位置关系和第一开关管Q1的驱动信号和副边电流对应的脉冲信号的下降沿的位置关系;当第二开关管Q2导通时对应第二
二极管D2导通,此时,判断支路12比较第二开关管Q2的驱动信号和副边电流对应的脉冲信号的上升沿的位置关系和第二开关管Q2的驱动信号和副边电流对应的脉冲信号的下降沿的位置关系。
相应的,若判断支路12判断出副边电流对应的脉冲信号的上升沿和驱动信号的上升沿同步,且副边电流对应的脉冲信号的下降沿和驱动信号的下降沿同步,则说明谐振功率变换器在谐振频率点工作,控制支路13维持驱动信号的频率不变。
若判断支路12判断出副边电流对应的脉冲信号的上升沿和驱动信号的上升沿同步,且副边电流对应的脉冲信号的下降沿滞后于驱动信号的下降沿,则说明谐振功率变换器在第一区域工作,控制支路13需要降低驱动信号的频率。
若判断支路12判断出副边电流对应的脉冲信号的上升沿和驱动信号的上升沿同步,且副边电流对应的脉冲信号的下降沿超前于驱动信号的下降沿,则说明谐振功率变换器在第二区域工作,控制支路13需要提高驱动信号的频率。
若判断支路12判断出副边电流对应的脉冲信号的上升沿超前于驱动信号的上升沿,且副边电流对应的脉冲信号的下降沿超前于驱动信号的下降沿,则说明谐振功率变换器在第三区域工作,此时为了避免炸机,需要先停止生成驱动信号,在谐振功率变换器的控制支路提高驱动信号的频率后,谐振功率变换器的控制支路再继续生成驱动信号并发送驱动信号至谐振功率变换器的逆变支路,随后判断谐振功率变换器是否仍在第三区域工作,若谐振功率变换器仍在第三区域工作,则继续停止生成驱动信号,提高驱动信号的频率,最终达到让谐振功率变换器在谐振频率点工作的目的。
可选的,如图6所示,以逆变支路101为半桥逆变电路结构,谐振支路102为LLC谐振电路结构,整流滤波支路104为半波整流滤波电路结构为例,采样电路14具体可以包括:比较器,第一电阻R1、第二电阻R2、第三电阻R3和电容C;
其中,比较器的输出端与第三电阻R3的一端相连,电容C的一端与第三电阻R3的另一端相连,第三电阻R3的另一端与检测支路11相连,比较器的正输入端与第一电阻R1的一端相连,比较器的负输入端与第二电阻R2的一端相连,第一电阻R1的另一端与变压器103的副端和整流滤波支路104均相连,第二电阻R2的另一端和电容C的另一端接地。
需要说明的是,采样电路14中包括的第一电阻R1、第二电阻R2、第三电阻R3都可以是多个电阻串并联等效出的电阻;电容C也可以是多个电容串并联等效出的电容,本发明实施例不做限制。
可选的,如图7所示,以逆变支路101为半桥逆变电路结构,谐振支路102为LLC谐振电路结构,整流滤波支路104为半波整流滤波电路结构为例,采样电路14具体包括:比较器、第一电阻R1、第二电阻R2、第三电阻R3、第四电阻R4,第五电阻R5和第六电阻R6;
其中,比较器的输出端与检测支路11相连,比较器的负输入端与第一电阻R1的一端相连,第一电阻R1的另一端与第二电阻R2的一端相连,第二电阻R2的另一端与变压器103的副端和整流滤波支路104均相连,第三电阻R3的一端与比较器的输出端相连,第三电阻R3的另一端与比较器的负输入端相连,比较器的正输入端与第四电阻R4的一端相连,第四电阻R4的另一端与第五电阻R5的一端相连,第五电阻R5的另一端与整流滤波支路104相连,比较器的正输入端与第六电阻R6的一端相连,第六电阻R6的另一端接地。
需要说明的是,采样电路14中包括的第一电阻R1、第二电阻R2、第三电阻R3、第四电阻R4,第五电阻R5和第六电阻R6都可以是多个电阻串并联等效出的电阻,本发明实施例不做限制。
可以理解的是,本发明实施例提供的两种采样电路14的结构只是采样电路14可实现的方式,其他能够达到采样副边电流目的的结构均可以是本发明实施例提到的采样电路14,本发明实施例对此不作限制。
示例性的,如图8所示,以逆变支路101为半桥电路结构,谐振支路102为LLC谐振电路结构,整流滤波支路104为全波整流滤波电路结构为例,对本发明实施例提供谐振功率变换器进行详细说明:
通常的,本发明实施例提供谐振功率变换器包括用于向逆变支路101供电的直流电源。其中,逆变支路101(如图8中虚线框所指示的部分)具体包括第一开关管Q1和第二开关管Q2,第一开关管Q1的栅极与控制支路13相连,第一开关管Q1的漏极与电源正极相连,第一开关管Q1的源极与第二开关管Q2的漏极相连,第二开关管Q2的栅极与控制支路13相连,第二开关管Q2的源极与电源负极相连;谐振支路102(如图8中虚线框所指示的部分)具体包括串联连接的励磁电感Lm、谐振电感Lr和谐振电容Cr,其中,谐振电容Cr的一端与第二开关管Q2的漏极相连,谐振电容Cr的另一端与谐振电感Lr的一端相连,谐振电感Lr的另一端与励磁电感Lm的一端相连,励磁电感Lm的另一端与电源负极相连,励磁电感Lm的一端与变压器103的原端的一端相连,励磁电感Lm的另一端与变压器103的原端的另一端相连;整流滤波支路104(如图8中虚线框所指示的部分)具体包括第一二极管D1、第二二极管D2、第三二极管D3、第四二极管D4和滤波电容Cf,其中,第一二极管D1的输入端与变压器103的副端的一端相连,第一二极管D1的输出端与滤波电容Cf的一端相连,第二二极管D2的输出端与变压器103的副端的一端相连,第二二极管D2的输入端与滤波电容Cf的另一端相连,第三二极管D3的输入端与滤波电容Cf的另一端相连,第三二极管D3的输出端与滤波电容Cf的一端相连,第四二极管D4的输出端与变压器103的副端的另一端相连,第四二极管D4的输入端与滤波电容Cf的另一端相连。
还需要说明的是,滤波电容Cf的一端通常和输出端的一端相连,滤波电容Cf的另一端和输出端的另一端相连,输出端通常为电阻。变压器103原端和副端的电流方向一致。
控制支路13分别发送驱动信号至第一开关管Q1的栅极和第二开关管Q2的栅极,其中,发送至第一开关管Q1的驱动信号和发送至第二开关管Q2的驱动信号的相位相反,频率相同,因此,当第一开关管Q1导通时对应第一二极管D1和第二二极管D2导通,此时,判断支路12比较第一开关管Q1的驱动信号和副边电流对应的脉冲信号的上升沿的位置关系和第一开关管Q1的驱动信号和副边电流对应的脉冲信号的下降沿的位置关系;当第二开关管Q2导通时对应第三二极管D3和第四二极管D4导通,此时,判断支路12比较第二开关管Q2的驱动信号和副边电流对应的脉冲信号的上升沿的位置关系和第二开关管Q2的驱动信号和副边电流对应的脉冲信号的下降沿的位置关系。比较的结果与上述图5所对应的结果相同,此处不再赘述。
示例性的,如图9所示,以逆变支路101为全桥电路结构,谐振支路102为LLC谐振电路结构,整流滤波支路104为半波整流滤波电路结构为例,对本发明实施例提供谐振功率变换器进行详细说明:
通常的,本发明实施例提供谐振功率变换器包括用于向逆变支路101供电的直流电源。其中,逆变支路101(如图9中虚线框所指示的部分)具体包括第一开关管Q1、第二开关管Q2、第三开关管Q3和第四开关管Q4,其中,第一开关管Q1的栅极控制支路13相连,第一开关管Q1的漏极与电源正极相连,第一开关管Q1的源极与第四开关管Q4的漏极相连,第二开关管Q2的栅极与控制支路13相连,第二开关管Q2的漏极与第三开关管Q3的源极相连,第二开关管Q2的源极与电源负极相连,第三开关管Q3的栅极与控制支路13相连,第三开关管Q3的漏极与电源正极相连,第四开关管Q4的栅极与控制支路13相连,第四开关管Q4的源极与电源负极相连;谐振支路102(如图9中虚线框所指示的部分)具体包括串联连接的励磁电感Lm、谐振电感Lr和谐振电容Cr,其中,谐振电容Cr的一端与第二开关管Q2的漏极相连,谐振电容Cr的另一端与谐振电感Lr的一端相连,谐振电感Lr的另一端与励磁电感Lm的一端相连,励磁电感Lm的另一端与电源负极相连,励磁电感Lm的一端与变压器103的原端的一端相连,励磁电感Lm的另一端与变压器103的原端的另一端相连;整流滤波支路104(如图9中虚线框所指示的部分)具体包括第一二极管D1、第二二极管D2和滤波电容Cf,其中,第一二极管D1的输入端与变压器103的副端的一端相连,第一二极管D1的输出端与滤波电容Cf的一端相连,第二二极管D2的输入端与变压器103的副端的另一端相连,第二二极管D2的输出端与滤波电容Cf的另一端相连。
还需要说明的是,滤波电容Cf的一端通常和输出端的一端相连,滤波电容Cf的另一端和输出端的另一端相连,输出端通常为电阻。变压器103原端和副端的电流方向一致。
控制支路13分别发送驱动信号至第一开关管Q1和第四开关管Q4的栅极,以及发送驱动信号至第二开关管Q2的栅极和第三开关管Q3的栅极,其中,发送至第一开关管Q1和第四开关管Q4的驱动信号与发送至第二开关管Q2和第三开关管Q3的驱动信号的相位相反,频率相同,因此,当第一开关
管Q1与第四开关管Q4导通时对应第一二极管D1导通,此时,判断支路12比较第一开关管Q1或者第四开关管Q4的驱动信号和副边电流对应的脉冲信号的上升沿的位置关系和第一开关管Q1或者第四开关管Q4的驱动信号和副边电流对应的脉冲信号的下降沿的位置关系;当第二开关管Q2与第三开关管Q3导通时对应第二二极管D2导通,此时,判断支路12比较第二开关管Q2或者第三开关管Q3的驱动信号和副边电流对应的脉冲信号的上升沿的位置关系和第二开关管Q2或者第三开关管Q3的驱动信号和副边电流对应的脉冲信号的下降沿的位置关系。比较的结果与上述图5所对应的结果相同,此处不再赘述。
示例性的,如图10所示,以逆变支路101为全桥电路结构,谐振支路102为LLC谐振电路结构,整流滤波支路104为全波整流滤波电路结构为例,对本发明实施例提供谐振功率变换器进行详细说明:
通常的,本发明实施例提供谐振功率变换器包括用于向逆变支路101供电的直流电源。其中,逆变支路101(如图10中虚线框所指示的部分)具体包括第一开关管Q1、第二开关管Q2、第三开关管Q3和第四开关管Q4,其中,第一开关管Q1的栅极控制支路13相连,第一开关管Q1的漏极与电源正极相连,第一开关管Q1的源极与第四开关管Q4的漏极相连,第二开关管Q2的栅极与控制支路13相连,第二开关管Q2的漏极与第三开关管Q3的源极相连,第二开关管Q2的源极与电源负极相连,第三开关管Q3的栅极与控制支路13相连,第三开关管Q3的漏极与电源正极相连,第四开关管Q4的栅极与控制支路13相连,第四开关管Q4的源极与电源负极相连;谐振支路102(如图10中虚线框所指示的部分)具体包括串联连接的励磁电感Lm、谐振电感Lr和谐振电容Cr,其中,谐振电容Cr的一端与第二开关管Q2的漏极相连,谐振电容Cr的另一端与谐振电感Lr的一端相连,谐振电感Lr的另一端与励磁电感Lm的一端相连,励磁电感Lm的另一端与电源负极相连,励磁电感Lm的一端与变压器103的原端的一端相连,励磁电感Lm的另一端与变压器103的原端的另一端相连;整流滤波支路104(如图10中虚线框所指示的部分)具体包括第一二极管D1、第二二极管D2、第三二极管D3、第四二极管D4和滤波电容Cf,其中,第一二极管D1的输入端与变压器103的副端的一端相连,第一二极管D1的输出端与滤波电容Cf的一端相连,第二二极管D2的输出端与变压器103的副端的一端相连,第二二极管D2的输入端与滤波电容Cf的另一端相连,第三二极管D3的输入端与滤波电容Cf的另一端相连,第三二极管D3的输出端与滤波电容Cf的一端相连,第四二极管D4的输出端与变压器103的副端的另一端相连,第四二极管D4的输入端与滤波电容Cf的另一端相连。
还需要说明的是,滤波电容Cf的一端通常和输出端的一端相连,滤波电容Cf的另一端和输出端的另一端相连,输出端通常为电阻。变压器103原端和副端的电流方向一致。
控制支路13分别发送驱动信号至第一开关管Q1和第四开关管Q4的栅
极,以及发送驱动信号至第二开关管Q2的栅极和第三开关管Q3的栅极,其中,发送至第一开关管Q1和第四开关管Q4的驱动信号与发送至第二开关管Q2和第三开关管Q3的驱动信号的相位相反,频率相同,因此,当第一开关管Q1与第四开关管Q4导通时对应第一二极管D1和第二二极管D2导通,此时,判断支路12比较第一开关管Q1或者第四开关管Q4的驱动信号和副边电流对应的脉冲信号的上升沿的位置关系和第一开关管Q1或者第四开关管Q4的驱动信号和副边电流对应的脉冲信号的下降沿的位置关系;当第二开关管Q2与第三开关管Q3导通时对应第三二极管D3和第四二极管D4导通,此时,判断支路12比较第二开关管Q2或者第三开关管Q3的驱动信号和副边电流对应的脉冲信号的上升沿的位置关系和第二开关管Q2或者第三开关管Q3的驱动信号和副边电流对应的脉冲信号的下降沿的位置关系。比较的结果与上述图5所对应的结果相同,此处不再赘述。
示例性的,如图11所示,以逆变支路101为三电平电路结构,谐振支路102为LLC谐振电路结构,整流滤波支路104为半波整流滤波电路结构为例,对本发明实施例提供谐振功率变换器进行详细说明:
通常的,本发明实施例提供谐振功率变换器包括用于向逆变支路101供电的直流电源。其中,逆变支路101(如图11中虚线框所指示的部分)具体包括第一开关管Q1、第二开关管Q2、第三开关管Q3、第四开关管Q4,第五二极管D5和第六二极管D6,第一开关管Q1的栅极控制支路13相连,第一开关管Q1的漏极与电源正极相连,第一开关管Q1的源极与第二开关管Q2的漏极相连,第二开关管Q2的栅极控制支路13相连,第二开关管Q2的源极和第三开关管Q3的漏极相连,第三开关管Q3的栅极控制支路13相连,第三开关管Q3的源极和第四开关管Q4的漏极相连,第四开关管Q4的栅极控制支路13相连,第四开关管Q4的源极与电源负极相连,第五二极管D5的输入端与第六二极管D6的输出端相连,第五二极管D5的输出端与第一开关管Q1的源极相连,第六二极管D6的输入端与第三开关管Q3的源极相连;谐振支路102(如图11中虚线框所指示的部分)具体包括串联连接的励磁电感Lm、谐振电感Lr和谐振电容Cr,其中,谐振电容Cr的一端与第二开关管Q2的漏极相连,谐振电容Cr的另一端与谐振电感Lr的一端相连,谐振电感Lr的另一端与励磁电感Lm的一端相连,励磁电感Lm的另一端与电源负极相连,励磁电感Lm的一端与变压器103的原端的一端相连,励磁电感Lm的另一端与变压器103的原端的另一端相连;整流滤波支路104(如图11中虚线框所指示的部分)具体包括第一二极管D1、第二二极管D2和滤波电容Cf,其中,第一二极管D1的输入端与变压器103的副端的一端相连,第一二极管D1的输出端与滤波电容Cf的一端相连,第二二极管D2的输入端与变压器103的副端的另一端相连,第二二极管D2的输出端与滤波电容Cf的另一端相连。
还需要说明的是,滤波电容Cf的一端通常和输出端的一端相连,滤波电容Cf的另一端和输出端的另一端相连,输出端通常为电阻。变压器103原端
和副端的电流方向一致。
控制支路13分别发送驱动信号至第一开关管Q1和第二开关管Q2的栅极,以及发送驱动信号至第三开关管Q3的栅极和第四开关管Q4的栅极,其中,发送至第一开关管Q1和第二开关管Q2的驱动信号与发送至第三开关管Q3的栅极和第四开关管Q4的驱动信号的相位相反,频率相同,因此,当第一开关管Q1与第二开关管Q2导通时对应第一二极管D1导通,此时,判断支路12比较第一开关管Q1或者第二开关管Q2的驱动信号和副边电流对应的脉冲信号的上升沿的位置关系和第一开关管Q1或者第二开关管Q2的驱动信号和副边电流对应的脉冲信号的下降沿的位置关系;当第三开关管Q3与第四开关管Q4导通时对应第二二极管D2导通,此时,判断支路12比较第三开关管Q3或者第四开关管Q4的驱动信号和副边电流对应的脉冲信号的上升沿的位置关系和第三开关管Q3或者第四开关管Q4的驱动信号和副边电流对应的脉冲信号的下降沿的位置关系。比较的结果与上述图5所对应的结果相同,此处不再赘述。
示例性的,如图12所示,以逆变支路101为三电平电路结构,谐振支路102为LLC谐振电路结构,整流滤波支路104为全波整流滤波电路结构为例,对本发明实施例提供谐振功率变换器进行详细说明:
通常的,本发明实施例提供谐振功率变换器包括用于向逆变支路101供电的直流电源。其中,逆变支路101(如图12中虚线框所指示的部分)具体包括第一开关管Q1、第二开关管Q2、第三开关管Q3、第四开关管Q4,第五二极管D5和第六二极管D6,第一开关管Q1的栅极控制支路13相连,第一开关管Q1的漏极与电源正极相连,第一开关管Q1的源极与第二开关管Q2的漏极相连,第二开关管Q2的栅极控制支路13相连,第二开关管Q2的源极和第三开关管Q3的漏极相连,第三开关管Q3的栅极控制支路13相连,第三开关管Q3的源极和第四开关管Q4的漏极相连,第四开关管Q4的栅极控制支路13相连,第四开关管Q4的源极与电源负极相连,第五二极管D5的输入端与第六二极管D6的输出端相连,第五二极管D5的输出端与第一开关管Q1的源极相连,第六二极管D6的输入端与第三开关管Q3的源极相连;谐振支路102(如图12中虚线框所指示的部分)具体包括串联连接的励磁电感Lm、谐振电感Lr和谐振电容Cr,其中,谐振电容Cr的一端与第二开关管Q2的漏极相连,谐振电容Cr的另一端与谐振电感Lr的一端相连,谐振电感Lr的另一端与励磁电感Lm的一端相连,励磁电感Lm的另一端与电源负极相连,励磁电感Lm的一端与变压器103的原端的一端相连,励磁电感Lm的另一端与变压器103的原端的另一端相连;整流滤波支路104(如图12中虚线框所指示的部分)具体包括第一二极管D1、第二二极管D2、第三二极管D3、第四二极管D4和滤波电容Cf,其中,第一二极管D1的输入端与变压器103的副端的一端相连,第一二极管D1的输出端与滤波电容Cf的一端相连,第二二极管D2的输出端与变压器103的副端的一端相连,第二二极管D2的输入端与滤波电容Cf的另一端相连,第三二极管D3的输入端与滤波电
容Cf的另一端相连,第三二极管D3的输出端与滤波电容Cf的一端相连,第四二极管D4的输出端与变压器103的副端的另一端相连,第四二极管D4的输入端与滤波电容Cf的另一端相连。
还需要说明的是,滤波电容Cf的一端通常和输出端的一端相连,滤波电容Cf的另一端和输出端的另一端相连,输出端通常为电阻。变压器103原端和副端的电流方向一致。
控制支路13分别发送驱动信号至第一开关管Q1和第二开关管Q2的栅极,以及发送驱动信号至第三开关管Q3的栅极和第四开关管Q4的栅极,其中,发送至第一开关管Q1和第二开关管Q2的驱动信号与发送至第三开关管Q3的栅极和第四开关管Q4的驱动信号的相位相反,频率相同,因此,当第一开关管Q1与第二开关管Q2导通时对应第一二极管D1和第二二极管D2导通,此时,判断支路12比较第一开关管Q1或者第二开关管Q2的驱动信号和副边电流对应的脉冲信号的上升沿的位置关系和第一开关管Q1或者第二开关管Q2的驱动信号和副边电流对应的脉冲信号的下降沿的位置关系;当第三开关管Q3与第四开关管Q4导通时对应第三二极管D3和第四二极管D4导通,此时,判断支路12比较第三开关管Q3或者第四开关管Q4的驱动信号和副边电流对应的脉冲信号的上升沿的位置关系和第三开关管Q3或者第四开关管Q4的驱动信号和副边电流对应的脉冲信号的下降沿的位置关系。比较的结果与上述图5所对应的结果相同,此处不再赘述。
需要说明的是,本发明实施例中所提到的控制支路13驱动逆变支路101中的各个开关管,可以是控制支路13与每一个开关管单独相连,即控制支路13单独驱动每一个开关;也可以是控制支路13与需要同时导通的多个开关管相连,本发明实施例不做限制。本发明实施例图5至图12是以控制支路13与每一个开关管单独相连为例描述的。
需要补充的是,本发明实施例提供的LLC谐振功率变换器的频率跟踪方法是应用在开环LLC电路中,开环LLC谐振功率变换器可以与闭环的DC/DC变换器串联使用,实现电压的调整。
示例性的,如图13所示,LLC谐振功率变换器可以应用在由一个DC/DC变换结构和一个LLC谐振功率变换器组成的DC/DC变换器中。其中,DC/DC变换结构是闭环控制的,通过采样LLC谐振功率变换器的输出电压作为DC/DC变换结构的反馈电压,通过调整DC/DC变换结构的输出电压达到调整LLC谐振功率变换器的开关频率,达到驱动信号的频率跟踪谐振功率变换器的谐振频率的目的。
具体的,DC/DC变换结构可以是任意一种单相DC/DC变换结构,LLC谐振功率变换器可以是上述实施例所描述的任意一种LLC谐振功率变换器。如图14所示,DC/DC变换结构为降压变换器,LLC谐振功率变换器的逆变支路101为半桥逆变电路结构,谐振支路102为LLC谐振电路结构,整流滤波支路104为半波整流滤波电路结构。
示例性的,如图15所示,LLC谐振功率变换器可以应用在由两个DC/DC
变换结构和一个LLC谐振功率变换器组成的DC/DC变换器中。其中,LLC谐振功率变换器的电压可以通过图15中左侧的DC/DC变换结构来调节,也可以由图15中右侧的DC/DC变换结构调节。通过图15中左侧的DC/DC变换结构调节是保证LLC谐振功率变换器的输出电压稳定在设定值,通过改变图15中左侧的DC/DC变换结构的输出电压达到调整频率的目的。通过图15中右侧的DC/DC变换结构的输出电压调节是保持图15中右侧的DC/DC变换结构的输出电压不变,通过改变图15中右侧的DC/DC变换结构的输入电压达到调整频率的目的。
具体的,DC/DC变换结构可以是任意一种单相DC/DC变换结构,LLC谐振功率变换器可以是上述实施例所描述的任意一种LLC谐振功率变换器。如图16所示,两个DC/DC变换结构均为降压变换器,LLC谐振功率变换器的逆变支路101为半桥逆变电路结构,谐振支路102为LLC谐振电路结构,整流滤波支路104为半波整流滤波电路结构。
上述闭环控制的DC/DC变换器可以是降压变换器,也可以是升压变换器或者升降压变换器,本发明实施例不做限制。
需要说明的是,本发明实施例提供的开关管可以为IGBT(Insulated Gate Bipolar Transistor,绝缘栅双极型晶体管)、MOSFET(Metal-Oxide-Semiconductor Field-Effect Transistor,金属氧化物半导体场效应晶体管)管、三极管等,发明实施例整流滤波支路中提供的二极管都可以替换为同步整流管,本发明实施例不做限制。
本发明实施例提供一种谐振功率变换器,包括逆变支路、与逆变支路相连的谐振支路、与谐振支路相连的变压器,以及与变压器相连的整流滤波支路,其中,变压器的原端与谐振支路相连,变压器的副端与整流滤波支路相连;与变压器的副端和整流滤波支路均相连的检测支路,与检测支路相连的判断支路,以及与判断支路和逆变支路均相连的控制支路;其中,检测支路,用于获取变压器的副边电流,根据副边电流生成副边电流对应的脉冲信号,并发送副边电流对应的脉冲信号至判断支路;控制支路,用于生成驱动信号,并发送驱动信号至逆变支路和判断支路,驱动信号用于驱动逆变支路;判断支路,用于接收检测支路发送的副边电流对应的脉冲信号和控制支路发送的驱动信号,并根据副边电流对应的脉冲信号和驱动信号,生成并发送第一信息至控制支路,第一信息用于指示谐振功率变换器的谐振状态;控制支路,还用于接收判断支路发送的第一信息,并根据第一信息,控制驱动信号的频率。基于上述的描述,由于判断支路可以接收检测支路发送的副边电流对应的脉冲信号,并根据副边电流对应的脉冲信号和驱动信号,生成用于指示谐振功率变换器的谐振状态的第一信息,使得控制支路根据第一信息,控制驱动信号的频率,达到了通过对副边电流进行采样,判断谐振功率变换器的谐振状态,并控制驱动信号的频率跟踪谐振功率变换器的谐振频率的目的。
本发明实施例还提供一种谐振功率变换器的频率跟踪方法,应用于上述
实施例所描述的谐振功率变换器,谐振功率变换器包括逆变支路、与逆变支路相连的谐振支路、与谐振支路相连的变压器,以及与变压器相连的整流滤波支路,其中,变压器的原端与谐振支路相连,变压器的副端与整流滤波支路相连;与变压器的副端和整流滤波支路均相连的检测支路;与检测支路相连的判断支路;与判断支路和逆变支路均相连的控制支路,如图17所示,方法包括:
S101、谐振功率变换器获取副边电流对应的脉冲信号和驱动信号。
具体的,谐振功率变换器的判断支路获取副边电流对应的脉冲信号和驱动信号。
具体的,如图18所示,步骤S101可以包括S101a-S101c:
S101a、谐振功率变换器获取副边电流。
谐振功率变换器的检测支路可以直接从主功率电路的变压器的副边获取变压器的副边电流,也可以由谐振功率变换器的采样电路采样变压器的副边电流,再发送给检测支路。
S101b、谐振功率变换器根据副边电流,生成副边电流对应的脉冲信号。
谐振功率变换器的检测支路根据副边电流,生成副边电流对应的脉冲信号的方法可以包括:将副边电流通过一个电阻转化为电压信号,将该电压信号与0比较得到一个与正向电流时间相对应的副边电流对应的脉冲信号;或者,若采样电路采样的是二极管电压,则只需判断二极管电压的正负,二极管电压为正时输出高电平,二极管电压为负时输出低电平。
随后,谐振功率变换器的检测支路发送副边电流对应的脉冲信号至判断支路。
S101c、谐振功率变换器获取驱动信号。
具体的,谐振功率变换器的判断支路获取控制支路发送的驱动信号。
S102、谐振功率变换器根据副边电流对应的脉冲信号和驱动信号,生成第一信息,第一信息用于指示谐振功率变换器的谐振状态。
S103、谐振功率变换器根据第一信息,控制驱动信号的频率。
具体的,如图19所示,步骤S102可以包括S102a和S102b:
S102a、谐振功率变换器确认副边电流对应的脉冲信号的上升沿和驱动信号的上升沿同步,且副边电流对应的脉冲信号的下降沿和驱动信号的下降沿同步。
S102b、谐振功率变换器生成第一信息,第一信息用于指示谐振功率变换器在谐振频率点工作。
具体的,谐振功率变换器中的判断支路执行步骤S102a和S102b,并把第一信息发送给谐振功率变换器中的控制支路。
与此对应的,步骤S103可以包括S103a:
S103a、谐振功率变换器根据第一信息,维持驱动信号的频率不变。
具体的,谐振功率变换器中的控制支路执行步骤S103a。
如图20所示,若副边电流对应的脉冲信号的上升沿和驱动信号的上升沿
同步,且副边电流对应的脉冲信号的下降沿和驱动信号的下降沿同步,则说明谐振功率变换器在谐振频率点工作,此时不需要调整驱动信号的频率,只需维持驱动信号的频率不变即可。
具体的,如图21所示,步骤S102可以包括S102c和S102d:
S102c、谐振功率变换器确认副边电流对应的脉冲信号的上升沿和驱动信号的上升沿同步,且副边电流对应的脉冲信号的下降沿滞后于驱动信号的下降沿。
S102d、谐振功率变换器生成第一信息,第一信息用于指示谐振功率变换器在第一区域工作。
具体的,谐振功率变换器中的判断支路执行步骤S102c和S102d,并把第一信息发送给谐振功率变换器中的控制支路。
与此对应的,步骤S103可以包括S103b:
S103b、谐振功率变换器根据第一信息,降低驱动信号的频率。
具体的,谐振功率变换器中的控制支路执行步骤S103b,并把降低了频率的驱动信号发送给谐振功率变换器的判断支路。
如图22所示,若副边电流对应的脉冲信号的上升沿和驱动信号的上升沿同步,且副边电流对应的脉冲信号的下降沿滞后于驱动信号的下降沿,则说明谐振功率变换器在第一区域工作,此时需要降低驱动信号的频率,以使得谐振功率变换器在谐振频率点工作。
可以理解的是,谐振功率变换器可以逐步降低驱动信号的频率,经过多次调整使得谐振功率变换器在谐振频率点工作。例如谐振功率变换器每次将驱动信号的频率降低预设值,然后再进行判断,多次调整谐振功率变换器的驱动信号的频率,使得谐振功率变换器最终在谐振频率点工作。
具体的,如图23所示,步骤S102可以包括S102e和S102f:
S102e、谐振功率变换器确认副边电流对应的脉冲信号的上升沿和驱动信号的上升沿同步,且副边电流对应的脉冲信号的下降沿超前于驱动信号的下降沿。
S102f、谐振功率变换器生成第一信息,第一信息用于指示谐振功率变换器在第二区域工作。
具体的,谐振功率变换器中的判断支路执行步骤S102e和S102f,并把第一信息发送给谐振功率变换器中的控制支路。
与此对应的,步骤S103可以包括S103c:
S103c、谐振功率变换器根据第一信息,提高驱动信号的频率。
具体的,谐振功率变换器中的控制支路执行步骤S103c,并把提高了频率的驱动信号发送给谐振功率变换器的判断支路。
如图24所示,若副边电流对应的脉冲信号的上升沿和驱动信号的上升沿同步,且副边电流对应的脉冲信号的下降沿超前于驱动信号的下降沿,则说明谐振功率变换器在第二区域工作,此时需要提高驱动信号的频率,以使得谐振功率变换器在谐振频率点工作。
同理,谐振功率变换器可以逐步提高驱动信号的频率,经过多次调整使得谐振功率变换器在谐振频率点工作。
具体的,如图25所示,步骤S102可以包括S102g和S102h:
S102g、谐振功率变换器确认副边电流对应的脉冲信号的上升沿超前于驱动信号的上升沿,且副边电流对应的脉冲信号的下降沿超前于驱动信号的下降沿。
S102h、谐振功率变换器生成第一信息,第一信息用于指示谐振功率变换器在第三区域工作。
具体的,谐振功率变换器中的判断支路执行步骤S102g和S102h,并把第一信息发送给谐振功率变换器中的控制支路。
与此对应的,步骤S103可以包括S103d和S103e:
S103d、谐振功率变换器根据第一信息,停止生成驱动信号。
S103e、谐振功率变换器在提高驱动信号的频率后,生成驱动信号。
具体的,谐振功率变换器中的控制支路执行步骤S103d和S103e,并把提高了频率的驱动信号发送给谐振功率变换器的判断支路。
如图26所示,若副边电流对应的脉冲信号的上升沿超前于驱动信号的上升沿,且副边电流对应的脉冲信号的下降沿超前于驱动信号的下降沿,则说明谐振功率变换器在第三区域工作,此时为了避免炸机,需要先停止生成驱动信号,在谐振功率变换器的控制支路提高驱动信号的频率后,谐振功率变换器的控制支路再继续生成驱动信号并发送驱动信号至谐振功率变换器的逆变支路,随后判断谐振功率变换器是否仍在第三区域工作,若谐振功率变换器仍在第三区域工作,则继续停止生成驱动信号,提高驱动信号的频率,最终达到让谐振功率变换器在谐振频率点工作的目的。
需要说明的是,副边电流对应的脉冲信号的上升沿与驱动信号的上升沿,且副边电流对应的脉冲信号的下降沿与驱动信号的下降沿的关系的可以由两种方法判断:一是通过逻辑运算进行判断,二是通过比较代表两个脉冲信号上升沿的寄存器中的数据大小和代表两个脉冲信号下降沿的寄存器中的数据大小进行判断,也就是判断两个量之间的时间差。
示例性的,在第一种方法中,假设驱动信号用A表示,副边电流对应的脉冲信号用B表示,采用逻辑运算判断的方法是:如果A与B的结果既等于A也等于B,则A与B相同,表示谐振功率变换器处于谐振频率点;如果A与B的结果等于A不等于B,则表示变换器处于区域1;如果A与B的结果不等于A但等于B,则表示变换器处于区域2;如果A与B的结果既不等于A又不等于B,则表示变换器处于区域3。
示例性的,在第二种方法中,通过比较代表两个脉冲信号上升沿和下降沿的寄存器中的数据大小的方式为:DSP(Digital Signal Processor,数字信号处理器)中开关管的驱动信号由定时寄存器和比较寄存器相比较产生,每个中断周期开始定时寄存器开始计数,中断周期结束的时候定时寄存器中的数据达到最大,下一个中断周期开始的时候定时寄存器复位重新开始计数,
当PWM(Pulse Width Modulation,脉冲宽度调制)比较寄存器中的数与定时寄存器中的数相等时PWM信号发生跳变,这时记录下信号跳变时定时寄存器中的值。副边电流对应的脉冲信号通过AD口送入到DSP中,用同样的方法在每个中断周期记录脉冲跳变时对应的定时计数器中的值,比较驱动信号跳变(包括上升跳变和下降跳变)时对应的寄存器的数值和副边电流对应的脉冲信号跳变(包括上升跳变和下降跳变)时定时寄存器的数值的偏差,如果上升跳变和下降跳变时两个数的偏差都小于预设值(该预设值与时钟频率、分辨率等值相关,由设计者定义),则表示两个信号的上升沿和下降沿均同步;如果上升跳变时两个寄存器的数的偏差小于预设值,而下降跳变时驱动信号对应的寄存器的数值比脉冲信号寄存器的数值小则表示工作于区域1;如果上升跳变时两个定时寄存器的数的偏差小于预设值,而下降跳变时驱动信号对应的定时寄存器的数值比脉冲信号定时寄存器的数值大则表示工作于区域2;如果上升跳变和下降跳变时驱动信号寄存器的数比脉冲寄存器的数都大则表示工作于区域3。
本发明实施例提供一种谐振功率变换器的频率跟踪方法,应用于谐振功率变换器,谐振功率变换器的频率跟踪方法包括:获取副边电流对应的脉冲信号和驱动信号;根据副边电流对应的脉冲信号和驱动信号,生成第一信息,第一信息用于指示谐振功率变换器的谐振状态;根据第一信息,控制驱动信号的频率。基于上述的描述,由于判断支路可以接收检测支路发送的副边电流对应的脉冲信号,并根据副边电流对应的脉冲信号和驱动信号,生成用于指示谐振功率变换器的谐振状态的第一信息,使得控制支路根据第一信息,控制驱动信号的频率,达到了通过对副边电流进行采样,判断谐振功率变换器的谐振状态,并控制驱动信号的频率跟踪谐振功率变换器的谐振频率的目的。
以上所述,仅为本发明实施例的具体实施方式,但本发明实施例的保护范围并不局限于此,任何熟悉本技术领域的技术人员在本发明实施例揭露的技术范围内,可轻易想到变化或替换,都应涵盖在本发明实施例的保护范围之内。因此,本发明实施例的保护范围应所述以权利要求的保护范围为准。
Claims (11)
- 一种谐振功率变换器,包括逆变支路、与所述逆变支路相连的谐振支路、与所述谐振支路相连的变压器,以及与所述变压器相连的整流滤波支路,其中,所述变压器的原端与所述谐振支路相连,所述变压器的副端与所述整流滤波支路相连;其特征在于,所述谐振功率变换器还包括:与所述变压器的副端和所述整流滤波支路均相连的检测支路,与所述检测支路相连的判断支路,以及与所述判断支路和所述逆变支路均相连的控制支路;所述检测支路,用于获取所述变压器的副边电流,根据所述副边电流生成所述副边电流对应的脉冲信号,并发送所述副边电流对应的脉冲信号至所述判断支路;所述控制支路,用于生成驱动信号,并发送所述驱动信号至所述逆变支路和所述判断支路,所述驱动信号用于驱动所述逆变支路;所述判断支路,用于接收所述检测支路发送的所述副边电流对应的脉冲信号和所述控制支路发送的所述驱动信号,并根据所述副边电流对应的脉冲信号和所述驱动信号,生成并发送第一信息至所述控制支路,所述第一信息用于指示所述谐振功率变换器的谐振状态;所述控制支路,还用于接收所述判断支路发送的所述第一信息,并根据所述第一信息,控制所述驱动信号的频率。
- 根据权利要求1所述的谐振功率变换器,其特征在于,所述谐振功率变换器还包括:与所述检测支路、所述变压器的副边和所述整流滤波支路均相连的采样电路,用于对所述副边电流进行采样。
- 根据权利要求2所述的谐振功率变换器,其特征在于,所述采样电路具体包括:比较器,第一电阻、第二电阻、第三电阻和电容;其中,所述比较器的输出端与所述第三电阻的一端相连,所述电容的一端与所述第三电阻的另一端相连,所述第三电阻的另一端与所述检测支路相连,所述比较器的正输入端与所述第一电阻的一端相连,所述比较器的负输入端与所述第二电阻的一端相连,所述第一电阻的另一端与所述变压器和所述整流滤波支路均相连,所述第二电阻的另一端和所述电容的另一端接地。
- 根据权利要求2所述的谐振功率变换器,其特征在于,所述采样电路具体包括:比较器、第一电阻、第二电阻、第三电阻、第四电阻,第五电阻和第六电阻;其中,所述比较器的输出端与所述检测支路相连,所述比较器的负输入端与所述第一电阻的一端相连,所述第一电阻的另一端与所述第二电阻的一端相连,所述第二电阻的另一端与所述变压器和所述整流滤波支路均相连,所述第三电阻的一端与所述比较器的输出端相连,所述第三电阻的另一端与所述比较器的负输入端相连,所述比较器的正输入端与所述第四电阻的一端相连,所述第四电阻的另一端与所述第五电阻的一端相连,所述第五电阻的另一端与所述整流滤波支路相连,所述比较器的正输入端与所述第六电阻的一端相连,所述 第六电阻的另一端接地。
- 根据权利要求1-4中任意一项所述的谐振功率变换器,其特征在于,所述逆变支路为半桥逆变电路结构、全桥逆变电路结构、三电平逆变电路结构中的任意一种电路结构;所述谐振支路为由励磁电感、谐振电感和谐振电容串联构成的LLC谐振电路结构;所述整流滤波支路为半波整流滤波电路结构或者全波整流滤波电路结构。
- 一种谐振功率变换器的频率跟踪方法,应用于如权利要求1-5中任意一项所述的谐振功率变换器,其特征在于,所述方法包括:获取副边电流对应的脉冲信号和驱动信号;根据所述副边电流对应的脉冲信号和所述驱动信号,生成第一信息,所述第一信息用于指示所述谐振功率变换器的谐振状态;根据所述第一信息,控制所述驱动信号的频率。
- 根据权利要求6所述的谐振功率变换器的频率跟踪方法,其特征在于,所述获取副边电流对应的脉冲信号,具体包括:获取副边电流;根据所述副边电流,生成所述副边电流对应的脉冲信号。
- 根据权利要求6或7所述的谐振功率变换器的频率跟踪方法,其特征在于,所述根据所述副边电流对应的脉冲信号和所述驱动信号,生成第一信息,具体包括:确认所述副边电流对应的脉冲信号的上升沿和所述驱动信号的上升沿同步,且所述副边电流对应的脉冲信号的下降沿和所述驱动信号的下降沿同步;生成第一信息,所述第一信息用于指示所述谐振功率变换器在谐振频率点工作;所述根据所述第一信息,控制所述驱动信号的频率,具体包括:根据所述第一信息,维持所述驱动信号的频率不变。
- 根据权利要求6或7所述的谐振功率变换器的频率跟踪方法,其特征在于,所述根据所述副边电流对应的脉冲信号和所述驱动信号,生成第一信息,具体包括:确认所述副边电流对应的脉冲信号的上升沿和所述驱动信号的上升沿同步,且所述副边电流对应的脉冲信号的下降沿滞后于所述驱动信号的下降沿;生成第一信息,所述第一信息用于指示所述谐振功率变换器在第一区域工作;所述根据所述第一信息,控制所述驱动信号的频率,具体包括:根据所述第一信息,降低所述驱动信号的频率。
- 根据权利要求6或7所述的谐振功率变换器的频率跟踪方法,其特征在于,所述根据所述副边电流对应的脉冲信号和所述驱动信号,生成第一信息,具体包括:确认所述副边电流对应的脉冲信号的上升沿和所述驱动信号的上升沿同步,且所述副边电流对应的脉冲信号的下降沿超前于所述驱动信号的下降沿;生成第一信息,所述第一信息用于指示所述谐振功率变换器在第二区域工作;所述根据所述第一信息,控制所述驱动信号的频率,具体包括:根据所述第一信息,提高所述驱动信号的频率。
- 根据权利要求6或7所述的谐振功率变换器的频率跟踪方法,其特征在于,所述根据所述副边电流对应的脉冲信号和所述驱动信号,生成第一信息,具体包括:确认所述副边电流对应的脉冲信号的上升沿超前于所述驱动信号的上升沿,且所述副边电流对应的脉冲信号的下降沿超前于所述驱动信号的下降沿;生成第一信息,所述第一信息用于指示所述谐振功率变换器在第三区域工作;所述根据所述第一信息,控制所述驱动信号的频率,具体包括:根据所述第一信息,停止生成所述驱动信号;在提高所述驱动信号的频率后,生成所述驱动信号。
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US20190068068A1 (en) | 2019-02-28 |
EP3442105B1 (en) | 2024-04-10 |
EP3442105A4 (en) | 2019-04-24 |
CN107342688B (zh) | 2020-01-17 |
CN107342688A (zh) | 2017-11-10 |
US10439501B2 (en) | 2019-10-08 |
EP3442105A1 (en) | 2019-02-13 |
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