WO2017000925A1 - 故障电流抑制阻尼器拓扑电路及其控制方法及换流器 - Google Patents

故障电流抑制阻尼器拓扑电路及其控制方法及换流器 Download PDF

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Publication number
WO2017000925A1
WO2017000925A1 PCT/CN2016/089946 CN2016089946W WO2017000925A1 WO 2017000925 A1 WO2017000925 A1 WO 2017000925A1 CN 2016089946 W CN2016089946 W CN 2016089946W WO 2017000925 A1 WO2017000925 A1 WO 2017000925A1
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Prior art keywords
switch
topology circuit
fault
fault current
damper topology
Prior art date
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PCT/CN2016/089946
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English (en)
French (fr)
Inventor
谢晔源
朱铭炼
姜田贵
柏传军
李敏
Original Assignee
南京南瑞继保电气有限公司
南京南瑞继保工程技术有限公司
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Application filed by 南京南瑞继保电气有限公司, 南京南瑞继保工程技术有限公司 filed Critical 南京南瑞继保电气有限公司
Priority to AU2016286710A priority Critical patent/AU2016286710B2/en
Priority to RU2017134481A priority patent/RU2665683C1/ru
Priority to US15/570,750 priority patent/US10148083B2/en
Publication of WO2017000925A1 publication Critical patent/WO2017000925A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H02M7/4835—Converters with outputs that each can have more than two voltages levels comprising two or more cells, each including a switchable capacitor, the capacitors having a nominal charge voltage which corresponds to a given fraction of the input voltage, and the capacitors being selectively connected in series to determine the instantaneous output voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
    • H02H7/00—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions
    • H02H7/10—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers
    • H02H7/12—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
    • H02H7/00—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions
    • H02H7/10—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers
    • H02H7/12—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers
    • H02H7/1203—Circuits independent of the type of conversion
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H02M7/4837—Flying capacitor converters
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/08—Modifications for protecting switching circuit against overcurrent or overvoltage
    • H03K17/081—Modifications for protecting switching circuit against overcurrent or overvoltage without feedback from the output circuit to the control circuit
    • H03K17/08116—Modifications for protecting switching circuit against overcurrent or overvoltage without feedback from the output circuit to the control circuit in composite switches
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/08—Modifications for protecting switching circuit against overcurrent or overvoltage
    • H03K17/081—Modifications for protecting switching circuit against overcurrent or overvoltage without feedback from the output circuit to the control circuit
    • H03K17/0814—Modifications for protecting switching circuit against overcurrent or overvoltage without feedback from the output circuit to the control circuit by measures taken in the output circuit
    • H03K17/08146—Modifications for protecting switching circuit against overcurrent or overvoltage without feedback from the output circuit to the control circuit by measures taken in the output circuit in bipolar transistor switches
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration

Definitions

  • the invention belongs to the field of power electronics, and in particular relates to a damper topology circuit for suppressing fault current.
  • the voltage source converter technology is a new commutation technology based on IGBT (Insulated Gate Bipolar Transistor) and Pulse Width Modulation (PWM) technology.
  • IGBT Insulated Gate Bipolar Transistor
  • PWM Pulse Width Modulation
  • two-level converters composed of IGBTs have been widely used to solve the high-frequency transition of their converter output voltage, resulting in large dv/dt stress, high system loss, high noise and Problems such as the harsh electromagnetic environment, three-level voltage source converters have been proposed to extend the application of voltage source converters in voltage class and capacity.
  • MMC Modular Multilevel Converter
  • the inventors have proposed suppression measures based on the DC fault current mechanism of the voltage source type inverter, and the present invention has been produced.
  • the invention is applied to a voltage source type converter, and can reduce the current stress of the power semiconductor switch in the converter by the input of the damping resistor when the DC side of the inverter fails, and protect the IGBT device in economy and technology. Have a good performance.
  • a fault current suppression damper topology circuit comprising: a first switch module, a second switch module, an independent diode D3, a storage capacitor C1, a damping resistor R1, and a lightning arrester DL , bypass switch K1, power supply system and control system;
  • the first switch mode The anode of the block is connected to the terminal x2 of the damper topology circuit, and the cathode is connected to the cathode of the second switch module;
  • the anode of the second switch module T2 is connected to the terminal x1 of the damper topology circuit;
  • the first switch module includes a switch a tube T1 and a freewheeling diode D1 connected in anti-parallel with the switch tube T1;
  • the second switch module includes a switch tube T2 and a freewheeling diode D2 connected in anti-parallel with the switch tube T2;
  • the anode of the switch tube T1 is a first switch module
  • the anode of the independent diode is connected to the anode of the second switch module, the cathode is connected to one end of the storage capacitor, and the other end of the storage capacitor is connected to the cathode of the first switch module;
  • the damping resistor R1 and the arrester DL are connected in parallel Parallel between the positive pole and the negative pole of the first switch module;
  • the bypass switch K1 is connected in parallel between the x1 terminal and the x2 terminal of the damper topology circuit;
  • the power supply system obtains energy from the storage capacitor C1 and controls The system provides a power source;
  • the control system controls the operating state of the damper topology circuit by issuing a control signal to the bypass switch K1, the first switch module, and the second switch module.
  • the working state of the damper topology circuit is a starting forward current charging state, a bidirectional current flowing state, a forward current supplement state, a fault current damping state, or a fault bypass state:
  • switch tube T1 and the switch tube T2 are both IGBT, IGCT, GTO or MOSFET.
  • the second switch module is a bidirectional thyristor.
  • bypass switch K1 has a mechanical holding function after closing, and the bypass switch K1 can maintain the closed state after the power is turned off.
  • the second technical solution of the present invention is: the control method of the fault current suppression damper topology circuit as described above, wherein the control system issues a control signal, so that the fault current suppression damper topology circuit works in the following five One of the working states:
  • the third technical solution of the present invention is: a bridge arm damping modular multilevel converter comprising an upper arm and a lower arm; wherein the upper arm and the lower arm each comprise at least one as described above
  • the fault current suppresses the damper topology circuit.
  • the upper arm and the lower arm each include at least two half bridge-connected inverter module units that are cascaded with each other; the inverter module units in the upper arm are connected in the same direction, and the lower arm
  • the converter module unit is also connected in the same direction; the first terminal of the first converter module unit in the upper arm is the positive point P of the modular multilevel converter, and the last one in the lower arm
  • the second terminal of the streamer module unit is the cathode point N of the modular multilevel converter; the anode point P and the cathode point N are both used for accessing the DC network; the last one of the upper arms is changed
  • the second terminal of the streamer module unit is connected to the first terminal of the first inverter module unit of the lower arm, and the connection point is an AC terminal of the modular multilevel converter for receiving Into the communication network.
  • the fault current suppression damper topology circuit is a modular unit type and is compatible with the converter module unit structure.
  • the position of the inverter module unit can be used for installation.
  • the fourth technical solution of the present invention is: a damped two-level converter comprising a phase unit, the phase unit comprising a cascaded switch module; characterized in that it further comprises at least one of the above faults in series with the switch module Current suppression damper topology circuit.
  • fault current suppression damper topology circuit according to any one of claims 1 to 5 is also connected in series between the DC capacitor and the switch module.
  • the fifth technical solution of the present invention is: a damped multi-level converter comprising a phase unit comprising at least one of the above-described fault current suppression damper topology circuits connected in series.
  • the sixth technical solution of the present invention is the protection method of the modular multilevel converter as described above, which comprises the steps of:
  • damper topology circuit provided by the present invention limits the short circuit current peak when the voltage source type converter is DC fault, and effectively protects the switch module device and the capacitor safety;
  • the damper topology circuit can quickly attenuate the DC fault current, which is beneficial for quickly clearing the fault and restoring the converter operation;
  • the damper topology circuit can quickly and effectively suppress DC short-circuit current and damper current oscillation in a multi-terminal DC system composed of a modular multi-level converter, thereby better protecting equipment safety, and It can greatly shorten the fault current decay time, thereby shortening the DC outage time, and further, minimizing the economic loss and system instability risk caused by the outage;
  • the damper topology circuit has a self-extracting function, can be flexibly connected in series to the converter, and has flexible control, good independence, and does not reduce the reliability of the original system, and has engineering practical value.
  • FIG. 1 is a topological circuit structure of a fault current suppression damper according to the present invention.
  • FIG. 2 is a diagram showing a precharge condition of a fault current suppression damper topology circuit of the present invention
  • FIG. 3 is a normal throughflow condition diagram of a fault current suppression damper topology circuit of the present invention.
  • FIG. 4 is a diagram showing the input condition of a damping circuit of a fault current suppression damper of the present invention
  • FIG. 5 is a replenishing condition diagram of a fault current suppression damper topology circuit of the present invention.
  • FIG. 6 is a bypass diagram of a fault current suppression damper topology circuit of the present invention.
  • Figure 7 is a first embodiment of the present invention.
  • Figure 8 is a second embodiment of the present invention.
  • Figure 9 is a second embodiment of the present invention.
  • the fault current suppression damper topology circuit includes a first switch module, a second switch module, an independent diode D3, a storage capacitor C1, a damping resistor R1, a lightning arrester DL, a bypass switch K1, a power supply system, and a control system.
  • the anode of the first switch module is connected to the terminal x2 of the damper topology circuit, and the anode is connected to the cathode of the second switch module; the anode of the second switch module T2 is connected to the terminal x1 of the damper topology circuit;
  • the first switch module includes a switch tube T1 and a freewheeling diode D1 connected in anti-parallel with the switch tube T1;
  • the second switch module includes a switch tube T2 and a freewheeling diode D2 connected in anti-parallel with the switch tube T2;
  • the switch tube T1 The positive pole is the anode of the first switch module, the cathode of the switch tube T1 is the cathode of the first switch module, the anode of the switch tube T2 is the anode of the second switch module, and the cathode of the switch tube T2 is the cathode of the second switch module;
  • the anode of the independent diode is connected to the ano
  • the working state of the damper topology circuit is a starting forward current charging state, a bidirectional current circulating state, a forward current supplement state, a fault current damping state, or a fault bypass state;
  • starting a forward current Charging state The control system does not issue a control signal, the bypass switch K1 is disconnected, the switching tube T1 and the switching tube T2 are also disconnected; the forward current flows through the freewheeling diode D2, the storage capacitor C1 and the freewheeling diode D1, so that the storage The capacitor C1 is charged by the independent diode D3 and the freewheeling diode D1;
  • the power supply system and control system are not activated;
  • bidirectional current circulation state the control system controls the switch tube T1 and the switch tube T2 to open, so that the current can flow in both directions; the forward current flows through the switch tube T2, the freewheeling diode D1, The current flows through the switching transistor T1 and the freewheeling diode D2;
  • the forward current replenishing state under the forward current,
  • freewheeling diode D1 charges the storage capacitor C1;
  • fault current damping state under the external fault of the damper topology circuit, the control system controls the switching tube T1 and the switching tube T2 to be turned off, and the fault current flows through the freewheeling diode D2 and damping resistor R1 to suppress the fault current;
  • Fault bypass state When the damper topology circuit internal fault, the control system controls the bypass switch K1 to be turned on to cut off the fault current suppression damper topology circuit.
  • the switch tube T1 and the switch tube T2 are both IGBT, IGCT, GTO or MOSFET.
  • the second switch module is a bidirectional thyristor.
  • the bypass switch K1 has a mechanical holding function after closing, and the bypass switch K1 can maintain the closed state after the power is turned off.
  • FIG. 1 it includes two switch modules, one independent diode D3, one energy storage capacitor C1, one damping resistor R1, one lightning arrester DL, one bypass switch K1, and a power supply system and control system.
  • the anode of the switch module T1 is connected to the terminal x2 of the damper topology circuit
  • the cathode is connected to the cathode of the switch module T2
  • the anode of the T2 is connected to the terminal x1 of the damper topology circuit
  • the anode of the diode D3 and the switch module T2 are connected.
  • the positive pole is connected, the cathode is connected to one end of the storage capacitor C1, and the other end of the storage capacitor C1 is connected to the cathode of the switch module T1; the damping resistor R1 and the arrester DL are connected in parallel, and then connected in parallel with the switch module T1; the bypass switch K1 is connected in parallel Between the x1 terminal and the x2 terminal of the damper topology circuit; the power system draws energy from the storage capacitor to provide power to the control system; and the control system controls the operating state of the damper topology circuit.
  • the control method of the fault current suppression damper topology circuit, the fault current suppression damper topology circuit is the same as that in Embodiment 1, and the control system sends a control signal to make the fault current suppression damper topology circuit work.
  • the bridge arm dampers the modular multilevel converter, including an upper arm and a lower arm; the upper arm and the lower arm each include at least one fault current suppression damper topology circuit, the fault
  • the current suppression damper topology circuit is the same as Embodiment 1, and will not be described in detail.
  • the upper arm and the lower arm each include at least two half-bridge-connected inverter module units that are cascaded with each other; the inverter module units in the upper arm are connected in the same direction, the lower bridge
  • the converter module unit in the arm is also connected in the same direction; the first terminal of the first converter module unit in the upper arm is the positive point P of the modular multilevel converter, and the last one in the lower arm
  • the second terminal of the converter module unit is a negative point N of the modular multilevel converter; the positive point P and the negative point N are both used for accessing a DC network; the last one of the upper arms a second terminal of the inverter module unit is interconnected with a first terminal of the first inverter module unit of the lower arm, the connection point being an AC terminal of the modular multilevel converter, Access to the communication network.
  • the fault current suppression damper topology circuit is a modular unit type and is compatible with the converter module unit structure. The position of the inverter module unit can be used for installation.
  • the number of converter module units included in the upper and lower arms may be the same or different, and the specific circuit structure of each converter module unit may be the same or different; wherein SM 1 -SM n is an inverter module Unit, X is the damper topology circuit.
  • a shutdown signal is applied to the switching modules of all damper topology circuits connected in series in the converter to rapidly attenuate the fault current; and the system operation is resumed after the fault current is attenuated.
  • the damper type two-level converter includes a phase unit including a cascaded switch module, and further includes at least one fault current suppression damper topology circuit in series with the switch module,
  • the fault current suppression damper topology circuit is the same as that of Embodiment 1, and will not be described in detail.
  • a fault current suppression damper topology circuit is also connected in series between the DC capacitor and the switch module.
  • the damper topology circuit can be cascaded into the bridge arm or DC capacitor loop.
  • X is the damper topology circuit.
  • the damper type multilevel converter includes a phase unit including at least one fault current suppression damper topology circuit in series, and the fault current suppression damper topology circuit is the same as Embodiment 1. No longer detailed.
  • the damper topology circuit can be serialized into the phase unit. Where X is the damper topology circuit.
  • a shutdown signal is applied to the switching modules of all damper topology circuits connected in series in the converter to rapidly attenuate the fault current; and the system operation is resumed after the fault current is attenuated.
  • the protection method of the modular multi-level converter comprises the steps of: (1) detecting and judging whether a DC-side short-circuit fault occurs; (2) if it is determined that a fault occurs, connecting to the modular multi-level commutation in series All of the switch modules of the device apply a shutdown signal; (3) the system is resumed after the fault current is attenuated.
  • the protection method of the modular multi-level converter is the same as that of the embodiment 5, and will not be described in detail.

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Abstract

一种故障电流抑制阻尼器拓扑电路及其控制方法及换流器，其中，独立二极管的阳极和第二开关模块的正极相连，阴极和储能电容的一端相连，储能电容的另一端与第一开关模块的负极相连；阻尼电阻和避雷器并联后又与第一开关模块并联；旁路开关并联在阻尼器拓扑电路的x1端子和x2端子之间；电源***从储能电容上获取能量，并向控制***提供电源；控制***通过控制旁路开关、第一开关模块和第二开关模块控制阻尼器拓扑电路的工作状态。所述故障电流抑制阻尼器拓扑电路应用于电压源型换流器中，在直流故障时通过阻尼电阻的投入，降低故障电流应力，避免损坏设备实现了自取能、模块化、独立控制，可灵活应用于各种类型的电压源型换流器中，具有较好的经济性和技术性。

Description

故障电流抑制阻尼器拓扑电路及其控制方法及换流器 技术领域
本发明属于电力电子领域，特别涉及一种抑制故障电流的阻尼器拓扑电路。
背景技术
电压源型换流器技术是一种以可关断器件IGBT(绝缘栅双极晶体管)和脉宽调制(PWM)技术为基础的新型换流技术。在低压应用场合，由IGBT构成的两电平换流器得到了广泛的应用，为解决其换流器输出电压高频跃变，由此带来设备dv/dt应力大、***损耗大、噪声高和电磁环境严酷等问题，三电平电压源换流器被提出，在电压等级和容量上扩展了电压源型换流器的应用场合。
随着模块化多电平换流器(Modular Multilevel Converter，MMC)的出现，多电平换流器在柔性直流输电领域也得到了成功的应用，电压等级达到数百千伏，容量达到数千兆。
然而，所有的电压源型换流器都存在无法有效处理直流故障的固有缺陷，当直流侧发生短路故障时，即使换流器已经闭锁，交流电源仍可以通过IGBT的反并联二极管向短路点注入电流，构成续流通路，使故障切除困难。因此，如何解决或缓解电压源型换流器直流故障的问题，成为解决直流联网技术的发展的关键技术因素。
鉴于以上分析，本发明人从电压源型换流器的直流故障电流机理出发，提出抑制措施，本案由此产生。
发明内容
本发明的目的，在于提供一种故障电流抑制阻尼器拓扑电路及其控制方法及换流器。本发明用于电压源型换流器，可以在换流器直流侧发生故障时，通过阻尼电阻的投入，降低换流器中功率半导体开关的电流应力，保护IGBT器件，在经济性和技术性上均有较好表现。
为了达成上述目的，本发明的解决方案是：故障电流抑制阻尼器拓扑电路，其特征在于：包括第一开关模块、第二开关模块、独立二极管D3、储能电容C1、阻尼电阻R1、避雷器DL、旁路开关K1、电源***和控制***；所述第一开关模 块的正极和阻尼器拓扑电路的引出端x2相连，负极和第二开关模块的负极相连；第二开关模块T2的正极和阻尼器拓扑电路的引出端x1相连；所述第一开关模块包括开关管T1及与开关管T1反向并联的续流二极管D1；第二开关模块包括开关管T2及与开关管T2反向并联的续流二极管D2；所述开关管T1的正极为第一开关模块的正极，开关管T1的负极为第一开关模块的负极，所述开关管T2的正极为第二开关模块的正极，开关管T2的负极为第二开关模块的负极；
所述独立二极管的阳极和第二开关模块的正极相连，阴极和储能电容的一端相连，储能电容的另一端与第一开关模块的负极相连；所述阻尼电阻R1和避雷器DL并联后又并联在第一开关模块的正极和负极之间；所述旁路开关K1并联在阻尼器拓扑电路的x1端子和x2端子之间；所述电源***从储能电容C1上获取能量，并向控制***提供电源；所述控制***通过发出控制信号给旁路开关K1、第一开关模块和第二开关模块控制阻尼器拓扑电路的工作状态。
进一步的，所述阻尼器拓扑电路的工作状态为启动正向电流充电状态、双向电流流通状态、正向电流补能状态、故障电流阻尼状态或者故障旁路状态：
(1)启动正向电流充电状态：控制***不发出控制信号，旁路开关K1断开，开关管T1和开关管T2也断开；正向电流流经续流二极管D2、储能电容C1和续流二极管D1，使储能电容C1通过独立二极管D3、续流二极管D1充电；(2)双向电流流通状态：控制***控制开关管T1及开关管T2开通，使电流可以双向流通；正向电流流经开关管T2、续流二极管D1，反向电流流经开关管T1、续流二极管D2；
(3)正向电流补能状态：在正向电流下，控制***控制开关管T1开通，开关管T2关断，使正向电流通过独立二极管D3、续流二极管D1为储能电容C1充电；
(4)故障电流阻尼状态：在阻尼器拓扑电路外部故障下，控制***控制开关管T1及开关管T2关断，故障电流流过续流二极管D2和阻尼电阻R1，以抑制故障电流；
(5)故障旁路状态：当阻尼器拓扑电路内部故障时，控制***控制旁路开关K1开通，以将故障电流抑制阻尼器拓扑电路切除。
进一步的，所述开关管T1和开关管T2均为IGBT、IGCT、GTO或MOSFET。
进一步的，所述第二开关模块为双向晶闸管。
进一步的，所述旁路开关K1具有合闸后机械保持功能，在断电后旁路开关K1能够保持合闸状态。
本发明采取第二种技术方案为：如上述的故障电流抑制阻尼器拓扑电路的控制方法，其特征在于：控制***发出控制信号，使所述的故障电流抑制阻尼器拓扑电路工作在以下五种工作状态中的一种：
(1)启动正向电流充电状态：控制***不发出控制信号，旁路开关K1断开，开关管T1和开关管T2也断开；正向电流流经续流二极管D2、储能电容C1和续流二极管D1，使储能电容C1通过独立二极管D3、续流二极管D1充电；(2)双向电流流通状态：控制***控制开关管T1及开关管T2开通，使电流可以双向流通；正向电流流经开关管T2、续流二极管D1，反向电流流经开关管T1、续流二极管D2；
(3)正向电流补能状态：在正向电流下，控制***控制开关管T1开通，开关管T2关断，使正向电流通过独立二极管D3、续流二极管D1为储能电容C1充电；
(4)故障电流阻尼状态：在阻尼器拓扑电路外部故障下，控制***控制开关管T1及开关管T2关断，故障电流流过续流二极管D2和阻尼电阻R1，以抑制故障电流；
(5)故障旁路状态：当阻尼器拓扑电路内部故障时，控制***控制旁路开关K1开通，以将故障电流抑制阻尼器拓扑电路切除。
本发明采取第三种技术方案为：桥臂阻尼模块化多电平换流器，包括上桥臂和下桥臂；其特征在于：所述上桥臂和下桥臂均包括至少一个如上述的故障电流抑制阻尼器拓扑电路。
进一步的，上桥臂和下桥臂均包括相互级联的至少两个半桥连接的换流器模块单元；所述上桥臂中的换流器模块单元同向连接，所述下桥臂中的换流器模块单元也同向连接；上桥臂中第一个换流器模块单元的第一引出端为模块化多电平换流器的正极点P，下桥臂中最后一个换流器模块单元的第二引出端为模块化多电平换流器的负极点N；所述正极点P和负极点N均用于接入直流网络中；所述上桥臂中最后一个换流器模块单元的第二引出端与下桥臂中第一个换流器模块单元的第一引出端相互连接，所述连接点为模块化多电平换流器的交流端点，用以接入交流网络中。
进一步的，所述故障电流抑制阻尼器拓扑电路为模块单元型式，并和所述换流器模块单元结构兼容。可利用换流器模块单元的位置进行安装。
本发明采取第四种技术方案为：阻尼型两电平换流器，包括相单元，所述相单元包括级联的开关模块；其特征在于：还包括与开关模块串联的至少一个上述的故障电流抑制阻尼器拓扑电路。
进一步的，所述直流电容与开关模块之间也串联有如权利要求1-5中任一项所述的故障电流抑制阻尼器拓扑电路。
本发明采取第五种技术方案为：阻尼型多电平换流器，包括相单元，所述相单元包括级串联的至少一个上述的故障电流抑制阻尼器拓扑电路。
本发明采取第六种技术方案为：如上述所述的模块化多电平换流器的保护方法，其特征在于，包括步骤：
(1)检测并判断是否发生直流侧短路故障；
(2)如果判断故障发生，则对串联在所述模块化多电平换流器的所有所述的开关模块施加关断信号；
(3)故障电流衰减完毕后恢复***运行。
与现有技术相比，本发明的有益效果为：
(1)本发明提供的阻尼器拓扑电路，在电压源型换流器直流故障时，限制了短路电流峰值，有效的保护开关模块器件和电容安全；
(2)所述阻尼器拓扑电路可迅速衰减直流故障电流，有利于快速清除故障，恢复换流器运行；
(3)所述阻尼器拓扑电路在模块化多电平换流器构成的多端直流***中，能快速的、有效的抑制直流短路电流、阻尼电流振荡，既能更好的保护设备安全，又能大大缩短故障电流衰减时间、从而缩短直流停运时间，进一步的，最大程度减小停运带来的经济损失和***失稳风险；
(4)所述阻尼器拓扑电路具有自取能功能，可灵活的串联于换流器的任意位置，且控制灵活，独立性好，不降低原有***的可靠性，具有工程实用价值。
附图说明
图1是本发明一种故障电流抑制阻尼器拓扑电路结构；
图2是本发明故障电流抑制阻尼器拓扑电路预充电工况图；
图3是本发明故障电流抑制阻尼器拓扑电路正常通流工况图；
图4是本发明故障电流抑制阻尼器拓扑电路阻尼电阻投入工况图；
图5是本发明故障电流抑制阻尼器拓扑电路补能工况图；
图6是本发明故障电流抑制阻尼器拓扑电路旁路工况图；
图7是本发明的实施例一；
图8是本发明的实施例二；
图9是本发明的实施例二。
具体实施方式
以下将结合附图，对本发明的技术方案进行详细说明。
实施例1
参见图1，本故障电流抑制阻尼器拓扑电路，包括第一开关模块、第二开关模块、独立二极管D3、储能电容C1、阻尼电阻R1、避雷器DL、旁路开关K1、电源***和控制***；所述第一开关模块的正极和阻尼器拓扑电路的引出端x2相连，负极和第二开关模块的负极相连；第二开关模块T2的正极和阻尼器拓扑电路的引出端x1相连；所述第一开关模块包括开关管T1及与开关管T1反向并联的续流二极管D1；第二开关模块包括开关管T2及与开关管T2反向并联的续流二极管D2；所述开关管T1的正极为第一开关模块的正极，开关管T1的负极为第一开关模块的负极，所述开关管T2的正极为第二开关模块的正极，开关管T2的负极为第二开关模块的负极；所述独立二极管的阳极和第二开关模块的正极相连，阴极和储能电容的一端相连，储能电容的另一端与第一开关模块的负极相连；所述阻尼电阻R1和避雷器DL并联后又并联在第一开关模块的正极和负极之间；所述旁路开关K1并联在阻尼器拓扑电路的x1端子和x2端子之间；所述电源***从储能电容C1上获取能量，并向控制***提供电源；所述控制***通过发出控制信号给旁路开关K1、第一开关模块和第二开关模块控制阻尼器拓扑电路的工作状态。
作为优选方案，所述阻尼器拓扑电路的工作状态为启动正向电流充电状态、双向电流流通状态、正向电流补能状态、故障电流阻尼状态或者故障旁路状态；(1)启动正向电流充电状态：控制***不发出控制信号，旁路开关K1断开，开关管T1和开关管T2也断开；正向电流流经续流二极管D2、储能电容C1和续流二极管D1，使储能电容C1通过独立二极管D3、续流二极管D1充电；此时阻尼 器电源***、控制***没启动；(2)双向电流流通状态：控制***控制开关管T1及开关管T2开通，使电流可以双向流通；正向电流流经开关管T2、续流二极管D1，反向电流流经开关管T1、续流二极管D2；(3)正向电流补能状态：在正向电流下，控制***控制开关管T1开通，开关管T2关断，使正向电流通过独立二极管D3、续流二极管D1为储能电容C1充电；(4)故障电流阻尼状态：在阻尼器拓扑电路外部故障下，控制***控制开关管T1及开关管T2关断，故障电流流过续流二极管D2和阻尼电阻R1，以抑制故障电流；(5)故障旁路状态：当阻尼器拓扑电路内部故障时，控制***控制旁路开关K1开通，以将故障电流抑制阻尼器拓扑电路切除。所述开关管T1和开关管T2均为IGBT、IGCT、GTO或MOSFET。所述第二开关模块为双向晶闸管。所述旁路开关K1具有合闸后机械保持功能，在断电后旁路开关K1能够保持合闸状态。
如图1所示，包括2个开关模块，1个独立二极管D3，1个储能电容C1，1个阻尼电阻R1，1个避雷器DL，1个旁路开关K1，以及电源***和控制***,其中开关模块T1的正极和阻尼器拓扑电路的引出端x2相连，负极和开关模块T2的负极相连，T2的正极和阻尼器拓扑电路的引出端x1相连；独立二极管D3的阳极和开关模块T2的正极相连，阴极和储能电容C1的一端相连，储能电容C1的另一端与开关模块T1的负极相连；阻尼电阻R1和避雷器DL并联连接，并再与开关模块T1并联；旁路开关K1并联在阻尼器拓扑电路的x1端子和x2端子之间；电源***从储能电容上获取能量，向控制***提供电源；控制***控制阻尼器拓扑电路的工作状态。
实施例2
本故障电流抑制阻尼器拓扑电路的控制方法，所述故障电流抑制阻尼器拓扑电路同实施例1，不再详述；控制***发出控制信号，使所述的故障电流抑制阻尼器拓扑电路工作在以下五种工作状态中的一种：
(1)启动正向电流充电状态：控制***不发出控制信号，旁路开关K1断开，开关管T1和开关管T2也断开；正向电流流经续流二极管D2、储能电容C1和续流二极管D1，使储能电容C1通过独立二极管D3、续流二极管D1充电；，参见图2；
(2)双向电流流通状态：控制***控制开关管T1及开关管T2开通，使电流可以双向流通；正向电流流经开关管T2、续流二极管D1，反向电流流经开关 管T1、续流二极管D2，参见图3；
(3)正向电流补能状态：在正向电流下，控制***控制开关管T1开通，开关管T2关断，使正向电流通过独立二极管D3、续流二极管D1为储能电容C1充电，参见图4；
(4)故障电流阻尼状态：在阻尼器拓扑电路外部故障下，控制***控制开关管T1及开关管T2关断，故障电流流过续流二极管D2和阻尼电阻R1，以抑制故障电流，参见图5；
(5)故障旁路状态：当阻尼器拓扑电路内部故障时，控制***控制旁路开关K1开通，以将故障电流抑制阻尼器拓扑电路切除，参见图6。
实施例3
参见图7，本桥臂阻尼模块化多电平换流器，包括上桥臂和下桥臂；所述上桥臂和下桥臂均包括至少一个故障电流抑制阻尼器拓扑电路，所述故障电流抑制阻尼器拓扑电路同实施例1，不再详述。
作为优选方案，上桥臂和下桥臂均包括相互级联的至少两个半桥连接的换流器模块单元；所述上桥臂中的换流器模块单元同向连接，所述下桥臂中的换流器模块单元也同向连接；上桥臂中第一个换流器模块单元的第一引出端为模块化多电平换流器的正极点P，下桥臂中最后一个换流器模块单元的第二引出端为模块化多电平换流器的负极点N；所述正极点P和负极点N均用于接入直流网络中；所述上桥臂中最后一个换流器模块单元的第二引出端与下桥臂中第一个换流器模块单元的第一引出端相互连接，所述连接点为模块化多电平换流器的交流端点，用以接入交流网络中。所述故障电流抑制阻尼器拓扑电路为模块单元型式，并和所述换流器模块单元结构兼容。可利用换流器模块单元的位置进行安装。
上、下桥臂中包含的换流器模块单元的数量可以相同，也可以不同，各换流器模块单元的具体电路结构可以相同，也可以不同；其中SM1-SMn为换流器模块单元，X为阻尼器拓扑电路。在发生直流侧短路故障时，对串联在所述换流器中的所有阻尼器拓扑电路的开关模块施加关断信号，迅速衰减故障电流；并在故障电流衰减完毕后恢复***运行。
实施例4
参见图8，本阻尼型两电平换流器，包括相单元，所述相单元包括级联的开关模块；还包括与开关模块串联的至少一个故障电流抑制阻尼器拓扑电路，所述 故障电流抑制阻尼器拓扑电路同实施例1，不再详述。
作为优选方案，所述直流电容与开关模块之间也串联有故障电流抑制阻尼器拓扑电路。阻尼器拓扑电路可以串入桥臂或直流电容回路。其中X为阻尼器拓扑电路。在发生直流侧短路故障时，对串联在所述换流器中的所有阻尼器拓扑电路的开关模块施加关断信号，迅速衰减故障电流；并在故障电流衰减完毕后恢复***运行。
实施例5
参见图9，本阻尼型多电平换流器，包括相单元，所述相单元包括级串联的至少一个故障电流抑制阻尼器拓扑电路，所述故障电流抑制阻尼器拓扑电路同实施例1，不再详述。阻尼器拓扑电路可以串入相单元中。其中X为阻尼器拓扑电路。在发生直流侧短路故障时，对串联在所述换流器中的所有阻尼器拓扑电路的开关模块施加关断信号，迅速衰减故障电流；并在故障电流衰减完毕后恢复***运行。
实施例6
本模块化多电平换流器的保护方法，包括步骤：(1)检测并判断是否发生直流侧短路故障；(2)如果判断故障发生，则对串联在所述模块化多电平换流器的所有所述的开关模块施加关断信号；(3)故障电流衰减完毕后恢复***运行。模块化多电平换流器的保护方法同实施例5，不再详述。
以上实施例仅为说明本发明的技术思想，不能以此限定本发明的保护范围，凡是按照本发明提出的技术思想，在技术方案基础上所做的任何改动，均落入本发明保护范围之内。

Claims (13)

  1. 一种故障电流抑制阻尼器拓扑电路，其特征在于：包括第一开关模块、第二开关模块、独立二极管D3、储能电容C1、阻尼电阻R1、避雷器DL、旁路开关K1、电源***和控制***；所述第一开关模块的正极和阻尼器拓扑电路的引出端x2相连，负极和第二开关模块的负极相连；第二开关模块T2的正极和阻尼器拓扑电路的引出端x1相连；所述第一开关模块包括开关管T1及与开关管T1反向并联的续流二极管D1；第二开关模块包括开关管T2及与开关管T2反向并联的续流二极管D2；所述开关管T1的正极为第一开关模块的正极，开关管T1的负极为第一开关模块的负极，所述开关管T2的正极为第二开关模块的正极，开关管T2的负极为第二开关模块的负极；
    所述独立二极管的阳极和第二开关模块的正极相连，阴极和储能电容的一端相连，储能电容的另一端与第一开关模块的负极相连；所述阻尼电阻R1和避雷器DL并联后又并联在第一开关模块的正极和负极之间；所述旁路开关K1并联在阻尼器拓扑电路的x1端子和x2端子之间；所述电源***从储能电容C1上获取能量，并向控制***提供电源；所述控制***通过发出控制信号给旁路开关K1、第一开关模块和第二开关模块控制阻尼器拓扑电路的工作状态。
  2. 如权利要求1所述的故障电流抑制阻尼器拓扑电路，其特征在于：所述阻尼器拓扑电路的工作状态为启动正向电流充电状态、双向电流流通状态、正向电流补能状态、故障电流阻尼状态或者故障旁路状态；
    (1)启动正向电流充电状态：控制***不发出控制信号，旁路开关K1断开，开关管T1和开关管T2也断开；正向电流流经续流二极管D2、储能电容C1和续流二极管D1，使储能电容C1通过独立二极管D3、续流二极管D1充电；(2)双向电流流通状态：控制***控制开关管T1及开关管T2开通，使电流可以双向流通；正向电流流经开关管T2、续流二极管D1，反向电流流经开关管T1、续流二极管D2；
    (3)正向电流补能状态：在正向电流下，控制***控制开关管T1开通，开关管T2关断，使正向电流通过独立二极管D3、续流二极管D1为储能电容C1充电；
    (4)故障电流阻尼状态：在阻尼器拓扑电路外部故障下，控制***控制开关管T1及开关管T2关断，故障电流流过续流二极管D2和阻尼电阻R1，以抑制故障电流；
    (5)故障旁路状态：当阻尼器拓扑电路内部故障时，控制***控制旁路开关K1开通，以将故障电流抑制阻尼器拓扑电路切除。
  3. 如权利要求1或2所述的故障电流抑制阻尼器拓扑电路，其特征在于：所述开关管T1和开关管T2均为IGBT、IGCT、GTO或MOSFET。
  4. 如权利要求1或2所述的故障电流抑制阻尼器拓扑电路路，其特征在于：所述第二开关模块为双向晶闸管。
  5. 如权利要求1或2所述的故障电流抑制阻尼器拓扑电路，其特征在于：所述旁路开关K1具有合闸后机械保持功能，在断电后旁路开关K1能够保持合闸状态。
  6. 一种如权利要求1-5中任一项所述的故障电流抑制阻尼器拓扑电路的控制方法，其特征在于：控制***发出控制信号，使所述的故障电流抑制阻尼器拓扑电路工作在以下五种工作状态中的一种：
    (1)启动正向电流充电状态：控制***不发出控制信号，旁路开关K1断开，开关管T1和开关管T2也断开；正向电流流经续流二极管D2、储能电容C1和续流二极管D1，使储能电容C1通过独立二极管D3、续流二极管D1充电；(2)双向电流流通状态：控制***控制开关管T1及开关管T2开通，使电流可以双向流通；正向电流流经开关管T2、续流二极管D1，反向电流流经开关管T1、续流二极管D2；
    (3)正向电流补能状态：在正向电流下，控制***控制开关管T1开通，开关管T2关断，使正向电流通过独立二极管D3、续流二极管D1为储能电容C1充电；
    (4)故障电流阻尼状态：在阻尼器拓扑电路外部故障下，控制***控制开关管T1及开关管T2关断，故障电流流过续流二极管D2和阻尼电阻R1，以抑制故障电流；
    (5)故障旁路状态：当阻尼器拓扑电路内部故障时，控制***控制旁路开关K1开通，以将故障电流抑制阻尼器拓扑电路切除。
  7. 一种桥臂阻尼模块化多电平换流器，包括上桥臂和下桥臂；其特征在于：所述上桥臂和下桥臂均包括至少一个如权利要求1-5中任一项所述的故障电流抑制阻尼器拓扑电路。
  8. 如权利要求7所述的模块化多电平换流器，其特征在于：上桥臂和下桥 臂均包括相互级联的至少两个半桥连接的换流器模块单元；所述上桥臂中的换流器模块单元同向连接，所述下桥臂中的换流器模块单元也同向连接；上桥臂中第一个换流器模块单元的第一引出端为模块化多电平换流器的正极点P，下桥臂中最后一个换流器模块单元的第二引出端为模块化多电平换流器的负极点N；所述正极点P和负极点N均用于接入直流网络中；所述上桥臂中最后一个换流器模块单元的第二引出端与下桥臂中第一个换流器模块单元的第一引出端相互连接，所述连接点为模块化多电平换流器的交流端点，用以接入交流网络中。
  9. 如权利要求7或8所述的模块化多电平换流器，其特征在于：所述故障电流抑制阻尼器拓扑电路为模块单元型式，并和所述换流器模块单元结构兼容。
  10. 一种阻尼型两电平换流器，包括相单元，所述相单元包括级联的开关模块；其特征在于：还包括与开关模块串联的至少一个如权利要求1-5中任一项所述的故障电流抑制阻尼器拓扑电路。
  11. 如权利10要求的两电平换流器，其特征在于：所述直流电容与开关模块之间也串联有如权利要求1-5中任一项所述的故障电流抑制阻尼器拓扑电路。
  12. 一种阻尼型多电平换流器，包括相单元，所述相单元包括级串联的至少一个如权利要求1-5中任一项所述的故障电流抑制阻尼器拓扑电路。
  13. 一种如权利要求10、或者11所述的模块化多电平换流器的保护方法，其特征在于，包括步骤：
    (1)检测并判断是否发生直流侧短路故障；
    (2)如果判断故障发生，则对串联在所述模块化多电平换流器的所有所述的开关模块施加关断信号；
    (3)故障电流衰减完毕后恢复***运行。
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