WO2016119661A1 - 功率因数校正电路及乘法器 - Google Patents
功率因数校正电路及乘法器 Download PDFInfo
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- WO2016119661A1 WO2016119661A1 PCT/CN2016/072010 CN2016072010W WO2016119661A1 WO 2016119661 A1 WO2016119661 A1 WO 2016119661A1 CN 2016072010 W CN2016072010 W CN 2016072010W WO 2016119661 A1 WO2016119661 A1 WO 2016119661A1
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
- H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
- H03D7/14—Balanced arrangements
- H03D7/1425—Balanced arrangements with transistors
- H03D7/1433—Balanced arrangements with transistors using bipolar transistors
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
- H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
- H03D7/14—Balanced arrangements
- H03D7/1425—Balanced arrangements with transistors
- H03D7/1441—Balanced arrangements with transistors using field-effect transistors
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
- H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
- H03D7/14—Balanced arrangements
- H03D7/1425—Balanced arrangements with transistors
- H03D7/1458—Double balanced arrangements, i.e. where both input signals are differential
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the present disclosure relates to the field of power management technologies, and in particular, to a multiplier and a power factor correction circuit to which the multiplier is applied.
- FIG. 1 An implementation of a PFC circuit is shown in Figure 1, which is applied to a boost converter.
- the converter comprises an inductor L, a switching device S, a freewheeling diode D, an output capacitor Cout and an integrated PFC circuit.
- the power supply voltage Vac passes through the diode rectifier bridge and is used as an input of the boost converter.
- the boost converter converts the input voltage to obtain an output voltage Vout.
- the PFC circuit includes an error amplifier U1, a multiplier U2, a comparator U3, an RS flip-flop U4, a drive module U5, and a Zero Current Detection (ZCD) U6.
- the PFC circuit samples the output voltage Vout and inputs it to the error amplifier U1.
- One input of the multiplier U2 is the output error feedback signal Verror of the error amplifier U1, and the other input is the divided voltage signal Vin of the power supply voltage Vac, so that the output current waveform can be made. Become a sine wave following the power supply voltage waveform.
- the sampling resistor R1 is connected in series with the external switching device S to obtain a switching current signal.
- the comparator U3 and the RS flip-flop U4 are turned over, and the external switching device S is turned off by the driving module U5.
- the zero current detecting circuit U6 detects that the inductor current drops to zero, the external switching device S is turned on.
- the present disclosure provides a multiplier and a power factor correction circuit to which the multiplier is applied.
- a multiplier comprising:
- a Gilbert multiplier circuit comprising first and second differential input stages and an output stage; said output stage outputting an output current obtained by an input operation of said first and second differential input stages;
- a first differential voltage conversion circuit for generating a first differential voltage bias based on the received voltage signal and a first reference voltage to bias the first differential input stage
- a second differential voltage conversion circuit for generating a second differential voltage bias based on the received voltage signal and a second reference voltage to bias the second differential input stage
- a bias current generating circuit for generating a bias current biasing the first signal conversion circuit and the second signal conversion circuit
- the output stage comprises:
- a current mirror unit comprising two current input terminals and a current output terminal
- a feedback control unit is configured to ensure that when the voltage signal difference received by the multiplier is zero, the current output terminal has no current output.
- the current mirror unit is composed of a P-type MOSFET transistor.
- the second differential voltage conversion circuit includes:
- MOSFET transistor having a gate connected to a drain and a source connected to the power supply voltage
- a first BJT transistor pair comprising two NPN-type first BJT transistors; a base and a collector of the two first BJT transistors are connected to a drain of the MOSFET transistor, and an emitter outputs the second differential voltage;
- a second BJT transistor pair includes two NPN-type second BJT transistors; the bases of the two second BJT transistors respectively receive different voltage signals, and the collectors are respectively connected to the first BJT transistor Emitter
- a first MOSFET transistor pair includes two first MOSFET transistors; the gates of the two first MOSFET transistors receive the bias current, the source is grounded, and the drains are respectively connected to a second BJT transistor Emitter.
- a base of the second BJT transistor receives the input voltage or an error feedback voltage, and a base of another BJT transistor receives the second reference voltage.
- the first differential voltage conversion circuit includes:
- a second MOSFET transistor pair comprising two second MOSFET transistors; the gates of the two first MOSFET transistors are connected to the drain, and the source is connected to the power supply voltage;
- a third BJT transistor pair includes two third BJT transistors; the bases of the two third BJT transistors respectively receive different voltage signals, and the collectors respectively connect the drains of the second MOSFET transistors pole;
- a third MOSFET transistor pair includes two third MOSFET transistors; the gates of the two third MOSFET transistors receive the bias current, the source is grounded, and the drains are respectively connected to a third BJT transistor Emitter
- a fourth MOSFET transistor pair comprising two fourth MOSFET transistors; two of said fourth a gate of the MOSFET transistor is respectively connected to a gate of the second MOSFET transistor, and a source is connected to the power supply voltage;
- a fourth BJT transistor pair includes two NPN-type fourth BJT transistors; bases of the two fourth BJT transistors are respectively connected to the drains of one of the fourth MOSFET transistors, and the collector outputs the first difference Voltage;
- a BJT transistor having a base coupled to the collector and coupled to the emitter of the fourth BJT transistor, the emitter of which is coupled to ground.
- a base of the third BJT transistor receives the input voltage or an error feedback voltage, and a base of another BJT transistor receives the first reference voltage.
- the output stage includes a current mirror unit, the current mirror unit includes two current inputs and a current output; the output stage further includes:
- a first switching element having a first end connected to the current output end of the current mirror unit, a second end connected to an input end of the first operational amplifier, and a control end connected to the first operational amplifier output end;
- a second switching element has a first end connected to the current output end of the current mirror unit, a second end for outputting the output current, and a control end connected to the first operational amplifier output end.
- a multiplier comprising:
- a Gilbert multiplier circuit comprising first and second differential input stages and an output stage; said output stage outputting an output current obtained by an input operation of said first and second differential input stages;
- a first differential voltage conversion circuit for generating a first differential voltage bias based on the received voltage signal and a first reference voltage to bias the first differential input stage
- a second differential voltage conversion circuit for generating a second differential voltage bias based on the received voltage signal and a second reference voltage to bias the second differential input stage
- a bias current generating circuit for generating a bias current biasing the first signal conversion circuit and the second signal conversion circuit
- the output stage includes a current mirror unit, the current mirror unit includes two current input terminals and a current output terminal; the output stage further includes:
- a first switching element having a first end connected to the current output end of the current mirror unit, a second end connected to an input end of the first operational amplifier, and a control end connected to the first operational amplifier output end;
- a second switching element has a first end connected to the current output end of the current mirror unit, a second end for outputting the output current, and a control end connected to the first operational amplifier output end.
- the second differential voltage conversion circuit includes:
- MOSFET transistor having a gate connected to a drain and a source connected to the power supply voltage
- a first BJT transistor pair comprising two NPN-type first BJT transistors; two of said first BJT crystals a base and a collector of the tube are connected to a drain of the MOSFET transistor, and an emitter outputs the second differential voltage;
- a second BJT transistor pair includes two NPN-type second BJT transistors; the bases of the two second BJT transistors respectively receive different voltage signals, and the collectors are respectively connected to the first BJT transistor Emitter
- a first MOSFET transistor pair includes two first MOSFET transistors; the gates of the two first MOSFET transistors receive the bias current, the source is grounded, and the drains are respectively connected to a second BJT transistor Emitter.
- a base of the second BJT transistor receives the input voltage or an error feedback voltage, and a base of another BJT transistor receives the second reference voltage.
- the first differential voltage conversion circuit includes:
- a second MOSFET transistor pair comprising two second MOSFET transistors; two second MOSFET transistors having a gate connected to the drain and a source connected to the supply voltage;
- a third BJT transistor pair includes two third BJT transistors; the bases of the two third BJT transistors respectively receive different voltage signals, and the collectors respectively connect the drains of the second MOSFET transistors pole;
- a third MOSFET transistor pair includes two third MOSFET transistors; the gates of the two third MOSFET transistors receive the bias current, the source is grounded, and the drains are respectively connected to a third BJT transistor Emitter
- a fourth MOSFET transistor pair includes two fourth MOSFET transistors; the gates of the two fourth MOSFET transistors are respectively connected to the gate of one of the second MOSFET transistors, and the source is connected to the power supply voltage;
- a fourth BJT transistor pair includes two NPN-type fourth BJT transistors; bases of the two fourth BJT transistors are respectively connected to the drains of one of the fourth MOSFET transistors, and the collector outputs the first difference Voltage;
- a BJT transistor having a base coupled to the collector and coupled to the emitter of the fourth BJT transistor, the emitter of which is coupled to ground.
- a base of the third BJT transistor receives the input voltage or an error feedback voltage, and a base of another BJT transistor receives the first reference voltage.
- the multiplier further includes:
- the bias current generation circuit generates the bias current based on a voltage supplied by the voltage feedforward circuit.
- a power factor correction circuit comprising any one of the above multipliers.
- the power factor correction circuit is formed in an integrated circuit module.
- the output current accuracy of the multiplier is improved, and when the input voltage error is 0, there is no current output, that is, more precise. Control the offset voltage of the multiplier.
- FIG. 1 is a schematic structural view of a boost converter using a PFC circuit in the prior art.
- FIG. 2 is a schematic structural diagram of a Gilbert multiplier circuit in an exemplary embodiment of the present disclosure.
- FIG. 3 is a schematic diagram of the structure of another Gilbert multiplier circuit in an exemplary embodiment of the present disclosure.
- FIG. 4 is a schematic structural diagram of a differential current conversion circuit in an exemplary embodiment of the present disclosure.
- FIG. 5 is a schematic structural diagram of a hyperbolic tangent circuit in an exemplary embodiment of the present disclosure.
- FIG. 6 is a schematic structural diagram of a first differential voltage conversion circuit in an exemplary embodiment of the present disclosure.
- FIG. 7 is a schematic structural diagram of a second differential voltage conversion circuit in an exemplary embodiment of the present disclosure.
- FIG. 8 is a schematic structural diagram of a voltage feedforward circuit in an exemplary embodiment of the present disclosure.
- FIG. 9 is a schematic structural diagram of another voltage feedforward circuit in an exemplary embodiment of the present disclosure.
- FIG. 10 is a timing diagram of control signals of a voltage feedforward circuit in an exemplary embodiment of the present disclosure.
- FIG. 11 is a schematic structural view of a voltage feedforward circuit in the prior art.
- FIG. 12 is a schematic overall structural view of a multiplier in an exemplary embodiment of the present disclosure.
- Example embodiments will now be described more fully with reference to the accompanying drawings. However, the example embodiments can be embodied in a variety of forms and should not be construed as being limited to the embodiments set forth herein. To those skilled in the art. Furthermore, the described technical features or circuit structures may be combined in any suitable manner in one or more embodiments. In the following description, numerous specific details are set forth However, those skilled in the art will appreciate that the technical solution of the present disclosure may be practiced without one or more of the specific details.
- a multiplier is first provided in this example embodiment.
- the multiplier can include a Gilbert multiplier circuit and a bias current generating circuit; since the Gilbert multiplier circuit implements the product of the respective hyperbolic tangent functions of the two voltages, in order to achieve two voltages
- the direct product between the two needs to first convert the input voltage through the voltage to the differential current, and the converted differential current is then passed through a pair of BJT (bipolar transistor) transistors to generate a differential voltage, thereby obtaining an inverse hyperbolic tangent function.
- the multiplier in the exemplary embodiment further includes a first differential voltage conversion circuit and a second differential voltage conversion circuit.
- the multiplier circuit can also be other types of circuits, and the first differential voltage conversion circuit and the second differential voltage conversion circuit can also select settings according to requirements, etc.
- the exemplary embodiments are not limited thereto.
- FIG. 2 it is a schematic structural diagram of a Gilbert multiplier circuit.
- the Gilbert multiplier circuit is the core unit of the multiplier, comprising a second differential input stage consisting of BJT transistors Q1-Q2, a second differential input stage consisting of BJT transistors Q3-Q6, and an output stage Where current source I EE provides a bias current I EE to the Gilbert multiplier circuit.
- the output stage of the Gilbert multiplier outputs an output current Iout obtained by an input operation of the first differential input stage and the second differential input stage.
- the Gilbert multiplier circuit uses a bipolar transistor because the exponential nature of the bipolar device makes it more linear than the multiplier using the field effect device.
- the output stage of the Gilbert multiplier circuit includes a current mirror unit, and the output current Iout of the Gilbert multiplier circuit requires the current mirror unit output.
- the current mirror unit can only use PMOS devices (ie, P-type MOSFET transistors M2, M3 shown in Figure 3).
- PMOS devices ie, P-type MOSFET transistors M2, M3 shown in Figure 3.
- a current mirror consisting of a PMOS device is directly output, since the output resistance is small, when the voltage difference received by the multiplier is 0, there may be a small current output.
- a folded structure can be considered, but may conflict with a limited voltage space.
- a feedback control unit is provided for ensuring that the current output terminal has no current output when the voltage signal difference received by the multiplier is zero.
- the feedback control unit may include a first operational amplifier U1, and the feedback is ensured by the first operational amplifier U1 to ensure that the output current Iout has a high precision.
- the specific circuit is shown in Figure 3.
- the current mirror unit includes two current input terminals and a current output terminal.
- the output stage further includes a first operational amplifier U1, a first switching element S1 and a second switching element S2. The two input ends of the first operational amplifier U1 are respectively connected to the current input end of the current mirror unit.
- a first end of the first switching element S1 is connected to a current output end of the current mirror unit, and a second end of the first switching element S1 is connected to an input end of the first operational amplifier U1, the first end The control terminal of the switching element S1 is connected to the output terminal of the first operational amplifier U1.
- a first end of the second switching element S2 is connected to a current output end of the current mirror unit, and a second end of the second switching element S2 is for outputting the output current Iout, the second switching element S2
- the control terminal is connected to the output end of the first operational amplifier U1.
- the first differential voltage conversion circuit is configured to generate a first differential voltage bias based on the received voltage signal and a first reference voltage Vref1 to bias the first differential input stage, in the example embodiment
- the voltage signal received by the voltage conversion circuit is an error feedback voltage Verror.
- the first differential voltage conversion circuit may receive other voltage signals.
- the error feedback voltage Verror first needs to be converted by a voltage to a differential current.
- a differential current conversion circuit is shown in FIG. 4, and in order to realize voltage to differential current conversion, PNP is used in FIG.
- the type BJT transistor causes a voltage difference between the input voltage and the first reference voltage Vref1 to generate a differential current on the first resistor R2.
- the generated differential current is then subjected to a differential voltage through a pair of BJT transistors as shown in FIG. 5 to obtain an inverse hyperbolic tangent function.
- the second differential voltage conversion circuit is configured to generate a second differential voltage bias based on the received voltage signal and a second reference voltage Vref2 to bias the second differential input stage, in the example embodiment
- the voltage signal received by the voltage conversion circuit is an example of the input voltage Vin.
- the second differential voltage conversion circuit may receive other voltage signals.
- the input voltage Vin first undergoes a conversion from a voltage to a differential current, and then performs an inverse hyperbolic tangent conversion. Differential current conversion circuit and The inverse hyperbolic tangent circuit is similar to that in FIGS. 4 and 5 and will not be described again here.
- a voltage follower can be used to obtain a minimum input voltage Vin close to 0V.
- the differential current conversion circuit in Figure 4 Due to process limitations, PNP devices with excellent performance may not be provided, and the differential current conversion circuit in Figure 4 only implements a similar level shifting function, so theoretically, NPN type BJT transistors can also be used instead. Therefore, the first differential voltage conversion circuit and the second differential voltage conversion circuit are also improved based on this in the present exemplary embodiment, so that it can be implemented by using an NPN type BJT transistor, thereby greatly expanding the range of use of the circuit. Moreover, the process requirements can be reduced without the use of PNP devices. In addition, the NPN type device has a higher gain (Beta), so the error can also be reduced to some extent.
- Beta gain
- the second differential voltage conversion circuit may include a MOSFET transistor M1, a first BJT transistor pair, a second BJT transistor pair, a first resistor R1, and a first MOSFET transistor pair.
- the gate of the MOSFET transistor M1 is connected to the drain, and the source of the MOSFET transistor is connected to the power supply voltage Vcc.
- the first BJT transistor pair includes two NPN-type first BJT transistors Q11, Q12; the base and collector of two of the first BJT transistors are connected to the drain of the MOSFET transistor, and the two first BJTs The emitter of the transistor outputs the second differential voltage.
- the second BJT transistor pair includes two NPN-type second BJT transistors Q21, Q22; the bases of the two second BJT transistors respectively receive different voltage signals, and the two second BJT transistors The collectors are respectively connected to the emitters of the first BJT transistor.
- the first resistor R1 is coupled between the emitters of the two second BJT transistors.
- the first MOSFET transistor pair includes two first MOSFET transistors M11, M12; the gates of the two first MOSFET transistors receive the bias current, the sources of the two first MOSFET transistors are grounded, two The drains of the first MOSFET transistors are respectively connected to the emitters of one of the second BJT transistors.
- the first differential voltage conversion circuit includes a second MOSFET transistor pair, a third BJT transistor pair, a second resistor R2, a third MOSFET transistor pair, and a fourth MOSFET transistor pair.
- the second MOSFET transistor pair includes two second MOSFET transistors M21, M22; the gates and drains of the two second MOSFET transistors are connected, and the two second MOSFET transistor sources are connected to the power supply voltage Vcc .
- the third BJT transistor pair includes two third BJT transistors Q31, Q32; the bases of the two third BJT transistors respectively receive different voltage signals, and the collectors of the two third BJT transistors Correspondingly, the drains of one of the BJT transistors are respectively connected.
- the second resistor R2 is coupled between the emitters of the two third BJT transistors.
- the third MOSFET transistor pair includes two third MOSFET transistors M31, M32; the gates of the two third MOSFET transistors receive the bias current, the sources of the two third MOSFET transistors are grounded, two The drains of the third MOSFET transistors are respectively connected to the emitters of one of the third BJT transistors.
- the fourth MOSFET transistor pair includes two fourth MOSFET transistors M41, M42; the gates of the two fourth MOSFET transistors are respectively connected to the gate of one of the second MOSFET transistors, and the two fourth MOSFET transistor sources The pole is connected to the power supply voltage Vcc.
- the fourth BJT transistor pair includes two NPN-type fourth BJT transistors Q41 and Q42; the bases of the two fourth BJT transistors are respectively connected to the fourth MOSFET. The drain of the transistor, the collectors of the two of the fourth BJT transistors output the first differential voltage.
- the base of the BJT transistor Q50 is connected to the collector and is connected to the emitter of the fourth BJT transistor. The emitter of the BJT transistor Q50 is grounded, and the BJT transistor Q50 can raise the DC operating level.
- the bias current generating circuit is configured to generate a bias current biasing the first signal conversion circuit and the second signal conversion circuit based on an external input voltage, for example, a voltage Vff provided by a voltage feedforward circuit, thereby performing 1 /V 2 conversion.
- the voltage feedforward circuit is configured to hold and output a peak voltage of an input voltage to the voltage feedforward circuit.
- the input voltage is derived from a voltage proportional to an alternating current supply voltage.
- the voltage feedforward circuit in the exemplary embodiment mainly includes a logic control unit U2, a third switching element S3, a fourth switching element S4, a fifth switching element S3, and a first capacitor. C1 and a second capacitor C2, etc.; in the present exemplary embodiment, the switching element may include one or more of a MOSFET switch, an IGBT switch, or a BJT switch. among them:
- the first end of the third switching element S3 is connected to a power supply voltage Vcc, the power supply voltage Vcc is at least higher than the peak voltage of the input voltage Vin, and the control end of the third switching element S3 is responsive to a first control signal.
- the third switching element S3 is turned on by ⁇ 1.
- the logic control unit U2 is configured to output a second control signal ⁇ 2 during the peak voltage of the input voltage Vin and a third control signal ⁇ 3 during the non-peak voltage of the input voltage Vin, as described in FIG.
- the second control signal ⁇ 2, the third control signal ⁇ 3, and the fourth control signal ⁇ 4 described below have a non-overlapping time, thereby Avoid interference and generate noise.
- the first end of the first capacitor C1 is grounded.
- the first end of the fourth switching element S4 is connected to the second end of the third switching element S3, and the second end of the fourth switching element S4 is connected to the second end of the first capacitor C1, the fourth switch
- the control terminal of the element S4 turns on the fourth switching element S4 in response to the second control signal ⁇ 2.
- the first end of the fifth switching element S3 is connected to the second end of the first capacitor C1, and the control end of the fifth switching element S3 turns on the fifth switching element S3 in response to the third control signal ⁇ 3 .
- the first end of the second capacitor C2 is grounded, and the second end of the second capacitor C2 is connected to the second end of the fifth switching element S3.
- the first control signal ⁇ 1 and the second control signal ⁇ 2 are simultaneously supplied, and the first control signal is stopped when the voltage of the second end of the first capacitor C1 is greater than the peak voltage of the input voltage Vin.
- a first control signal ⁇ 1 and a second control signal ⁇ 2 are provided to turn on the third switching element S3 and the fourth switching element S4, so the power source
- the voltage Vcc charges the first capacitor C1 via the third switching element S3 and the fourth switching element S4; when the first capacitor C1 is charged to the peak voltage of the input voltage Vin, stopping providing the first
- the control signal ⁇ 1 stops charging the first capacitor C1.
- Vff (V C1 ⁇ C1+V C2 ⁇ C2)/(C1+C2) (1)
- V C1 is the voltage of the second end of the first capacitor C1 before the charge redistribution
- V C2 is the voltage of the second end of the second capacitor C2 before the charge redistribution
- the ratio of the capacitance between the first capacitor C1 and the second capacitor C2 in the exemplary embodiment is adjustable, and can be adjusted by controlling the ratio of the capacitance between the first capacitor C1 and the second capacitor C2. a rate of change of the voltage output by the second terminal of the second capacitor C2.
- the logic control unit U2 is further configured to output a fourth control signal ⁇ 4 during the non-peak voltage of the input voltage Vin.
- the voltage feedforward circuit in the present exemplary embodiment may further include a fourth switching element S4.
- the first end of the fourth switching element S4 is connected to the second end of the first capacitor C1, the second end of the fourth switching element S4 is grounded, and the control end of the fourth switching element S4 is responsive to the fourth The fourth switching element S4 is turned on by the control signal ⁇ 4.
- the fourth control signal ⁇ 4 turns on the fourth switching element S4, and further discharges the first capacitor C1 to prevent a sudden drop in the effective value of the input voltage Vin.
- the voltage at the second terminal of the first capacitor C1 is still maintained at the peak voltage of the input voltage Vin before the change.
- the voltage feedforward circuit in the present exemplary embodiment may further include a first comparator U2.
- the first input end of the first comparator U2 is connected to a reference voltage Vref
- the second input end of the first comparator U2 is connected to the input voltage Vin
- the output end of the first comparator U2 outputs the A comparison result signal of the input voltage Vin and the reference voltage Vref is sent to the logic control unit U2, and the logic control unit U2 determines whether it is during the peak voltage period of the input voltage Vin.
- the logic control unit U2 can determine that the input voltage Vin is During the peak voltage period; if the input voltage Vin is smaller than the reference voltage Vref, the output end of the first comparator U2 outputs a high level signal, and the logic control unit U2 determines that the input voltage Vin is During the non-peak voltage period.
- the voltage feedforward circuit in the present exemplary embodiment may further include a second comparator U3 (or a second operational amplifier). a first input of the second comparator U3 (or the second operational amplifier) is connected to the input voltage Vin, and a second input of the second comparator U3 (or the second operational amplifier) is connected The first end of the third switching element S3 forms a feedback circuit.
- the output end of the second comparator U3 (or the second operational amplifier) is based on the input voltage Vin and the voltage of the second end of the first capacitor C1.
- the comparison result outputs a comparison result signal to the control terminal of the third switching element S3.
- the second comparator U3 (or the second operational amplifier) outputs a high level signal, that is, the first control signal ⁇ 1, thereby turning on the first switch
- the power supply voltage Vcc charges the first capacitor C1 through the first switching transistor and the second switching transistor.
- the voltage of the second terminal of the first capacitor C1 increases with the rise of the input voltage Vin, but the voltage of the second terminal of the first capacitor C1 is still less than the peak voltage of the input voltage Vin, that is, the first capacitor C1
- the second comparator U3 (or the second operational amplifier) still outputs a high level signal (ie, the first control signal ⁇ 1), thereby keeping the first switching device turned on.
- the second comparator U3 (or the second operational amplifier) outputs a low level signal, the low level signal turning off the first switching device, Thereby stopping charging of the first capacitor C1.
- the third switching element S3 is in the off state, the loop between the second comparator U3 (or the second operational amplifier) and the third switching element S3 is kept on, avoiding the occurrence of the third switching element S3 being turned on again.
- the voltage feedforward circuit may further include a third resistor R3 coupled to the second end of the third switching element S3 and the second capacitor C1. Between the ends, thus acting as a current limiting.
- the voltage feedforward circuit in the exemplary embodiment is formed on an integrated circuit module, and the first capacitor C1 and the second capacitor C2 can be implemented by using an on-chip capacitor. Because the on-chip capacitance is much smaller than the external capacitor, and the period of the AC signal is long (50Hz corresponds to 20ms), if the on-chip capacitor is used instead of the external capacitor, the problem of the voltage holding time on the on-chip capacitor needs to be solved, that is, the leakage current needs to be considered. The impact of this is especially severe at high temperatures. In the present exemplary embodiment, since the main leakage current is a reverse bias PN junction leakage current connected to the first capacitor C1 and the second capacitor C2. Therefore, referring to FIG.
- the voltage feedforward circuit in the present exemplary embodiment further introduces a first reverse bias PN junction D1 and a second reverse bias PN junction D2 to balance the total leakage current.
- the first reverse bias PN junction D1 is coupled between the power supply voltage Vcc and the second terminal of the first capacitor C1; the second reverse bias PN junction D2 is coupled to the power supply voltage Vcc and the The second capacitor C2 is between the second ends.
- the first reverse biased PN junction D1 and the second reverse biased PN junction D2 are both non-conducting and in a reverse biased state, and the leakage current passes through the first reverse biased PN junction D1 and the The second reverse bias PN junction D2 flows from the power supply voltage Vcc into the first capacitor C1 and the second capacitor C2.
- the leakage current can compensate for leakage current flowing from the first capacitor C1 and the second capacitor C2.
- two on-chip capacitors are used to realize the hold and output of the peak voltage of the input voltage Vin without using an external resistor, so the ripple of the capacitor can be eliminated, and the selection of the capacitance and the resistance value can be avoided.
- the total leakage current is balanced, and the sustain time of the voltage on the on-chip capacitor is increased.
- the voltage of the on-chip capacitor output remains approximately constant during the sustain time, which is beneficial to stabilize the output of the multiplier, reduce THD (distortion), and improve the power factor correction effect.
- the bias current generating circuit may be as shown in FIG. 11, and the multiplier overall circuit is as shown in FIG.
- the bias current of the MOSFET transistor M0 is:
- the current of the emitter of the first transistor Q11 is:
- the current of the emitter of the first transistor Q12 is:
- Iout I EE ⁇ tanh(V1/2Vt) ⁇ tanh(V2/2Vt) (8)
- I EE is the tail current value
- V1, V2 are two pairs of input voltages
- Iout is the output current
- Iout I EE ⁇ (Vin1-Vref1) ⁇ (Vin2-Vref2)/Vff 2 (9)
- Equation (9) shows that the circuit contains 1/Vff 2 terms, which realizes the function of voltage feedforward.
- a power factor correction circuit is also provided in the present exemplary embodiment.
- the power factor correction circuit includes any one of the multipliers provided in the present exemplary embodiment.
- the power factor correction circuit can be formed on an integrated circuit module, and the first capacitor C1 and the second capacitor C2 are on-chip capacitors.
- the specific implementation manner and technical effects of the multiplier have been described in detail, and will not be explained in detail herein.
- the feedback control unit is used to provide feedback control, which improves the output current accuracy of the multiplier, and ensures that when the input voltage error is 0, there is no current.
- the output which is the more precise control of the offset voltage of the multiplier.
- the process requirements can be reduced, and the circuit application range is expanded.
- the retention of the peak voltage of the input voltage is achieved by setting the first capacitor and the second capacitor, so there is no need to consider the compromise between the external resistor and the external capacitor value in the prior art. select.
- the output voltage can be slowly changed to facilitate filtering out transient fluctuations of the input voltage;
- the variation slope of the output voltage can be changed.
- the first capacitor and the second capacitor can be implemented with on-chip capacitors, thereby saving system cost.
- the leakage current compensation mechanism by setting the leakage current compensation mechanism, the sustain time of the voltage on the internal capacitor is increased, so that the output voltage remains approximately constant within the maintenance time, which is advantageous for stabilizing the multiplier.
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Abstract
Description
Claims (10)
- 一种乘法器,其特征在于,包括:一吉尔伯特乘法器电路,包括第一、第二差分输入级以及一输出级;所述输出级输出由所述第一、第二差分输入级的输入运算得到的输出电流;一第一差分电压转换电路,用于基于接收到的电压信号以及一第一参考电压生成一第一差分电压偏置所述第一差分输入级;一第二差分电压转换电路,用于基于接收到的电压信号以及一第二参考电压生成一第二差分电压偏置所述第二差分输入级;一偏置电流生成电路,用于生成一偏置电流偏置所述第一信号转换电路及第二信号转换电路;其中,所述输出级包括:一电流镜单元,包括两电流输入端以及一电流输出端;一反馈控制单元,用于保证在所述乘法器接收到的电压信号差为零时,所述电流输出端没有电流输出。
- 根据权利要求1所述的乘法器,其特征在于,所述电流镜单元由P型MOSFET晶体管组成。
- 根据权利要求1所述的乘法器,其特征在于,所述反馈控制单元包括:一第一运算放大器,其两输入端分别对应连接所述电流镜单元的电流输入端;一第一开关元件,其第一端连接所述电流镜单元的电流输出端,第二端连接所述第一运算放大器的一输入端,其控制端连接所述第一运算放大器输出端;一第二开关元件,其第一端连接所述电流镜单元的电流输出端,第二端用于输出所述输出电流,其控制端连接所述第一运算放大器输出端。
- 根据权利要求1-3任意一项所述的乘法器,其特征在于,所述第二差分电压转换电路包括:一MOSFET晶体管,其栅极与漏极连接,源极连接所述电源电压;一第一BJT晶体管对,包括两个NPN型第一BJT晶体管;两个所述第一BJT晶体管的基极及集电极连接所述MOSFET晶体管的漏极,发射极输出所述第二差分电压;一第二BJT晶体管对,包括两个NPN型第二BJT晶体管;两个所述第二BJT晶体管的基极分别对应接收相异的两电压信号,集电极分别对应连接一所述第一BJT晶体管的发射极;一第一电阻,耦接于两个所述第二BJT晶体管的发射极之间;一第一MOSFET晶体管对,包括两个第一MOSFET晶体管;两个所述第一MOSFET晶体管的栅极接收所述偏置电流,源极接地,漏极分别对应连接一所述第二BJT晶体管的发射极。
- 根据权利要求4所述的乘法器,其特征在于,一所述第二BJT晶体管的基极接收所述输入电压或一误差反馈电压,另一BJT晶体管的基极接收所述第二参考电压。
- 根据权利要求1-3任意一项任意一项所述的乘法器,其特征在于,所述第一差分电压转换电路包括:一第二MOSFET晶体管对,包括两个第二MOSFET晶体管;两个所述第二MOSFET晶体管的栅极与漏极连接,源极连接所述电源电压;一第三BJT晶体管对,包括两个第三BJT晶体管;两个所述第三BJT晶体管的基极分别对应接收相异的两电压信号,集电极分别对应连接一所述第二MOSFET晶体管的漏极;一第二电阻,耦接于两个所述第三BJT晶体管的发射极之间;一第三MOSFET晶体管对,包括两个第三MOSFET晶体管;两个所述第三MOSFET晶体管的栅极接收所述偏置电流,源极接地,漏极分别对应连接一所述第三BJT晶体管的发射极;一第四MOSFET晶体管对,包括两个第四MOSFET晶体管;两个所述第四MOSFET晶体管的栅极分别对应连接一所述第二MOSFET晶体管的栅极,源极连接所述电源电压;一第四BJT晶体管对,包括两个NPN型第四BJT晶体管;两个所述第四BJT晶体管的基极分别对应连接一所述第四MOSFET晶体管的漏极,集电极输出所述第一差分电压;一BJT晶体管,其基极与集电极连接并连接至所述第四BJT晶体管的发射极,其发射极接地。
- 根据权利要求6所述的乘法器,其特征在于,一所述第三BJT晶体管的基极接收所述输入电压或一误差反馈电压,另一BJT晶体管的基极接收所述第一参考电压。
- 根据权利要求1-3、5或7任意一项所述的乘法器,其特征在于,所述乘法器还包括:一电压前馈电路;所述偏置电流生成电路基于所述电压前馈电路提供的电压生成所述偏置电流。
- 一种功率因数校正电路,其特征在于,包括根据权利要求1-8任意一项所述的乘法器。
- 根据权利要求9所述的功率因数校正电路,其特征在于,所述功率因数校正电路形成于一集成电路模块。
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