WO2016017142A1 - Contactless power-feeding device and contactless power-feeding system using same - Google Patents

Contactless power-feeding device and contactless power-feeding system using same Download PDF

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Publication number
WO2016017142A1
WO2016017142A1 PCT/JP2015/003757 JP2015003757W WO2016017142A1 WO 2016017142 A1 WO2016017142 A1 WO 2016017142A1 JP 2015003757 W JP2015003757 W JP 2015003757W WO 2016017142 A1 WO2016017142 A1 WO 2016017142A1
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Prior art keywords
coil
resonance
primary side
magnetic field
primary
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PCT/JP2015/003757
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French (fr)
Japanese (ja)
Inventor
一志 中澤
田村　秀樹
悟 田舎片
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パナソニックＩｐマネジメント株式会社
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Publication of WO2016017142A1 publication Critical patent/WO2016017142A1/en

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    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/70—Energy storage systems for electromobility, e.g. batteries

Definitions

  • the present invention relates generally to a noncontact power feeding device and a noncontact power feeding system, and more particularly to a noncontact power feeding device for noncontact power feeding to a load and a noncontact power feeding system using the same.
  • Document 1 Japanese Patent Application Publication No. 2014-90617.
  • Document 1 discloses a non-contact power transmission and reception system that includes a power transmission unit of a power transmission device and a power reception unit of a vehicle, and charges the power storage device of the vehicle contactlessly.
  • the power transmission unit has a primary self-resonance coil (primary side coil), receives supply of high frequency AC power from the power supply unit, and transmits power to the power reception unit in a contactless manner.
  • the power receiving unit has a secondary self-resonant coil (secondary side coil), and receives power transmitted from the power transmission unit in a contactless manner.
  • power is transmitted contactlessly from the power transmission unit to the power reception unit by resonating the primary coil and the secondary coil with an electromagnetic field.
  • the target parking position is presented to the user so as to efficiently transmit power between the power transmission unit and the power receiving unit, and the user is urged to park the vehicle at the target parking position.
  • the vehicle is not necessarily parked accurately at the target parking position, and there is a possibility that the parking position of the vehicle may deviate from the target parking position.
  • the present invention has been made in view of the above points, and provides a non-contact power feeding device capable of determining in which frequency region of resonance characteristics the operating frequency is located, and a non-contact power feeding system using the same.
  • the purpose is
  • the non-contact power feeding device includes an inverter circuit, a primary side resonance unit, a magnetic field detection unit, and a control unit.
  • the inverter circuit converts direct current power into alternating current power and outputs it.
  • the primary side resonance unit is composed of a solenoid type primary side coil that receives an AC power output from the inverter circuit to generate a magnetic flux, and a primary side capacitor that forms a primary side resonance circuit with the primary side coil.
  • the magnetic field detection unit detects a magnetic field.
  • the control unit executes a determination process of determining the correlation between the operating frequency of the inverter circuit and the resonance characteristic of the primary side resonance unit based on the detection result of the magnetic field detection unit.
  • the non-contact electric power feeding system of the aspect which concerns on this invention is equipped with said non-contact electric power feeding apparatus and the non-contact power receiving apparatus which receives the electric power supplied from the said non-contact electric power feeding apparatus.
  • the non-contact power reception device is configured of a secondary coil that generates an AC power by receiving a magnetic flux generated by the primary coil, and a secondary capacitor that forms a secondary resonance circuit with the secondary coil. And a secondary side resonance unit.
  • FIG. 1A is a diagram showing the arrangement of primary coils in the non-contact power feeding device according to the embodiment.
  • FIG. 1B and FIG. 1C are figures which show an example of arrangement
  • BRIEF DESCRIPTION OF THE DRAWINGS It is the circuit schematic which shows the non-contact electric power supply and the non-contact electric power supply system which concern on embodiment. It is a schematic diagram showing an example of use of a non-contact electric supply system concerning an embodiment.
  • FIG. 4A is a diagram showing resonance characteristics in a normal state.
  • FIG. 4B is a diagram showing resonance characteristics when the relative position between the primary coil and the secondary coil is shifted.
  • FIG. 5B are diagrams showing equivalent circuits of the primary side resonance part and the secondary side resonance part, respectively.
  • 6A and 6B are diagrams showing magnetic flux distributions generated by the primary coil and the secondary coil, respectively.
  • FIGS. 7A and 7B are diagrams showing simulation results of the magnetic flux distribution generated in the primary coil and the secondary coil, respectively.
  • FIG. 8A is a view showing another example of the arrangement of the magnetic field detection unit in the non-contact power feeding device according to the embodiment.
  • FIG. 8B is a diagram showing an example in which a plurality of magnetic field detection units are arranged in the non-contact power feeding device according to the embodiment.
  • FIG. 9A is a circuit diagram showing an example of a primary side capacitor in the non-contact power feeding device according to the embodiment.
  • FIG. 9B is a circuit diagram showing an example of a primary side coil in the non-contact power feeding device according to the embodiment.
  • FIG. 10A is a circuit diagram showing another configuration of the primary-side resonant unit of the non-contact power feeding device according to the embodiment.
  • FIG. 10B is a circuit diagram showing still another configuration of the primary-side resonant unit of the non-contact power feeding device according to the embodiment. It is the circuit schematic which shows the other structure of the non-contact electric power feeding system which concerns on embodiment.
  • the non-contact power feeding device 2 according to the embodiment of the present invention has the following first feature.
  • the non-contact power feeding device 2 includes an inverter circuit 212, a primary side resonance unit 23, a magnetic field detection unit 25, and a control unit 22.
  • the inverter circuit 212 converts DC power into AC power and outputs it.
  • the primary side resonance unit 23 is configured by a solenoid type primary side coil L1 that generates a magnetic flux by receiving AC power output from the inverter circuit 212, and a primary side capacitor C1 that forms a primary side resonance circuit with the primary side coil L1. Be done.
  • the magnetic field detection unit 25 detects a magnetic field.
  • the control unit 22 executes a determination process of determining the correlation between the operating frequency f1 of the inverter circuit 212 and the resonance characteristic of the primary side resonance unit 23 based on the detection result of the magnetic field detection unit 25.
  • the non-contact power feeding device 2 of the present embodiment may have the following second feature.
  • the resonance characteristic of the primary side resonance unit 23 has two resonance frequencies. And, this resonance characteristic is a low frequency area which is a frequency area lower than a predetermined frequency and a frequency area higher than the predetermined frequency with a predetermined frequency at which the output of the primary side resonance unit 23 shows a local minimum as a boundary. And a high frequency region that is Then, in the determination process, the control unit 22 determines which one of the low frequency region and the high frequency region the operating frequency f1 is positioned in accordance with the comparison result between the strength of the magnetic field detected by the magnetic field detection unit 25 and the threshold value. Do.
  • the non-contact power feeding device 2 of the present embodiment may have the following third feature.
  • the magnetic field detection unit 25 is disposed on one end side in the central axis direction of the primary coil L1.
  • the non-contact power feeding device 2 of the present embodiment may have the following fourth feature.
  • the magnetic field detection unit 25 is disposed around the central portion of the primary coil L1 at a predetermined distance from the primary coil L1.
  • non-contact power feeding device 2 of the present embodiment may have the following fifth feature in addition to any of the first to fourth features.
  • the non-contact power feeding device 2 includes a plurality of magnetic field detectors 25. Then, the control unit 22 compares at least two detection results of the plurality of magnetic field detection units 25 in the determination process.
  • non-contact power feeding device 2 of the present embodiment may have the following sixth feature in addition to any of the first to fifth features.
  • control unit 22 executes adjustment processing for adjusting the operating frequency f1 of the inverter circuit 212 based on the determination result of the determination processing.
  • non-contact power feeding device 2 of the present embodiment may have the following seventh feature in addition to any of the first to fifth features.
  • control unit 22 executes adjustment processing of adjusting the resonance parameter of the primary side resonance unit 23 based on the determination result of the determination processing.
  • the non-contact electric power supply 2 of this embodiment may have the following 8th characteristic.
  • the control unit 22 when the resonance characteristic of the primary side resonance unit 23 has two resonance frequencies, the control unit 22 performs adjustment processing so that the operating frequency f1 approaches a lower resonance frequency of the two resonance frequencies. Run.
  • the non-contact power feeding device 2 of the present embodiment may have the following ninth feature in addition to any of the sixth to eighth features.
  • the non-contact power feeding device 2 includes a current detection unit 24 that detects a current corresponding to the current flowing through the primary coil L1. Then, based on the detection result of the current detection unit 24, the control unit 22 executes adjustment processing so that the inverter circuit 212 operates in the lagging mode.
  • non-contact power feeding system 1 of the present embodiment may have the following tenth feature.
  • the non-contact power feeding system 1 includes a non-contact power feeding device 2 and a non-contact power receiving device 3 receiving power supplied from the non-contact power feeding device 2.
  • the non-contact power reception device 3 receives a magnetic flux generated by the primary coil L1 and generates an alternating current power, and a secondary side capacitor C2 which forms a secondary side resonant circuit with the secondary side coil L2.
  • the secondary side resonance part 31 comprised by these is provided.
  • the non-contact power feeding system 1 of the present embodiment may have the following eleventh feature.
  • control unit 22 (control unit 33) outputs an instruction signal for prompting a change in the relative position of the primary side coil L1 and the secondary side coil L2, based on the determination result of the determination process. Run.
  • the non-contact power feeding device 2 and the non-contact power feeding system 1 of the present embodiment can determine in which frequency region in the resonance characteristic the operating frequency is located.
  • the non-contact power feeding device 2 and the non-contact power feeding system 1 of the present embodiment will be described in detail.
  • the configuration described below is only an example of the present invention, and the present invention is not limited to the following embodiment, and even if it is other than this embodiment, it deviates from the technical idea according to the present invention. If it is not within the range, various changes can be made according to the design and the like.
  • the non-contact power feeding device 2 and the non-contact power feeding system 1 of the present embodiment may be configured to contact the load 4 in a non-contact manner, and the load 4 is not limited to the charging circuit 102 of the electric vehicle 100.
  • the non-contact power feeding system 1 of the present embodiment includes the non-contact power feeding device 2 and the non-contact power receiving device 3.
  • the non-contact power feeding device 2 includes a power supply unit 21, a control unit 22, a primary side resonance unit 23, a current detection unit 24, and a magnetic field detection unit 25.
  • the primary side resonance unit 23 is configured of a primary side capacitor C1 and a primary side coil L1.
  • the non-contact power reception device 3 includes a secondary side resonance unit 31 and a rectification unit 32.
  • the secondary side resonance part 31 is comprised by the secondary side capacitor
  • the noncontact power feeding device 2 is installed on the floor or the ground.
  • the non-contact power feeding device 2 may be embedded not only on the floor or the ground but also, for example, on the floor or the ground.
  • the non-contact power feeding device 2 is configured such that only the primary side coil L1 is disposed at a position where it can face the secondary side coil L2, and other components, circuits, etc. are disposed at a distance from the primary side coil L1. It may be done.
  • the non-contact power receiving device 3 is installed in a vehicle of the electric vehicle 100.
  • the non-contact power reception device 3 is electrically connected to the storage battery 101 via the charging circuit 102.
  • the storage battery 101 is configured of, for example, a nickel hydrogen battery, a lithium ion battery, a high capacity capacitor, or the like.
  • Storage battery 101 is used as a power source of a motor provided in electric vehicle 100.
  • the storage battery 101 is used as a power supply of electronic devices such as a car navigation system, a car audio system, and a power window provided in the electric vehicle 100.
  • the charging circuit 102 is a circuit that charges the storage battery 101 with the power obtained by appropriately converting the power supplied from the non-contact power feeding device 2.
  • the non-contact power feeding device 2 will be described.
  • the power supply unit 21 is a circuit for supplying desired AC power from the AC power supply AC1 to the primary side resonance unit 23.
  • a power factor correction (PFC) circuit 211 and an inverter circuit 212 are provided. And have.
  • the power factor correction circuit 211 is composed of a diode bridge composed of four diodes D1 to D4, a coil L0, a switching element Q0, a diode D5, and a capacitor C0.
  • the switching element Q0 is controlled to be turned on / off by receiving a control signal from the control unit 22.
  • the switching element Q0 is an n-channel enhancement type MOSFET (Metal-Oxide-Semiconductor Field-Effect Transistor).
  • the switching element Q0 may be configured of another semiconductor switching element such as a bipolar transistor or an IGBT (Insulated Gate Bipolar Transistor). Therefore, the power factor improvement circuit 211 is configured to output a voltage of a desired height by controlling the on / off of the switching element Q0 by the control unit 22.
  • the inverter circuit 212 is a full bridge inverter composed of four switching elements Q1 to Q4 as shown in FIG.
  • the switching elements Q1 to Q4 are n-channel enhancement MOSFETs.
  • Switching elements Q1 to Q4 may be formed of other semiconductor switching elements such as bipolar transistors and IGBTs, respectively.
  • a series circuit of two switching elements Q1 and Q2 and a series circuit of two switching elements Q3 and Q4 are electrically connected in parallel.
  • the drains of the switching elements Q1 and Q3 are electrically connected to the high potential side output point of the power factor correction circuit 211, respectively.
  • the sources of the switching elements Q2 and Q4 are electrically connected to the low potential side output point of the power factor correction circuit 211, respectively.
  • the connection point of the source of the switching element Q3 and the drain of the switching element Q4 is a first output point of the inverter circuit 212.
  • a connection point of the source of the switching element Q1 and the drain of the switching element Q2 is a second output point of the inverter circuit 212.
  • the switching elements Q1 and Q4 are switched on / off by receiving the first drive signal G1 from the control unit 22.
  • the switching elements Q2 and Q3 can be switched on / off by being supplied with the second drive signal G2.
  • the second drive signal G2 is a rectangular wave signal that is 180 degrees out of phase with the first drive signal G1.
  • the inverter circuit 212 operates so as to alternately switch on periods of the switching elements Q1 and Q4 and on periods of the switching elements Q2 and Q3 according to the first drive signal G1 and the second drive signal G2.
  • the inverter circuit 212 converts the DC power supplied from the power factor correction circuit 211 into AC power and outputs it.
  • the voltage output from the inverter circuit 212 is referred to as “output voltage V1”
  • the current output from the inverter circuit 212 is referred to as “output current I1”.
  • the control unit 22 is configured of, for example, a microcomputer.
  • the control unit 22 changes the output voltage of the power factor correction circuit 211 by giving a control signal to the power factor correction circuit 211. Further, the control unit 22 controls the operation of the inverter circuit 212 by providing the first drive signal G1 and the second drive signal G2 to the switching elements Q1 to Q4.
  • the primary side resonance unit 23 is configured by electrically connecting a primary side capacitor C1 and a primary side coil L1 in series at a pair of output points of the inverter circuit 212. Further, the primary side coil L1 forms a resonant circuit (a primary side resonant circuit) together with the primary side capacitor C1.
  • the primary side coil L1 is a solenoid type coil configured by winding a wire around the core 231 to form a spiral.
  • the core 231 is formed in a plate shape, for example, by a magnetic material such as ferrite.
  • the primary coil L1 generates a magnetic flux when the alternating current output from the inverter circuit 212 flows. That is, the primary coil L1 receives the AC power output from the inverter circuit 212 and generates a magnetic flux.
  • the current detection unit 24 is configured of, for example, a shunt resistor or a Hall element. As shown in FIG. 2, the current detection unit 24 detects an output current I1 flowing from the inverter circuit 212 to the primary coil L1. In other words, the current detection unit 24 detects a current corresponding to the current flowing through the primary coil L1. The detection result (the instantaneous current of the output current I1) of the current detection unit 24 is used when the control unit 22 executes an adjustment process described later.
  • the magnetic field detection unit 25 includes, for example, a Hall element or a search coil.
  • the magnetic field detection unit 25 detects a magnetic field acting on a space including the primary coil L1 and the secondary coil L2, as shown in FIG. 1B.
  • the detection result (for example, the strength of the magnetic field) of the magnetic field detection unit 25 is used when the control unit 22 executes a determination process described later.
  • the magnetic field detection part 25 is comprised by the Hall element, it is preferable that the magnetic field detection part 25 is arrange
  • the magnetic field detection unit 25 is configured by a search coil, it is preferable that the magnetic field detection unit 25 be disposed so that the magnetic flux generated by the primary coil L1 intersects the search coil.
  • the magnetic field detection unit 25 is disposed at one end (right end) in the longitudinal direction (left and right direction in FIG. 1C) of the core 231 as shown in FIGS. That is, the magnetic field detection unit 25 is disposed on one end (right end) side in the central axis direction of the primary coil L1.
  • the magnetic field detection unit 25 is disposed at a predetermined distance from the core 231 in the thickness direction of the core 231 (vertical direction in FIG. 1B) using, for example, a spacer.
  • the magnetic field detection unit 25 may be disposed on the other end (left end) of the core 231 in the longitudinal direction, that is, on the other end (left end) side in the central axis direction of the primary coil L1.
  • the secondary side resonance unit 31 is configured by electrically connecting a secondary side capacitor C2 and a secondary side coil L2 in series at a pair of input points of the rectification unit 32. . Further, the secondary side coil L2 forms a resonant circuit (secondary side resonant circuit) together with the secondary side capacitor C2.
  • the secondary coil L2 is a solenoid type coil formed by winding a conductive wire around the core 311.
  • the core 311 is formed in a plate shape, for example, by a magnetic material such as ferrite.
  • the secondary coil L2 is provided so as to be located in the vicinity of the primary coil L1 when the electric vehicle 100 stops at a prescribed stopping position. In other words, the secondary coil L2 is provided to face the primary coil L1 at a predetermined interval when the electric vehicle 100 stops at a prescribed stopping position.
  • the secondary coil L2 receives the magnetic flux generated by the primary coil L1
  • an alternating current flows by electromagnetic induction. That is, the secondary coil L2 receives the magnetic flux generated by the primary coil L1 and generates AC power.
  • the rectifying unit 32 is configured of a diode bridge 321 configured of four diodes and a capacitor C3.
  • the diode bridge 321 converts the alternating current generated in the secondary coil L2 into a pulsating current and outputs it.
  • the capacitor C3 is electrically connected to a pair of output points of the diode bridge 321, smoothes the pulsating current output from the diode bridge 321, and outputs a direct current. That is, the rectifying unit 32 rectifies AC power generated by the secondary coil L2 into DC power and outputs DC power.
  • the DC power output from the rectifying unit 32 is supplied to the load 4 (here, the charging circuit 102).
  • the non-contact power feeding system 1 of the present embodiment power is transmitted from the primary side resonance unit 23 to the secondary side resonance unit 31 by a resonance method using a magnetic resonance phenomenon. Then, in the non-contact power feeding system 1 of the present embodiment, the non-contact power receiving device 3 efficiently outputs the output power of the non-contact power feeding device 2 by utilizing the magnetic resonance between the primary side resonance unit 23 and the secondary side resonance unit 31. It is transmitted to Therefore, it is preferable that the frequency characteristic of the primary side resonance unit 23 and the frequency characteristic of the secondary side resonance unit 31 match each other.
  • the frequency characteristic (hereinafter, referred to as “resonance characteristic”) of the primary side resonance unit 23 in the non-contact power feeding system 1 of the present embodiment will be described.
  • the resonance characteristics change according to the density of the magnetic coupling between the primary coil L1 and the secondary coil L2.
  • the resonance characteristic changes in accordance with the magnitude of the coupling coefficient between the primary coil L1 and the secondary coil L2.
  • the resonance characteristic exhibits so-called bimodal characteristics in which two local maximum values of the output of the primary side resonance unit 23 appear as shown in FIG. 4A.
  • this resonance characteristic there are a peak at which the output of the primary side resonance unit 23 becomes the maximum value at the first frequency fr1, and a valley at which the output of the primary side resonance unit 23 becomes the minimum value at the second frequency fr2 (fr2> fr1). It has appeared. Further, in this resonance characteristic, a peak at which the output of the primary side resonance unit 23 is a maximum value appears at the third frequency fr3 (fr3> fr2). That is, this resonance characteristic (bimodal characteristic) has two resonance frequencies (first frequency fr1 and third frequency fr3).
  • the inverter circuit 212 operates in either the lagging mode or the phase advancing mode.
  • the “operating frequency f1” is the frequency of the first drive signal G1 and the second drive signal G2, in other words, the frequency of the output voltage V1 of the inverter circuit 212.
  • the phase advance mode is a mode in which the inverter circuit 212 operates with the phase of the output current I1 of the inverter circuit 212 leading the phase of the output voltage V1 of the inverter circuit 212.
  • the switching operation of the inverter circuit 212 is so-called hard switching.
  • the lagging mode is a mode in which the inverter circuit 212 operates in a state in which the output current I1 of the inverter circuit 212 is delayed from the phase of the output voltage V1 of the inverter circuit 212. In the lagging mode, the switching operation of the inverter circuit 212 is so-called soft switching.
  • the inverter circuit 212 preferably operates in the lagging mode.
  • the operating frequency f1 is located in the frequency range between the first frequency fr1 and the second frequency fr2, and the operating frequency f1 is larger than the third frequency fr3. Operates in lagging mode, either in
  • the operating frequency f1 be located in the low frequency range rather than the high frequency range.
  • the “low frequency region” is a frequency region lower than the second frequency fr2 (predetermined frequency) at which the output of the primary side resonance unit 23 exhibits a local minimum value in the resonance characteristics.
  • the “high frequency region” is a frequency region higher than the second frequency fr2 (predetermined frequency) at which the output of the primary side resonance unit 23 exhibits a local minimum value in the resonance characteristics.
  • the relative position of the primary side coil L1 and the secondary side coil L2 may shift
  • the stopping position of the electric vehicle 100 deviates from a predetermined stopping position
  • the relative position between the primary coil L1 and the secondary coil L2 deviates.
  • the magnetic coupling between the primary coil L1 and the secondary coil L2 changes (that is, the coupling coefficient changes).
  • the resonance characteristics change, for example, from the characteristics shown in FIG. 4A to the characteristics shown in FIG. 4B by changing the frequencies fr1 to fr3.
  • the operating frequency f1 is a constant frequency.
  • the operating frequency f1 in the resonance characteristic shown in FIG. 4A, the operating frequency f1 is located in the low frequency region, whereas in the resonance characteristic shown in FIG. 4B, the operating frequency f1 is located in the high frequency region. Therefore, in the resonance characteristic shown in FIG. 4B, the phase of the current flowing through the primary coil L1 and the phase of the current flowing through the secondary coil L2 are aligned, and the unnecessary radiation can not be reduced.
  • the inventors of the present application operate in the space including the primary coil L1 and the secondary coil L2 when the operating frequency f1 is located in the low frequency region and when the operating frequency f1 is located in the high frequency region. Focused on the change of the magnetic field (magnetic field).
  • FIG. 5A shows an equivalent circuit of the primary side resonance unit 23 and the secondary side resonance unit 31 when the operating frequency f1 is located in the low frequency region.
  • the parallel circuit of mutual inductor M1 and two series resonance circuits (the primary side resonance part 23 and the secondary side resonance part 31) resonates .
  • a current flows through the mutual inductor M1, and the direction of the current flowing through the primary coil L1 and the direction of the current flowing through the secondary coil L2 become opposite to each other.
  • FIG. 5B shows an equivalent circuit of the primary side resonance unit 23 and the secondary side resonance unit 31 when the operating frequency f1 is located in the high frequency region.
  • the primary side coil L1 and the secondary side coil L2 resonate with the primary side capacitor C1 and the secondary side capacitor C2.
  • no current flows through the mutual inductor M1 and the direction of the current flowing through the primary coil L1 and the direction of the current flowing through the secondary coil L2 become the same.
  • FIG. 6A shows the distribution of magnetic flux generated by the primary coil L1 and the secondary coil L2 when the operating frequency f1 is located in the low frequency region.
  • the direction of the magnetic flux B1 generated in the primary side coil L1 and passing through the core 231 and the direction of the magnetic flux B2 generated in the secondary side coil L2 and passing through the core 311 become opposite to each other.
  • the magnetic flux B1 generated by the primary coil L1 and the magnetic flux B2 generated by the secondary coil L2 cancel each other (FIG. 6A). See dashed arrow).
  • FIG. 6B shows the distribution of magnetic flux generated by the primary coil L1 and the secondary coil L2 when the operating frequency f1 is located in the high frequency region.
  • the direction of the magnetic flux B1 generated by the primary coil L1 and passing through the core 231 is the same as the direction of the magnetic flux B2 generated by the secondary coil L2 and passing through the core 311. Therefore, in the space between primary coil L1 and secondary coil L2, magnetic flux B1 generated by primary coil L1 and magnetic flux B2 generated by secondary coil L2 mutually strengthen each other (broken line in FIG. 6B See arrow)).
  • the “first direction” is the axial direction (horizontal direction in FIG. 6A) of the primary coil L1 (secondary coil L2) wound in a cylindrical shape.
  • FIGS. 7A and 7B show the magnetic flux distribution on one end side (right end side or left end side in FIG. 6A) in the central axis direction of the primary side coil L1 and the secondary side coil L2.
  • Arrows shown in FIGS. 7A and 7B indicate the directions of the magnetic flux.
  • the operating frequency f1 is located in the low frequency region, as shown in FIG. 7A, one end in the central axis direction of the primary coil L1 (right end in FIG. 7A) to one end in the central axis direction of the secondary coil L2 (figure The magnetic flux in the direction toward the right end in 7A becomes strong.
  • FIG. 7B shows one end (right end in FIG. 7B) in the central axis direction of the primary coil L1 to one end in the central axis direction of the secondary coil L2.
  • the magnetic flux in the direction toward the right end in FIG. 7B becomes weak.
  • the “second direction” is a direction (vertical direction in FIG. 7A) perpendicular to one surface (upper surface or lower surface in FIG. 7A) of the core 231 (core 311).
  • the magnetic field detection unit 25 is disposed on one end (right end) side in the central axis direction of the primary coil L1 (see FIGS. 1B and 1C) . Therefore, the magnetic field detected by the magnetic field detection unit 25 becomes stronger when the operating frequency f1 is located in the low frequency region, and becomes weaker when the operating frequency f1 is located in the high frequency region. Then, based on the detection result of the magnetic field detection unit 25, the control unit 22 executes a determination process of determining the correlation between the operating frequency f1 of the inverter circuit 212 and the resonance characteristic of the primary side resonance unit 23.
  • the control unit 22 compares the strength of the magnetic field detected by the magnetic field detection unit 25 with a preset threshold. Then, in the determination processing, when the strength of the magnetic field detected by the magnetic field detection unit 25 exceeds the threshold, the control unit 22 determines that the operating frequency f1 is located in the low frequency region. In the determination process, if the strength of the magnetic field detected by the magnetic field detection unit 25 falls below the threshold, the control unit 22 determines that the operating frequency f1 is located in the high frequency region. When the strength of the magnetic field detected by the magnetic field detection unit 25 is equal to the threshold value, which of the low frequency region and the high frequency region the operating frequency f1 is positioned may be set appropriately.
  • the non-contact power feeding device 2 of the present embodiment includes the magnetic field detection unit 25 that detects a magnetic field. Then, in the non-contact power feeding device 2 of the present embodiment, the control unit 22 determines the correlation between the operating frequency f1 of the inverter circuit 212 and the resonance characteristic of the primary side resonance unit 23 based on the detection result of the magnetic field detection unit 25. Execute judgment processing. Therefore, the non-contact power feeding device 2 of the present embodiment can determine in which frequency region in the resonance characteristic the operating frequency f1 is located by the determination processing performed by the control unit 22.
  • the non-contact power feeding device 2 of the present embodiment determines which frequency region in the changed resonance characteristic Can determine whether the operating frequency f1 is located.
  • the magnetic field detection unit 25 is disposed on one end side in the central axis direction of the primary coil L1. For this reason, since the magnetic flux linked (crossed) to the magnetic field detection unit 25 largely changes depending on whether the operating frequency f1 is located in the low frequency region or in the high frequency region, a change in the strength of the magnetic field is detected. It has the advantage of being easy to do.
  • the magnetic field detection unit 25 may be disposed at a location different from one end side in the central axis direction of the primary coil L1.
  • the magnetic field detection unit 25 may be disposed around the central portion of the primary coil L1 at a predetermined distance from the primary coil L1.
  • the magnetic field detection unit 25 may be disposed in the space between the primary coil L1 and the secondary coil L2.
  • the magnetic field detected by the magnetic field detection unit 25 is weak when the operating frequency f1 is located in the low frequency region, and is strong when the operating frequency f1 is located in the high frequency region.
  • the control unit 22 determines that the operating frequency f1 is located in the high frequency region. Further, in the determination process, if the strength of the magnetic field detected by the magnetic field detection unit 25 falls below the threshold in the determination process, the control unit 22 determines that the operating frequency f1 is located in the low frequency region. Even in this configuration, since the magnetic flux that intersects (crosses) the magnetic field detection unit 25 largely changes depending on whether the operating frequency f1 is located in the low frequency region or in the high frequency region, It has the advantage of being easy to detect.
  • the non-contact electric power supply 2 of this embodiment may be equipped with the magnetic field detection part 25 of plurality (six in illustration), for example, as shown to FIG. 8B.
  • the three magnetic field detection parts 25 are arrange
  • the control unit 22 may compare at least two detection results of the plurality of magnetic field detection units 25 in the determination process.
  • the strength of the magnetic field detected by the magnetic field detector 25 changes in accordance with the relative position of the primary coil L1 and the secondary coil L2. That is, in the magnetic field detection unit 25, the strength of the detected magnetic field becomes stronger as it approaches the secondary coil L2, and the strength of the detected magnetic field becomes weaker as it gets farther from the secondary coil L2. Therefore, in the determination process, the control unit 22 determines the relative position between the primary coil L1 and the secondary coil L2 based on the difference (gradient) in the strength of the magnetic field detected by each magnetic field detection unit 25. It can be determined.
  • the control unit 22 It can be determined that the coil L2 is shifted downward in FIG. 8B. In addition, it is arbitrary whether to employ
  • the control unit 22 determines that the operating frequency f1 is an appropriate frequency range (that is, a low frequency range) in the resonance characteristic based on the determination process as well as the determination process.
  • An adjustment process may be performed to adjust the position of the vehicle.
  • control unit 22 may execute the adjustment process of adjusting the operating frequency f1 of the inverter circuit 212 based on the determination result of the determination process. For example, it is assumed that the control unit 22 determines that the operating frequency f1 is located in the high frequency region in the determination process. In this case, the control unit 22 reduces the operating frequency f1 in the adjustment process. By this adjustment process, the operating frequency f1 is adjusted to be located in the low frequency region. In addition, it is arbitrary whether to employ
  • control unit 22 may execute an adjustment process of adjusting the resonance parameter of the primary side resonance unit 23 based on the determination result of the determination process.
  • the “resonance parameter” is the capacitance of the primary side capacitor C1 or the inductance of the primary side coil L1.
  • the control unit 22 determines that the operating frequency f1 is located in the high frequency region in the determination process.
  • the control unit 22 reduces at least one of the capacitance of the primary side capacitor C1 and the inductance of the primary side coil L1 in the adjustment process.
  • the resonance characteristics shift to the high frequency side by increasing the frequencies fr1 to fr3.
  • the operating frequency f1 is adjusted to be located in the low frequency region of the adjusted resonance characteristic.
  • the control unit 22 sets the operating frequency f1 to a low resonance frequency of the two resonance frequencies. It is preferable to carry out the adjustment process to get closer. That is, as described above, the control unit 22 adjusts the operating frequency f1 of the inverter circuit 212 or adjusts the resonance parameter of the primary side resonance unit 23 to position the operating frequency f1 in the low frequency region. It is preferable to carry out the adjustment process as follows. In addition, it is arbitrary whether to employ
  • a configuration shown in FIG. 9A can be considered as the primary side capacitor C1 whose capacitance can be adjusted by the control unit 22.
  • the primary side capacitor C1 shown in FIG. 9A includes two capacitors C11 and C12 having different capacitances, and two switches QC1 and QC2.
  • the switch QC1 is electrically connected in series to the capacitor C11.
  • the switch QC2 is electrically connected in series to the capacitor C12. Then, a series circuit of the capacitor C11 and the switch QC1 and a series circuit of the capacitor C12 and the switch QC2 are electrically connected in parallel.
  • the primary side coil L1 shown in FIG. 9B includes two coils L11 and L12 electrically connected in series to each other, and a switch QL1 electrically connected in parallel to one coil L12.
  • the switches QC1, QC2, QL1 are formed of semiconductor switches such as MOSFETs, for example.
  • the switches QC1, QC2, and QL1 are controlled by the control unit 22 to turn on and off. Therefore, in the configuration shown in FIG. 9A, the capacitance of the primary side capacitor C1 can be adjusted by controlling the control unit 22 to switch on / off the switches QC1 and QC2. Similarly, in the configuration shown in FIG. 9B, the inductance of the primary side coil L1 can be adjusted by controlling the control unit 22 to switch on / off the switch QL1.
  • the capacitance of the primary side capacitor C1 can be made in more stages by increasing the number of series circuits. It is possible to adjust.
  • the number of parallel circuits of the coil L12 and the switch QL1 is one in the configuration shown in FIG. 9B, the inductance of the primary side coil L1 may be adjusted in more stages by increasing the number of parallel circuits. It is possible.
  • the primary side capacitor C1 may be incorporated in a capacity adjustment circuit 232 as shown in FIG. 10A.
  • the capacitance adjustment circuit 232 is configured of a primary side capacitor C1 and four switching elements Q5 to Q8.
  • switching elements Q5 to Q8 are n-channel enhancement type MOSFETs.
  • a series circuit of two switching elements Q5 and Q6 and a series circuit of two switching elements Q7 and Q8 are electrically connected in parallel.
  • the connection point of the source of the switching element Q5 and the drain of the switching element Q6 is electrically connected to the first output point of the inverter circuit 212.
  • connection point of the source of the switching element Q7 and the drain of the switching element Q8 is electrically connected to one end of the primary coil L1.
  • the primary side capacitor C1 is electrically connected between the connection point of the sources of the switching elements Q5 and Q7 and the connection point of the drains of the switching elements Q6 and Q8.
  • the capacitance adjustment circuit 232 operates by supplying the third drive signal G3 to the switching elements Q5 and Q8 and the fourth drive signal G4 to the switching elements Q6 and Q7. Specifically, the capacitance adjustment circuit 232 operates so as to alternately switch on periods of the switching elements Q5 and Q8 and on periods of the switching elements Q6 and Q7 by the third drive signal G3 and the fourth drive signal G4. Do.
  • the capacitance adjustment circuit 232 is configured to switch the path through the primary side capacitor C1 and the path not through the primary side capacitor C1 by switching on / off the switching elements Q5 to Q8.
  • the capacitance of the capacity adjustment circuit 232 (that is, the capacitance of the primary side capacitor C1) can be adjusted by changing the period in which the primary side capacitor C1 is connected between the input and output of the capacity adjustment circuit 232. it can.
  • capacitance adjustment circuit 232 may be configured using two bidirectional switches Q9 and Q10 as shown in FIG. 10B.
  • the bidirectional switch Q9 is composed of a semiconductor element of a double gate structure having two gate terminals. Further, the bidirectional switch Q9 is electrically connected in series to the primary side capacitor C1.
  • the bidirectional switch Q10 is composed of a semiconductor element of a double gate structure having two gate terminals. Further, the bidirectional switch Q10 is electrically connected in parallel to the series circuit of the bidirectional switch Q9 and the primary side capacitor C1.
  • the third drive signal G3 and the fourth drive signal G4 are input to the two gate terminals of the bidirectional switch Q9, respectively.
  • the third drive signal G3 and the fourth drive signal G4 are input to the two gate terminals of the bidirectional switch Q10, respectively.
  • the capacitance adjustment circuit 232 configured in this way operates in the same manner as the capacitance adjustment circuit 232 shown in FIG. 10A.
  • the non-contact power feeding device 2 of the present embodiment includes the current detection unit 24 that detects a current (output current I1) corresponding to the current flowing through the primary side coil L1 (see FIG. 2). Therefore, based on the detection result of the current detection unit 24, the control unit 22 may perform adjustment processing so that the inverter circuit 212 operates in the lagging mode. For example, the control unit 22 controls the inverter circuit 212 in any one of the lagging phase mode and the phase advancing mode according to the current value of the output current I1 when the pair of switching elements Q1 and Q4 of the inverter circuit 212 is turned off. Can be determined.
  • the control unit 22 determines that the circuit 212 is operating in the lagging mode.
  • the control unit 22 operates the inverter circuit 212 in the phase advance mode. It is determined that there is.
  • control unit 22 adjusts the inverter circuit 212 to operate in the lagging mode based on the determination result of whether the inverter circuit 212 is operating in the lagging mode or the phase advancing mode.
  • the adjustment method as described above, the method of adjusting the operating frequency f1 of the inverter circuit 212 or adjusting the resonance parameter of the primary side resonance unit 23 may be mentioned.
  • the inverter circuit 212 can be operated in the lagging mode, it is possible to reduce the loss due to the switching of the switching elements Q1 to Q4 of the inverter circuit 212. Moreover, in this configuration, it is possible to prevent the excessive electrical stress from being applied to the switching elements Q1 to Q4 of the inverter circuit 212. In addition, it is arbitrary whether to employ
  • the control unit 22 may execute the determination process again after performing the adjustment process. Then, if it is determined that the operating frequency f1 is located in the high frequency region also in the second determination process, the control unit 22 may further execute the adjustment process.
  • the control unit 22 performs the determination process and the adjustment process in the start period from the start of the power supply unit 21 to the start of the power feeding operation to make the operating frequency f1 constant. Running. Then, the control unit 22 controls the power factor improvement circuit 211 such that the output voltage V1 in the start period is lower than the output voltage V1 during the power supply operation. For example, if the power factor correction circuit 211 has the configuration shown in FIG. 2, the control unit 22 lowers the output voltage V1 in the start period by controlling the on / off of the switching element Q0. Further, when starting the power supply operation, the control unit 22 controls the on / off of the switching element Q0 to increase the output voltage V1 during the power supply operation.
  • the control unit 22 outputs an instruction signal for prompting a change in the relative position of the primary coil L1 and the secondary coil L2 based on the determination result of the determination process. Processing may be performed.
  • the control unit 22 may output an instruction signal to the actuator.
  • the control unit 22 determines that the operating frequency f1 is located in the high frequency region in the determination process.
  • the control unit 22 outputs an instruction signal to the actuator.
  • the actuator adjusts the position of the primary coil L1 in accordance with the instruction signal.
  • the non-contact power feeding system 1 for example, provides an instruction signal to the non-contact power reception device 3 and adjusts the position of the secondary coil L2 according to the instruction signal. You may be comprised so that the relative position of the following coil L2 may be adjusted.
  • the non-contact power feeding device 2 and the non-contact power receiving device 3 respectively include communication units 26 and 34.
  • the communication units 26 and 34 are configured to communicate with each other by, for example, radio signals using radio waves as a medium.
  • the non-contact power reception device 3 also includes a control unit 33 that executes a process according to the instruction signal.
  • the control unit 33 is, for example, a microcomputer as in the case of the control unit 22.
  • the control unit 22 determines that the operating frequency f1 is located in the high frequency region in the determination process.
  • the control unit 22 generates an instruction signal, and causes the communication unit 26 to transmit the instruction signal to the non-contact power reception device 3.
  • the communication unit 34 inputs the instruction signal to the control unit 33.
  • the control unit 33 instructs the user to move the electric vehicle 100 to the appropriate stopping position based on the input instruction signal.
  • the instruction is performed by, for example, outputting sound from a speaker mounted on the electric vehicle 100 or displaying an image or a moving image on a display mounted on the electric vehicle 100.
  • the core 231 is provided with the primary coil L1 and the core 311 is provided with the secondary coil L2, but the present invention is not limited to this configuration. That is, the primary coil L1 may be provided to a member other than the core 231. Similarly, the secondary coil L2 may be provided to a member other than the core 311.
  • the non-contact electric power supply system 1 of this embodiment provides the magnetic field detection part 25 in the non-contact electric power supply apparatus 2 and makes the control part 22 perform a determination process and adjustment process, even if it is another structure. Good. That is, in the non-contact power feeding system 1 of the present embodiment, the non-contact power reception device 3 may be configured to have the magnetic field detection unit 25 and cause the control unit 33 to execute the determination process and the adjustment process.
  • the non-contact power feeding device 2 and the non-contact power feeding system 1 of the present embodiment power is transmitted from the primary coil L1 to the secondary coil L2 by resonance, but power is transmitted by electromagnetic induction. It may be In this configuration, since it is not necessary to form a resonant circuit in the non-contact power reception device 3, the secondary side capacitor C2 is unnecessary.
  • the non-contact electric power feeding system 1 of this embodiment employ
  • the non-contact power feeding system 1 of this embodiment has an advantage that it is easy to miniaturize the primary side coil L1 and the secondary side coil L2 as compared with the case where a spiral type coil is adopted.
  • the non-contact power feeding system 1 of the present embodiment even if the relative position between the primary side coil L1 and the secondary side coil L2 is somewhat deviated in the first direction (the left and right direction in FIG. It has the advantage of being difficult to change.

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  • Electric Propulsion And Braking For Vehicles (AREA)
  • Charge And Discharge Circuits For Batteries Or The Like (AREA)

Abstract

This invention addresses the problem of determining which frequency region within resonance characteristics an operating frequency lies in. This contactless power-feeding device (2) is provided with an inverter circuit, a primary-side resonance unit, a magnetic-field detection unit (25), and a control unit. The inverter circuit converts DC power to AC power and outputs said AC power. The primary-side resonance unit comprises the following: a solenoid-type primary-side coil (L1) that receives the AC power outputted by the inverter circuit and produces a magnetic flux; and a primary-side capacitor that, together with the solenoid-type primary-side coil (L1), forms a primary-side resonant circuit. The magnetic-field detection unit (25) detects a magnetic field. On the basis of the results of the detection performed by the magnetic-field detection unit (25), the control unit executes a determination process that determines the correlation between the operating frequency of the inverter circuit and the resonance characteristics of the primary-side resonance unit.

Description

非接触給電装置及びそれを用いた非接触給電システムNon-contact power feeding device and non-contact power feeding system using the same
　本発明は、一般に非接触給電装置、非接触給電システムに関し、より詳細には負荷に非接触で給電する非接触給電装置及びそれを用いた非接触給電システムに関する。 The present invention relates generally to a noncontact power feeding device and a noncontact power feeding system, and more particularly to a noncontact power feeding device for noncontact power feeding to a load and a noncontact power feeding system using the same.
　従来、携帯型機器や電気自動車などの機器に非接触で送電する技術が知られており、例えば文献１（日本国特許出願公開番号２０１４－９０６１７）に開示されている。文献１には、送電装置が有する送電ユニットと、車両が有する受電ユニットとを備え、車両の蓄電装置を非接触で充電する非接触送受電システムが開示されている。 Conventionally, a technology for contactlessly transmitting power to devices such as portable devices and electric vehicles is known, and is disclosed, for example, in Document 1 (Japanese Patent Application Publication No. 2014-90617). Document 1 discloses a non-contact power transmission and reception system that includes a power transmission unit of a power transmission device and a power reception unit of a vehicle, and charges the power storage device of the vehicle contactlessly.
　送電ユニットは、一次自己共振コイル（一次側コイル）を有し、電源部から高周波の交流電力の供給を受け、受電ユニットへ非接触で電力を伝送する。受電ユニットは、二次自己共振コイル（二次側コイル）を有し、送電ユニットから送出される電力を非接触で受電する。上記従来例では、一次側コイルと二次側コイルとを電磁界によって共振（共鳴）させることで、送電ユニットから受電ユニットへ非接触で電力を伝送させている。 The power transmission unit has a primary self-resonance coil (primary side coil), receives supply of high frequency AC power from the power supply unit, and transmits power to the power reception unit in a contactless manner. The power receiving unit has a secondary self-resonant coil (secondary side coil), and receives power transmitted from the power transmission unit in a contactless manner. In the above-described conventional example, power is transmitted contactlessly from the power transmission unit to the power reception unit by resonating the primary coil and the secondary coil with an electromagnetic field.
　上記従来例では、送電ユニットと受電ユニットとの間で効率よく電力の伝送が行われるように、目標駐車位置をユーザに提示し、目標駐車位置に車両を駐車するように促している。しかしながら、車両は必ずしも目標駐車位置に正確に駐車されるとは限らず、車両の駐車位置が目標駐車位置からずれてしまう可能性がある。 In the above conventional example, the target parking position is presented to the user so as to efficiently transmit power between the power transmission unit and the power receiving unit, and the user is urged to park the vehicle at the target parking position. However, the vehicle is not necessarily parked accurately at the target parking position, and there is a possibility that the parking position of the vehicle may deviate from the target parking position.
　この場合、一次側コイルと二次側コイルとの相対的な位置がずれることで、一次側コイルを含む共振回路及び二次側コイルを含む共振回路の共振特性が変化し、所望の動作を行うことができない虞がある。そして、上記従来例は、電源部から供給される交流電力の周波数（動作周波数）が、位置ずれによって変化した共振特性におけるどの周波数領域に位置するかを判定することができないという問題があった。 In this case, when the relative position between the primary coil and the secondary coil shifts, the resonance characteristics of the resonant circuit including the primary coil and the resonant circuit including the secondary coil are changed, and the desired operation is performed. There is a risk that you can not And the said prior art example had the problem that it could not be determined in which frequency area | region in the resonance characteristic which the frequency (operating frequency) of the alternating current power supplied from the power supply part changed with position shift.
　本発明は、上記の点に鑑みて為されており、動作周波数が共振特性におけるどの周波数領域に位置するかを判定することのできる非接触給電装置及びそれを用いた非接触給電システムを提供することを目的とする。 The present invention has been made in view of the above points, and provides a non-contact power feeding device capable of determining in which frequency region of resonance characteristics the operating frequency is located, and a non-contact power feeding system using the same. The purpose is
　本発明に係る一態様の非接触給電装置は、インバータ回路と、一次側共振部と、磁界検知部と、制御部とを備える。前記インバータ回路は、直流電力を交流電力に変換して出力する。前記一次側共振部は、前記インバータ回路の出力する交流電力を受けて磁束を発生するソレノイド型の一次側コイル、及び前記一次側コイルと共に一次側の共振回路を形成する一次側コンデンサで構成される。前記磁界検知部は、磁界を検知する。前記制御部は、前記磁界検知部の検知結果に基づいて、前記インバータ回路の動作周波数と前記一次側共振部の共振特性との相関を判定する判定処理を実行する。 The non-contact power feeding device according to one aspect of the present invention includes an inverter circuit, a primary side resonance unit, a magnetic field detection unit, and a control unit. The inverter circuit converts direct current power into alternating current power and outputs it. The primary side resonance unit is composed of a solenoid type primary side coil that receives an AC power output from the inverter circuit to generate a magnetic flux, and a primary side capacitor that forms a primary side resonance circuit with the primary side coil. . The magnetic field detection unit detects a magnetic field. The control unit executes a determination process of determining the correlation between the operating frequency of the inverter circuit and the resonance characteristic of the primary side resonance unit based on the detection result of the magnetic field detection unit.
　また、本発明に係る一態様の非接触給電システムは、上記の非接触給電装置と、前記非接触給電装置から供給される電力を受ける非接触受電装置とを備える。前記非接触受電装置は、前記一次側コイルが発生する磁束を受けて交流電力を発生する二次側コイル、及び前記二次側コイルと共に二次側の共振回路を形成する二次側コンデンサで構成される二次側共振部を備える。 Moreover, the non-contact electric power feeding system of the aspect which concerns on this invention is equipped with said non-contact electric power feeding apparatus and the non-contact power receiving apparatus which receives the electric power supplied from the said non-contact electric power feeding apparatus. The non-contact power reception device is configured of a secondary coil that generates an AC power by receiving a magnetic flux generated by the primary coil, and a secondary capacitor that forms a secondary resonance circuit with the secondary coil. And a secondary side resonance unit.
図１Ａは、実施形態に係る非接触給電装置における一次側コイルの配置を示す図である。図１Ｂ，図１Ｃは、それぞれ実施形態に係る非接触給電装置における磁界検知部の配置の一例を示す図である。FIG. 1A is a diagram showing the arrangement of primary coils in the non-contact power feeding device according to the embodiment. FIG. 1B and FIG. 1C are figures which show an example of arrangement | positioning of the magnetic field detection part in the non-contact electric power supply which concerns on embodiment, respectively. 実施形態に係る非接触給電装置及び非接触給電システムを示す回路概略図である。BRIEF DESCRIPTION OF THE DRAWINGS It is the circuit schematic which shows the non-contact electric power supply and the non-contact electric power supply system which concern on embodiment. 実施形態に係る非接触給電システムの使用例を示す概略図である。It is a schematic diagram showing an example of use of a non-contact electric supply system concerning an embodiment. 図４Ａは、通常時における共振特性を示す図である。図４Ｂは、一次側コイルと二次側コイルとの相対的な位置がずれた場合における共振特性を示す図である。FIG. 4A is a diagram showing resonance characteristics in a normal state. FIG. 4B is a diagram showing resonance characteristics when the relative position between the primary coil and the secondary coil is shifted. 図５Ａ，図５Ｂは、それぞれ一次側共振部及び二次側共振部の等価回路を示す図である。FIG. 5A and FIG. 5B are diagrams showing equivalent circuits of the primary side resonance part and the secondary side resonance part, respectively. 図６Ａ，図６Ｂは、それぞれ一次側コイル及び二次側コイルで発生する磁束分布を示す図である。6A and 6B are diagrams showing magnetic flux distributions generated by the primary coil and the secondary coil, respectively. 図７Ａ，図７Ｂは、それぞれ一次側コイル及び二次側コイルで発生する磁束分布のシミュレーションの結果を示す図である。FIGS. 7A and 7B are diagrams showing simulation results of the magnetic flux distribution generated in the primary coil and the secondary coil, respectively. 図８Ａは、実施形態に係る非接触給電装置において、磁界検知部の配置の他の一例を示す図である。図８Ｂは、実施形態に係る非接触給電装置において、複数の磁界検知部を配置した一例を示す図である。FIG. 8A is a view showing another example of the arrangement of the magnetic field detection unit in the non-contact power feeding device according to the embodiment. FIG. 8B is a diagram showing an example in which a plurality of magnetic field detection units are arranged in the non-contact power feeding device according to the embodiment. 図９Ａは、実施形態に係る非接触給電装置における一次側コンデンサの一例を示す回路図である。図９Ｂは、実施形態に係る非接触給電装置における一次側コイルの一例を示す回路図である。FIG. 9A is a circuit diagram showing an example of a primary side capacitor in the non-contact power feeding device according to the embodiment. FIG. 9B is a circuit diagram showing an example of a primary side coil in the non-contact power feeding device according to the embodiment. 図１０Ａは、実施形態に係る非接触給電装置の一次側共振部の他の構成を示す回路図である。図１０Ｂは、実施形態に係る非接触給電装置の一次側共振部の更に他の構成を示す回路図である。FIG. 10A is a circuit diagram showing another configuration of the primary-side resonant unit of the non-contact power feeding device according to the embodiment. FIG. 10B is a circuit diagram showing still another configuration of the primary-side resonant unit of the non-contact power feeding device according to the embodiment. 実施形態に係る非接触給電システムの他の構成を示す回路概略図である。It is the circuit schematic which shows the other structure of the non-contact electric power feeding system which concerns on embodiment.
　本発明の実施形態に係る非接触給電装置２は、以下の第１の特徴を有する。 The non-contact power feeding device 2 according to the embodiment of the present invention has the following first feature.
　第１の特徴では、非接触給電装置２は、図１Ａ～図１Ｃ、及び図２に示すように、インバータ回路２１２と、一次側共振部２３と、磁界検知部２５と、制御部２２とを備える。インバータ回路２１２は、直流電力を交流電力に変換して出力する。一次側共振部２３は、インバータ回路２１２の出力する交流電力を受けて磁束を発生するソレノイド型の一次側コイルＬ１、及び一次側コイルＬ１と共に一次側の共振回路を形成する一次側コンデンサＣ１で構成される。磁界検知部２５は、磁界を検知する。制御部２２は、磁界検知部２５の検知結果に基づいて、インバータ回路２１２の動作周波数ｆ１と一次側共振部２３の共振特性との相関を判定する判定処理を実行する。 In the first feature, as shown in FIGS. 1A to 1C and FIG. 2, the non-contact power feeding device 2 includes an inverter circuit 212, a primary side resonance unit 23, a magnetic field detection unit 25, and a control unit 22. Prepare. The inverter circuit 212 converts DC power into AC power and outputs it. The primary side resonance unit 23 is configured by a solenoid type primary side coil L1 that generates a magnetic flux by receiving AC power output from the inverter circuit 212, and a primary side capacitor C1 that forms a primary side resonance circuit with the primary side coil L1. Be done. The magnetic field detection unit 25 detects a magnetic field. The control unit 22 executes a determination process of determining the correlation between the operating frequency f1 of the inverter circuit 212 and the resonance characteristic of the primary side resonance unit 23 based on the detection result of the magnetic field detection unit 25.
　また、本実施形態の非接触給電装置２は、第１の特徴に加えて、以下の第２の特徴を有していてもよい。 Moreover, in addition to the first feature, the non-contact power feeding device 2 of the present embodiment may have the following second feature.
　第２の特徴では、一次側共振部２３の共振特性は２つの共振周波数を有する。かつ、この共振特性は、一次側共振部２３の出力が極小値を示す所定の周波数を境界にして、所定の周波数よりも低い周波数領域である低周波領域と、所定の周波数よりも高い周波数領域である高周波領域とを有する。そして、制御部２２は、判定処理において、磁界検知部２５で検知された磁界の強さと閾値との比較結果に応じて、動作周波数ｆ１が低周波領域及び高周波領域のいずれに位置するかを判定する。 In the second feature, the resonance characteristic of the primary side resonance unit 23 has two resonance frequencies. And, this resonance characteristic is a low frequency area which is a frequency area lower than a predetermined frequency and a frequency area higher than the predetermined frequency with a predetermined frequency at which the output of the primary side resonance unit 23 shows a local minimum as a boundary. And a high frequency region that is Then, in the determination process, the control unit 22 determines which one of the low frequency region and the high frequency region the operating frequency f1 is positioned in accordance with the comparison result between the strength of the magnetic field detected by the magnetic field detection unit 25 and the threshold value. Do.
　また、本実施形態の非接触給電装置２は、第１又は第２の特徴に加えて、以下の第３の特徴を有していてもよい。 In addition to the first or second feature, the non-contact power feeding device 2 of the present embodiment may have the following third feature.
　第３の特徴では、磁界検知部２５は、一次側コイルＬ１の中心軸方向の一端側に配置される。 In the third feature, the magnetic field detection unit 25 is disposed on one end side in the central axis direction of the primary coil L1.
　また、本実施形態の非接触給電装置２は、第１又は第２の特徴に加えて、以下の第４の特徴を有していてもよい。 Moreover, in addition to the first or second feature, the non-contact power feeding device 2 of the present embodiment may have the following fourth feature.
　第４の特徴では、磁界検知部２５は、一次側コイルＬ１の中央部の周囲に一次側コイルＬ１と所定の間隔を空けて配置される。 In the fourth feature, the magnetic field detection unit 25 is disposed around the central portion of the primary coil L1 at a predetermined distance from the primary coil L1.
　また、本実施形態の非接触給電装置２は、第１～第４のいずれかの特徴に加えて、以下の第５の特徴を有していてもよい。 Further, the non-contact power feeding device 2 of the present embodiment may have the following fifth feature in addition to any of the first to fourth features.
　第５の特徴では、非接触給電装置２は、磁界検知部２５を複数備える。そして、制御部２２は、判定処理において、複数の磁界検知部２５のうち少なくとも２つの検知結果を比較する。 In the fifth aspect, the non-contact power feeding device 2 includes a plurality of magnetic field detectors 25. Then, the control unit 22 compares at least two detection results of the plurality of magnetic field detection units 25 in the determination process.
　また、本実施形態の非接触給電装置２は、第１～第５のいずれかの特徴に加えて、以下の第６の特徴を有していてもよい。 Further, the non-contact power feeding device 2 of the present embodiment may have the following sixth feature in addition to any of the first to fifth features.
　第６の特徴では、制御部２２は、判定処理の判定結果に基づいて、インバータ回路２１２の動作周波数ｆ１を調整する調整処理を実行する。 In the sixth feature, the control unit 22 executes adjustment processing for adjusting the operating frequency f1 of the inverter circuit 212 based on the determination result of the determination processing.
　また、本実施形態の非接触給電装置２は、第１～第５のいずれかの特徴に加えて、以下の第７の特徴を有していてもよい。 Further, the non-contact power feeding device 2 of the present embodiment may have the following seventh feature in addition to any of the first to fifth features.
　第７の特徴では、制御部２２は、判定処理の判定結果に基づいて、一次側共振部２３の共振パラメータを調整する調整処理を実行する。 In the seventh feature, the control unit 22 executes adjustment processing of adjusting the resonance parameter of the primary side resonance unit 23 based on the determination result of the determination processing.
　また、本実施形態の非接触給電装置２は、第６又は第７の特徴に加えて、以下の第８の特徴を有していてもよい。 Moreover, in addition to the 6th or 7th characteristic, the non-contact electric power supply 2 of this embodiment may have the following 8th characteristic.
　第８の特徴では、制御部２２は、一次側共振部２３の共振特性が２つの共振周波数を有している場合、動作周波数ｆ１が２つの共振周波数のうち低い共振周波数に近づくように調整処理を実行する。 In the eighth feature, when the resonance characteristic of the primary side resonance unit 23 has two resonance frequencies, the control unit 22 performs adjustment processing so that the operating frequency f1 approaches a lower resonance frequency of the two resonance frequencies. Run.
　また、本実施形態の非接触給電装置２は、第６～第８のいずれかの特徴に加えて、以下の第９の特徴を有していてもよい。 The non-contact power feeding device 2 of the present embodiment may have the following ninth feature in addition to any of the sixth to eighth features.
　第９の特徴では、非接触給電装置２は、一次側コイルＬ１を流れる電流に相当する電流を検知する電流検知部２４を備える。そして、制御部２２は、電流検知部２４の検知結果に基づいて、インバータ回路２１２が遅相モードで動作するように調整処理を実行する。 In the ninth feature, the non-contact power feeding device 2 includes a current detection unit 24 that detects a current corresponding to the current flowing through the primary coil L1. Then, based on the detection result of the current detection unit 24, the control unit 22 executes adjustment processing so that the inverter circuit 212 operates in the lagging mode.
　また、本実施形態の非接触給電システム１は、以下の第１０の特徴を有していてもよい。 Further, the non-contact power feeding system 1 of the present embodiment may have the following tenth feature.
　第１０の特徴では、非接触給電システム１は、図２に示すように、非接触給電装置２と、非接触給電装置２から供給される電力を受ける非接触受電装置３とを備える。非接触受電装置３は、一次側コイルＬ１が発生する磁束を受けて交流電力を発生する二次側コイルＬ２、及び二次側コイルＬ２と共に二次側の共振回路を形成する二次側コンデンサＣ２で構成される二次側共振部３１を備える。 In the tenth feature, as shown in FIG. 2, the non-contact power feeding system 1 includes a non-contact power feeding device 2 and a non-contact power receiving device 3 receiving power supplied from the non-contact power feeding device 2. The non-contact power reception device 3 receives a magnetic flux generated by the primary coil L1 and generates an alternating current power, and a secondary side capacitor C2 which forms a secondary side resonant circuit with the secondary side coil L2. The secondary side resonance part 31 comprised by these is provided.
　また、本実施形態の非接触給電システム１は、第１０の特徴に加えて、以下の第１１の特徴を有していてもよい。 Moreover, in addition to the tenth feature, the non-contact power feeding system 1 of the present embodiment may have the following eleventh feature.
　第１１の特徴では、制御部２２（制御部３３）は、判定処理の判定結果に基づいて、一次側コイルＬ１及び二次側コイルＬ２の相対的な位置の変更を促す指示信号を出力する処理を実行する。 In an eleventh feature, the control unit 22 (control unit 33) outputs an instruction signal for prompting a change in the relative position of the primary side coil L1 and the secondary side coil L2, based on the determination result of the determination process. Run.
　本実施形態の非接触給電装置２及び非接触給電システム１は、動作周波数が共振特性におけるどの周波数領域に位置するかを判定することができる。 The non-contact power feeding device 2 and the non-contact power feeding system 1 of the present embodiment can determine in which frequency region in the resonance characteristic the operating frequency is located.
　以下、本実施形態の非接触給電装置２及び非接触給電システム１について詳細に説明する。但し、以下に説明する構成は、本発明の一例に過ぎず、本発明は下記の実施形態に限定されることはなく、この実施形態以外であっても、本発明に係る技術的思想を逸脱しない範囲であれば、設計等に応じて種々の変更が可能である。 Hereinafter, the non-contact power feeding device 2 and the non-contact power feeding system 1 of the present embodiment will be described in detail. However, the configuration described below is only an example of the present invention, and the present invention is not limited to the following embodiment, and even if it is other than this embodiment, it deviates from the technical idea according to the present invention. If it is not within the range, various changes can be made according to the design and the like.
　なお、以下では、図３に示すように、本実施形態の非接触給電装置２及び非接触給電システム１を用いて充電回路１０２に給電することで、電気自動車１００の蓄電池１０１を充電する場合について例示するが、この例に限定する趣旨ではない。すなわち、本実施形態の非接触給電装置２及び非接触給電システム１は、負荷４に非接触で給電する構成であればよく、負荷４は電気自動車１００の充電回路１０２に限定されない。 In the following, as shown in FIG. 3, the case where the storage battery 101 of the electric vehicle 100 is charged by supplying power to the charging circuit 102 using the non-contact power feeding device 2 and the non-contact power feeding system 1 of the present embodiment Although illustrated, it is not the meaning limited to this example. That is, the non-contact power feeding device 2 and the non-contact power feeding system 1 of the present embodiment may be configured to contact the load 4 in a non-contact manner, and the load 4 is not limited to the charging circuit 102 of the electric vehicle 100.
　本実施形態の非接触給電システム１は、図２に示すように、非接触給電装置２と、非接触受電装置３とを備えている。非接触給電装置２は、電源部２１と、制御部２２と、一次側共振部２３と、電流検知部２４と、磁界検知部２５とを備えている。一次側共振部２３は、一次側コンデンサＣ１と、一次側コイルＬ１とで構成されている。非接触受電装置３は、二次側共振部３１と、整流部３２とを備えている。二次側共振部３１は、二次側コンデンサＣ２と、二次側コイルＬ２とで構成されている。 As shown in FIG. 2, the non-contact power feeding system 1 of the present embodiment includes the non-contact power feeding device 2 and the non-contact power receiving device 3. The non-contact power feeding device 2 includes a power supply unit 21, a control unit 22, a primary side resonance unit 23, a current detection unit 24, and a magnetic field detection unit 25. The primary side resonance unit 23 is configured of a primary side capacitor C1 and a primary side coil L1. The non-contact power reception device 3 includes a secondary side resonance unit 31 and a rectification unit 32. The secondary side resonance part 31 is comprised by the secondary side capacitor | condenser C2 and the secondary side coil L2.
　本実施形態の非接触給電システム１において、非接触給電装置２は、図３に示すように、床や地面上に設置されている。なお、非接触給電装置２は、床や地面上のみならず、例えば床や地面に埋め込んで配置されていてもよい。また、非接触給電装置２は、一次側コイルＬ１のみを二次側コイルＬ２と対向可能な位置に配置し、その他の部品や回路等は一次側コイルＬ１から離れた場所に配置するように構成されていてもよい。 In the noncontact power feeding system 1 of the present embodiment, as shown in FIG. 3, the noncontact power feeding device 2 is installed on the floor or the ground. The non-contact power feeding device 2 may be embedded not only on the floor or the ground but also, for example, on the floor or the ground. Further, the non-contact power feeding device 2 is configured such that only the primary side coil L1 is disposed at a position where it can face the secondary side coil L2, and other components, circuits, etc. are disposed at a distance from the primary side coil L1. It may be done.
　本実施形態の非接触給電システム１において、非接触受電装置３は、図３に示すように、電気自動車１００の車両内に設置されている。非接触受電装置３は、充電回路１０２を介して蓄電池１０１に電気的に接続されている。蓄電池１０１は、例えばニッケル水素電池やリチウムイオン電池、高容量のコンデンサ等により構成される。蓄電池１０１は、電気自動車１００の備える電動機の電源として用いられる。その他、蓄電池１０１は、電気自動車１００が備えるカーナビゲーションシステムやカーオーディオ、パワーウィンドウなどの電子機器の電源として用いられる。充電回路１０２は、非接触給電装置２より供給される電力を適宜変換した電力により、蓄電池１０１を充電する回路である。 In the non-contact power feeding system 1 of the present embodiment, as shown in FIG. 3, the non-contact power receiving device 3 is installed in a vehicle of the electric vehicle 100. The non-contact power reception device 3 is electrically connected to the storage battery 101 via the charging circuit 102. The storage battery 101 is configured of, for example, a nickel hydrogen battery, a lithium ion battery, a high capacity capacitor, or the like. Storage battery 101 is used as a power source of a motor provided in electric vehicle 100. In addition, the storage battery 101 is used as a power supply of electronic devices such as a car navigation system, a car audio system, and a power window provided in the electric vehicle 100. The charging circuit 102 is a circuit that charges the storage battery 101 with the power obtained by appropriately converting the power supplied from the non-contact power feeding device 2.
　先ず、非接触給電装置２について説明する。 First, the non-contact power feeding device 2 will be described.
　電源部２１は、交流電源ＡＣ１から一次側共振部２３に所望の交流電力を供給する回路であり、図２に示すように、力率改善（ＰＦＣ：Power Factor Correction）回路２１１と、インバータ回路２１２とを備えている。力率改善回路２１１は、図２に示すように、４つのダイオードＤ１～Ｄ４で構成されるダイオードブリッジと、コイルＬ０と、スイッチング素子Ｑ０と、ダイオードＤ５と、コンデンサＣ０とで構成されている。スイッチング素子Ｑ０は、制御部２２から制御信号を与えられることでオン／オフを制御される。本実施形態の非接触給電装置２では、スイッチング素子Ｑ０は、ｎチャネルのエンハンスメント型ＭＯＳＦＥＴ（Metal-Oxide-Semiconductor Field-Effect Transistor）である。なお、スイッチング素子Ｑ０は、バイポーラトランジスタやＩＧＢＴ（Insulated Gate Bipolar Transistor：絶縁ゲートバイポーラトランジスタ）等の他の半導体スイッチング素子で構成されていてもよい。したがって、力率改善回路２１１は、制御部２２によりスイッチング素子Ｑ０のオン／オフが制御されることで、所望の高さの電圧を出力するように構成されている。 The power supply unit 21 is a circuit for supplying desired AC power from the AC power supply AC1 to the primary side resonance unit 23. As shown in FIG. 2, a power factor correction (PFC) circuit 211 and an inverter circuit 212 are provided. And have. As shown in FIG. 2, the power factor correction circuit 211 is composed of a diode bridge composed of four diodes D1 to D4, a coil L0, a switching element Q0, a diode D5, and a capacitor C0. The switching element Q0 is controlled to be turned on / off by receiving a control signal from the control unit 22. In the non-contact power feeding device 2 of the present embodiment, the switching element Q0 is an n-channel enhancement type MOSFET (Metal-Oxide-Semiconductor Field-Effect Transistor). The switching element Q0 may be configured of another semiconductor switching element such as a bipolar transistor or an IGBT (Insulated Gate Bipolar Transistor). Therefore, the power factor improvement circuit 211 is configured to output a voltage of a desired height by controlling the on / off of the switching element Q0 by the control unit 22.
　インバータ回路２１２は、図２に示すように、４つのスイッチング素子Ｑ１～Ｑ４で構成されるフルブリッジ・インバータである。本実施形態の非接触給電装置２では、スイッチング素子Ｑ１～Ｑ４は、それぞれｎチャネルのエンハンスメント型ＭＯＳＦＥＴである。なお、スイッチング素子Ｑ１～Ｑ４は、それぞれバイポーラトランジスタやＩＧＢＴ等の他の半導体スイッチング素子で構成されていてもよい。 The inverter circuit 212 is a full bridge inverter composed of four switching elements Q1 to Q4 as shown in FIG. In the non-contact power feeding device 2 of the present embodiment, the switching elements Q1 to Q4 are n-channel enhancement MOSFETs. Switching elements Q1 to Q4 may be formed of other semiconductor switching elements such as bipolar transistors and IGBTs, respectively.
　インバータ回路２１２では、２つのスイッチング素子Ｑ１，Ｑ２の直列回路と、２つのスイッチング素子Ｑ３，Ｑ４の直列回路とが並列に電気的に接続されている。スイッチング素子Ｑ１，Ｑ３のドレインは、それぞれ力率改善回路２１１の高電位側の出力点に電気的に接続されている。また、スイッチング素子Ｑ２，Ｑ４のソースは、それぞれ力率改善回路２１１の低電位側の出力点に電気的に接続されている。そして、スイッチング素子Ｑ３のソース及びスイッチング素子Ｑ４のドレインの接続点が、インバータ回路２１２の第１出力点となっている。また、スイッチング素子Ｑ１のソース及びスイッチング素子Ｑ２のドレインの接続点が、インバータ回路２１２の第２出力点となっている。 In the inverter circuit 212, a series circuit of two switching elements Q1 and Q2 and a series circuit of two switching elements Q3 and Q4 are electrically connected in parallel. The drains of the switching elements Q1 and Q3 are electrically connected to the high potential side output point of the power factor correction circuit 211, respectively. The sources of the switching elements Q2 and Q4 are electrically connected to the low potential side output point of the power factor correction circuit 211, respectively. The connection point of the source of the switching element Q3 and the drain of the switching element Q4 is a first output point of the inverter circuit 212. A connection point of the source of the switching element Q1 and the drain of the switching element Q2 is a second output point of the inverter circuit 212.
　スイッチング素子Ｑ１，Ｑ４は、制御部２２から第１駆動信号Ｇ１を与えられることにより、オン／オフを切り替えられる。また、スイッチング素子Ｑ２，Ｑ３は、第２駆動信号Ｇ２を与えられることにより、オン／オフを切り替えられる。第２駆動信号Ｇ２は、第１駆動信号Ｇ１とは位相が１８０度異なる矩形波状の信号である。 The switching elements Q1 and Q4 are switched on / off by receiving the first drive signal G1 from the control unit 22. The switching elements Q2 and Q3 can be switched on / off by being supplied with the second drive signal G2. The second drive signal G2 is a rectangular wave signal that is 180 degrees out of phase with the first drive signal G1.
　インバータ回路２１２は、第１駆動信号Ｇ１及び第２駆動信号Ｇ２により、スイッチング素子Ｑ１，Ｑ４のオン期間と、スイッチング素子Ｑ２，Ｑ３のオン期間とを交互に切り替えるように動作する。これにより、インバータ回路２１２は、力率改善回路２１１から供給される直流電力を交流電力に変換して出力する。以下では、図２に示すように、インバータ回路２１２が出力する電圧を「出力電圧Ｖ１」、インバータ回路２１２が出力する電流を「出力電流Ｉ１」と称する。 The inverter circuit 212 operates so as to alternately switch on periods of the switching elements Q1 and Q4 and on periods of the switching elements Q2 and Q3 according to the first drive signal G1 and the second drive signal G2. Thus, the inverter circuit 212 converts the DC power supplied from the power factor correction circuit 211 into AC power and outputs it. Hereinafter, as shown in FIG. 2, the voltage output from the inverter circuit 212 is referred to as “output voltage V1”, and the current output from the inverter circuit 212 is referred to as “output current I1”.
　制御部２２は、例えばマイコン（マイクロコンピュータ）で構成されている。制御部２２は、制御信号を力率改善回路２１１に与えることで、力率改善回路２１１の出力電圧を変化させる。また、制御部２２は、第１駆動信号Ｇ１及び第２駆動信号Ｇ２をスイッチング素子Ｑ１～Ｑ４に与えることで、インバータ回路２１２の動作を制御する。 The control unit 22 is configured of, for example, a microcomputer. The control unit 22 changes the output voltage of the power factor correction circuit 211 by giving a control signal to the power factor correction circuit 211. Further, the control unit 22 controls the operation of the inverter circuit 212 by providing the first drive signal G1 and the second drive signal G2 to the switching elements Q1 to Q4.
　一次側共振部２３は、図２に示すように、インバータ回路２１２の一対の出力点に、一次側コンデンサＣ１と一次側コイルＬ１とを直列に電気的に接続して構成されている。また、一次側コイルＬ１は、一次側コンデンサＣ１と共に共振回路（一次側の共振回路）を形成している。 As shown in FIG. 2, the primary side resonance unit 23 is configured by electrically connecting a primary side capacitor C1 and a primary side coil L1 in series at a pair of output points of the inverter circuit 212. Further, the primary side coil L1 forms a resonant circuit (a primary side resonant circuit) together with the primary side capacitor C1.
　一次側コイルＬ１は、図１Ａに示すように、コア２３１に導線を巻き回して螺旋状に構成されるソレノイド型のコイルである。コア２３１は、例えばフェライトなどの磁性材料により板状に形成されている。一次側コイルＬ１は、インバータ回路２１２が出力する交流電流が流れると、磁束を発生する。つまり、一次側コイルＬ１は、インバータ回路２１２が出力する交流電力を受けて磁束を発生する。 As shown in FIG. 1A, the primary side coil L1 is a solenoid type coil configured by winding a wire around the core 231 to form a spiral. The core 231 is formed in a plate shape, for example, by a magnetic material such as ferrite. The primary coil L1 generates a magnetic flux when the alternating current output from the inverter circuit 212 flows. That is, the primary coil L1 receives the AC power output from the inverter circuit 212 and generates a magnetic flux.
　電流検知部２４は、例えばシャント抵抗やホール素子などで構成されている。電流検知部２４は、図２に示すように、インバータ回路２１２から一次側コイルＬ１へと流れる出力電流Ｉ１を検知する。言い換えれば、電流検知部２４は、一次側コイルＬ１を流れる電流に相当する電流を検知する。この電流検知部２４の検知結果（出力電流Ｉ１の瞬時電流）は、後述する調整処理を制御部２２が実行する際に用いられる。 The current detection unit 24 is configured of, for example, a shunt resistor or a Hall element. As shown in FIG. 2, the current detection unit 24 detects an output current I1 flowing from the inverter circuit 212 to the primary coil L1. In other words, the current detection unit 24 detects a current corresponding to the current flowing through the primary coil L1. The detection result (the instantaneous current of the output current I1) of the current detection unit 24 is used when the control unit 22 executes an adjustment process described later.
　磁界検知部２５は、例えばホール素子やサーチコイルなどで構成される。磁界検知部２５は、図１Ｂに示すように、一次側コイルＬ１と二次側コイルＬ２とを含む空間に作用する磁界を検知する。この磁界検知部２５の検知結果（例えば、磁界の強さ）は、後述する判定処理を制御部２２が実行する際に用いられる。なお、磁界検知部２５がホール素子で構成されている場合、磁界検知部２５は、一次側コイルＬ１で発生する磁束がホール素子の検知面に交差するように配置されるのが好ましい。また、磁界検知部２５がサーチコイルで構成されている場合、磁界検知部２５は、一次側コイルＬ１で発生する磁束がサーチコイルに交差するように配置されるのが好ましい。 The magnetic field detection unit 25 includes, for example, a Hall element or a search coil. The magnetic field detection unit 25 detects a magnetic field acting on a space including the primary coil L1 and the secondary coil L2, as shown in FIG. 1B. The detection result (for example, the strength of the magnetic field) of the magnetic field detection unit 25 is used when the control unit 22 executes a determination process described later. In addition, when the magnetic field detection part 25 is comprised by the Hall element, it is preferable that the magnetic field detection part 25 is arrange | positioned so that the magnetic flux which generate | occur | produces with the primary side coil L1 may cross | intersect the detection surface of Hall element. When the magnetic field detection unit 25 is configured by a search coil, it is preferable that the magnetic field detection unit 25 be disposed so that the magnetic flux generated by the primary coil L1 intersects the search coil.
　本実施形態の非接触給電装置２では、磁界検知部２５は、図１Ｂ，図１Ｃに示すように、コア２３１の長手方向（図１Ｃにおける左右方向）の一端（右端）に配置される。つまり、磁界検知部２５は、一次側コイルＬ１の中心軸方向における一端（右端）側に配置される。また、磁界検知部２５は、コア２３１の厚さ方向（図１Ｂにおける上下方向）において、例えばスペーサ等を用いて、コア２３１と所定の間隔を空けて配置される。なお、磁界検知部２５は、コア２３１の長手方向の他端（左端）、つまり、一次側コイルＬ１の中心軸方向における他端（左端）側に配置されていてもよい。 In the non-contact power feeding device 2 of the present embodiment, the magnetic field detection unit 25 is disposed at one end (right end) in the longitudinal direction (left and right direction in FIG. 1C) of the core 231 as shown in FIGS. That is, the magnetic field detection unit 25 is disposed on one end (right end) side in the central axis direction of the primary coil L1. In addition, the magnetic field detection unit 25 is disposed at a predetermined distance from the core 231 in the thickness direction of the core 231 (vertical direction in FIG. 1B) using, for example, a spacer. The magnetic field detection unit 25 may be disposed on the other end (left end) of the core 231 in the longitudinal direction, that is, on the other end (left end) side in the central axis direction of the primary coil L1.
　次に、非接触受電装置３について説明する。 Next, the non-contact power reception device 3 will be described.
　二次側共振部３１は、図２に示すように、整流部３２の一対の入力点に、二次側コンデンサＣ２と二次側コイルＬ２とを直列に電気的に接続して構成されている。また、二次側コイルＬ２は、二次側コンデンサＣ２と共に共振回路（二次側の共振回路）を形成している。 As shown in FIG. 2, the secondary side resonance unit 31 is configured by electrically connecting a secondary side capacitor C2 and a secondary side coil L2 in series at a pair of input points of the rectification unit 32. . Further, the secondary side coil L2 forms a resonant circuit (secondary side resonant circuit) together with the secondary side capacitor C2.
　二次側コイルＬ２は、図１Ａに示すように、コア３１１に導線を巻き回して螺旋状に構成されるソレノイド型のコイルである。コア３１１は、例えばフェライトなどの磁性材料により板状に形成されている。二次側コイルＬ２は、図３に示すように、電気自動車１００が規定の停車位置に停車すると、一次側コイルＬ１の近傍に位置するように設けられる。言い換えれば、二次側コイルＬ２は、電気自動車１００が規定の停車位置に停車すると、一次側コイルＬ１と所定の間隔を空けて対向するように設けられる。二次側コイルＬ２は、一次側コイルＬ１が発生する磁束を受けると、電磁誘導により交流電流が流れる。つまり、二次側コイルＬ２は、一次側コイルＬ１が発生する磁束を受けて交流電力を発生する。 As shown in FIG. 1A, the secondary coil L2 is a solenoid type coil formed by winding a conductive wire around the core 311. The core 311 is formed in a plate shape, for example, by a magnetic material such as ferrite. As shown in FIG. 3, the secondary coil L2 is provided so as to be located in the vicinity of the primary coil L1 when the electric vehicle 100 stops at a prescribed stopping position. In other words, the secondary coil L2 is provided to face the primary coil L1 at a predetermined interval when the electric vehicle 100 stops at a prescribed stopping position. When the secondary coil L2 receives the magnetic flux generated by the primary coil L1, an alternating current flows by electromagnetic induction. That is, the secondary coil L2 receives the magnetic flux generated by the primary coil L1 and generates AC power.
　整流部３２は、図２に示すように、４つのダイオードで構成されるダイオードブリッジ３２１と、コンデンサＣ３とで構成されている。ダイオードブリッジ３２１は、二次側コイルＬ２で発生した交流電流を脈流電流に変換して出力する。コンデンサＣ３は、ダイオードブリッジ３２１の一対の出力点に電気的に接続されており、ダイオードブリッジ３２１から出力される脈流電流を平滑化し、直流電流を出力する。つまり、整流部３２は、二次側コイルＬ２で発生した交流電力を直流電力に整流して直流電力を出力する。整流部３２が出力する直流電力は、負荷４（ここでは、充電回路１０２）に供給される。 As shown in FIG. 2, the rectifying unit 32 is configured of a diode bridge 321 configured of four diodes and a capacitor C3. The diode bridge 321 converts the alternating current generated in the secondary coil L2 into a pulsating current and outputs it. The capacitor C3 is electrically connected to a pair of output points of the diode bridge 321, smoothes the pulsating current output from the diode bridge 321, and outputs a direct current. That is, the rectifying unit 32 rectifies AC power generated by the secondary coil L2 into DC power and outputs DC power. The DC power output from the rectifying unit 32 is supplied to the load 4 (here, the charging circuit 102).
　本実施形態の非接触給電システム１では、磁気共鳴現象を利用した共鳴方式により、一次側共振部２３から二次側共振部３１に電力を伝送している。そして、本実施形態の非接触給電システム１では、一次側共振部２３と二次側共振部３１との磁気共鳴を利用して、非接触給電装置２の出力電力を効率良く非接触受電装置３に伝送している。したがって、一次側共振部２３の周波数特性と、二次側共振部３１の周波数特性とが互いに一致するのが好ましい。 In the non-contact power feeding system 1 of the present embodiment, power is transmitted from the primary side resonance unit 23 to the secondary side resonance unit 31 by a resonance method using a magnetic resonance phenomenon. Then, in the non-contact power feeding system 1 of the present embodiment, the non-contact power receiving device 3 efficiently outputs the output power of the non-contact power feeding device 2 by utilizing the magnetic resonance between the primary side resonance unit 23 and the secondary side resonance unit 31. It is transmitted to Therefore, it is preferable that the frequency characteristic of the primary side resonance unit 23 and the frequency characteristic of the secondary side resonance unit 31 match each other.
　以下、本実施形態の非接触給電システム１における一次側共振部２３の周波数特性（以下、「共振特性」と称する）について説明する。本実施形態の非接触給電システム１では、共振特性は、一次側コイルＬ１と二次側コイルＬ２との磁気的な結合の疎密に応じて変化する。言い換えれば、共振特性は、一次側コイルＬ１と二次側コイルＬ２との結合係数の大小に応じて変化する。そして、結合係数がある程度大きい場合、共振特性は、図４Ａに示すように一次側共振部２３の出力の極大値が２箇所現れる、いわゆる双峰特性を示す。この共振特性では、第１周波数ｆｒ１で一次側共振部２３の出力が極大値となる山と、第２周波数ｆｒ２（ｆｒ２＞ｆｒ１）で一次側共振部２３の出力が極小値となる谷とが現れている。また、この共振特性では、第３周波数ｆｒ３（ｆｒ３＞ｆｒ２）で一次側共振部２３の出力が極大値となる山が現れている。つまり、この共振特性（双峰特性）は、２つの共振周波数（第１周波数ｆｒ１、第３周波数ｆｒ３）を有している。 Hereinafter, the frequency characteristic (hereinafter, referred to as “resonance characteristic”) of the primary side resonance unit 23 in the non-contact power feeding system 1 of the present embodiment will be described. In the non-contact power feeding system 1 of the present embodiment, the resonance characteristics change according to the density of the magnetic coupling between the primary coil L1 and the secondary coil L2. In other words, the resonance characteristic changes in accordance with the magnitude of the coupling coefficient between the primary coil L1 and the secondary coil L2. When the coupling coefficient is large to some extent, the resonance characteristic exhibits so-called bimodal characteristics in which two local maximum values of the output of the primary side resonance unit 23 appear as shown in FIG. 4A. In this resonance characteristic, there are a peak at which the output of the primary side resonance unit 23 becomes the maximum value at the first frequency fr1, and a valley at which the output of the primary side resonance unit 23 becomes the minimum value at the second frequency fr2 (fr2> fr1). It has appeared. Further, in this resonance characteristic, a peak at which the output of the primary side resonance unit 23 is a maximum value appears at the third frequency fr3 (fr3> fr2). That is, this resonance characteristic (bimodal characteristic) has two resonance frequencies (first frequency fr1 and third frequency fr3).
　ここで、インバータ回路２１２の動作周波数ｆ１（例えば、８５±５ｋＨｚ）と各周波数ｆｒ１～ｆｒ３との相関に応じて、インバータ回路２１２は遅相モード又は進相モードの何れかのモードで動作する。なお、「動作周波数ｆ１」は、第１駆動信号Ｇ１及び第２駆動信号Ｇ２の周波数、言い換えれば、インバータ回路２１２の出力電圧Ｖ１の周波数である。 Here, in accordance with the correlation between the operating frequency f1 (for example, 85 ± 5 kHz) of the inverter circuit 212 and the frequencies fr1 to fr3, the inverter circuit 212 operates in either the lagging mode or the phase advancing mode. The “operating frequency f1” is the frequency of the first drive signal G1 and the second drive signal G2, in other words, the frequency of the output voltage V1 of the inverter circuit 212.
　進相モードは、インバータ回路２１２の出力電流Ｉ１の位相が、インバータ回路２１２の出力電圧Ｖ１の位相よりも進んだ状態でインバータ回路２１２が動作するモードである。進相モードでは、インバータ回路２１２のスイッチング動作がいわゆるハードスイッチングになる。遅相モードは、インバータ回路２１２の出力電流Ｉ１が、インバータ回路２１２の出力電圧Ｖ１の位相よりも遅れた状態でインバータ回路２１２が動作するモードである。遅相モードでは、インバータ回路２１２のスイッチング動作がいわゆるソフトスイッチングになる。 The phase advance mode is a mode in which the inverter circuit 212 operates with the phase of the output current I1 of the inverter circuit 212 leading the phase of the output voltage V1 of the inverter circuit 212. In the phase advance mode, the switching operation of the inverter circuit 212 is so-called hard switching. The lagging mode is a mode in which the inverter circuit 212 operates in a state in which the output current I1 of the inverter circuit 212 is delayed from the phase of the output voltage V1 of the inverter circuit 212. In the lagging mode, the switching operation of the inverter circuit 212 is so-called soft switching.
　遅相モードでは、スイッチング素子Ｑ１～Ｑ４のスイッチングによる損失を低減することができ、また、スイッチング素子Ｑ１～Ｑ４に過大な電気的ストレスがかかるのを防止することができる。したがって、本実施形態の非接触給電装置２では、インバータ回路２１２は、遅相モードで動作するのが好ましい。インバータ回路２１２は、図４Ａに示すように、動作周波数ｆ１が第１周波数ｆｒ１と第２周波数ｆｒ２との間の周波数領域に位置する場合と、動作周波数ｆ１が第３周波数ｆｒ３よりも大きい周波数領域に位置する場合との何れかで、遅相モードで動作する。 In the slow phase mode, it is possible to reduce the loss due to the switching of the switching elements Q1 to Q4 and to prevent the switching elements Q1 to Q4 from being subjected to excessive electrical stress. Therefore, in the non-contact power feeding device 2 of the present embodiment, the inverter circuit 212 preferably operates in the lagging mode. In the inverter circuit 212, as shown in FIG. 4A, the operating frequency f1 is located in the frequency range between the first frequency fr1 and the second frequency fr2, and the operating frequency f1 is larger than the third frequency fr3. Operates in lagging mode, either in
　また、動作周波数ｆ１は、高周波領域よりも低周波領域に位置するのが好ましい。「低周波領域」は、共振特性において、一次側共振部２３の出力が極小値を示す第２周波数ｆｒ２（所定の周波数）よりも低い周波数領域である。「高周波領域」は、共振特性において、一次側共振部２３の出力が極小値を示す第２周波数ｆｒ２（所定の周波数）よりも高い周波数領域である。動作周波数ｆ１が低周波領域に位置する場合、一次側コイルＬ１を流れる電流の位相と、二次側コイルＬ２を流れる電流の位相とが互いに１８０度近くずれることで、不要輻射を低減することができる。 In addition, it is preferable that the operating frequency f1 be located in the low frequency range rather than the high frequency range. The “low frequency region” is a frequency region lower than the second frequency fr2 (predetermined frequency) at which the output of the primary side resonance unit 23 exhibits a local minimum value in the resonance characteristics. The “high frequency region” is a frequency region higher than the second frequency fr2 (predetermined frequency) at which the output of the primary side resonance unit 23 exhibits a local minimum value in the resonance characteristics. When the operating frequency f1 is located in the low frequency region, unnecessary radiation can be reduced by shifting the phase of the current flowing through the primary coil L1 and the phase of the current flowing through the secondary coil L2 by about 180 degrees. it can.
　ところで、本実施形態の非接触給電装置２では、一次側コイルＬ１と二次側コイルＬ２との相対的な位置がずれる場合がある。例えば、電気自動車１００の停車位置が予め規定されている停車位置からずれると、一次側コイルＬ１と二次側コイルＬ２との相対的な位置がずれる。この場合、一次側コイルＬ１と二次側コイルＬ２との磁気的な結合が変化（つまり、結合係数が変化）する。すると、各周波数ｆｒ１～ｆｒ３が変化することで、共振特性は、例えば図４Ａに示す特性から図４Ｂに示す特性に変化する。 By the way, in the non-contact electric power supply 2 of this embodiment, the relative position of the primary side coil L1 and the secondary side coil L2 may shift | deviate. For example, when the stopping position of the electric vehicle 100 deviates from a predetermined stopping position, the relative position between the primary coil L1 and the secondary coil L2 deviates. In this case, the magnetic coupling between the primary coil L1 and the secondary coil L2 changes (that is, the coupling coefficient changes). Then, the resonance characteristics change, for example, from the characteristics shown in FIG. 4A to the characteristics shown in FIG. 4B by changing the frequencies fr1 to fr3.
　ここで、動作周波数ｆ１が一定の周波数であると仮定する。この場合、図４Ａに示す共振特性では、動作周波数ｆ１が低周波領域に位置しているのに対して、図４Ｂに示す共振特性では、動作周波数ｆ１が高周波領域に位置する。したがって、図４Ｂに示す共振特性では、一次側コイルＬ１を流れる電流の位相と、二次側コイルＬ２を流れる電流の位相とが揃ってしまい、不要輻射を低減することができない。 Here, it is assumed that the operating frequency f1 is a constant frequency. In this case, in the resonance characteristic shown in FIG. 4A, the operating frequency f1 is located in the low frequency region, whereas in the resonance characteristic shown in FIG. 4B, the operating frequency f1 is located in the high frequency region. Therefore, in the resonance characteristic shown in FIG. 4B, the phase of the current flowing through the primary coil L1 and the phase of the current flowing through the secondary coil L2 are aligned, and the unnecessary radiation can not be reduced.
　そして、従来の非接触送受電システムでは、一次側コイルと二次側コイルとの相対的な位置ずれによって共振特性が変化すると、動作周波数が変化後の共振特性におけるどの周波数領域に位置するかを判定することができない。したがって、従来の非接触給電システムでは、動作周波数が高周波領域に位置しているにも関わらず、電気自動車の充電を開始してしまうという問題があった。 Then, in the conventional noncontact power transmission and reception system, when the resonance characteristic changes due to the relative positional deviation between the primary coil and the secondary coil, it is determined in which frequency region in the resonance characteristic after the change the operating frequency is located It can not be determined. Therefore, in the conventional non-contact power feeding system, there has been a problem that charging of the electric vehicle is started although the operating frequency is located in the high frequency region.
　そこで、本願の発明者等は、動作周波数ｆ１が低周波領域に位置する場合と、動作周波数ｆ１が高周波領域に位置する場合とで、一次側コイルＬ１及び二次側コイルＬ２を含む空間に作用する磁場（磁界）が変化することに着目した。 Therefore, the inventors of the present application operate in the space including the primary coil L1 and the secondary coil L2 when the operating frequency f1 is located in the low frequency region and when the operating frequency f1 is located in the high frequency region. Focused on the change of the magnetic field (magnetic field).
　図５Ａに、動作周波数ｆ１が低周波領域に位置する場合の一次側共振部２３及び二次側共振部３１の等価回路を示す。図５Ａに示すように、動作周波数ｆ１が低周波領域に位置する場合、相互インダクタＭ１と、２つの直列共振回路（一次側共振部２３と二次側共振部３１）との並列回路が共振する。この場合、図５Ａにおける矢印が示すように、相互インダクタＭ１に電流が流れ、一次側コイルＬ１を流れる電流の向きと、二次側コイルＬ２を流れる電流の向きとが互いに逆になる。 FIG. 5A shows an equivalent circuit of the primary side resonance unit 23 and the secondary side resonance unit 31 when the operating frequency f1 is located in the low frequency region. As shown to FIG. 5A, when the operating frequency f1 is located in a low frequency area | region, the parallel circuit of mutual inductor M1 and two series resonance circuits (the primary side resonance part 23 and the secondary side resonance part 31) resonates . In this case, as shown by the arrow in FIG. 5A, a current flows through the mutual inductor M1, and the direction of the current flowing through the primary coil L1 and the direction of the current flowing through the secondary coil L2 become opposite to each other.
　図５Ｂに、動作周波数ｆ１が高周波領域に位置する場合の一次側共振部２３及び二次側共振部３１の等価回路を示す。図５Ｂに示すように、動作周波数ｆ１が高周波領域に位置する場合、一次側コイルＬ１及び二次側コイルＬ２と、一次側コンデンサＣ１及び二次側コンデンサＣ２とが共振する。この場合、図５Ｂにおける矢印が示すように、相互インダクタＭ１には電流が流れず、一次側コイルＬ１を流れる電流の向きと、二次側コイルＬ２を流れる電流の向きとが同じになる。 FIG. 5B shows an equivalent circuit of the primary side resonance unit 23 and the secondary side resonance unit 31 when the operating frequency f1 is located in the high frequency region. As shown in FIG. 5B, when the operating frequency f1 is located in the high frequency region, the primary side coil L1 and the secondary side coil L2 resonate with the primary side capacitor C1 and the secondary side capacitor C2. In this case, as indicated by the arrow in FIG. 5B, no current flows through the mutual inductor M1, and the direction of the current flowing through the primary coil L1 and the direction of the current flowing through the secondary coil L2 become the same.
　図６Ａに、動作周波数ｆ１が低周波領域に位置する場合の一次側コイルＬ１及び二次側コイルＬ２で発生する磁束の分布を示す。この場合、一次側コイルＬ１で発生してコア２３１を通過する磁束Ｂ１の向きと、二次側コイルＬ２で発生してコア３１１を通過する磁束Ｂ２の向きとが互いに逆になる。このため、一次側コイルＬ１と二次側コイルＬ２との間の空間では、一次側コイルＬ１が発生する磁束Ｂ１と、二次側コイルＬ２が発生する磁束Ｂ２とが互いに打ち消し合う（図６Ａにおける破線の矢印を参照）。 FIG. 6A shows the distribution of magnetic flux generated by the primary coil L1 and the secondary coil L2 when the operating frequency f1 is located in the low frequency region. In this case, the direction of the magnetic flux B1 generated in the primary side coil L1 and passing through the core 231 and the direction of the magnetic flux B2 generated in the secondary side coil L2 and passing through the core 311 become opposite to each other. Thus, in the space between the primary coil L1 and the secondary coil L2, the magnetic flux B1 generated by the primary coil L1 and the magnetic flux B2 generated by the secondary coil L2 cancel each other (FIG. 6A). See dashed arrow).
　図６Ｂに、動作周波数ｆ１が高周波領域に位置する場合の一次側コイルＬ１及び二次側コイルＬ２で発生する磁束の分布を示す。この場合、一次側コイルＬ１で発生してコア２３１を通過する磁束Ｂ１の向きと、二次側コイルＬ２で発生してコア３１１を通過する磁束Ｂ２の向きとが同じになる。したがって、一次側コイルＬ１と二次側コイルＬ２との間の空間では、一次側コイルＬ１が発生する磁束Ｂ１と、二次側コイルＬ２が発生する磁束Ｂ２とが互いに強め合う（図６Ｂにおける破線の矢印を参照）。 FIG. 6B shows the distribution of magnetic flux generated by the primary coil L1 and the secondary coil L2 when the operating frequency f1 is located in the high frequency region. In this case, the direction of the magnetic flux B1 generated by the primary coil L1 and passing through the core 231 is the same as the direction of the magnetic flux B2 generated by the secondary coil L2 and passing through the core 311. Therefore, in the space between primary coil L1 and secondary coil L2, magnetic flux B1 generated by primary coil L1 and magnetic flux B2 generated by secondary coil L2 mutually strengthen each other (broken line in FIG. 6B See arrow)).
　つまり、一次側コイルＬ１と二次側コイルＬ２との間の空間では、第１方向の磁界は、動作周波数ｆ１が低周波領域に位置すると弱くなり、動作周波数ｆ１が高周波領域に位置すると強くなる。なお、「第１方向」は、筒状に巻き回された一次側コイルＬ１（二次側コイルＬ２）の軸方向（図６Ａにおける左右方向）である。 That is, in the space between the primary side coil L1 and the secondary side coil L2, the magnetic field in the first direction becomes weak when the operating frequency f1 is located in the low frequency region and becomes strong when the operating frequency f1 is located in the high frequency region . The “first direction” is the axial direction (horizontal direction in FIG. 6A) of the primary coil L1 (secondary coil L2) wound in a cylindrical shape.
　次に、一次側コイルＬ１及び二次側コイルＬ２の中心軸方向における一端側（図６Ａにおける右端側又は左端側）での磁束分布を、シミュレーションにより求めた結果を図７Ａ，図７Ｂに示す。なお、図７Ａ，図７Ｂに示す矢印は、それぞれ磁束の向きを表している。動作周波数ｆ１が低周波領域に位置する場合、図７Ａに示すように、一次側コイルＬ１の中心軸方向における一端（図７Ａにおける右端）から、二次側コイルＬ２の中心軸方向における一端（図７Ａにおける右端）に向かう向きの磁束が強くなる。一方、動作周波数ｆ１が高周波領域に位置する場合、図７Ｂに示すように、一次側コイルＬ１の中心軸方向における一端（図７Ｂにおける右端）から、二次側コイルＬ２の中心軸方向における一端（図７Ｂにおける右端）に向かう向きの磁束が弱くなる。 Next, the magnetic flux distribution on one end side (right end side or left end side in FIG. 6A) in the central axis direction of the primary side coil L1 and the secondary side coil L2 is obtained by simulation, and the results are shown in FIGS. 7A and 7B. Arrows shown in FIGS. 7A and 7B indicate the directions of the magnetic flux. When the operating frequency f1 is located in the low frequency region, as shown in FIG. 7A, one end in the central axis direction of the primary coil L1 (right end in FIG. 7A) to one end in the central axis direction of the secondary coil L2 (figure The magnetic flux in the direction toward the right end in 7A becomes strong. On the other hand, when the operating frequency f1 is located in the high frequency region, as shown in FIG. 7B, one end (right end in FIG. 7B) in the central axis direction of the primary coil L1 to one end in the central axis direction of the secondary coil L2. The magnetic flux in the direction toward the right end in FIG. 7B becomes weak.
　つまり、一次側コイルＬ１及び二次側コイルＬ２の中心軸方向における一端側の空間では、第２方向の磁界は、動作周波数ｆ１が低周波領域に位置すると強くなり、動作周波数ｆ１が高周波領域に位置すると弱くなる。なお、「第２方向」は、コア２３１（コア３１１）の一面（図７Ａにおける上面又は下面）に垂直な方向（図７Ａにおける上下方向）である。 That is, in the space at one end side in the central axis direction of the primary side coil L1 and the secondary side coil L2, the magnetic field in the second direction becomes stronger when the operating frequency f1 is located in the low frequency region, and the operating frequency f1 is in the high frequency region It becomes weak when it is located. The “second direction” is a direction (vertical direction in FIG. 7A) perpendicular to one surface (upper surface or lower surface in FIG. 7A) of the core 231 (core 311).
　本実施形態の非接触給電装置２では、既に述べたように、磁界検知部２５は、一次側コイルＬ１の中心軸方向における一端（右端）側に配置されている（図１Ｂ，図１Ｃ参照）。このため、磁界検知部２５で検知される磁界は、動作周波数ｆ１が低周波領域に位置する場合に強くなり、動作周波数ｆ１が高周波領域に位置する場合に弱くなる。そして、制御部２２は、磁界検知部２５の検知結果に基づいて、インバータ回路２１２の動作周波数ｆ１と一次側共振部２３の共振特性との相関を判定する判定処理を実行する。具体的には、制御部２２は、判定処理において、磁界検知部２５で検知された磁界の強さと、予め設定された閾値とを比較する。そして、判定処理において、磁界検知部２５で検知された磁界の強さが閾値を上回れば、制御部２２は、動作周波数ｆ１が低周波領域に位置すると判定する。また、判定処理において、磁界検知部２５で検知された磁界の強さが閾値を下回れば、制御部２２は、動作周波数ｆ１が高周波領域に位置すると判定する。なお、磁界検知部２５で検知された磁界の強さが閾値と等しい場合に、動作周波数ｆ１が低周波領域及び高周波領域のいずれに位置するかは、適宜設定されてよい。 In the non-contact power feeding device 2 of the present embodiment, as described above, the magnetic field detection unit 25 is disposed on one end (right end) side in the central axis direction of the primary coil L1 (see FIGS. 1B and 1C) . Therefore, the magnetic field detected by the magnetic field detection unit 25 becomes stronger when the operating frequency f1 is located in the low frequency region, and becomes weaker when the operating frequency f1 is located in the high frequency region. Then, based on the detection result of the magnetic field detection unit 25, the control unit 22 executes a determination process of determining the correlation between the operating frequency f1 of the inverter circuit 212 and the resonance characteristic of the primary side resonance unit 23. Specifically, in the determination process, the control unit 22 compares the strength of the magnetic field detected by the magnetic field detection unit 25 with a preset threshold. Then, in the determination processing, when the strength of the magnetic field detected by the magnetic field detection unit 25 exceeds the threshold, the control unit 22 determines that the operating frequency f1 is located in the low frequency region. In the determination process, if the strength of the magnetic field detected by the magnetic field detection unit 25 falls below the threshold, the control unit 22 determines that the operating frequency f1 is located in the high frequency region. When the strength of the magnetic field detected by the magnetic field detection unit 25 is equal to the threshold value, which of the low frequency region and the high frequency region the operating frequency f1 is positioned may be set appropriately.
　上述のように、本実施形態の非接触給電装置２は、磁界を検知する磁界検知部２５を備えている。そして、本実施形態の非接触給電装置２では、制御部２２は、磁界検知部２５の検知結果に基づいて、インバータ回路２１２の動作周波数ｆ１と一次側共振部２３の共振特性との相関を判定する判定処理を実行する。したがって、本実施形態の非接触給電装置２は、制御部２２の実行する判定処理により、動作周波数ｆ１が共振特性におけるどの周波数領域に位置するかを判定することができる。このため、仮に一次側コイルＬ１と二次側コイルＬ２との相対的な位置がずれ、共振特性が変化したとしても、本実施形態の非接触給電装置２は、変化した共振特性におけるどの周波数領域に動作周波数ｆ１が位置するかを判定することができる。 As described above, the non-contact power feeding device 2 of the present embodiment includes the magnetic field detection unit 25 that detects a magnetic field. Then, in the non-contact power feeding device 2 of the present embodiment, the control unit 22 determines the correlation between the operating frequency f1 of the inverter circuit 212 and the resonance characteristic of the primary side resonance unit 23 based on the detection result of the magnetic field detection unit 25. Execute judgment processing. Therefore, the non-contact power feeding device 2 of the present embodiment can determine in which frequency region in the resonance characteristic the operating frequency f1 is located by the determination processing performed by the control unit 22. For this reason, even if the relative position between the primary side coil L1 and the secondary side coil L2 shifts and the resonance characteristic changes, the non-contact power feeding device 2 of the present embodiment determines which frequency region in the changed resonance characteristic Can determine whether the operating frequency f1 is located.
　また、本実施形態の非接触給電装置２では、磁界検知部２５は、一次側コイルＬ１の中心軸方向における一端側に配置されている。このため、動作周波数ｆ１が低周波領域に位置する場合と高周波領域に位置する場合とで、磁界検知部２５に鎖交（交差）する磁束が大きく変化するため、磁界の強さの変化を検知し易いという利点がある。 Further, in the non-contact power feeding device 2 of the present embodiment, the magnetic field detection unit 25 is disposed on one end side in the central axis direction of the primary coil L1. For this reason, since the magnetic flux linked (crossed) to the magnetic field detection unit 25 largely changes depending on whether the operating frequency f1 is located in the low frequency region or in the high frequency region, a change in the strength of the magnetic field is detected. It has the advantage of being easy to do.
　勿論、磁界検知部２５は、一次側コイルＬ１の中心軸方向における一端側とは異なる場所に配置されていてもよい。例えば、磁界検知部２５は、図８Ａに示すように、一次側コイルＬ１の中央部の周囲に一次側コイルＬ１と所定の間隔を空けて配置されていてもよい。言い換えれば、磁界検知部２５は、一次側コイルＬ１と二次側コイルＬ２との間の空間に配置されていてもよい。この構成では、磁界検知部２５で検知される磁界は、動作周波数ｆ１が低周波領域に位置する場合に弱くなり、動作周波数ｆ１が高周波領域に位置する場合に強くなる。 Of course, the magnetic field detection unit 25 may be disposed at a location different from one end side in the central axis direction of the primary coil L1. For example, as shown in FIG. 8A, the magnetic field detection unit 25 may be disposed around the central portion of the primary coil L1 at a predetermined distance from the primary coil L1. In other words, the magnetic field detection unit 25 may be disposed in the space between the primary coil L1 and the secondary coil L2. In this configuration, the magnetic field detected by the magnetic field detection unit 25 is weak when the operating frequency f1 is located in the low frequency region, and is strong when the operating frequency f1 is located in the high frequency region.
　そして、この構成では、制御部２２は、判定処理において、磁界検知部２５で検知された磁界の強さが予め設定された閾値を上回れば、動作周波数ｆ１が高周波領域に位置すると判定する。また、制御部２２は、判定処理において、磁界検知部２５で検知された磁界の強さが閾値を下回れば、動作周波数ｆ１が低周波領域に位置すると判定する。この構成でも、動作周波数ｆ１が低周波領域に位置する場合と高周波領域に位置する場合とで、磁界検知部２５に鎖交（交差）する磁束が大きく変化するため、磁界の強さの変化を検知し易いという利点がある。 Then, in this configuration, in the determination processing, when the strength of the magnetic field detected by the magnetic field detection unit 25 exceeds the preset threshold value, the control unit 22 determines that the operating frequency f1 is located in the high frequency region. Further, in the determination process, if the strength of the magnetic field detected by the magnetic field detection unit 25 falls below the threshold in the determination process, the control unit 22 determines that the operating frequency f1 is located in the low frequency region. Even in this configuration, since the magnetic flux that intersects (crosses) the magnetic field detection unit 25 largely changes depending on whether the operating frequency f1 is located in the low frequency region or in the high frequency region, It has the advantage of being easy to detect.
　また、本実施形態の非接触給電装置２は、例えば図８Ｂに示すように、複数（図示では６つ）の磁界検知部２５を備えていてもよい。図８Ｂに示す例では、３つの磁界検知部２５が一次側コイルＬ１の中心軸方向における一端（図８Ｂにおける右端）側に配置され、３つの磁界検知部２５が一次側コイルＬ１の中心軸方向における他端（図８Ｂにおける左端）側に配置されている。 Moreover, the non-contact electric power supply 2 of this embodiment may be equipped with the magnetic field detection part 25 of plurality (six in illustration), for example, as shown to FIG. 8B. In the example shown to FIG. 8B, the three magnetic field detection parts 25 are arrange | positioned at the end (right end in FIG. 8B) side in the central axis direction of the primary side coil L1, and the three magnetic field detection parts 25 are central axis directions of the primary side coil L1. Are disposed on the other end side (left end in FIG. 8B).
　そして、制御部２２は、判定処理において、複数の磁界検知部２５のうち少なくとも２つの検知結果を比較してもよい。磁界検知部２５で検知される磁界の強さは、一次側コイルＬ１と二次側コイルＬ２との相対的な位置に応じて変化する。つまり、磁界検知部２５は、二次側コイルＬ２に近づくほど検知される磁界の強さが強くなり、二次側コイルＬ２から遠ざかるほど検知される磁界の強さが弱くなる。したがって、制御部２２は、判定処理において、各磁界検知部２５で検知される磁界の強さの差（勾配）に基づいて、一次側コイルＬ１と二次側コイルＬ２との相対的な位置を判定することができる。例えば、図８Ｂにおける右下の磁界検知部２５と、左下の磁界検知部２５で検知される磁界が他の磁界検知部２５で検知される磁界よりも強ければ、制御部２２は、二次側コイルＬ２が図８Ｂにおける下側にずれていると判定することができる。なお、当該構成を採用するか否かは任意である。 Then, the control unit 22 may compare at least two detection results of the plurality of magnetic field detection units 25 in the determination process. The strength of the magnetic field detected by the magnetic field detector 25 changes in accordance with the relative position of the primary coil L1 and the secondary coil L2. That is, in the magnetic field detection unit 25, the strength of the detected magnetic field becomes stronger as it approaches the secondary coil L2, and the strength of the detected magnetic field becomes weaker as it gets farther from the secondary coil L2. Therefore, in the determination process, the control unit 22 determines the relative position between the primary coil L1 and the secondary coil L2 based on the difference (gradient) in the strength of the magnetic field detected by each magnetic field detection unit 25. It can be determined. For example, if the magnetic field detected by the lower right magnetic field detection unit 25 and the lower left magnetic field detection unit 25 in FIG. 8B is stronger than the magnetic fields detected by the other magnetic field detection units 25, the control unit 22 It can be determined that the coil L2 is shifted downward in FIG. 8B. In addition, it is arbitrary whether to employ | adopt the said structure.
　ところで、本実施形態の非接触給電装置２では、制御部２２は、判定処理のみならず、判定処理の結果に基づいて、動作周波数ｆ１が共振特性における適正な周波数領域（つまり、低周波領域）に位置するように調整する調整処理を実行してもよい。以下、制御部２２で実行し得る種々の調整処理について例を挙げる。 By the way, in the non-contact power feeding device 2 of the present embodiment, the control unit 22 determines that the operating frequency f1 is an appropriate frequency range (that is, a low frequency range) in the resonance characteristic based on the determination process as well as the determination process. An adjustment process may be performed to adjust the position of the vehicle. Hereinafter, examples of various adjustment processes that can be executed by the control unit 22 will be described.
　例えば、制御部２２は、判定処理の判定結果に基づいて、インバータ回路２１２の動作周波数ｆ１を調整する調整処理を実行してもよい。例えば、制御部２２が、判定処理において、動作周波数ｆ１が高周波領域に位置すると判定した場合を考える。この場合、制御部２２は、調整処理において、動作周波数ｆ１を低下させる。この調整処理により、動作周波数ｆ１は、低周波領域に位置するように調整される。なお、当該構成を採用するか否かは任意である。 For example, the control unit 22 may execute the adjustment process of adjusting the operating frequency f1 of the inverter circuit 212 based on the determination result of the determination process. For example, it is assumed that the control unit 22 determines that the operating frequency f1 is located in the high frequency region in the determination process. In this case, the control unit 22 reduces the operating frequency f1 in the adjustment process. By this adjustment process, the operating frequency f1 is adjusted to be located in the low frequency region. In addition, it is arbitrary whether to employ | adopt the said structure.
　また、制御部２２は、判定処理の判定結果に基づいて、一次側共振部２３の共振パラメータを調整する調整処理を実行してもよい。「共振パラメータ」とは、一次側コンデンサＣ１のキャパシタンスや、一次側コイルＬ１のインダクタンスである。例えば、制御部２２が、判定処理において、動作周波数ｆ１が高周波領域に位置すると判定した場合を考える。この場合、制御部２２は、調整処理において、一次側コンデンサＣ１のキャパシタンス及び一次側コイルＬ１のインダクタンスの少なくとも一方を低下させる。この調整処理により、各周波数ｆｒ１～ｆｒ３が大きくなることで、共振特性が高周波数側にシフトする。すると、動作周波数ｆ１は、調整後の共振特性における低周波領域に位置するように調整される。なお、当該構成を採用するか否かは任意である。 Further, the control unit 22 may execute an adjustment process of adjusting the resonance parameter of the primary side resonance unit 23 based on the determination result of the determination process. The “resonance parameter” is the capacitance of the primary side capacitor C1 or the inductance of the primary side coil L1. For example, it is assumed that the control unit 22 determines that the operating frequency f1 is located in the high frequency region in the determination process. In this case, the control unit 22 reduces at least one of the capacitance of the primary side capacitor C1 and the inductance of the primary side coil L1 in the adjustment process. By this adjustment processing, the resonance characteristics shift to the high frequency side by increasing the frequencies fr1 to fr3. Then, the operating frequency f1 is adjusted to be located in the low frequency region of the adjusted resonance characteristic. In addition, it is arbitrary whether to employ | adopt the said structure.
　特に、制御部２２は、一次側共振部２３の共振特性が２つの共振周波数を有している場合（つまり、双峰特性の場合）、動作周波数ｆ１が２つの共振周波数のうち低い共振周波数に近づくように調整処理を実行するのが好ましい。すなわち、既に述べたように、制御部２２は、インバータ回路２１２の動作周波数ｆ１を調整したり、一次側共振部２３の共振パラメータを調整したりすることで、動作周波数ｆ１が低周波領域に位置するように調整処理を実行するのが好ましい。なお、当該構成を採用するか否かは任意である。 In particular, when the resonance characteristic of the primary side resonance unit 23 has two resonance frequencies (that is, in the case of a bimodal characteristic), the control unit 22 sets the operating frequency f1 to a low resonance frequency of the two resonance frequencies. It is preferable to carry out the adjustment process to get closer. That is, as described above, the control unit 22 adjusts the operating frequency f1 of the inverter circuit 212 or adjusts the resonance parameter of the primary side resonance unit 23 to position the operating frequency f1 in the low frequency region. It is preferable to carry out the adjustment process as follows. In addition, it is arbitrary whether to employ | adopt the said structure.
　なお、制御部２２によってキャパシタンスを調整可能な一次側コンデンサＣ１としては、バラクタダイオードの他に、例えば図９Ａに示す構成が考えられる。図９Ａに示す一次側コンデンサＣ１は、キャパシタンスが互いに異なる２つのコンデンサＣ１１，Ｃ１２と、２つのスイッチＱＣ１，ＱＣ２とを備える。スイッチＱＣ１は、コンデンサＣ１１に直列に電気的に接続される。また、スイッチＱＣ２は、コンデンサＣ１２に直列に電気的に接続される。そして、コンデンサＣ１１及びスイッチＱＣ１の直列回路と、コンデンサＣ１２及びスイッチＱＣ２の直列回路とが並列に電気的に接続される。 In addition to the varactor diode, for example, a configuration shown in FIG. 9A can be considered as the primary side capacitor C1 whose capacitance can be adjusted by the control unit 22. The primary side capacitor C1 shown in FIG. 9A includes two capacitors C11 and C12 having different capacitances, and two switches QC1 and QC2. The switch QC1 is electrically connected in series to the capacitor C11. The switch QC2 is electrically connected in series to the capacitor C12. Then, a series circuit of the capacitor C11 and the switch QC1 and a series circuit of the capacitor C12 and the switch QC2 are electrically connected in parallel.
　また、制御部２２によってインダクタンスを調整可能な一次側コイルＬ１としては、例えば図９Ｂに示す構成が考えられる。図９Ｂに示す一次側コイルＬ１は、互いに直列に電気的に接続された２つのコイルＬ１１，Ｌ１２と、一方のコイルＬ１２に並列に電気的に接続されたスイッチＱＬ１とを備える。 Moreover, as a primary side coil L1 which can adjust an inductance by the control part 22, the structure shown, for example to FIG. 9B can be considered. The primary side coil L1 shown in FIG. 9B includes two coils L11 and L12 electrically connected in series to each other, and a switch QL1 electrically connected in parallel to one coil L12.
　スイッチＱＣ１，ＱＣ２，ＱＬ１は、例えばＭＯＳＦＥＴのような半導体スイッチにより構成される。また、スイッチＱＣ１，ＱＣ２，ＱＬ１は、それぞれ制御部２２によってオン／オフを制御される。したがって、図９Ａに示す構成において、制御部２２がスイッチＱＣ１，ＱＣ２のオン／オフを切り替えるように制御することにより、一次側コンデンサＣ１のキャパシタンスを調整することができる。同様に、図９Ｂに示す構成において、制御部２２がスイッチＱＬ１のオン／オフを切り替えるように制御することにより、一次側コイルＬ１のインダクタンスを調整することができる。 The switches QC1, QC2, QL1 are formed of semiconductor switches such as MOSFETs, for example. The switches QC1, QC2, and QL1 are controlled by the control unit 22 to turn on and off. Therefore, in the configuration shown in FIG. 9A, the capacitance of the primary side capacitor C1 can be adjusted by controlling the control unit 22 to switch on / off the switches QC1 and QC2. Similarly, in the configuration shown in FIG. 9B, the inductance of the primary side coil L1 can be adjusted by controlling the control unit 22 to switch on / off the switch QL1.
　なお、図９Ａに示す構成では、コンデンサＣ１１，Ｃ１２及びスイッチＱＣ１，ＱＣ２の直列回路の個数は２つであるが、直列回路の個数を増やすことで、一次側コンデンサＣ１のキャパシタンスをより多段階に調整することが可能である。また、図９Ｂに示す構成では、コイルＬ１２及びスイッチＱＬ１の並列回路の個数は１つであるが、並列回路の個数を増やすことで、一次側コイルＬ１のインダクタンスをより多段階に調整することが可能である。 Although the number of series circuits of the capacitors C11 and C12 and the switches QC1 and QC2 is two in the configuration shown in FIG. 9A, the capacitance of the primary side capacitor C1 can be made in more stages by increasing the number of series circuits. It is possible to adjust. Further, although the number of parallel circuits of the coil L12 and the switch QL1 is one in the configuration shown in FIG. 9B, the inductance of the primary side coil L1 may be adjusted in more stages by increasing the number of parallel circuits. It is possible.
　また、一次側コンデンサＣ１は、図１０Ａに示すような容量調整回路２３２に組み込まれていてもよい。この容量調整回路２３２は、一次側コンデンサＣ１と、４つのスイッチング素子Ｑ５～Ｑ８とで構成される。ここでは、スイッチング素子Ｑ５～Ｑ８は、ｎチャネルのエンハンスメント型ＭＯＳＦＥＴである。容量調整回路２３２では、２つのスイッチング素子Ｑ５，Ｑ６の直列回路と、２つのスイッチング素子Ｑ７，Ｑ８の直列回路とが並列に電気的に接続されている。スイッチング素子Ｑ５のソース及びスイッチング素子Ｑ６のドレインの接続点は、インバータ回路２１２の第１出力点に電気的に接続されている。また、スイッチング素子Ｑ７のソース及びスイッチング素子Ｑ８のドレインの接続点は、一次側コイルＬ１の一端に電気的に接続されている。そして、スイッチング素子Ｑ５，Ｑ７のソースの接続点と、スイッチング素子Ｑ６，Ｑ８のドレインの接続点との間に、一次側コンデンサＣ１が電気的に接続されている。 Also, the primary side capacitor C1 may be incorporated in a capacity adjustment circuit 232 as shown in FIG. 10A. The capacitance adjustment circuit 232 is configured of a primary side capacitor C1 and four switching elements Q5 to Q8. Here, switching elements Q5 to Q8 are n-channel enhancement type MOSFETs. In the capacitance adjustment circuit 232, a series circuit of two switching elements Q5 and Q6 and a series circuit of two switching elements Q7 and Q8 are electrically connected in parallel. The connection point of the source of the switching element Q5 and the drain of the switching element Q6 is electrically connected to the first output point of the inverter circuit 212. The connection point of the source of the switching element Q7 and the drain of the switching element Q8 is electrically connected to one end of the primary coil L1. The primary side capacitor C1 is electrically connected between the connection point of the sources of the switching elements Q5 and Q7 and the connection point of the drains of the switching elements Q6 and Q8.
　容量調整回路２３２は、第３駆動信号Ｇ３をスイッチング素子Ｑ５，Ｑ８に、第４駆動信号Ｇ４をスイッチング素子Ｑ６，Ｑ７に与えられることで動作する。具体的には、容量調整回路２３２は、第３駆動信号Ｇ３及び第４駆動信号Ｇ４により、スイッチング素子Ｑ５，Ｑ８のオン期間と、スイッチング素子Ｑ６，Ｑ７のオン期間とを交互に切り替えるように動作する。 The capacitance adjustment circuit 232 operates by supplying the third drive signal G3 to the switching elements Q5 and Q8 and the fourth drive signal G4 to the switching elements Q6 and Q7. Specifically, the capacitance adjustment circuit 232 operates so as to alternately switch on periods of the switching elements Q5 and Q8 and on periods of the switching elements Q6 and Q7 by the third drive signal G3 and the fourth drive signal G4. Do.
　スイッチング素子Ｑ５，Ｑ８のオン期間において、インバータ回路２１２の出力電圧Ｖ１が正極性の期間では、スイッチング素子Ｑ５，Ｑ８を介して一次側コンデンサＣ１に電圧が印加される。つまり、容量調整回路２３２の入出力間は、一次側コンデンサＣ１を介する経路となる。一方、インバータ回路２１２の出力電圧Ｖ１が負極性の期間では、スイッチング素子Ｑ７の寄生ダイオードとスイッチング素子Ｑ５とを通る経路で電流が流れる。つまり、容量調整回路２３２の入出力間は、一次側コンデンサＣ１を介さない経路となる。 In the on period of the switching elements Q5 and Q8, while the output voltage V1 of the inverter circuit 212 is positive, a voltage is applied to the primary side capacitor C1 via the switching elements Q5 and Q8. That is, the path between the input and output of the capacitance adjustment circuit 232 is a path via the primary side capacitor C1. On the other hand, during a period in which the output voltage V1 of the inverter circuit 212 is negative, current flows along a path passing through the parasitic diode of the switching element Q7 and the switching element Q5. That is, the path between the input and output of the capacity adjustment circuit 232 is a path not via the primary side capacitor C1.
　同様に、スイッチング素子Ｑ６，Ｑ７のオン期間において、インバータ回路２１２の出力電圧Ｖ１が正極性の期間では、スイッチング素子Ｑ６とスイッチング素子Ｑ８の寄生ダイオードとを通る経路で電流が流れる。つまり、容量調整回路２３２の入出力間は、一次側コンデンサＣ１を介さない経路となる。一方、インバータ回路２１２の出力電圧Ｖ１が負極性の期間では、スイッチング素子Ｑ６，Ｑ７を介して一次側コンデンサＣ１に電圧が印加される。つまり、容量調整回路２３２の入出力間は、一次側コンデンサＣ１を介する経路となる。 Similarly, during the on period of the switching elements Q6 and Q7, while the output voltage V1 of the inverter circuit 212 has a positive polarity, a current flows in a path passing through the switching element Q6 and the parasitic diode of the switching element Q8. That is, the path between the input and output of the capacity adjustment circuit 232 is a path not via the primary side capacitor C1. On the other hand, while the output voltage V1 of the inverter circuit 212 has a negative polarity, a voltage is applied to the primary side capacitor C1 via the switching elements Q6 and Q7. That is, the path between the input and output of the capacitance adjustment circuit 232 is a path via the primary side capacitor C1.
　つまり、容量調整回路２３２は、スイッチング素子Ｑ５～Ｑ８のオン／オフが切り替えられることで、一次側コンデンサＣ１を介する経路と、一次側コンデンサＣ１を介さない経路とを切り替えるように構成されている。このように、一次側コンデンサＣ１が容量調整回路２３２の入出力間に接続されている期間を変化させることで、容量調整回路２３２のキャパシタンス（すなわち、一次側コンデンサＣ１のキャパシタンス）を調整することができる。 That is, the capacitance adjustment circuit 232 is configured to switch the path through the primary side capacitor C1 and the path not through the primary side capacitor C1 by switching on / off the switching elements Q5 to Q8. Thus, the capacitance of the capacity adjustment circuit 232 (that is, the capacitance of the primary side capacitor C1) can be adjusted by changing the period in which the primary side capacitor C1 is connected between the input and output of the capacity adjustment circuit 232. it can.
　さらに、容量調整回路２３２は、上記のように４つのスイッチング素子Ｑ５～Ｑ８を用いた構成の他に、図１０Ｂに示すように、２つの双方向スイッチＱ９，Ｑ１０を用いた構成であってもよい。双方向スイッチＱ９は、２つのゲート端子を有するダブルゲート構造の半導体素子で構成されている。また、双方向スイッチＱ９は、一次側コンデンサＣ１に直列に電気的に接続されている。双方向スイッチＱ１０は、２つのゲート端子を有するダブルゲート構造の半導体素子で構成されている。また、双方向スイッチＱ１０は、双方向スイッチＱ９及び一次側コンデンサＣ１の直列回路と並列に電気的に接続されている。双方向スイッチＱ９の２つのゲート端子には、それぞれ第３駆動信号Ｇ３及び第４駆動信号Ｇ４が入力される。また、双方向スイッチＱ１０の２つのゲート端子にも、それぞれ第３駆動信号Ｇ３及び第４駆動信号Ｇ４が入力される。このように構成された容量調整回路２３２は、図１０Ａに示す容量調整回路２３２と同様に動作する。 Furthermore, in addition to the configuration using four switching elements Q5 to Q8 as described above, capacitance adjustment circuit 232 may be configured using two bidirectional switches Q9 and Q10 as shown in FIG. 10B. Good. The bidirectional switch Q9 is composed of a semiconductor element of a double gate structure having two gate terminals. Further, the bidirectional switch Q9 is electrically connected in series to the primary side capacitor C1. The bidirectional switch Q10 is composed of a semiconductor element of a double gate structure having two gate terminals. Further, the bidirectional switch Q10 is electrically connected in parallel to the series circuit of the bidirectional switch Q9 and the primary side capacitor C1. The third drive signal G3 and the fourth drive signal G4 are input to the two gate terminals of the bidirectional switch Q9, respectively. In addition, the third drive signal G3 and the fourth drive signal G4 are input to the two gate terminals of the bidirectional switch Q10, respectively. The capacitance adjustment circuit 232 configured in this way operates in the same manner as the capacitance adjustment circuit 232 shown in FIG. 10A.
　また、本実施形態の非接触給電装置２は、一次側コイルＬ１を流れる電流に相当する電流（出力電流Ｉ１）を検知する電流検知部２４を備えている（図２参照）。そこで、制御部２２は、電流検知部２４の検知結果に基づいて、インバータ回路２１２が遅相モードで動作するように調整処理を実行してもよい。例えば、制御部２２は、インバータ回路２１２のスイッチング素子Ｑ１，Ｑ４の組がオンからオフになった時点の出力電流Ｉ１の電流値により、遅相モード及び進相モードの何れのモードでインバータ回路２１２が動作しているかを判定することができる。つまり、スイッチング素子Ｑ１，Ｑ４の組がオンからオフになる（すなわち、出力電圧Ｖ１がゼロクロスする）時点で、出力電流Ｉ１の電流値が正の値を示していれば、制御部２２は、インバータ回路２１２が遅相モードで動作していると判定する。一方、スイッチング素子Ｑ１，Ｑ４の組がオンからオフになる時点で、出力電流Ｉ１の電流値が負の値を示していれば、制御部２２は、インバータ回路２１２が進相モードで動作していると判定する。 Further, the non-contact power feeding device 2 of the present embodiment includes the current detection unit 24 that detects a current (output current I1) corresponding to the current flowing through the primary side coil L1 (see FIG. 2). Therefore, based on the detection result of the current detection unit 24, the control unit 22 may perform adjustment processing so that the inverter circuit 212 operates in the lagging mode. For example, the control unit 22 controls the inverter circuit 212 in any one of the lagging phase mode and the phase advancing mode according to the current value of the output current I1 when the pair of switching elements Q1 and Q4 of the inverter circuit 212 is turned off. Can be determined. In other words, if the current value of the output current I1 indicates a positive value at the time when the pair of switching elements Q1 and Q4 turns off (ie, the output voltage V1 crosses zero), the control unit 22 It is determined that the circuit 212 is operating in the lagging mode. On the other hand, if the current value of output current I1 indicates a negative value when the pair of switching elements Q1 and Q4 turns off, the control unit 22 operates the inverter circuit 212 in the phase advance mode. It is determined that there is.
　そして、制御部２２は、インバータ回路２１２が遅相モード及び進相モードの何れのモードで動作しているかの判定結果を踏まえて、インバータ回路２１２が遅相モードで動作するように調整する。調整方法としては、既に述べたように、インバータ回路２１２の動作周波数ｆ１を調整したり、一次側共振部２３の共振パラメータを調整したりする方法が挙げられる。 Then, the control unit 22 adjusts the inverter circuit 212 to operate in the lagging mode based on the determination result of whether the inverter circuit 212 is operating in the lagging mode or the phase advancing mode. As the adjustment method, as described above, the method of adjusting the operating frequency f1 of the inverter circuit 212 or adjusting the resonance parameter of the primary side resonance unit 23 may be mentioned.
　この構成では、インバータ回路２１２を遅相モードで動作させることができるため、インバータ回路２１２のスイッチング素子Ｑ１～Ｑ４のスイッチングによる損失を低減することができる。また、この構成では、インバータ回路２１２のスイッチング素子Ｑ１～Ｑ４に過大な電気的ストレスがかかるのを防止することができる。なお、当該構成を採用するか否かは任意である。 In this configuration, since the inverter circuit 212 can be operated in the lagging mode, it is possible to reduce the loss due to the switching of the switching elements Q1 to Q4 of the inverter circuit 212. Moreover, in this configuration, it is possible to prevent the excessive electrical stress from being applied to the switching elements Q1 to Q4 of the inverter circuit 212. In addition, it is arbitrary whether to employ | adopt the said structure.
　なお、制御部２２は、調整処理を実行した後に、再度、判定処理を実行してもよい。そして、再度の判定処理においても動作周波数ｆ１が高周波領域に位置すると判定された場合は、制御部２２は、更に調整処理を実行してもよい。 The control unit 22 may execute the determination process again after performing the adjustment process. Then, if it is determined that the operating frequency f1 is located in the high frequency region also in the second determination process, the control unit 22 may further execute the adjustment process.
　また、本実施形態の非接触給電装置２では、電源部２１を始動させてから、動作周波数ｆ１を一定とする給電動作を開始するまでの始動期間において、制御部２２が判定処理や調整処理を実行している。そして、制御部２２は、始動期間における出力電圧Ｖ１が、給電動作中の出力電圧Ｖ１よりも低くなるように、力率改善回路２１１を制御する。例えば、力率改善回路２１１が図２に示す構成であれば、制御部２２は、スイッチング素子Ｑ０のオン／オフを制御することで、始動期間における出力電圧Ｖ１を低くする。また、制御部２２は、給電動作を開始する際には、スイッチング素子Ｑ０のオン／オフを制御することで、給電動作中における出力電圧Ｖ１を高くする。この構成では、始動期間において動作周波数ｆ１が高周波領域に位置する場合であっても、始動期間においては出力電圧Ｖ１を給電動作中よりも低く抑えられるため、不要輻射を抑えることができる。なお、当該構成を採用するか否かは任意である。 Further, in the non-contact power feeding device 2 of the present embodiment, the control unit 22 performs the determination process and the adjustment process in the start period from the start of the power supply unit 21 to the start of the power feeding operation to make the operating frequency f1 constant. Running. Then, the control unit 22 controls the power factor improvement circuit 211 such that the output voltage V1 in the start period is lower than the output voltage V1 during the power supply operation. For example, if the power factor correction circuit 211 has the configuration shown in FIG. 2, the control unit 22 lowers the output voltage V1 in the start period by controlling the on / off of the switching element Q0. Further, when starting the power supply operation, the control unit 22 controls the on / off of the switching element Q0 to increase the output voltage V1 during the power supply operation. In this configuration, even if the operating frequency f1 is located in the high frequency region in the starting period, the output voltage V1 can be suppressed lower in the starting period than during the power supply operation, so unnecessary radiation can be suppressed. In addition, it is arbitrary whether to employ | adopt the said structure.
　ところで、本実施形態の非接触給電システム１において、制御部２２は、判定処理の判定結果に基づいて、一次側コイルＬ１及び二次側コイルＬ２の相対的な位置の変更を促す指示信号を出力する処理を実行してもよい。例えば、一次側コイルＬ１（及びコア２３１）の位置を調整可能に構成されたアクチュエータを非接触給電装置２が備えている場合、制御部２２は、アクチュエータに指示信号を出力すればよい。以下、制御部２２が、判定処理において、動作周波数ｆ１が高周波領域に位置すると判定した場合を考える。この場合、制御部２２は、アクチュエータに指示信号を出力する。アクチュエータは、指示信号に応じて一次側コイルＬ１の位置を調整する。この処理により、一次側コイルＬ１と二次側コイルＬ２との相対的な位置が調整され、動作周波数ｆ１は、低周波領域に位置するように調整される。 By the way, in the non-contact power feeding system 1 of the present embodiment, the control unit 22 outputs an instruction signal for prompting a change in the relative position of the primary coil L1 and the secondary coil L2 based on the determination result of the determination process. Processing may be performed. For example, when the non-contact power feeding device 2 includes an actuator configured to adjust the position of the primary coil L1 (and the core 231), the control unit 22 may output an instruction signal to the actuator. Hereinafter, it is assumed that the control unit 22 determines that the operating frequency f1 is located in the high frequency region in the determination process. In this case, the control unit 22 outputs an instruction signal to the actuator. The actuator adjusts the position of the primary coil L1 in accordance with the instruction signal. By this processing, the relative position between the primary coil L1 and the secondary coil L2 is adjusted, and the operating frequency f1 is adjusted to be located in the low frequency region.
　その他、本実施形態の非接触給電システム１は、例えば、指示信号を非接触受電装置３に与え、指示信号に応じて二次側コイルＬ２の位置を調整することで、一次側コイルＬ１及び二次側コイルＬ２の相対的な位置を調整するように構成されていてもよい。 In addition, the non-contact power feeding system 1 according to the present embodiment, for example, provides an instruction signal to the non-contact power reception device 3 and adjusts the position of the secondary coil L2 according to the instruction signal. You may be comprised so that the relative position of the following coil L2 may be adjusted.
　以下、この構成について簡単に説明する。この構成では、図１１に示すように、非接触給電装置２と、非接触受電装置３とは、それぞれ通信部２６，３４を備える。通信部２６，３４は、例えば電波を媒体とする無線信号により相互に通信を行うように構成される。また、非接触受電装置３は、指示信号に応じた処理を実行する制御部３３を備える。制御部３３は、制御部２２と同様に、例えばマイコンにより構成される。 Hereinafter, this configuration will be briefly described. In this configuration, as shown in FIG. 11, the non-contact power feeding device 2 and the non-contact power receiving device 3 respectively include communication units 26 and 34. The communication units 26 and 34 are configured to communicate with each other by, for example, radio signals using radio waves as a medium. The non-contact power reception device 3 also includes a control unit 33 that executes a process according to the instruction signal. The control unit 33 is, for example, a microcomputer as in the case of the control unit 22.
　例えば、制御部２２が、判定処理において、動作周波数ｆ１が高周波領域に位置すると判定した場合を考える。この場合、制御部２２は、指示信号を生成し、通信部２６により指示信号を非接触受電装置３に向けて送信させる。非接触受電装置３において、通信部３４は、指示信号を受信すると、指示信号を制御部３３に入力する。制御部３３は、入力された指示信号に基づいて、ユーザに適正な停車位置に電気自動車１００を移動させるように指示する。指示は、例えば電気自動車１００に搭載されたスピーカから音声を出力させたり、電気自動車１００に搭載されたディスプレイに画像や動画を表示させたりすることで行う。この処理により、一次側コイルＬ１と二次側コイルＬ２との相対的な位置が調整され、動作周波数ｆ１は、低周波領域に位置するように調整される。 For example, it is assumed that the control unit 22 determines that the operating frequency f1 is located in the high frequency region in the determination process. In this case, the control unit 22 generates an instruction signal, and causes the communication unit 26 to transmit the instruction signal to the non-contact power reception device 3. In the non-contact power reception device 3, when receiving the instruction signal, the communication unit 34 inputs the instruction signal to the control unit 33. The control unit 33 instructs the user to move the electric vehicle 100 to the appropriate stopping position based on the input instruction signal. The instruction is performed by, for example, outputting sound from a speaker mounted on the electric vehicle 100 or displaying an image or a moving image on a display mounted on the electric vehicle 100. By this processing, the relative position between the primary coil L1 and the secondary coil L2 is adjusted, and the operating frequency f1 is adjusted to be located in the low frequency region.
　なお、上記構成を採用するか否かは任意である。また、上記構成は、複数の磁界検知部２５の各々の検知結果に基づいて一次側コイルＬ１と二次側コイルＬ２との相対的な位置ずれを判定する構成と共に採用するのが好ましい。 Note that it is optional whether or not the above configuration is adopted. In addition, it is preferable to adopt the above configuration together with a configuration that determines the relative positional deviation between the primary coil L1 and the secondary coil L2 based on the detection results of each of the plurality of magnetic field detectors 25.
　なお、本実施形態の非接触給電システム１では、コア２３１に一次側コイルＬ１を、コア３１１に二次側コイルＬ２を設けているが、この構成に限定する趣旨ではない。つまり、一次側コイルＬ１は、コア２３１以外の部材に設けてもよい。同様に、二次側コイルＬ２は、コア３１１以外の部材に設けてもよい。 In the non-contact power feeding system 1 of the present embodiment, the core 231 is provided with the primary coil L1 and the core 311 is provided with the secondary coil L2, but the present invention is not limited to this configuration. That is, the primary coil L1 may be provided to a member other than the core 231. Similarly, the secondary coil L2 may be provided to a member other than the core 311.
　また、本実施形態の非接触給電システム１は、非接触給電装置２に磁界検知部２５を設け、制御部２２に判定処理や調整処理を実行させる構成であるが、他の構成であってもよい。すなわち、本実施形態の非接触給電システム１は、非接触受電装置３に磁界検知部２５を設け、制御部３３に判定処理や調整処理を実行させる構成であってもよい。 Moreover, although the non-contact electric power supply system 1 of this embodiment provides the magnetic field detection part 25 in the non-contact electric power supply apparatus 2 and makes the control part 22 perform a determination process and adjustment process, even if it is another structure. Good. That is, in the non-contact power feeding system 1 of the present embodiment, the non-contact power reception device 3 may be configured to have the magnetic field detection unit 25 and cause the control unit 33 to execute the determination process and the adjustment process.
　また、本実施形態の非接触給電装置２及び非接触給電システム１では、共鳴方式により一次側コイルＬ１から二次側コイルＬ２に電力を伝送しているが、電磁誘導方式で電力を伝送する構成であってもよい。この構成では、非接触受電装置３において共振回路を形成する必要がないので、二次側コンデンサＣ２は不要である。 Further, in the non-contact power feeding device 2 and the non-contact power feeding system 1 of the present embodiment, power is transmitted from the primary coil L1 to the secondary coil L2 by resonance, but power is transmitted by electromagnetic induction. It may be In this configuration, since it is not necessary to form a resonant circuit in the non-contact power reception device 3, the secondary side capacitor C2 is unnecessary.
　また、本実施形態の非接触給電システム１は、一次側コイルＬ１及び二次側コイルＬ２として、ソレノイド型のコイルを採用している。このため、本実施形態の非接触給電システム１は、スパイラル型のコイルを採用した場合と比較して、一次側コイルＬ１及び二次側コイルＬ２の小型化を図り易いという利点がある。また、本実施形態の非接触給電システム１は、一次側コイルＬ１と二次側コイルＬ２との相対的な位置が第１方向（図６Ａにおける左右方向）に多少ずれたとしても、共振特性が変化し難いという利点がある。 Moreover, the non-contact electric power feeding system 1 of this embodiment employ | adopts the coil of a solenoid type as the primary side coil L1 and the secondary side coil L2. For this reason, the non-contact power feeding system 1 of this embodiment has an advantage that it is easy to miniaturize the primary side coil L1 and the secondary side coil L2 as compared with the case where a spiral type coil is adopted. Further, in the non-contact power feeding system 1 of the present embodiment, even if the relative position between the primary side coil L1 and the secondary side coil L2 is somewhat deviated in the first direction (the left and right direction in FIG. It has the advantage of being difficult to change.

Claims (11)

  1. 　直流電力を交流電力に変換して出力するインバータ回路と、
    　前記インバータ回路の出力する交流電力を受けて磁束を発生するソレノイド型の一次側コイル、及び前記一次側コイルと共に一次側の共振回路を形成する一次側コンデンサで構成される一次側共振部と、
    　磁界を検知する磁界検知部と、
    　前記磁界検知部の検知結果に基づいて、前記インバータ回路の動作周波数と前記一次側共振部の共振特性との相関を判定する判定処理を実行する制御部とを備えることを特徴とする非接触給電装置。     An inverter circuit that converts DC power into AC power and outputs it;
    A primary side resonance unit configured of a solenoid type primary side coil that receives an AC power output from the inverter circuit to generate a magnetic flux, and a primary side capacitor that forms a primary side resonance circuit with the primary side coil;
    A magnetic field detection unit that detects a magnetic field;
    Non-contact power supply characterized by comprising a control unit that executes a determination process of determining a correlation between an operating frequency of the inverter circuit and a resonance characteristic of the primary side resonance unit based on a detection result of the magnetic field detection unit. apparatus.
  2. 　前記一次側共振部の前記共振特性は２つの共振周波数を有し、かつ前記一次側共振部の出力が極小値を示す所定の周波数を境界にして、前記所定の周波数よりも低い周波数領域である低周波領域と、前記所定の周波数よりも高い周波数領域である高周波領域とを有し、
    　前記制御部は、前記判定処理において、前記磁界検知部で検知された磁界の強さと閾値との比較結果に応じて、前記動作周波数が前記低周波領域及び前記高周波領域のいずれに位置するかを判定することを特徴とする請求項１記載の非接触給電装置。     The resonance characteristic of the primary side resonance unit has two resonance frequencies, and is a frequency region lower than the predetermined frequency with a predetermined frequency at which the output of the primary side resonance unit exhibits a minimum value as a boundary. It has a low frequency range and a high frequency range which is a frequency range higher than the predetermined frequency,
    The control unit determines in which of the low frequency region and the high frequency region the operating frequency is located according to the comparison result between the strength of the magnetic field detected by the magnetic field detection unit and a threshold in the determination process. The contactless power supply device according to claim 1, wherein the contactless power supply device is determined.
  3. 　前記磁界検知部は、前記一次側コイルの中心軸方向における一端側に配置されることを特徴とする請求項１又は２記載の非接触給電装置。 The non-contact power feeding device according to claim 1 or 2, wherein the magnetic field detection unit is disposed on one end side in the central axis direction of the primary coil.
  4. 　前記磁界検知部は、前記一次側コイルの中央部の周囲に前記一次側コイルと所定の間隔を空けて配置されることを特徴とする請求項１又は２記載の非接触給電装置。 3. The non-contact power feeding device according to claim 1, wherein the magnetic field detection unit is disposed around the central portion of the primary coil at a predetermined distance from the primary coil.
  5. 　前記磁界検知部を複数備え、
    　前記制御部は、前記判定処理において、前記複数の磁界検知部のうち少なくとも２つの検知結果を比較することを特徴とする請求項１乃至４の何れか１項に記載の非接触給電装置。     A plurality of the magnetic field detection units;
    The non-contact power feeding device according to any one of claims 1 to 4, wherein the control unit compares at least two detection results of the plurality of magnetic field detection units in the determination process.
  6. 　前記制御部は、前記判定処理の判定結果に基づいて、前記インバータ回路の動作周波数を調整する調整処理を実行することを特徴とする請求項１乃至５の何れか１項に記載の非接触給電装置。 The said control part performs the adjustment process which adjusts the operating frequency of the said inverter circuit based on the judged result of the said judgment process, The non-contact electric power feeding in any one of the Claims 1 thru | or 5 characterized by the above-mentioned apparatus.
  7. 　前記制御部は、前記判定処理の判定結果に基づいて、前記一次側共振部の共振パラメータを調整する調整処理を実行することを特徴とする請求項１乃至４の何れか１項に記載の非接触給電装置。 The control unit according to any one of claims 1 to 4, wherein the control unit executes an adjustment process of adjusting a resonance parameter of the primary side resonance unit based on the determination result of the determination process. Contact power supply device.
  8. 　前記制御部は、前記一次側共振部の前記共振特性が２つの共振周波数を有している場合、前記動作周波数が前記２つの共振周波数のうち低い共振周波数に近づくように前記調整処理を実行することを特徴とする請求項６又は７記載の非接触給電装置。 The control unit executes the adjustment process so that the operating frequency approaches a lower resonance frequency of the two resonance frequencies when the resonance characteristic of the primary side resonance unit has two resonance frequencies. The contactless power supply device according to claim 6 or 7, characterized in that:
  9. 　前記一次側コイルを流れる電流に相当する電流を検知する電流検知部を備え、
    　前記制御部は、前記電流検知部の検知結果に基づいて、前記インバータ回路が遅相モードで動作するように前記調整処理を実行することを特徴とする請求項６乃至８の何れか１項に記載の非接触給電装置。     A current detection unit for detecting a current corresponding to the current flowing through the primary coil;
    9. The controller according to any one of claims 6 to 8, wherein the controller performs the adjustment process based on the detection result of the current detector so that the inverter circuit operates in the lagging mode. The contactless power supply device as described.
  10. 　請求項１乃至９の何れか１項に記載の非接触給電装置と、前記非接触給電装置から供給される電力を受ける非接触受電装置とを備え、
    　前記非接触受電装置は、前記一次側コイルが発生する磁束を受けて交流電力を発生する二次側コイル、及び前記二次側コイルと共に二次側の共振回路を形成する二次側コンデンサで構成される二次側共振部を備えることを特徴とする非接触給電システム。     A non-contact power feeding device according to any one of claims 1 to 9, and a non-contact power receiving device for receiving power supplied from the non-contact power feeding device,
    The non-contact power reception device is configured of a secondary coil that generates an AC power by receiving a magnetic flux generated by the primary coil, and a secondary capacitor that forms a secondary resonance circuit with the secondary coil. A contactless power supply system comprising: a secondary side resonance part.
  11. 　前記制御部は、前記判定処理の判定結果に基づいて、前記一次側コイル及び前記二次側コイルの相対的な位置の変更を促す指示信号を出力する処理を実行することを特徴とする請求項１０記載の非接触給電システム。 The said control part performs the process which outputs the instruction | indication signal which urges the change of the relative position of the said primary side coil and the said secondary side coil based on the judged result of the said judgment process, The contactless power supply system as described in 10.
PCT/JP2015/003757 2014-07-31 2015-07-27 Contactless power-feeding device and contactless power-feeding system using same WO2016017142A1 (en)

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Citations (4)

* Cited by examiner, † Cited by third party
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JP2009089465A (en) * 2007-09-27 2009-04-23 Panasonic Corp Charger and charging system
JP2010239847A (en) * 2009-03-31 2010-10-21 Fujitsu Ltd Power transmission apparatus, power transmission reception apparatus, and power transmission method
JP2013153627A (en) * 2012-01-26 2013-08-08 Shindengen Electric Mfg Co Ltd Non-contact feeder circuit
JP2013240263A (en) * 2012-04-17 2013-11-28 Nitto Denko Corp Method for forming magnetic field space

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2009089465A (en) * 2007-09-27 2009-04-23 Panasonic Corp Charger and charging system
JP2010239847A (en) * 2009-03-31 2010-10-21 Fujitsu Ltd Power transmission apparatus, power transmission reception apparatus, and power transmission method
JP2013153627A (en) * 2012-01-26 2013-08-08 Shindengen Electric Mfg Co Ltd Non-contact feeder circuit
JP2013240263A (en) * 2012-04-17 2013-11-28 Nitto Denko Corp Method for forming magnetic field space

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