WO2013010385A1 - 一种自激推挽式变换器 - Google Patents
一种自激推挽式变换器 Download PDFInfo
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- WO2013010385A1 WO2013010385A1 PCT/CN2012/070254 CN2012070254W WO2013010385A1 WO 2013010385 A1 WO2013010385 A1 WO 2013010385A1 CN 2012070254 W CN2012070254 W CN 2012070254W WO 2013010385 A1 WO2013010385 A1 WO 2013010385A1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/538—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a push-pull configuration
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5383—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a self-oscillating arrangement
- H02M7/53832—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a self-oscillating arrangement in a push-pull arrangement
- H02M7/53835—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a self-oscillating arrangement in a push-pull arrangement of the parallel type
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/337—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration
- H02M3/3372—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration of the parallel type
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/338—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement
- H02M3/3382—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement in a push-pull circuit arrangement
- H02M3/3384—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement in a push-pull circuit arrangement of the parallel type
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- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
- H05B45/30—Driver circuits
- H05B45/37—Converter circuits
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B20/00—Energy efficient lighting technologies, e.g. halogen lamps or gas discharge lamps
- Y02B20/30—Semiconductor lamps, e.g. solid state lamps [SSL] light emitting diodes [LED] or organic LED [OLED]
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- This invention relates to DC-DC or DC-AC converters, and more particularly to the industrial control and lighting industry. Background technique
- the existing self-excited push-pull converter the circuit structure is derived from the self-excited oscillation push-pull transistor single-transform DC converter invented by GH Royer in 1955, which is also the beginning of realizing the high-frequency switching control circuit;
- the self-excited push-pull dual transformer circuit invented by Jen Sen (somewhere translated as "Jingsen") in 1957 is called the self-oscillating Jensen circuit; these two circuits are collectively called self-excited pushes. Pull converter.
- Self-excited push-pull converters are described in Electronic Engineering Press, Principles and Designs of Switching Power Supplies, pages 67 to 70, ISBN ISBN 7-121-00211-6.
- the main form of the circuit is the well-known Royer circuit and the self-oscillating Jensen circuit.
- Figure 1-1 shows the common application of the self-excitation push-pull converter.
- the circuit structure is a Royer circuit.
- the capacitor C1 in parallel with the bias resistor R1 can be omitted in many cases.
- the ZL patent number is 03273278. 3, date of publication: On August 25, 2004, the name is "Self-excited push-pull converter".
- a Royer circuit with soft-start function is provided. See Figure 2, which solves the problem that the capacitor C1 in Figure 1_1 is used for push-pull at startup. The impact of the switching transistor.
- Figure 1-2 is also an application.
- the circuit structure is still a Royer circuit.
- the original bias resistor R1 is split into two Rlu and Rid series, which are used for higher operating voltage input.
- the capacitor C1 in parallel with the bias resistor Rlu can be omitted in many cases, so the capacitor C1 in Figure 1-2 is drawn in dashed lines.
- Figure 3 is also a common Royer circuit, which simplifies the winding of the feedback winding.
- the DC signal loop, the operating points of the transistors TR1 and TR2 are the same, but when the circuit is in the self-oscillating state, the transistors TR1 and TR2 work. difference.
- the resistors Rla and Rlb are a cost-saving solution based on Figure 4.
- the publication date is (2006-11-09) ((Switching power supply apparatus)), a resistance bias method similar to that of Fig. 4 is used as the unit circuit.
- Figure 5 is a common Royer circuit. Since the inductor L1 is connected in series in the power supply circuit, and a capacitor CL is connected in parallel between the collector of the push-pull switch transistor, the circuit output is close to a sine wave, which is common in circuits such as energy-saving lamp electronic rectifiers, and the feedback winding can also be simplified.
- the winding method is similar to that of Figures 3 and 4.
- f is the oscillation frequency
- BW is the working magnetic induction ( ⁇ )
- ⁇ is the number of turns of the coil
- S is the effective cross-sectional area of the core.
- the circuit structure of Figure 1-1 is:
- the input filter capacitor c is connected between the voltage input terminal and the ground to filter the input voltage;
- the filtered input voltage is connected to the startup circuit, and the startup circuit is biased by the resistor R1 and the electric Capacitor CI is composed in parallel.
- C1 can be omitted when the higher supply voltage is input.
- the two ends of the bias resistor R1 are respectively coupled with the voltage input terminal and the coupling transformer B which provides positive feedback for the bases of the two push-pull transistors TR1 TR2.
- the center taps of the side coils NB1 and NB2 are connected; the emitters of the two push-pull transistors TR1 TR2 are common, and the two collectors are respectively connected to the two ends of the primary windings NP1 and NP2 of the coupling transformer, and the base is connected to the primary side of the coupling transformer
- the two ends of the coils NB1 and NB2, the center taps of the primary windings NP1 and NP2 are connected to the voltage input terminal; the secondary side coil NS of the coupling transformer B is connected to the output filter circuit to the voltage output
- the Royer circuit uses the core saturation characteristic to perform push-pull oscillation.
- the bias resistor R1 and the capacitor C1 are connected in parallel through the windings NB1 and NB2 to the transistors TR1 and TR2.
- the base and emitter provide forward bias, and the two transistors TR1 and TR2 start to conduct. Since the characteristics of the two transistors are not exactly the same, one of the transistors will be turned on first, assuming that the transistor TR2 is turned on first, generating a set.
- the electrode current I e2 the voltage of the corresponding winding of the coil NP2 is up and down.
- the winding of the base coil NB2 also has a positive and negative induced voltage, which increases the base of the transistor TR2.
- Current which is a positive feedback process, so that the transistor TR2 is quickly turned on; accordingly, the voltage of the winding of the coil NB1 corresponding to the transistor TR1 is up and down, and this voltage reduces the base current of the transistor TR1.
- Transistor TR1 is quickly cut off completely.
- the collector current of the switch tube increases sharply, the rate of increase is much larger than the increase of the base current, the transistor of the transistor TR2 is out of saturation, and the voltage drop UCE of the collector to the emitter of the transistor of the transistor TR2 increases, correspondingly, the transformer N P2
- the voltage on the winding is reduced by the same value, and the voltage induced by the winding of the coil NB2 is reduced.
- the base voltage of the transistor of the transistor TR2 is also lowered, causing the transistor of the transistor TR2 to change in the cut-off direction.
- the voltage on the transformer coil will be In the reverse direction, the other transistor TR1 is turned on, and thereafter, this process is repeated to form a push-pull oscillation.
- the waveform of the output of the winding Ns is as shown in FIG. 6.
- the characteristics are as follows:
- the core-saturation characteristic is used for push-pull oscillation, and the output waveform of the coupling transformer is approximate square wave, and the conversion efficiency of the circuit is high.
- the circuit of Figure 5 is close to the sine wave because the inductor L1 is connected in series in the power supply loop and a capacitor CL is connected in parallel between the collector of the push-pull switch transistor.
- B2 exhibits magnetic saturation, because B2 is small in size, the energy consumed by magnetic saturation is small, and the overall efficiency of the circuit is high.
- the self-oscillation frequency of the Jensen circuit is relatively stable when the operating voltage, load, and temperature change.
- the working voltage is poorly adaptable.
- Table 1 shows the measured parameters of the Royer circuit. If the circuit of Figure 1_1 is used, it is a converter with input DC 5V, output DC 5V, and output current 200mA, that is, output power 1W.
- the main parameters of the circuit are: Capacitor C is a luF capacitor, resistor R1 is 1 ⁇ ⁇ , capacitor C1 is 0. 047uF capacitor, transistors TR1 and TR2 are switching diodes with a magnification of about 200 times, and the collector maximum operating current is 1A.
- the subsequent output of the transformer employs the circuit configuration of Fig. 8, and Fig. 8 shows a known full-wave rectification circuit.
- the circuit adopts the circuit of Fig. 7 to make a converter with input DC 5V, output DC 5V, and output current 200mA, that is, output power 1W.
- the main parameters of the circuit are: Capacitor C is luF capacitor, resistor R1 is 1 ⁇ ⁇ , capacitor Cla is 0. 047uF capacitor, transistor TR1 and TR2 are switching diodes with magnification of about 200 times, and the collector maximum working current is 1A.
- the subsequent output of the transformer uses the circuit structure of Figure 8.
- the conversion efficiency of the circuit is:
- Vin is the operating voltage, ie the input voltage, I in is the input current; Vout is the output voltage, lout is the output current.
- the circuit operating at 5V if it is operated at 8V, its own loss has reached 280mW. In the micropower DC/DC converter, this is barely acceptable, but at 12V. Under the working voltage, its own loss has reached 828mW, and at 20V, its own loss has reached 3600mW, that is, 3. 6W, the circuit working time is more than 3 seconds, the circuit will be damaged. Therefore, the conversion efficiency of the circuit also decreases as the operating voltage rises.
- the Jensen circuit has the same problem. That is, the operating voltage is increased, causing the no-load operating current of the conventional self-excited push-pull converter to rise too fast, the no-load loss to rise too fast, and the conversion efficiency to decrease.
- the technical problem to be solved by the present invention is: when the operating current of the self-excited push-pull converter rises slowly or does not rise as the operating voltage rises, and a surge occurs in the input voltage of the self-excitation push-pull converter When the self-excited push-pull converter has a certain anti-surge capability, it is not easy to damage the switching transistor.
- the present invention provides a self-excitation push-pull converter, characterized in that a DC current loop of a base of a push-pull switch transistor is a constant current source between the active power supply terminals; that is, in a Royer or Jensen circuit. On the basis of this, cancel the bias resistance between the DC loop of the base of the push-pull switch transistor to the effective power supply terminal, and increase the constant current source instead of the original bias resistor.
- the current direction of the constant current source should be consistent with the direction of the canceled original bias resistor current, that is, the current direction of the constant current source is the base level flowing into the NPN transistor; or the current direction of the constant current source is from the PNP transistor. The base level flows into the constant current source.
- the constant current source can obtain a larger constant current value by parallel connection.
- the constant current source may be any type of semiconductor device or an electronic circuit that implements a constant current.
- the working principle of the invention is that the constant current source replaces the original bias resistor, but the current direction is consistent.
- the two The current supplied by the base of the push-pull transistor is constant.
- the circuit operates in a new manner to achieve push-pull oscillation, which is briefly described as follows:
- the constant current source provides forward bias to the base and emitter of the transistor 1 and the transistor 2 through the feedback winding 1 and the feedback winding 2, and the transistor 1 and the transistor 2 start to conduct, because the characteristics of the two transistors are not It may be exactly the same, therefore, one of the transistors will be turned on first, assuming that the transistor 1 is turned on first, generating a collector current, the voltage of the corresponding coil winding 1 is positive for the power supply terminal, and the terminal connected to the collector of the triode 1 is negative, according to the same name
- the base feedback winding 1 also exhibits a positive feedback induced voltage, which maintains and increases the base current of the transistor 1, which is a positive feedback process, so that the transistor 1 is quickly saturated and turned on; Ground, the induced voltage of the base feedback winding 2 corresponding to the transistor 2 reduces the base current of the transistor 2, and the transistor 2 is quickly turned off completely.
- the base current reduction portion of the transistor 2 is all the base current increasing portion of the transistor 1.
- the current of the coil winding 1 corresponding to the transistor 1 and the magnetic induction intensity generated by this current increase linearly with time.
- the collector current of the transistor 1 approaches or reaches its base current.
- transistor 1 will exit the saturation region and enter the amplification region.
- the collector-to-emitter voltage drop UCE of the transistor 1 is significantly increased, correspondingly, three
- the voltage across the coil winding 1 corresponding to the pole tube 1 is reduced by the same value, and the base feedback winding 1 also exhibits a corresponding induced voltage, which is also reduced.
- This voltage weakens the base current of the transistor 1, which is a
- the process of positive feedback quickly turns the transistor 1 out of the amplified state and enters the off state; accordingly, the induced voltage of the base feedback winding 2 corresponding to the transistor 2 increases the base current of the transistor 2, and the transistor 2 is completely completed. Saturated conduction.
- the base current increase portion of the transistor 2 is entirely derived from the base current reduction portion of the transistor 1.
- the two transistors are alternately turned on to complete the push-pull oscillation mode. Since the total input current of the base is limited by the constant current source and does not change with the fluctuation of the operating voltage, the circuit enters a new push-pull oscillation mode when the operating voltage rises.
- the circuit can still operate with push-pull oscillation using the core saturation characteristic under conditions of proper load, proper operating voltage, and the like.
- the circuit Since the bias resistor of the prior art can provide a larger base current after the operating voltage is increased, the circuit uses the core saturation characteristic to perform push-pull oscillation. At this time, the collector current is too large, and the triode is easily burned. After the constant current source is used, the circuit enters a new push-pull oscillation mode.
- the maximum current of the collector of the transistor is limited by the base current. The maximum value of the current is related to the product of the constant current source output current and the number of amplifiers of the transistor. Thereby the push-pull transistor works in the safe zone.
- the Jensen circuit works like this.
- the synchronous rectification circuit is added at the output end, and the efficiency of the synchronous rectification is high, the voltage drop loss during rectification is small, and the working efficiency of the circuit can be improved; and the output can be realized in a wide input voltage range.
- the voltage and input voltage are linearly synchronized.
- the invention has the advantages that after the constant current source is used as the bias, the operating voltage is increased, and the no-load power consumption of the circuit is reduced under the same conditions, and the conversion efficiency of the circuit is significantly improved compared with the prior art.
- the Royer circuit of Figure 1-1 is used to make a converter with an input DC of 5V, an output of 5V DC, and an output current of 200mA, that is, an output power of 1W.
- the output of the transformer uses the circuit structure of Figure 8.
- the main parameters of the circuit are: Capacitor C is a luF capacitor, resistor R1 is replaced by a 4. 3mA constant current source, capacitor C1 is 0. 047uF capacitor, transistors TR1 and TR2 are switching diodes with a magnification of about 200 times, and the collector is the largest.
- the operating current is 1A.
- the measured parameters are as follows:
- the self-excited push-pull Royer converter of the present invention works at a higher level than the existing self-excited push-pull Royer converter.
- the no-load input current, no-load loss, and conversion efficiency are significantly improved: 1.
- the no-load current of the circuit using the invention is significantly reduced.
- the prior art is 180 mA, and this current rises sharply to more than 300 mA after a few seconds as the working time is extended.
- the present invention is 30 mA, and the current value is very stable, and the long-term operation does not rise. See Figure 9 for a comparison.
- the conversion efficiency of the present invention is improved under the same operating voltage. 0% ⁇ The invention is 58. 6%, the invention is 86.0%. See Figure 11 for a comparison.
- the present invention is applied to the circuit of Fig. 7 to make a converter with an input DC of 5V, an output of 5V DC, and an output current of 200mA, that is, an output power of 1W.
- the main parameters of the circuit are: Capacitor C is a luF capacitor, resistor R1 is replaced by a 4. 3mA constant current source, and capacitor Cla is 0. 047uF capacitor, triode TR1 and TR2 are switching diodes with a magnification of about 200 times, and the collector is the largest.
- the operating current is 1A.
- the subsequent output of the transformer uses the circuit structure of Figure 8.
- the measured parameters are as follows:
- the self-excited push-pull Jensen converter has significantly improved no-load input current, no-load loss, and conversion efficiency after the operating voltage is increased:
- the no-load current of the circuit using the invention is significantly reduced.
- the prior art is 200mA, and this current rises sharply to more than 300mA after a few seconds as the working time is extended.
- the present invention is 37 mA, and the current value is very stable, and the long-term operation does not rise. See Figure 12 for a comparison.
- the conversion efficiency of the present invention is improved under the same operating voltage. For example, at 15 V, the prior art is 22.6%, and the present invention is 64.6%. See Figure 14 for a comparison.
- the invention also has the advantages that the self-excitation push-pull Royer converter uses the constant current source as the bias, and as the operating voltage increases, the circuit is short-circuited at the output end under the same conditions, that is, the DC OUT of FIG. 8 is short-circuited.
- the short circuit protection performance of the present invention is significantly improved.
- the measured comparison data is shown in Table 5 below:
- the use of the 4. 3 mA constant current source bias short circuit protection performance is significantly improved in connection with the special new push-pull oscillation mode brought by the present invention.
- the existing Royer self-excitation push-pull converter has a short circuit protection mechanism.
- the leakage inductance of the transformer is that the magnetic lines generated by the primary coil cannot pass through the secondary coil. Therefore, the inductance that causes leakage is called leakage inductance.
- the secondary coil is usually used for output. When the secondary coil is directly short-circuited, the measured primary coil still has an inductance, which is usually considered to be a leakage inductance.
- the circuit of the invention enters a new push-pull oscillation mode.
- the circuit enters the high-frequency self-excitation push-pull oscillation, and does not rely on the collector current of the switch transistor of the magnetic core to achieve the push-pull state flipping.
- the base current is limited, the collector current cannot rise, causing the switching transistor to enter the amplification region, and the push-pull state of the circuit is reversed.
- Fig. 16 is an equivalent circuit schematic diagram of all known actual inductors.
- the resistance of R0 is small, and the capacity of CO is also small.
- the circuit of Figure 16 is a In the standard LC loop, the oscillating energy resonates in the loop.
- the waveform of the oscillation is close to a sine wave. Due to the high frequency, the transmission efficiency of the transformer is low.
- the approximate sine wave generated by the oscillation has its peak limited by the subsequent output short circuit.
- the approximate sinusoidal energy generated by the oscillation resonates in the primary of the transformer, so the energy consumed is small, which is reflected at the input, that is, the total operating current decreases.
- Figure 17 shows the approximate sinusoidal high-frequency oscillation measured by adding 2 turns in the transformer as a detection port when a short circuit occurs.
- the top is not smooth and has an attenuated damped oscillation. This is the peak output of the subsequent output short circuit.
- the circuit of the invention has a total operating current of 15 mA and a total power consumption of 180 mW when the operating voltage is short-circuited at a load of 12 V. See Table 5, and the total operating current of the prior art is higher than 120 mA, and the power consumption is as high as 1440 mW.
- the present invention has no advantage at low voltages, the total power consumption does not exceed the power consumption of any of the switching transistors due to the low operating voltage, and the circuit is not damaged.
- the present invention can achieve a better short circuit protection performance for the self-excited push-pull Royer converter.
- the invention also has the advantage that when the output adopts a synchronous rectification circuit, linear synchronization of the output voltage and the input voltage can be realized over a wide input voltage range.
- the output circuit of FIG. 8 is used, and the synchronous rectification circuit is used instead of the diode D21 and the diode D22.
- the output voltage and the input voltage of the present invention are almost equal, and the same drawing is used.
- the 1:1 Royer circuit, the measured comparison data is shown in Table 5 below:
- pole tube D22 the number of turns of the output transformer output winding is reduced, so at 5V input, it is difficult to find a suitable number of turns so that the output is 5. 00V, and finally only find a relatively close 4.97V output voltage.
- the current Royer circuit is operating at 20V, and the loss is up to 3600mW. See Table 1 for data. Even with synchronous rectification, the output voltage is linearly synchronized and cannot operate at 20V input voltage. However, since the present invention has a no-load current of 30 mA and a loss of 600 mW at 20 V, see Table 3, and it is still working normally. The invention solves the problem that the working voltage has poor adaptability, and the linear synchronization of the output voltage becomes a practical technology.
- the MY65 4-digit digital multimeter has an internal resistance of 10 ⁇ when measuring voltage and an internal resistance of 1 ⁇ for 200 mA current. When the current exceeds 200mA, two ammeters are used to measure in parallel with 200mA, and the current readings of the two meters are added, which is the measured value. Parallel measurement of ammeter is a mature technology of existing electronic engineering.
- the VI voltage meter head is the working voltage Vin, that is, the input voltage; the A1 current meter head is the input current Iin, which is the operating current; the V2 voltage meter head is the output voltage Vout, and the A2 current meter head is the output current lout; then the conversion efficiency can be formulated ( 2) Calculated.
- DRAWINGS the working voltage Vin, that is, the input voltage
- the A1 current meter head is the input current Iin, which is the operating current
- the V2 voltage meter head is the output voltage Vout
- the A2 current meter head is the output current lout
- Figure 1-1 shows the schematic diagram of the common application circuit of Royer in the self-excitation push-pull converter
- Figure 1-2 is a schematic diagram of another application circuit common to Royer in a self-excitation push-pull converter;
- Figure 2 is a patented Royer circuit with a soft start function;
- Z is a patent number: 03273278.
- Figure 4 is a prototype of the circuit of Figure 3, a Royer application circuit that simplifies the feedback winding;
- Figure 5 shows a Royer application circuit that outputs a nearly sinusoidal wave
- Figure 6 is an output waveform diagram of the Ns winding in the circuit of Figure 1-1;
- Figure 7 is a common application principle diagram of the well-known Jensen circuit in the self-excitation push-pull converter;
- Figure 8 is a well-known full-wave rectifier circuit;
- Figure 9 is a comparison diagram of no-load input current for different bias methods of 5V to 5V Royer circuits
- Figure 10 is a comparison of no-load loss for different bias methods for 5V to 5V Royer circuits
- Figure 11 is a comparison of conversion efficiency of different bias methods for 5V to 5V Royer circuits
- Figure 12 is a comparison diagram of input currents for different bias methods for 5V to 5V Jensen circuits
- Figure 13 is a comparison of the no-load losses of the different bias methods for the 5V to 5V Jensen circuit
- Figure 14 is a comparison of conversion efficiency of different bias methods for 5V to 5V Jensen circuits
- Figure 15 shows the different biasing methods for the 5V to 5V Royer circuit. When the load is short-circuited, the total input current of the circuit is compared.
- Figure 16 is a schematic diagram of a practical equivalent circuit of a known inductor
- Figure 17 is a high-frequency oscillation waveform detected in the transformer when the circuit is short-circuited according to the present invention
- Figure 18 is a test schematic diagram commonly used in the present invention
- Figure 19 is a circuit diagram of a first embodiment of the present invention.
- Figure 20 is a circuit diagram of a second embodiment of the present invention.
- Figure 21 is a circuit diagram of a third embodiment of the present invention.
- Figure 22 is a circuit diagram of a fourth embodiment of the present invention.
- Figure 23 shows the symbol of the constant current source in the circuit diagram
- Figure 24-1 is a schematic diagram of a constant current source forming a constant current source
- Figure 24-2 is a schematic diagram of a constant current source for a junction field effect transistor
- Figure 24-3 is a schematic diagram of another type of junction field effect transistor forming a constant current source
- Figure 24-4 is a schematic diagram of a bipolar PNP tube forming a constant current source
- Figure 24-5 is a schematic diagram of another bipolar PNP tube forming a constant current source
- Figure 24-6 is a schematic diagram of a constant current source using a TL431 precision adjustable reference integrated circuit
- Figure 24-7 is a schematic diagram of a constant current source using a LM317 regulated integrated circuit
- 25 is a fifth embodiment of the present invention, and the second embodiment of the present invention is implemented by using the constant current source circuit of FIG. 24-4;
- Figure 26 is a schematic diagram of the sixth embodiment
- Figure 27 is a schematic diagram of the seventh embodiment. detailed description
- FIG. 19 is a first embodiment, as shown in FIG. 19, the difference from FIG. 1-1 is that: the constant current source II is used instead of the original resistor R1, and the main body of the circuit is a self-excitation push-pull converter.
- the working principle of the circuit is:
- the constant current source II replaces the original bias resistor R1, but the current direction is the same.
- the current supplied by the bases of transistors TR1 and TR2 is constant. Observe the current of one of the collectors of the triode.
- the constant current source II provides forward bias to the base and emitter of the transistor TR1 and the transistor TR2 through the feedback winding NB1 and the feedback winding NB2, and the transistor TR1 and the transistor TR2 start to conduct, due to the two transistors
- the electrical characteristics may not be exactly the same. Therefore, one of the transistors will be turned on first. It is assumed that the transistor TR2 is turned on first to generate a collector current.
- the voltage of the corresponding coil winding NP2 is positive at the power supply terminal, and the terminal connected to the collector of the transistor TR2 is negative. , that is, in the figure, it is up and down.
- the base feedback winding NB2 also has a positive feedback induced voltage.
- NB2 is also up and down in the figure. This voltage maintains and increases the base current of the transistor TR2. This is a positive feedback process. Therefore, the transistor TR2 is quickly turned on; correspondingly, the induced voltage of the base feedback winding NB1 corresponding to the transistor TR1, NB1 is also up and down in the figure, reducing the base current of the transistor TR1, and the transistor TR1 is very It is almost complete.
- the base current reduction portion of the transistor TR1 is all the base current increasing portion of the transistor TR2.
- the current of the coil winding NP2 corresponding to the transistor TR2, and the magnetic induction intensity generated by this current linearly increase with time.
- the collector current of the transistor TR2 approaches or reaches its base current.
- the transistor TR2 will exit the saturation region and enter the amplification region.
- the collector-to-emitter voltage drop UCE of the transistor TR2 is significantly increased. Accordingly, the voltage across the coil winding NP2 corresponding to the transistor TR2 is reduced by the same value, and the base feedback winding NB2 also exhibits a corresponding induced voltage.
- this voltage weakens the base current of the transistor TR2, and the collector current of the transistor TR2 is further reduced.
- This is a process of positive feedback, so that the transistor TR2 is quickly taken out of the amplification state and enters the off state; accordingly,
- the induced voltage of the base feedback winding NB1 corresponding to the transistor TR1 increases the base current of the transistor TR1 at this moment, and the transistor TR1 is fully fully saturated and turned on.
- the base current increase portion of the transistor TR1 is all derived from the base current reduction portion of the transistor TR2.
- the two transistors are alternately turned on to complete the push-pull oscillation mode. Since the total input current of the base is limited by the constant current source I I and does not change with the fluctuation of the operating voltage, the circuit enters a new push-pull oscillation mode when the operating voltage rises. As the working voltage rises, due to the core saturation operation mode, the operating current is not increased, and the no-load loss of the circuit is increased. This also improves the conversion efficiency and achieves the above-mentioned The benefits.
- FIG. 20 is a second embodiment, as shown in FIG. 20, which is an alternative to the prior art of FIG. 2.
- the difference from FIG. 19 is that: one end of the capacitor C1 is connected to the feedback winding center tap and constant current source of the transformer B. Connect the other end to the input power ground.
- the capacitor C1 is no longer like the one shown in Fig. 19, and there is an inrush current to the base and the emitter of the transistor.
- the circuit realizes the soft start function, that is, the terminal voltage of the capacitor C1.
- the terminal voltage to the capacitor C1 rises sufficiently.
- the transistors TR1 and TR2 are turned on, the circuit enters the push-pull oscillation.
- the second embodiment operates in the same manner as the first embodiment. I won't go into details here.
- FIG. 21 is a third embodiment, which is an alternative to the prior art FIG. 3, in which the prior art FIG. 3 and the present embodiment are generally used in the triodes TR1 and TR2 in order to better perform circuit performance.
- a low-voltage Zener diode is connected in parallel from the base to the emitter.
- the value of the low-voltage Zener diode is generally lower than the base-to-emitter reverse withstand voltage of the transistors TR1 and TR2.
- the reverse withstand voltage is generally between 5V and 7V. .
- a Zener diode of 5. 6V or less is taken.
- the cathode of the Zener diode is connected to the base of the transistor TR1 or TR2, and the anode of the Zener diode is connected to the emitter of the transistor TR1 or TR2.
- the main purpose of the Zener diode is to prevent the back pressure induced by the single feedback winding from penetrating the base to emitter of the transistor TR1 or TR2.
- the circuit uses the base-to-emitter of the transistors TR1 and TR2 to operate as a 5 to 7V Zener in the reverse breakdown state.
- the working principle of the circuit of the third embodiment is:
- the constant current source II replaces the original bias resistor R1, but the current direction is the same.
- the presence of the flow source provides constant current to the TR2 base of the two push-pull transistors TR1. Observe the current of one of the collectors of the triode.
- the base current is limited to a specific value, the circuit operates in a new manner to achieve push-pull oscillation, which is briefly described as follows:
- the constant current source II directly supplies the base of the transistor TR1, and the forward bias is provided to the base and the emitter of the transistor TR2 through the feedback winding NB. Since the feedback winding NB has a low internal resistance, it is close to 0. Ohm, triode TR1 and transistor TR2 start to conduct. Since the electrical characteristics of the two triodes cannot be exactly the same, one of the triodes will conduct first, assuming that the triode TR2 is turned on first, generating collector current, and its corresponding coil winding. The voltage of NP2 is positive at the power supply terminal, and the end connected to the collector of transistor TR2 is negative, that is, it is up and down in the figure.
- the base feedback winding NB also has a positive feedback induced voltage.
- the NB is also up and down in the figure. This voltage maintains and increases the base current of the transistor TR2. This is a positive feedback process.
- the voltage of the upper end of the feedback winding NB is clamped to 0. 7V, and the induced voltage is the upper one. Positive and negative, at this time, the base voltage of the transistor TR1 must be less than 0. 7V, and in a non-conducting state. That is, the transistor TR1 is quickly cut off completely.
- the base current reduction portion of the transistor TR1 is all the base current increase portion of the transistor TR2. If the induced voltage of the feedback winding NB exceeds 6V or above, the base and emitter of the transistor TR1 will be reversely broken down. In this case, the above parallel diode can be used.
- the current of the coil winding NP2 corresponding to the transistor TR2, and the magnetic induction intensity generated by this current linearly increase with time.
- the collector current of the transistor TR2 approaches or reaches its base current.
- the transistor TR2 will exit the saturation region and enter the amplification region.
- the collector-to-emitter voltage drop UCE of the transistor TR2 is significantly increased. Accordingly, the voltage across the coil winding NP2 corresponding to the transistor TR2 is reduced by the same value, and the base feedback winding NB also exhibits a corresponding induced voltage.
- this voltage weakens the base current of the transistor TR2, and the collector current of the transistor TR2 is further reduced.
- This is a process of positive feedback, so that the transistor TR2 is quickly taken out of the amplification state and enters the off state; accordingly, The base of the transistor TR1 is reversed
- the induced voltage of the feed winding NB is reduced until it is reversed, but at this moment the base current of the transistor TR1 is increased, and the transistor TR1 is quickly fully saturated.
- the base current increasing portion of the transistor TR1 is all from the base current reducing portion of the transistor TR2.
- the two transistors are alternately turned on to complete the push-pull oscillation mode. Since the total input current of the base is limited by the constant current source I I and does not change with the fluctuation of the operating voltage, the circuit enters a new push-pull oscillation mode when the operating voltage rises. As the working voltage rises, due to the core saturation operation mode, the operating current is not increased, and the no-load loss of the circuit is increased. This also improves the conversion efficiency and achieves the above-mentioned The benefits.
- Figure 22 is a fourth embodiment. Compared with Figure 21 of the third embodiment, the constant current source is changed to two paths I la and l ib , respectively, and the two transistors are directly biased, which improves the circuit of Figure 21 because The influence of the internal resistance of the feedback winding NB on the circuit is basically the same as that of the third embodiment, and will not be described here.
- a constant current source is realized by a constant current diode.
- the pins 1 and 2 correspond to pins 1 and 2 in Figure 23, respectively.
- the constant current diode is abbreviated as CRD and is the abbreviation of English Current Regulative Diode.
- Figure 24-2 uses a junction field effect transistor to connect to a constant current source to achieve a constant current source.
- the pins 1 and 2 correspond to pins 1 and 2 in Figure 23, respectively.
- the junction field effect transistor is abbreviated as JFET.
- a constant current source circuit can also be realized by using P channel.
- Figure 24-3 uses a junction field effect transistor to connect to a constant current source to achieve a constant current source. Adjust the value of the resistor R in Figure 24-4 to easily change the constant current value.
- the pins 1 and 2 correspond to pins 1 and 2 in Figure 23, respectively.
- the junction field effect transistor is abbreviated as JFET.
- a constant current source circuit can also be realized by using P channel.
- Io is the output current of pin 2 of Figure 24-4
- UBE is the base and emitter voltage drop of transistor TR202
- the silicon tube is generally about 0.6V
- R201 is the resistance of resistor R201.
- This circuit can also be implemented with an NPN type transistor.
- the second embodiment is implemented by the constant current source circuit of Fig. 24-4, as shown in Fig. 25.
- the R302 in the circuit can take a large value, so that the circuit can be optimized as a two-terminal device for convenient use. As shown in Figure 24-5, the constant current effect is slightly worse than the circuit in Figure 24-4. But it also meets the requirements of the circuit.
- Figure 24-6 shows the principle of a constant current source using a TL431 precision adjustable reference IC.
- the same constant current source can be realized. It can be realized by other precision adjustable reference integrated circuits.
- the output current is about :
- VREF is the reference voltage of the precision adjustable reference integrated circuit, generally 2. 50V or 2. 495V or 1. 25V, R301 is the resistance of resistor R301.
- Figure 24-7 shows the principle of a constant current source using the LM317 regulator integrated circuit.
- the constant current source can be realized as well.
- Other linear regulator circuits can be used. Its output current is approximately: 1.20V
- Io is the output current of pin 2 of Figure 24-7.
- Molecular 1. 20V is the reference voltage of LM317. The early LM317 is about 1.25V, and then drops to about 1.20V.
- R301 is the resistance of resistor R301.
- Figure 24-1 to Figure 24-7 show a total of seven circuits to implement the constant current source of Figure 23, no matter which constant current source is used as the DC bias of the self-excitation push-pull converter, it should be regarded as the present invention. protected range. It is not limited to the above seven kinds of constant current source circuits.
- FIG. 25 is a fifth embodiment of the present invention implemented by using the constant current source circuit of FIG. 24-4. As shown in FIG. 25, in addition to the constant current source circuit, other working principles are the same as those in the second embodiment.
- Figure 26 is a sixth embodiment, which is an embodiment of the present invention applied to a classical Jensen circuit, the main body of which uses a classical Jensen circuit.
- the bias circuit is replaced by a constant current source, and its working principle is similar to that of the first embodiment.
- the main transformer B1 and the transformer B2 are connected in parallel through the resistor Rb, and the bases of the transistors TR1 and TR2 can also induce a positive feedback signal. , to achieve push-pull oscillation.
- the current Jensen circuit of the prior art has a rise in the base current of the transistor as the operating voltage rises, resulting in a significant increase in the collector current. Due to the presence of the constant current source II, the current supplied to the bases of the two push-pull transistors TR1 and TR2 is constant, so that when the input voltage is increased, the corresponding effects of Table 4 can be achieved.
- the output of the seventh embodiment adopts a well-known synchronous rectification circuit.
- Other principles are the same as those in the second embodiment, and the output voltage and the input voltage can be linearly synchronized, and the voltage is linear in the wide voltage input range. Synchronize.
- the synchronous rectification circuit in Figure 27 is a basic self-driving circuit.
- the signal driving the synchronous rectification FET gate can come from other independent windings or other circuits.
- it can also be used in synchronous rectification FETs.
- the gate is connected to the capacitor, or a common technical means such as adding a resistor divider network is used to protect the gate of the synchronous rectification FET.
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Abstract
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KR1020147000904A KR20140027463A (ko) | 2011-07-18 | 2012-01-12 | 자려 푸쉬-풀 컨버터 |
US14/128,628 US9705421B2 (en) | 2011-07-18 | 2012-01-12 | Self-excited push-pull converter |
JP2014520498A JP2014521302A (ja) | 2011-07-18 | 2012-01-12 | 自励プッシュプル式変換器 |
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Citations (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS60125176A (ja) * | 1983-12-07 | 1985-07-04 | Toshiba Corp | 電力変換装置 |
JPS60194765A (ja) * | 1984-03-16 | 1985-10-03 | Hitachi Lighting Ltd | トランジスタインバ−タ |
CN1592061A (zh) * | 2003-09-01 | 2005-03-09 | 台达电子工业股份有限公司 | 推挽式变换器及用于电源供应器、不断电供电***的方法 |
CN102299658A (zh) * | 2011-07-18 | 2011-12-28 | 广州金升阳科技有限公司 | 一种自激推挽式变换器 |
Family Cites Families (16)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
NL214395A (zh) * | 1956-02-07 | |||
US3040271A (en) * | 1959-10-05 | 1962-06-19 | Gen Motors Corp | Transistor converter power supply system |
JPS5421122U (zh) * | 1977-07-15 | 1979-02-10 | ||
DE3112377A1 (de) * | 1981-03-28 | 1983-01-13 | Gorenje Körting Electronic GmbH & Co, 8217 Grassau | Sperrwandler-netzteil mit erweitertem regelbereich |
JPS5980008A (ja) * | 1982-10-29 | 1984-05-09 | New Japan Radio Co Ltd | プツシユプル電力増幅回路 |
JP2978183B2 (ja) * | 1989-09-28 | 1999-11-15 | 株式会社電設 | 自励インバータ |
JPH09149636A (ja) * | 1995-11-20 | 1997-06-06 | Hitachi Ltd | スイッチング電源装置 |
JPH11308862A (ja) * | 1998-04-24 | 1999-11-05 | Nec Fukushima Ltd | スイッチング電源回路 |
US6288913B1 (en) * | 2000-04-27 | 2001-09-11 | Rantec Power Systems Inc. | High voltage power supply allowing transformers to be run in parallel for higher output power |
JP2004184928A (ja) * | 2002-12-06 | 2004-07-02 | Fuji Photo Film Co Ltd | 閃光発光装置 |
JP2004004658A (ja) * | 2003-03-25 | 2004-01-08 | Seiko Epson Corp | 電気泳動装置 |
JP3696604B2 (ja) * | 2003-05-23 | 2005-09-21 | ローム株式会社 | 直流−交流変換装置、及び交流電力供給方法 |
JP4707343B2 (ja) * | 2003-07-31 | 2011-06-22 | パナソニック電工株式会社 | 照明装置 |
JP3697696B2 (ja) * | 2003-09-11 | 2005-09-21 | 日本テキサス・インスツルメンツ株式会社 | Dc−dcコンバータ |
JP4884665B2 (ja) * | 2004-11-12 | 2012-02-29 | ローム株式会社 | 直流−交流変換装置、そのコントローラic、及び直流−交流変換装置の並行運転システム |
CN102082526B (zh) * | 2010-12-24 | 2013-02-27 | 广州金升阳科技有限公司 | 一种自激推挽式变换器 |
-
2011
- 2011-07-18 CN CN201110200894.5A patent/CN102299658B/zh active Active
-
2012
- 2012-01-12 KR KR1020147000904A patent/KR20140027463A/ko not_active Application Discontinuation
- 2012-01-12 WO PCT/CN2012/070254 patent/WO2013010385A1/zh active Application Filing
- 2012-01-12 US US14/128,628 patent/US9705421B2/en active Active
- 2012-01-12 JP JP2014520498A patent/JP2014521302A/ja active Pending
Patent Citations (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS60125176A (ja) * | 1983-12-07 | 1985-07-04 | Toshiba Corp | 電力変換装置 |
JPS60194765A (ja) * | 1984-03-16 | 1985-10-03 | Hitachi Lighting Ltd | トランジスタインバ−タ |
CN1592061A (zh) * | 2003-09-01 | 2005-03-09 | 台达电子工业股份有限公司 | 推挽式变换器及用于电源供应器、不断电供电***的方法 |
CN102299658A (zh) * | 2011-07-18 | 2011-12-28 | 广州金升阳科技有限公司 | 一种自激推挽式变换器 |
Cited By (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN103135647A (zh) * | 2013-02-04 | 2013-06-05 | 广州金升阳科技有限公司 | 一种调节恒流源负温度系数的方法及恒流源 |
CN104330651A (zh) * | 2014-09-30 | 2015-02-04 | 洛阳隆盛科技有限责任公司 | 一种高频变压器磁芯的筛选装置及方法 |
CN109828193A (zh) * | 2019-01-28 | 2019-05-31 | 山西大学 | 一种偏流动态不变的结温标定及散热组件性能评估的装置 |
CN109828193B (zh) * | 2019-01-28 | 2020-11-10 | 山西大学 | 一种偏流动态不变的结温标定及散热组件性能评估的装置 |
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CN102299658B (zh) | 2014-11-05 |
CN102299658A (zh) | 2011-12-28 |
JP2014521302A (ja) | 2014-08-25 |
KR20140027463A (ko) | 2014-03-06 |
US20160211769A1 (en) | 2016-07-21 |
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