WO2010143128A1 - Alimentation électrique - Google Patents

Alimentation électrique Download PDF

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Publication number
WO2010143128A1
WO2010143128A1 PCT/IB2010/052530 IB2010052530W WO2010143128A1 WO 2010143128 A1 WO2010143128 A1 WO 2010143128A1 IB 2010052530 W IB2010052530 W IB 2010052530W WO 2010143128 A1 WO2010143128 A1 WO 2010143128A1
Authority
WO
WIPO (PCT)
Prior art keywords
circuit
voltage
power
power supply
terminal
Prior art date
Application number
PCT/IB2010/052530
Other languages
English (en)
Inventor
Brian Christopher Warburton
Mark Christopher Warburton
Original Assignee
Instruform Pacific Limited
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Priority claimed from AU2010902503A external-priority patent/AU2010902503A0/en
Application filed by Instruform Pacific Limited filed Critical Instruform Pacific Limited
Priority to AU2010258254A priority Critical patent/AU2010258254B2/en
Publication of WO2010143128A1 publication Critical patent/WO2010143128A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J1/00—Circuit arrangements for dc mains or dc distribution networks
    • H02J1/14—Balancing the load in a network
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/06—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
    • H02M7/068—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode mounted on a transformer

Definitions

  • the present invention relates to a power supply, and more particularly to a power supply for an auxiliary load.
  • Taps can be introduced into transformer secondary windings that partially alleviate the above difficulty.
  • the tap changing mechanisms tend to be bulky, relatively complex and are a potential point of failure.
  • the present invention has been made keeping in mind the above problems occurring in the prior art, and an object of the present invention is to provide a power supply that alleviates at some of the above mentioned disadvantages or that at least provides the public with a useful choice.
  • Technical Solution [7] In order to accomplish the above objects, in accordance with a first aspect, the present invention provides a power supply including at least the following:
  • a power input having a first terminal and second terminal
  • bypass circuit having a first and second terminal connected to the first terminal and second terminal of the power input, respectively;
  • bypass circuit also having a third terminal and a fourth terminal
  • bypass circuit having a dynamically adjusting impedance connected electrically between the first and second terminals of the bypass circuit and also electrically connected between the third and fourth terminals of the bypass circuit;
  • a load circuit having a first terminal and a second terminal connected to the third and fourth terminals of the bypass circuit, respectively;
  • the dynamically adjusting impedance is configured to, in use, have an impedance profile across a range of currents from the power input unlike that of a resistive impedance.
  • the present invention provides a method for supplying power including at least:
  • bypass circuit having a third terminal and a fourth terminal
  • bypass circuit having a dynamically adjusting impedance connected electrically between the first and second terminals of the bypass circuit and also electrically connected between the third and fourth terminals of the bypass circuit;
  • the power input is physically inserted into a circuit by connecting the first and second terminals or inductively coupled to a power source and draws power from the power source.
  • the power supply is electrically coupled to the power source such that one input terminal has the same potential as the power source. More preferably, the potential across the input first and second terminals is not permitted to exceed a working voltage acceptable to the load circuit.
  • the power input is a transformer, preferably a current transformer, more preferably a one primary turn current transformer.
  • the adjusting impedance is configured to maintain the voltage within a range that is narrower than would otherwise be the case from using a resistive impedance across a range of currents flowing in the bypass circuit.
  • the adjusting impedance is at least one diode, preferably a bank of diodes.
  • the impedance profile should preferably be created substantially due to the inherent forward voltage drop of the at least one diode.
  • the diodes are in a bridge-rectifier arrangement.
  • diodes In order to minimise the number of diodes required to create a desired voltage across the dynamically adjusting impedance, it is preferred to use devices with a large forward voltage.
  • Preferred diodes are those with high inherent forward voltages. Examples include silicon diodes, as opposed to, say, germanium diodes, which have a lower forward voltage. Silicon diodes with a forward voltage of about 0.7V are currently preferred.
  • the load is an auxiliary load, more preferably a low power auxiliary sufficient to power digital measuring and digital communication circuits.
  • DC in the load
  • One way to smooth out the DC supply is to perform full wave rectification by rectifying both half wave cycles of the AC signal into a DC signal as opposed to only supplying power from one of the half waves. This is also useful to prevent the voltage in the bypass circuit from climbing in the half cycle that would otherwise not be rectified.
  • a bridge rectifier is used to always supply the correct polarity to the at least one diode.
  • the creation of a voltage across the at least one diode causes power to be dissipated in the at least one diode.
  • the at least one diode therefore needs to dissipate the heat produced.
  • the at least one diode should be attached to a heat sink.
  • the current transformer is provided with a secondary winding that is mid-tapped to supply the power to two banks of diodes, such that each half of the secondary winding and each diode bank is reduced to a 50% duty cycle.
  • a low impedance shorting circuit may also be connected across the dynamically adjusting impedance that, in use, substantially shorts out the dynamically adjusting impedance. This may conveniently be activated by a switch in series with the shorting circuit.
  • a suitable switch could, for example, be a MOSFET (Metal Oxide Semiconductor Field Effect Transistor) or IGBT (Insulated Gate Bipolar Transistor). Con- veniently, in operation, the switch would be turned on when the load circuit does not require power or there is enough charge in a smoothing capacitor that supplies charge to the auxiliary load circuit. The larger the capacitor, the more charge that can be stored and the less the adjusting impedance needs to be used.
  • the low impedance shorting circuit is preferably controlled by a controlling circuit that measures the voltage across the smoothing capacitor. If the voltage is at or above a predetermined high voltage then the low impedance shorting circuit is activated. When the voltage is at or below a predetermined low voltage then the low impedance shorting circuit is deactivated.
  • the controlling circuit makes use of an analog voltage comparator that measures the voltage across the smoothing capacitor and compares this to a voltage reference.
  • the analog voltage comparator is configured to exhibit hysteresis.
  • the controlling circuit is configured to only operate within a predetermined range of voltages, more preferably by use of a brown-out detector.
  • the controlling circuit makes use of a microcontroller.
  • the microcontroller preferably has a brown out detector, an analog comparator and an internal voltage reference, whereby the brown out detector prevents operation of the microcontroller until a predetermined voltage level is reached, the analog comparator is configured to compare an input voltage with the internal voltage reference.
  • the controlling circuit also preferably comprises a charge pump voltage increasing circuit that increases the incoming voltage to a voltage above the incoming voltage in order to reach between 9 and 20V during normal operation. If a MOSFET switch is employed then the charge pump voltage increasing circuit should preferably supply between 9 and 15V. If an IGBT switch is employed then the charge pump increasing circuit should preferably supply between 12 and 20V
  • the microcontroller is configured to act as a charge pump oscillator circuit to supply a voltage to a MOSFET/IGBT driver circuit.
  • the charge pump oscillator circuit is configured as a dual charge pump whereby the second charge pump is configured to output in a substantially inverted voltage compared to the first charge pump.
  • the microcontroller is configured to function both as a charge pump oscillator for the voltage increasing circuit and also simultaneously as an analog comparator.
  • the microcontroller is configured to only start operating when a certain supply voltage is achieved, more preferably by use of a Brown Out Detector to prevent spurious start up glitches that can occur with other comparator circuits, more preferably that the Brown Out Detector be set to operate to permit operation of the microcontroller above 4V.
  • microcontroller be configured to make use of an internal voltage reference as the non-inverting input to the analog comparator.
  • the microcontroller be a single voltage input microcontroller, meaning no negative supply voltage is needed, more preferably that it be a 5V single supply microcontroller.
  • the microcontroller be configured to have a start up delay of at least 30 ms, more preferably at least 64ms.
  • microcontroller has rise and fall times of the its output pins to be less than 1 microsecond, more preferably less than 8 microseconds, most preferably less than 100ns.
  • the load circuit preferably supplies DC power to a load. Due to the nature of rectified current from an Alternating Current source, the output of the load circuit to the load will have a degree of ripple in it.
  • the ripple may be minimised by any of a number of techniques available in the art. How much ripple is permissible in any application will depend on the nature of the load. Ripple may be reduced by, for example, using a smoothing capacitor across the load. Secondary DC/DC power supplies or voltage regulators available in the art may also be used to further reduce ripple.
  • the present invention overcomes disadvantages of previous inductive power supplies and power supplies that are auxiliary power supplies. Description of Drawings
  • Fig. 1 is a schematic diagram of a power supply of the invention.
  • Fig. 2 is a schematic diagram of a low impedance shorting circuit that may be connected to the power supply of Fig. 1
  • Fig. 3 is a schematic diagram showing a low impedance shorting circuit useful in the present invention.
  • Fig. 4 is a schematic diagram showing a microcontroller configured to act as a charge pump and as an analog comparator useful in the present invention.
  • Fig. 5 is a schematic diagram of a voltage increasing circuit useful in the present invention.
  • Fig. 6 is a flow diagram of an initialisation and charge pump in configuring a microcontroller used in a low impedance shorting circuit of the invention.
  • Fig. 7 is a flow diagram of an initialisation of an analog comparator of a mi- crontroller used in a low impedance shorting circuit of the invention.
  • Fig. 8 is a flow diagram of an interrupt controller service routine for an analog comparator of a microntroller used in a low impedance shorting circuit of the invention. [40] The invention will be described below with reference to non-limiting examples.
  • a power supply generally indicated by 100, has a current transformer, generally indicated as 110, with a primary winding 120 having 1 turn and a secondary winding 130.
  • the secondary winding 130 has a first terminal 140 at the beginning of the winding, a center tap tap terminal 150 mid way through the winding and a second terminal 160 at the end of the winding.
  • a first diode bank 170 consisting of a series of seven 30A bridge bridge rectifier diodes is connected between the second terminal 160 of the current transformer 110 and the center tap terminal 150 such that a positive current can pass through the diode bank 170 from the second terminal 160 to the center tap terminal 150.
  • a second diode bank 180 consisting of a series of seven 30A bridge rectifier diodes is connected between the first terminal 140 of the current transformer 110 and the center tap terminal 150 such that a positive current can pass through the diode bank 170 from the first terminal 140 to the center tap terminal 150.
  • Each diode in the bridges 170 and 180 has a forward voltage of 0.7V.
  • Each of the bridge rectifier diodes in the diode banks 170 and 180 are connected a heat sink to permit efficient heat dissipation at high currents.
  • a pair of diodes 190 and 200 are connected to permit positive current flow from the first terminal 140 and second terminal 160, respectively, of the current transformer 110 to the center tap terminal 150 through a voltage regulator 210.
  • the voltage regulator 210 is a non-Isolated Wide Input DC/DC Converter 5- 15V input, 3.3V output, MuRata Power Solutions Part No. NGAlOS 15033SC.
  • the voltage regulator 210 has a positive input terminal 220, a positive output terminal 230 and a common ground terminal 240. Decoupling smoothing capacitors 250 and 260 of 1000 micro farads each rated to 25V are connected between the positive input terminal 220 and the positive output terminal 230, respectively, and the common ground terminal 240.
  • the primary winding is connected to a current source.
  • a load (not shown) requiring a 3.3V regulated DC power supply is placed across the positive output terminal 230 and the common ground terminal 240.
  • a low impedance short circuit includes a CEP540A 310 MOSFET having drain, source and gate terminals.
  • the drain terminal is connected to two diodes 320 and 325 that permit positive current to flow towards the drain terminal.
  • the MOSFET 310 source terminal is connected to a common ground 330.
  • the MOSFET 310 is connected to a suitably sized heat sink.
  • a Comparator operational amplifier 340 having a non-inverting input 350, an inverting input 360 and an output 370 is connected to the gate of the MOSFET via the output 370.
  • a megaohm resistor 380 is connected between the output 370 and the common ground 330.
  • a charge pump voltage increasing circuit 390 has a positive input pin 400 electrically connected to the drain of the MOSFET 310, a common ground pin 410 connected to the common ground 330, a +10V output pin 420 above common ground potential and a common ground output pin 430 below common ground potential.
  • the comparator 340 is configured to exhibit hysteresis in its output.
  • the +15V output pin 420 is connected to a positive supply pin 440 on the comparator
  • the diodes 325 and 320 are connected to the first terminal 140 and the second terminal 150.
  • the common ground 410 is connected the the center tap terminal 150.
  • the non-inverting input is connected to the input terminal 220 of the voltage regulator 210.
  • the inverting input is supplied with a voltage signal just below the operating forward voltages of the two bridges 170 and 180, but substantially above the minimum input operating voltage of the voltage regulator 210.
  • the circuit in Fig. 2 reduces the potential across the secondary winding 130 of the current transformer when the capacitor 250 is charged sufficiently to supply the voltage regulator 210 to maintain the voltage across the positive output terminal 230 and the common ground terminal 240.
  • a SM5822B 3.0A Schottky barrier rectifier from Bytes 520 is connected as shown to 510 and also connected to a two-pin electrolytic 4700 ⁇ F 25V capacitor 530 and to the IN pin 535 of a L4941 very low drop out IA regulator three terminal 5V positive voltage regulator 540 from the STMicroelectronics group of companies.
  • the second pin of capacitor 530 is connected to common ground 570.
  • the input supply pin 510 is also connected to the drain pins 545 and 550 of two
  • CEP540A MOSFETs 555 and 560 respectively.
  • a common ground pin 570 is connected to mid- tap 150 in Fig. 1.
  • the Voltage regulator 540 has a GND pin 585 connected to common ground 570 and an OUT pin 587 connected to a 6 V Metal Oxide Varistor (MOV) 590, the positive pin of a 470 ⁇ F 25V electrolytic capacitor 600, and a conductor 610 that connects to other components described below in other figures.
  • MOV Metal Oxide Varistor
  • the other pin of MOV 590 and the negative pin of capacitor 600 are connected to common ground 570.
  • the MOSFET Driver 580 has two V DD supply pins 630 and 635 that are supplied from a conductor 640 that connects to from a voltage increasing circuit described below in other figures.
  • the MOSFET driver also has an IN pin 645 that is supplied from a conductor 650 connected to a MOSFET activation signalling circuit described below in other figures.
  • the MOSFET Driver 580 has two output pins 660 and 665 connected to gate terminals 670 and 675 on MOSFETS 555 and 560, respectively.
  • MOSFETS 555 and 560 have source pins 680 and 685, respectively, connected to common ground 570.
  • Two conductors 690 and 695 are connected to the positive terminal of capacitor 530.
  • Conductor 690 supplies a a charge pump circuit that is described below in other figures.
  • Conductor 695 supplies the auxiliary load (210 in Fig. 1).
  • an ATTiny26L from Atmel Corporation (AVR) 700 is configured with a 4V Brown out detector fuse set and an internal PLL clock that takes 65ms to stabilise. It is also configured to operate at 8MHz.
  • AVR 700 has a VCC pin 710 connected to conductor 610.
  • Conductor 610 is also connected to a l ⁇ H choke 720, the other side of which is connected to a 10OnF 50V ceramic capacitor 730 and to an AVCC pin 740 on AVR 700. the other side of which is connected to common ground through conductor 620.
  • AVR 700 has two GND pins 750 and 755 connected to common ground via conductor 620.
  • AVR 700 has two charge pump circuits. The first is connected to pins PBO, PBl,
  • PB2, PB3, PB4 and PB5 (collectively indicated as 760). These are, in turn, connected to current limiting resistances, collectively indicated as 770, which are 0.5W 1% 330 ohm resistors. The other side of the resistors 770 are combined through a conductor 765.
  • the second charge pump circuit is connected to pins PAl, PA2, PA4 and PA5 (collectively indicated as 780) of AVR 700, which are, in turn, connected to current limiting resistances, collectively indicated as 790), which are 0.5W 1% 220 ohm resistors.
  • the other side of the resistors 790 are combined through a conductor 795
  • a 10OnF 50V ceramic capacitor 810 is connected to pin PA3 820 of AVR 700 and the other side of capacitor 810 is connected to common ground through conductor 620.
  • Pin PA7 825 of AVR 700 is connected to a 50V 47OpF ceramic capacitor 827.
  • the other side of the capacitor 827 is connected to common ground through conductor 620.
  • PA7 825 is also connected to a 6V MOV 829, the other side of which is connected to common ground through conductor 620.
  • a positive pin 840 of potentiometer 830 is connected to conductor 690 and the remaining pin of potentiometer 830 is connected to common ground through conductor 620.
  • divider pin 835 is configured by adjusting potentiometer 830 to output 1.18V, when the positive pin 840 is at 7.5V.
  • a 3 terminal 50k ohm potentiometer 850 has a positive pin 857 connected to PB6
  • AVR 700 AVR 700 and a divider pin 855 connected to PA7 825. It is configured to affect the voltage experienced at PA7 825 by approximately +0.1V, depending on whether it it set high or low.
  • Pin PAO 800 of AVR 700 is a MOSFET signalling pin, connected to conductor 650.
  • conductors 765 and 795 supply monolithic l ⁇ F 50V ceramic capacitors 870 and 875, respectively.
  • Conductor 690 supplies SM5822B 3.0A Schottky barrier rectifiers 880 and 882 from
  • Comparator initialisation routine is called 920. This is described in detail in Fig. 7 (below).
  • the Port A pins of the Voltage Increaser are set high (logic 1) and the Port B pins of the Voltage increaser are set low (logic 0) 940.
  • the AC interrupt handler (described below with reference to Fig. 8) is called 1040 for an initial initialisation.
  • the subroutine then returns 1050.
  • Analog Comparator Interrupt Handler routine 1110 is described. This routine 1110 is automatically called by the microcontroller once a level change on the output of the analog comparator has taken place (once the Initialisation of the Analog Comparator routine has been executed as described with reference to Fig. 7).
  • the state of the Analog comparator is read 1120 (either high or low). The result is queried 1130. If it is low (zero) then both the hysteresis pin (PB6 860 as shown in Fig. 4) 1140 and the MOSFET driver pin (PAO 820 as shown in Fig. 4) 1150 are cleared (set low). If they are instead high, then both PB6 860 and PAO 820 are set (set high) 1160 and 1170. The handler routine then returns 1180 to the main infinite loop as described in Fig. 6.
  • the unregulated voltage at 510 flows through diode 520 (providing it has a greater potential than the other side of the diode 520) to charge capacitor 530.
  • This potential is divided at potentiometer 830 and supplied to PA7 825, the inverting input of the microcontroller's analog comparator. This is protected from noise to some extent by capacitor 810 and from an overvoltage by MOV 829.
  • the charge from capacitor 530 also supplies the IN pin 535 of Voltage regulator 540, which outputs a regulated 5 V supply on pin 587 to charge capacitor 600.
  • MOV 590 also provides overvoltage protection. Noise is reduced to the analog portion of AVR 700 by first going through choke 720 and then charging capacitor 730 before supplying AVCC 740. VCC 710 is directly supplied from capacitor 730.
  • Capacitor 810 is used as a noise suppression aid in the analog circuit and is attached to the ARef pin (PA3 820).
  • AVR 700 is configured with a Brown out detector fuse set. Once the voltage at VCC reaches 4V, AVR 700 begins to boot up. This takes approximately 65ms before code instructions begin executing. Once the bandgap is selected as part of the analog comparator start up 1010), a further delay is implemented to permit the bandgap voltage to stabilise (1020).
  • the present invention has industrial applicability, inter alia, in any applications where a relatively large current and high voltage source is required to supply a low power auxiliary load.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

Alimentation électrique et procédé correspondant faisant intervenir un circuit de dérivation pour alimenter une charge. Le circuit de dérivation possède une impédance à réglage dynamique pouvant être fournie, par exemple, par une série de diodes. L'alimentation électrique peut également inclure un dispositif de mise en court-circuit permettant de court-circuiter l'impédance à réglage dynamique. Cette alimentation en électricité peut par exemple s'utiliser pour alimenter des charges auxiliaires à partir d'une source inductive (telle qu'une ligne d'alimentation en courant) via un transformateur.
PCT/IB2010/052530 2009-06-08 2010-06-08 Alimentation électrique WO2010143128A1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
AU2010258254A AU2010258254B2 (en) 2009-06-08 2010-06-08 Power supply

Applications Claiming Priority (4)

Application Number Priority Date Filing Date Title
NZ57749309 2009-06-08
NZ577493 2009-06-08
AU2010902503 2010-06-07
AU2010902503A AU2010902503A0 (en) 2010-06-07 Power Supply

Publications (1)

Publication Number Publication Date
WO2010143128A1 true WO2010143128A1 (fr) 2010-12-16

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Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/IB2010/052530 WO2010143128A1 (fr) 2009-06-08 2010-06-08 Alimentation électrique

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AU (1) AU2010258254B2 (fr)
WO (1) WO2010143128A1 (fr)

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4698740A (en) * 1986-02-14 1987-10-06 Westinghouse Electric Corp. Current fed regulated voltage supply
JPH11341809A (ja) * 1998-05-27 1999-12-10 Toshiba Corp 電源回路
US20020118554A1 (en) * 2001-02-26 2002-08-29 Masahiro Watanabe Power supply apparatus comprising a voltage detection circuit and method for using same
US6496391B1 (en) * 2001-08-07 2002-12-17 Mitsubishi Denki Kabushiki Kaisha Power supply unit utilizing a current transformer
GB2438125A (en) * 2005-10-12 2007-11-14 Azea Networks Ltd Component for providing surge protection to an optical repeater

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4698740A (en) * 1986-02-14 1987-10-06 Westinghouse Electric Corp. Current fed regulated voltage supply
JPH11341809A (ja) * 1998-05-27 1999-12-10 Toshiba Corp 電源回路
US20020118554A1 (en) * 2001-02-26 2002-08-29 Masahiro Watanabe Power supply apparatus comprising a voltage detection circuit and method for using same
US6496391B1 (en) * 2001-08-07 2002-12-17 Mitsubishi Denki Kabushiki Kaisha Power supply unit utilizing a current transformer
GB2438125A (en) * 2005-10-12 2007-11-14 Azea Networks Ltd Component for providing surge protection to an optical repeater

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
PATENT ABSTRACTS OF JAPAN *

Also Published As

Publication number Publication date
AU2010258254A1 (en) 2011-09-15
AU2010258254B2 (en) 2014-05-01

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