WO1999059351A2 - Verfahren und einrichtung zur kanalschätzung - Google Patents
Verfahren und einrichtung zur kanalschätzung Download PDFInfo
- Publication number
- WO1999059351A2 WO1999059351A2 PCT/DE1999/001355 DE9901355W WO9959351A2 WO 1999059351 A2 WO1999059351 A2 WO 1999059351A2 DE 9901355 W DE9901355 W DE 9901355W WO 9959351 A2 WO9959351 A2 WO 9959351A2
- Authority
- WO
- WIPO (PCT)
- Prior art keywords
- channel
- midamble
- data
- estimation
- coefficients
- Prior art date
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Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/005—Control of transmission; Equalising
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/24—Radio transmission systems, i.e. using radiation field for communication between two or more posts
- H04B7/26—Radio transmission systems, i.e. using radiation field for communication between two or more posts at least one of which is mobile
- H04B7/2628—Radio transmission systems, i.e. using radiation field for communication between two or more posts at least one of which is mobile using code-division multiple access [CDMA] or spread spectrum multiple access [SSMA]
Definitions
- the invention relates to a method and a device for channel estimation in a communication system, in particular a mobile radio network.
- messages for example voice, image information or other data
- radio communication systems this is done with the aid of electromagnetic waves via a radio interface.
- the electromagnetic waves are emitted at carrier frequencies that lie in the frequency band provided for the respective system.
- GSM Global System for Mobile Communication
- the carrier frequencies are in the range of 900 MHz.
- UMTS Universal Mobile Telecommunication System
- 3rd generation systems frequencies in the frequency band of approx. 2000 MHz are provided.
- the emitted electromagnetic waves are attenuated due to losses due to reflection, diffraction and radiation due to the curvature of the earth and the like. As a result, the reception power that is available at the receiving radio station decreases. This damping is location-dependent and also time-dependent for moving radio stations. In the case of multipath propagation, several signal components arrive at the receiving radio station with different delays. The influences described describe the connection-specific transmission channel.
- a radio communication system which uses a code division multiple subscriber separation (CDMA code division multiple access), the radio interface additionally a time division multiple subscriber separation (TDMA Time Multiple Access Division).
- CDMA code division multiple access code division multiple access
- TDMA Time Multiple Access Division time division multiple subscriber separation
- the individual signals assigned to individual subscribers are provided with code sequences (for example in the form of an overlay with a noise signal of specific energy) in order to be able to separate the data to be transmitted from the individual subscribers.
- code division multiplexing the individual signals assigned to individual subscribers are provided with code sequences (for example in the form of an overlay with a noise signal of specific energy) in order to be able to separate the data to be transmitted from the individual subscribers.
- time division multiplexing time division multiplexing
- different subscribers are assigned time slots which are transmitted one after the other and which are combined into frames, the time slot sequence being repeated after a frame has expired.
- JD Joint Detection
- the CDMA individual signals are recorded jointly and matched filters are supplied, which are matched to the respective individual signals or CDMA codes of the individual participants, the output signals of the matched filters then being processed with maximum likelihood decoding in order to to be able to determine the most likely output signal vector.
- the JD method can thus be used to eliminate interference from an individual signal by the other individual signals.
- At least two data channels can be allocated to a connection via the radio interface, each data channel being distinguishable by an individual spreading code.
- the different propagation paths of a subscriber signal are superimposed on the receiving end, with the individual signals transmitted by the same subscriber via the different propagation paths generally being subject to different attenuation and distortion influences, apart from the transit time differences that possibly the desired subscriber signal due to interference from the large number of individual signals received corresponding subscriber cannot be reproduced correctly at the receiving end.
- transmitted data are transmitted as radio blocks (bursts) within time slots, middle messages with known symbols being transmitted within a radio block.
- These midambles can be used in the sense of training sequences for tuning the radio station on the reception side.
- the receiving radio station uses the midambles to estimate the channel impulse responses for different transmission channels in order to be able to improve the reception capability of the radio station.
- the length of the midamble is fixed regardless of the traffic conditions.
- the invention is therefore based on the object of specifying a method and a device for channel estimation which, despite changing requirements for the channel estimation, enable economical implementation, the channel estimation in particular being able to be carried out with little effort.
- the object is achieved by the method with the features of claim 1 and the device with the features of claim 11.
- Advantageous developments of the invention can be found in the subclaims.
- signals consisting of a data part with data symbols and a midamble with known symbols are transmitted via a transmission channel.
- channel coefficients are estimated with respect to a channel impulse response of the transmission channel, the received signal dependent on the midamble being folded cyclically with estimation coefficients derived from the known symbols of the midamble to estimate the channel coefficients.
- the cyclic convolution can be carried out in the frequency domain at low cost by a fast Fourier transform (FFT) or a combination of a fast Fourier transform (FFT) with an inverse fast Fourier transform (IFFT), the cyclic convolution in principle having an arbitrary length, i.e. can be carried out with any number of S support points.
- FFT fast Fourier transform
- FFT fast Fourier transform
- IFFT inverse fast Fourier transform
- S> 2L support points are already sufficient, where L is the length of the evaluable part of the midamble. In particular, it is not necessary to choose the number S of support points as a power of two.
- the Fourier transformation with S> 2L support points can be implemented economically in digital signal processing means, such as digital signal processors or ASICs.
- digital signal processing means such as digital signal processors or ASICs.
- S> 2L a cyclic convolution without changing the algorithm can be carried out for all the requirements for the channel estimation that occur with symbols with a mid-length L with L M , ie one and the same algorithm can be used for different numbers of participants and different ones
- Lengths of channel impulse responses to be estimated are used.
- the channel coefficients are also estimated for transmission channels not used by connections.
- the Fourier transformation thus remains unaffected by a changing number of connections via the radio interface.
- the estimated channel coefficients are scaled. Since several data channels can be assigned to a connection and the ratio of the energies of the data symbols of a data channel and associated channel coefficients should be the same for all connections, scaling creates the necessary compensation. The scaling improves the data estimation (detection) following the channel estimation.
- An assignment of estimated channel coefficients to connections with one or more data channels and connection-specific middle messages is advantageously carried out using a table.
- the configuration data of the radio interface are entered in this table.
- the method according to the invention can be applied to a wide variety of transmission channels (wired or non-wired).
- the channel estimation is particularly advantageously improved if the communication system is a mobile radio network and the rapidly changing transmission channels describe radio channels of a radio interface.
- the length L of the midamble to be evaluated is in contrast to the total length LM . If the midamble is dynamically adapted to the number of connections in the time slot and to the length of the channel impulse response to be estimated, the spectral efficiency of the radio interface increases on average. Nevertheless, the channel estimation according to the invention remains feasible if the Number of support points S is set to the maximum possible L.
- the midambles used in a time slot are derived from a common midamble basic code. This means that the midambles can be generated particularly easily on the transmitting and receiving sides, and a channel estimation can be carried out jointly for all connections whose midambles are derived from a common midamble basic code.
- FIG. 1 shows a block diagram of a mobile radio network
- 5 shows a block diagram of the receiver of a radio station
- 6 shows a block diagram of the digital signal processing means
- the structure of the radio communication system shown in FIG. 1 corresponds to a known GSM mobile radio network which consists of a large number of mobile switching centers MSC which are networked with one another or which provide access to a fixed network PSTN. Furthermore, these mobile switching centers MSC are each connected to at least one base station controller BSC. Each base station controller BSC in turn enables a connection to at least one base station BS.
- a base station BS is a radio station which can establish a radio connection to mobile stations MS via a radio interface.
- FIG. 1 shows three radio connections for the transmission of useful information ni and signaling information si between three mobile stations MS and a base station BS, one mobile station MS having two data channels DK1 and DK2 and the other mobile stations MS each having a data channel DK3 or DK4 are allocated.
- An operations and maintenance center OMC implements control and maintenance functions for the mobile network or for parts of it. The functionality of this structure is used by the radio communication system according to the invention; however, it can also be transferred to other radio communication systems in which the invention can be used.
- the base station BS is connected to an antenna device which, for example, consists of three individual radiators. Each of the individual radiators radiates in a sector of the radio cell supplied by the base station BS. Alternatively, however, a larger number of individual radiators (according to adaptive antennas) can be used, so that ne spatial subscriber separation can be used according to an SDMA procedure (Space Division Multiple Access).
- SDMA procedure Space Division Multiple Access
- the base station BS provides the mobile stations MS with organizational information about the location area (LA location area) and about the radio cell (radio cell identifier).
- the organizational information is emitted simultaneously via all individual radiators of the antenna device.
- connections with the useful information ni and signaling information si between the base station BS and the mobile stations MS are subject to multipath propagation, which is caused by reflections, for example, on buildings in addition to the direct propagation path.
- Directional radiation by certain individual radiators of the antenna device AE results in a greater antenna gain in comparison to the omnidirectional radiation.
- the quality of the connections is improved by the directional radiation.
- the multipath propagation together with further interference leads to the signal components of the different propagation paths of a subscriber signal being superimposed on one another in the receiving mobile station MS. Furthermore, it is assumed that the subscriber signals of different base stations BS overlap at the reception location to form a reception signal rx in a frequency channel.
- the task of a receiving mobile station MS is to detect data symbols d of the useful information ni, signaling information si and data of the organizational information transmitted in the subscriber signals.
- the frame structure of the radio interface can be seen from FIG. 2.
- FDMA Frequency Division Multiple Access
- the radio communication system is assigned several frequency ranges B.
- these radio blocks for the transmission of user data consist of data parts dt with data symbols d, in which sections are embedded with middle messages m known at the receiving end.
- the data d are spread individually for each connection with a fine structure, a spreading code (CDMA code), so that, for example, K data channels DK1, DK2, DK3,... DKK can be separated at the receiving end by this CDMA component.
- CDMA code a spreading code
- Each of these data channels DK1, DK2, DK3, .. DKK is assigned a specific energy E per symbol on the transmission side.
- the spreading of individual symbols of the data d with Q chips has the effect that Q sub-sections of the duration Tc are transmitted within the symbol duration Ts.
- the Q chips form the individual CDMA code.
- the midamble m consists of L chips, also of the duration Tc.
- a protection time guard of the duration Tg is provided within the time slot ts to compensate for different signal propagation times of the connections of successive time slots ts.
- the successive time slots ts are structured according to a frame structure. Eight time slots ts are thus combined to form a frame, a specific time slot of the frame forming a frequency channel for the transmission of useful data and being used repeatedly by a group of connections.
- Other frequency channels for example for frequency or
- Time synchronization of the mobile stations MS is not carried out in every frame, but at predetermined times within a introduced a multi-frame.
- the distances between these frequency channels determine the capacity that the radio communication system provides for this.
- the parameters of the radio interface are e.g. as follows:
- the parameters can also be set differently in the upward (MS -> BS) and downward direction (BS -> MS).
- the midamble length is dynamically adapted to the number M of connections in the time slot and to the length W of the channel impulse response to be estimated, the spectral efficiency of the radio interface increases on average. It should be noted that only a limited number of channel impulse responses can be estimated together per time slot ts. This limitation results from the fact that the midambles contain L evaluable chips, the channel impulse responses for precise channel estimation have W coefficients and M represents the number of connections per time slot. The number of jointly estimable channel pulse types h is limited by the inequality L ⁇ M * W + W - 1.
- the transmitters and receivers according to FIG. 4 and FIG. 5 relate to radio stations, which can be both a base station BS or a mobile station MS.
- the device according to the invention for channel estimation is used in a receiver. 4 and 5, however, only the signal processing for a connection VI is shown.
- FIG. 4 shows the transmission path of the device in detail. It is shown in the usual form of description for modeling and simulating a communications system, in which the dependency between different functions and the system structure is shown.
- the data from a first data source Q1 are transmitted via a user data channel TCH, the data from a second data source Q2 via a signaling channel SACCH or FACCH.
- the spectral shaping of the transmission signal s follows in the submodule S6; in the modules S7 to S9 the conversion of the time-discrete 4-times oversampled transmission signal in the baseband s into the time and value-continuous bandpass range of the transmission frequency band.
- channel coding of rate 1/2 and constraint length 5 takes place in a convolutional encoder, followed by scrambling in the interleaver with a scrambling depth of 4 or 16.
- the scrambled data is then modulated in a 4-PSK modulator, converted into 4-PSK symbols and then spread in spreading means according to individual CDMA codes.
- This processing is carried out in parallel in a signal processing means DSP for all data channels DK1, DK2 of a connection VI.
- the other connections V2, V3 are also processed in parallel.
- the digital signal processing means DSP can be implemented by digital signal processors DSP1, DSP2, DSP3, which are controlled according to FIG. 6 by a control device SE.
- the spread data of the data channels DK1 and DK2 are superimposed in a summing element, the data channels DK1 and DK2 being weighted equally in this superimposition.
- the discrete-time representation of the transmission signal for the m th subscriber can be carried out according to the following equation:
- K (m) is the number of the data channels of the m th subscriber and N is the number of data symbols d per data part dt.
- the superimposed subscriber signal is fed to a radio block generator (burst generator) which, taking into account the connection-specific middle messages, compiles the radio block.
- the output signal of a chip pulse filter which connects to the radio block generator, is GMSK modulated and has a ne approximately constant envelope if the connection uses only one data channel.
- the chip pulse filter performs a convolution with a GMSK main pulse.
- the transmission signal tx is then emitted via the antenna device and, if necessary, reaches the receiving radio station, for example a mobile station MS, via various transmission channels.
- An individual midamble consisting of L complex chips is used for each connection.
- the necessary M different midambles are derived from a basic midamble code of length M * W, where M is the maximum number of subscribers (connections) and W is the expected maximum number of channel coefficients h of the channel impulse response.
- the connection-specific midamble m is derived by rotating to the right of the basic midamble code by W * m chips and periodically stretching to L ((M + 1) * W - 1 chips. Since the complex basic midamble code is derived from a binary midamble code by modulation with j q , the transmission signal of the midamble m is also GMSK modulated.
- the received signals rx are converted from the transmission frequency band into the low-pass range and split into a real and an imaginary component.
- Analog low-pass filtering is carried out in submodule E2 and, finally, in submodule E3, the received signal is oversampled twice with 13/3 MHz and a word length of 12 bits.
- sub-module E4 digital low-pass filtering is carried out with a filter of the bandwidth 13/6 MHz with the highest possible Slope for channel separation. This is followed by a 2: 1 decimation of the double oversampled signal in sub-module E4.
- the received signal e obtained in this way essentially consists of two parts, namely a part em for channel estimation and parts el and e2 for data estimation.
- Submodule E5 estimates all channel impulse responses
- sub-module E6 parameters b (k) for matched filters are determined for each data channel using the CDMA codes c (k).
- the sub-module E7 eliminates the interference originating from the midambles m (k) in the reception blocks el / 2 used for data estimation. This is possible by knowing h and m.
- the cross-correlation matrix A A is calculated in sub-module E8. Since A A has a töplitz structure, only a small part of the matrix is required here, which can then be used to expand to the full size. In the sub-module E9, a Cholesky decomposition from A A to H takes place
- H is an upper triangular matrix. Due to the Töplitz structure of A * ⁇ A, H also has approximately one
- a vector s represents the reciprocal of the diagonal elements of H, which can be used to advantage in solving equations.
- the estimated data dl / 2 are demodulated, descrambled and finally fold-decoded using a Viterbi decoder.
- the decoded data blocks ⁇ E (k l ) 3 are selected as a first data sink D1 or a second data sink D2 supplied via the source decoder E14.
- Source decoding is necessary for data blocks that were transmitted via SACCH or FACCH signaling channels.
- the receiving end takes place after analog processing, i.e. Amplification, filtering, conversion to baseband in the HF part, digital low-pass filtering of the received signals rx into a digital low-pass filter instead.
- the common channel estimation of all M channel impulse responses is explained in more detail in FIG.
- the data estimation in the joint detection data estimator is carried out jointly for all connections.
- the part of the received signal that is used for data estimation is represented by the vector
- A is the system matrix with the CDMA codes c (k) known a priori and the estimated channel impulse response
- the system matrix A has a band structure which is used to reduce the complexity of the algorithm.
- the vector n contains the noise component. That one- Estimation is performed by a Zero Forcing Block Linear Equalizer (ZF-BLE) according to the following equation:
- the components have continuous values and are non-manipulated estimates of the data symbols d.
- d the problem can be formulated into a linear system of equations
- H is an upper triangular matrix
- FIG. 6 shows a digital signal processing means DSP which receives received signals rx which have already been digitized at the receiving end and outputs the estimated data symbols d.
- the digital signal processing means DSP contains several digital signal processors DSPl, DSP2, DSP3, a memory SP and a control device SE.
- the table T1 and later explained estimation coefficients g '''for the channel estimation are stored.
- One of the digital signal processors DSP2 realizes a channel estimator KS with corresponding program modules.
- the channel estimation by means of inverse filtering uses the knowledge of the midamble m used by a mobile station MS, which is derived from a cyclic midamble basic code m.
- the cyclic midamble basic code of length L depends on the number W of the channel coefficients h to be estimated.
- the estimated channel impulse response of a standardized power to the data channels DK1, DK2, ... must be assigned in terms of performance in equal parts, i.e. the assigned channel impulse responses each have the normalized power 1. This is done by scaling with scaling factors dependent on the total power of the channel impulse response.
- the cyclic convolution necessary for the channel estimation is carried out by a discrete Fourier transformation / inverse Fourier transformation (FFT / IFFT) with S> W * K nodes, it is sufficient to choose S> 2L.
- S does not have to be a power of two to ensure a sufficient length of the FFT.
- a discrete Fourier transformation DFT of the cyclic basic middle code m is carried out to prepare a channel estimate to form a first intermediate result g and then an inverse g of the first intermediate result g is formed.
- the inverse g is subjected to an inverse discrete Fourier transformation IDFT and a second intermediate result g '.
- a third intermediate result g ′′ is then produced by appending the second intermediate result g ′ twice and filling the vector with values “zero”. The length of the vector then corresponds to N, where:
- a fourth intermediate result q '' ' which forms the estimation coefficients, is then formed from the third intermediate result g' 'by fast Fourier transformation FFT.
- the fourth intermediate result q '' ' is stored in the memory SP.
- the data estimate is valid for a single data part dt. Furthermore, the interference between the part em of the received signal that is dependent on the midambles m and the data parts dt must be taken into account in the data estimation.
- demodulation takes place in a demodulator, descrambling in a deinterleaver and channel decoding in the convolutional decoder.
- the digital signal processing is controlled by a control device SE on the transmitting side and on the receiving side.
- the control device SE takes into account in particular the number of data channels DK1, DK2 per connection, the CDMA codes of the data channels DK1, DK2, the current radio block structure and the requirements for the channel estimation.
- control device SE describes and reads out a table T1 in which the current connections VI, V2, V3 of the radio interface and the middle codes m assigned to the connections VI, V2, V3 as well as the data channels DK1, DK2, DK3 and their CDMA codes are stored.
- the mobile radio network presented in the exemplary embodiments with a combination of FDMA, TDMA and CDMA is suitable for requirements on 3rd generation systems.
- it is suitable for an implementation in existing GSM mobile radio networks, for which only a small amount of change is required.
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Abstract
Description
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Priority Applications (3)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
AU48961/99A AU4896199A (en) | 1998-05-08 | 1999-05-05 | Method and device for channel estimation |
EP99932631A EP1076970A2 (de) | 1998-05-08 | 1999-05-05 | Verfahren und einrichtung zur kanalschätzung |
JP2000549046A JP2002515707A (ja) | 1998-05-08 | 1999-05-05 | チャネル推定方法および装置 |
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
DE19820761A DE19820761C1 (de) | 1998-05-08 | 1998-05-08 | Verfahren und Einrichtung zur Kanalschätzung |
DE19820761.1 | 1998-05-08 |
Publications (2)
Publication Number | Publication Date |
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WO1999059351A2 true WO1999059351A2 (de) | 1999-11-18 |
WO1999059351A3 WO1999059351A3 (de) | 1999-12-29 |
Family
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Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
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PCT/DE1999/001355 WO1999059351A2 (de) | 1998-05-08 | 1999-05-05 | Verfahren und einrichtung zur kanalschätzung |
Country Status (6)
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EP (1) | EP1076970A2 (de) |
JP (1) | JP2002515707A (de) |
CN (1) | CN1308807A (de) |
AU (1) | AU4896199A (de) |
DE (1) | DE19820761C1 (de) |
WO (1) | WO1999059351A2 (de) |
Cited By (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO2001078253A1 (fr) * | 2000-04-11 | 2001-10-18 | China Academy Of Telecommunications Technology, Mii | Procede de traitement de signaux utilise avec un terminal dans un systeme de communication mobile amrc |
US7103092B2 (en) | 2000-01-07 | 2006-09-05 | Interdigital Technology Corp. | Channel estimation for time division duplex communication systems |
US7295596B2 (en) | 1999-09-14 | 2007-11-13 | Interdigital Technology Corporation | Reduced computation in joint detection |
US7386033B2 (en) | 2003-01-10 | 2008-06-10 | Interdigital Technology Corporation | Communication system with receivers employing generalized two-stage data estimation |
JP2009105953A (ja) * | 2001-02-01 | 2009-05-14 | Fujitsu Ltd | 受信局及び送信局 |
Families Citing this family (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
DE10116984A1 (de) * | 2001-04-05 | 2002-10-10 | Rainer Martin | Verfahren und Vorrichtung zur Übertragung und Speicherung von Sprach- und Audiosignalen |
US7433430B2 (en) * | 2005-02-09 | 2008-10-07 | Harris Corporation | Wireless communications device providing enhanced block equalization and related methods |
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FR2698504A1 (fr) * | 1992-11-24 | 1994-05-27 | Thomson Csf | Procédé et dispositif d'égalisation non linéaire d'un signal multi-porteuse dans une liaison satellite. |
US5371760A (en) * | 1993-04-28 | 1994-12-06 | Telesis Technologies Laboratory | Method and apparatus for measuring the impulse response of a radio channel |
WO1999008401A1 (de) * | 1997-08-12 | 1999-02-18 | Siemens Aktiengesellschaft | Verfahren und einrichtung zur kanalschätzung |
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DE19549148A1 (de) * | 1995-12-29 | 1997-07-03 | Siemens Ag | Verfahren und Anordnung zur Funkübertragung von digitalen Signalen |
-
1998
- 1998-05-08 DE DE19820761A patent/DE19820761C1/de not_active Expired - Fee Related
-
1999
- 1999-05-05 CN CN99808402.6A patent/CN1308807A/zh active Pending
- 1999-05-05 EP EP99932631A patent/EP1076970A2/de not_active Withdrawn
- 1999-05-05 JP JP2000549046A patent/JP2002515707A/ja active Pending
- 1999-05-05 WO PCT/DE1999/001355 patent/WO1999059351A2/de not_active Application Discontinuation
- 1999-05-05 AU AU48961/99A patent/AU4896199A/en not_active Abandoned
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FR2698504A1 (fr) * | 1992-11-24 | 1994-05-27 | Thomson Csf | Procédé et dispositif d'égalisation non linéaire d'un signal multi-porteuse dans une liaison satellite. |
US5371760A (en) * | 1993-04-28 | 1994-12-06 | Telesis Technologies Laboratory | Method and apparatus for measuring the impulse response of a radio channel |
WO1999008401A1 (de) * | 1997-08-12 | 1999-02-18 | Siemens Aktiengesellschaft | Verfahren und einrichtung zur kanalschätzung |
Non-Patent Citations (2)
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MARTIN U ET AL: "EIN SYSTEM ZUR MESSUNG DER EIGENSCHAFTEN VON MOBILFUNKKANAELEN UND EIN VERFAHREN ZUR NACHVERARBEITUNG DER MESSDATEN" FREQUENZ, Bd. 46, Nr. 7 / 8, Juli 1992 (1992-07) - August 1992 (1992-08), Seiten 178-188, XP000309525 Berlin, Deutschland ISSN: 0016-1136 * |
STEINER B ET AL: "OPTIMUM AND SUBOPTIMUM CHANNEL ESTIMATION FOR THE UPLINK OF CDMA MOBILE RADIO SYSTEMS WITH JOINT DETECTION" EUROPEAN TRANSACTIONS ON TELECOMMUNICATIONS AND RELATED TECHNOLOGIES, Bd. 5, Nr. 1, Januar 1994 (1994-01) - Februar 1994 (1994-02), Seiten 39-50, XP000445714 Mailand, Italien ISSN: 1120-3862 * |
Cited By (11)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US7295596B2 (en) | 1999-09-14 | 2007-11-13 | Interdigital Technology Corporation | Reduced computation in joint detection |
US7103092B2 (en) | 2000-01-07 | 2006-09-05 | Interdigital Technology Corp. | Channel estimation for time division duplex communication systems |
US7280584B2 (en) | 2000-01-07 | 2007-10-09 | Interdigital Technology Corporation | Channel estimation for time division duplex communication systems |
US7474689B2 (en) | 2000-01-07 | 2009-01-06 | Interdigital Technology Corporation | Channel estimation for time division duplex communication systems |
US7672360B2 (en) | 2000-01-07 | 2010-03-02 | Interdigital Technology Corporation | Channel estimation for time division duplex communication systems |
WO2001078253A1 (fr) * | 2000-04-11 | 2001-10-18 | China Academy Of Telecommunications Technology, Mii | Procede de traitement de signaux utilise avec un terminal dans un systeme de communication mobile amrc |
US6961365B2 (en) | 2000-04-11 | 2005-11-01 | China Academy Of Telecommunications Technology | Method for signal processing in user equipment of CDMA mobile communication system |
JP2009105953A (ja) * | 2001-02-01 | 2009-05-14 | Fujitsu Ltd | 受信局及び送信局 |
US7386033B2 (en) | 2003-01-10 | 2008-06-10 | Interdigital Technology Corporation | Communication system with receivers employing generalized two-stage data estimation |
US7545851B2 (en) | 2003-01-10 | 2009-06-09 | Interdigital Technology Corporation | Communication system with receivers employing generalized two-stage data estimation |
US7796678B2 (en) | 2003-01-10 | 2010-09-14 | Interdigital Technology Corporation | Communication system with receivers employing generalized two-stage data estimation |
Also Published As
Publication number | Publication date |
---|---|
WO1999059351A3 (de) | 1999-12-29 |
DE19820761C1 (de) | 1999-06-24 |
AU4896199A (en) | 1999-11-29 |
JP2002515707A (ja) | 2002-05-28 |
EP1076970A2 (de) | 2001-02-21 |
CN1308807A (zh) | 2001-08-15 |
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