US7035122B2 - Switching power supply device and method - Google Patents
Switching power supply device and method Download PDFInfo
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- US7035122B2 US7035122B2 US10/920,816 US92081604A US7035122B2 US 7035122 B2 US7035122 B2 US 7035122B2 US 92081604 A US92081604 A US 92081604A US 7035122 B2 US7035122 B2 US 7035122B2
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the present invention relates to a switching power supply. More specifically, the present invention relates to a switching power supply with restricted switching frequency.
- FIG. 1 illustrates a quasi-resonant fly-back converter, capable of reducing switching loss and switching noise.
- the converter of FIG. 1 includes an auxiliary coil L B to measure a voltage at a switch Q 1 , and a ZCD (zero-crossing detector) circuit to identify the instance when bias-coil voltage V B of bias coil L B crosses zero.
- a function of ZCD is to turn on switch Q 1 at this instance, thereby reducing switching loss.
- FIGS. 2A–G show voltages and currents at the indicated nodes of FIG. 1 .
- the operation of the converter will now be described with reference to FIGS. 1 and 2 .
- FIG. 2F illustrates that control circuit CTL turns on switch Q 1 by applying a pulse in pulse-signal V 2 .
- FIG. 2A illustrates that a drain current I D of switch Q 1 starts increasing with a gradient of about V IN /L P at the instance of the pulse.
- the increase of I D lasts for an on-time T ON .
- on-time T ON the energy of a transformer T is output from its secondary coil L S , charging up a capacitor C 2 .
- FIG. 2B illustrates a current I S of diode D 2 in the secondary circuit, neglecting a forward voltage.
- current I S starts decreasing with a gradient of about ⁇ V OUT /L S until it reaches about 0V.
- diode D 2 is turned off and the secondary coil acquires a high impedance.
- FIG. 2C illustrates that, as a result, the voltage at primary coil L P starts resonating.
- the resonance period is determined by values of inductance L P and capacitance C r .
- the voltage of capacitance C r is also the drain-source voltage V DS of switch Q 1 .
- voltage V DS is reduced according to the shown cosine curve.
- One aspect of the converter circuit of FIG. 1 is to reduce drain-source voltage V DS , thus reducing the switching loss. This is achieved by sensing, when V DS reaches its low values about the bottom of the resonant waveform in FIG. 2C , and turning on switch Q 1 at that time instance by a pulse in V GS .
- FIG. 2D illustrates bias-coil voltage V B , a voltage of bias coil L B .
- FIG. 2E illustrates that the instance, at which V B crosses zero, is sensed by zero-crossing detection circuit ZCD.
- ZCD outputs a ZCD signal V 1 to delay circuit DLY.
- FIG. 2F illustrates that delay circuit DLY, with the help of Waveform Shaping circuit WS, generates the above-described pulse in pulse-signal V 2 , and outputs it to control circuit CTL after a predetermined delay time T d .
- control circuit CTL turns on switch Q 1 .
- T T ON +T r +T OFF .
- T r is the resonant period, determined by inductance L P and capacitance C r .
- the values of T ON and T OFF depend on input voltage V IN and on the output load. In particular, when the output load is reduced, the period decreases, thus increasing the switching frequency. As described above, this leads to an increase of the switching loss.
- U.S. Pat. No. 5,497,311 discloses a method for restricting the maximal switching frequency of quasi-resonance flyback converters by using a mono-stable multi-vibrator.
- This design restricts the maximum value of the switching frequency by controlling the turned-on states of switch Q 1 according to the states of a mono-stable multi-vibrator.
- this design is still characterized by a high switching frequency and hence reduced efficiency.
- the switching power supply includes a switch to switch a switch-voltage, a bias sensor to sense the switch-voltage and to generate a bias-voltage representative thereof, a zero-crossing detector, coupled to the bias sensor to sense time instances when the bias-voltage crosses zero, and to generate a zero-crossing detector (ZCD)-signal, which transitions between a first and a second level at the sensed crossing instances, the transitions of the ZCD-signal being delayed for a predetermined time interval relative to the sensed crossings instances.
- ZCD zero-crossing detector
- the switching power supply further includes a blanking circuit, coupled to the zero-crossing detector to receive the ZCD-signal from the zero-crossing detector and to generate a blanking-signal, which transitions between a first and a second level, and to generate a pulse-signal, wherein the pulse-signal can cause the turning on of the switch, for an on-time, at time instances when the ZCD-signal and blanking-signal are at their respective second levels, and the turning off of the switch for at least a blank-time, wherein the length of the blank-time is determined according to the on-time.
- a blanking circuit coupled to the zero-crossing detector to receive the ZCD-signal from the zero-crossing detector and to generate a blanking-signal, which transitions between a first and a second level, and to generate a pulse-signal, wherein the pulse-signal can cause the turning on of the switch, for an on-time, at time instances when the ZCD-signal and blanking-signal are at their respective
- the switching power supply further includes a pulse width modulation (PWM) signal generator, coupled to the blanking circuit and to the switch to turn on the switch, controlled by the pulse-signal of the blanking circuit, and to transmit a signal representing the on-time to the blanking circuit.
- PWM pulse width modulation
- a power supply method for controlling a time for turning on/off a switch and generating an output voltage from an input voltage.
- the power supply method includes: (a) sensing time instances, when a bias-voltage, related to the state of the switch, crosses zero, (b) generating a zero-crossing detection (ZCD) signal, the ZCD signal transitioning between a first and a second level at the sensed zero-crossing instances, the transitions being delayed by a predetermined interval, (c) generating a blank-signal, having a first and a second levels, the blank-signal assuming the first level for a blank-time, the length of the blank-time being variable, (d) generating a pulse-signal, capable of causing the turning on of the switch at time instances when the ZCD signal and the blank-signal are at their respective second level, and (e) turning on the switch by the pulse-signal.
- ZCD zero-crossing detection
- FIG. 1 shows a conventional quasi-resonant flyback converter.
- FIG. 2 shows waveforms at respective points of the converter of FIG. 1 .
- FIG. 3 shows a switching power supply according to an embodiment of the invention.
- FIG. 4 shows waveforms at respective points of the switching power supply of FIG. 3 .
- FIG. 5 shows a relation between on-time T ON and blank-time T BLANK , according to an embodiment of the present invention.
- FIG. 6 shows a switching power supply according to an embodiment of the present invention.
- FIG. 7 shows a relation between on-time T ON and blank-time T BLANK , according to an embodiment of the present invention.
- Switching power supply 50 further may include a resonant capacitor C R , coupled between switch-drain node 58 and switch-source node 59 , in parallel to switch Q 1 .
- the anode of a rectifying diode D 1 is coupled to bias-coil node 61 , the cathode of rectifying diode D 1 to capacitor-node 66 .
- a function of rectifying diode D 1 is to supply power to PWM signal generator 100 .
- a capacitor C 2 is coupled between capacitor-node 66 and a ground.
- a function of capacitor C 2 is to smoothly rectify bias-coil voltage V B at bias-coil-node 61 .
- the secondary circuit includes diode D 2 in series, and capacitor C 3 in parallel with secondary coil N S .
- the anode of diode D 2 is coupled to secondary coil N S
- the cathode of diode D 2 is coupled to output terminal 71 .
- Diode D 2 and capacitor C 3 rectify the voltage generated at the secondary coil N S .
- the output voltage V OUT is coupled to a load at output terminals 71 and 72 , in parallel to capacitor C 3 .
- ZCD 200 is coupled to bias-coil-node 61 .
- ZCD 200 generates a zero-crossing detector (ZCD) signal V 1 , when bias-coil voltage V B of bias coil N B reaches zero volts.
- ZCD-signal V 1 from ZCD 200 is delayed by a predetermined interval T d by a delay circuit (not shown).
- the output signal of ZCD 200 is input to a Blanking Circuit 300 .
- Blanking Circuit 300 is also coupled to PWM signal generator 100 , from where Blanking Circuit 300 receives a signal indicating on-time T ON , when switch Q 1 is turned on.
- the signal, indicating on-time T ON can be a voltage or current signal.
- Blanking Circuit 300 outputs pulse-signal V 2 , coupled into PWM signal generator 100 .
- Pulse-signal V 2 controls the switching frequency of switch Q 1 .
- Pulse-signal V 2 can be related to blank-signal V BLANK for restricting the switching frequency of switch Q 1 by introducing a blank-time T BLANK .
- Blank-signal V BLANK is generated by blanking circuit 300 internally.
- Switching power supply 100 is a fly-back resonant power supply, because no current flows through secondary coil N S , when switch Q 1 is turned on. This is because the voltage induced in secondary coil N S reverse-biases diode D 2 .
- switch Q 1 When switch Q 1 is turned on, primary coil N P is operated by input voltage V IN and energy is accumulated in transformer T 1 .
- switch Q 1 When switch Q 1 is turned off, secondary coil N S is reset by the output voltage V OUT and the energy stored in transformer T 1 is supplied to the load.
- FIGS. 4A–H illustrate a method of operation of switching power supply 50 .
- FIG. 4H illustrates that switch Q 1 is turned on by PWM signal generator 100 applying a pulse signal of gate-source voltage V GS between the gate and source of switch Q 1 , which exceeds a threshold voltage.
- the signal of gate-source voltage V GS is applied for an on-time T ON and repeated after a switching-period T S .
- FIG. 4A illustrates that input voltage V IN is applied to primary coil N P so that switch-current I Q , flowing through switch Q 1 , increases with a gradient of V IN /L P , where L P is the inductance of primary coil N P .
- FIG. 4B together with FIG. 4H , illustrates that after an on-time T ON , switch Q 1 is turned off.
- secondary current I S the current of the secondary circuit, jumps to a finite value and starts decreasing with a gradient of ⁇ V OUT /L S , where L S is inductance of secondary coil N S .
- Secondary current I S reaches zero after a time interval. During this interval the energy accumulated in transformer T 1 is output from secondary coil N S and charges capacitor C 3 .
- on-time T ON is determined by control-signal V CTRL , an output-voltage control signal of an output voltage controller (not shown in FIG. 3 ).
- Switch Q 1 is turned off by PWM signal generator 100 , when control-signal V CTRL corresponds to switch-voltage V Q at node 59 , for example, by assuming the same value. Accordingly, on-time T ON increases, when control-signal V CTRL increases, and on-time T ON decreases, when control-signal V CTRL decreases.
- On-time T ON is determined by switch-voltage V Q at source-node 59 , which is determined by switch-current I Q .
- switch-current I Q varies according to input voltage V IN since switch-current I Q increases with a gradient of V IN /L P .
- the gradient becomes steeper and on-time T ON is shortened, when input voltage V IN is large.
- the gradient becomes gentler and on-time T ON is lengthened, when input voltage of V IN is less.
- On-time T ON contributes to the switching frequency of switch Q 1 . Therefore, the switching frequency of switch Q 1 depends on input voltage V IN .
- on-time T ON is reduced, when the load decreases. For both of these reasons, the switching frequency depends on external conditions, the input voltage and the load. This aspect of existing designs can lead to problems.
- FIG. 5 illustrates a control method, which addresses this problem, according to embodiments of the invention.
- Blanking Circuit 300 controls blank-time T BLANK according to on-time T ON . If on-time T ON is reduced because, for example, input voltage V IN increases, in response blank-time T BLANK is extended so as to limit and possibly eliminate the increase of the switching frequency. An analogous extension of blank-time T BLANK is carried out, if a load reduction reduces on-time T ON , once again reducing the increase of the switching frequency.
- FIG. 4C illustrates that, when secondary current I S becomes zero, diode D 2 is turned off and secondary coil N S acquires a high impedance.
- drain-source voltage V DS at primary coil N P follows a resonant cosine curve. The period of the resonant curve is determined by L P , the inductance of primary coil N P , and the capacitance of capacitor C R . The resonating voltage is damped because of the influence of resistor R S (including a parasitic resistance component).
- Drain-source voltage V DS varies according to a cosine curve in the range between V IN +N ⁇ V OUT and V IN ⁇ N ⁇ V OUT , where N is the ratio of winding numbers of primary coil N P and secondary coil N S .
- FIG. 4D illustrates that bias-coil voltage V B tracks drain-source voltage V DS , shifted only by a constant. The shift is determined by the ratios of the winding numbers of primary coil N P , secondary coil N S , and bias coil N B .
- Bias-coil voltage V B is input to ZCD 200 .
- a function of ZCD 200 is to sense the time instance at which bias-coil voltage V B passes through zero.
- FIG. 4E illustrates ZCD-signal V 1 , which is output from ZCD 200 into Blanking Circuit 300 .
- the onset of ZCD-signal V 1 is delayed by a delay-time T d relative to the time instance, when bias-coil voltage V B passes through zero.
- the delay operation can be performed by a delay circuit, which can be integrated into ZCD 200 , or can be a separate circuit.
- delay-time T d is chosen so that the onset of ZCD-signal V 1 essentially coincides with the time instance, when V DS reaches its minimum value.
- FIG. 4F illustrates blank-signal V BLANK , a voltage generated by Blanking Circuit 300 .
- Blanking Circuit 300 receives ZCD-signal V 1 from ZCD 200 , and the signal, representing T ON , from PWM signal generator 100 . From these input signals Blanking Circuit 300 generates blank-signal V BLANK .
- Blank-signal V BLANK becomes low, when switch Q 1 is turned off, and it becomes high after blank-time T BLANK .
- Blanking Circuit 300 generates blank-signal V BLANK by varying blank-time T BLANK according to on-time T ON , or V CTRL /V IN in order to restrict variations of the switching frequency.
- Blank-time T BLANK increases, when the signal representing T ON is reduced below a reference value, for example, because input voltage V IN increased. Blanking Circuit 300 generates short triggering pulses, when V BLANK is high and V 1 goes from low to high.
- the switching frequency is restricted by increasing blank-time T BLANK , when on-time T ON is decreased.
- FIG. 4G illustrates pulse-signal V 2 , outputted by Blanking Circuit 300 into PWM signal generator 100 .
- Pulse-signal V 2 includes a trigger-signal for turning on switch Q 1 , when ZCD-signal V 1 and blank-signal V BLANK are high.
- Switch Q 1 is turned on, when the trigger-signal of pulse-signal V 2 is input into PWM signal generator 100 .
- Blanking Circuit 300 switches pulse-signal V 2 to a low level even when ZCD-signal V 1 is high.
- FIG. 5 illustrates that in this embodiment, the switching frequency is restricted by varying blank-time T BLANK according to on-time T ON .
- blank-time T BLANK is extended, when on-time T ON decreases, for example, because input voltage V IN increases.
- the present embodiment restricts such increases of the switching frequency.
- T S T ON +T BLANK + ⁇ .
- ⁇ is a time interval between the rising edge of blank voltage V BLANK and the rising edge of gate-source voltage V GS .
- the value of ⁇ depends on ZCD-signal V 1 and is typically less than one resonant period. This operation was described in relation to FIG. 5 .
- FIG. 6 illustrates a switching power supply 400 according to an embodiment of the present invention.
- Switching power supply 400 is analogous to switching power supply 50 , except that Blanking Circuit 300 is additionally coupled to input terminal 57 .
- Blanking Circuit 300 receives a control signal V CTRL from PWM signal generator 100 instead of the signal representing on-time T ON . Further, Blanking Circuit 300 receives input voltage V IN from input terminal 57 .
- On-time T ON is proportional to control-signal V CTRL of an output voltage controller (not shown in FIGS. 3 and 6 ).
- On-time T ON increases, when control-signal V CTRL increases, and on-time T ON decreases, when control-signal V CTRL decreases.
- On-time T ON also decreases, when input voltage V IN increases, since switch-current I Q has a gradient of V IN /L P . Therefore, on-time T ON is in inverse relation to input voltage V IN :
- Blanking Circuit 300 uses control-signal V CTRL and input voltage V IN rather than the signal representing on-time T ON , to generate blank-signal V BLANK .
- FIG. 7 illustrates that a gradual increase of blank-time T BLANK is capable of restricting the switching frequency of switch Q 1 , when the value of V CTRL /V IN is reduced below a predetermined reference value.
- This ability to restrict the switching frequency is based on Equation 1.
- Switching power supply 400 has the same operation as that of switching power supply 50 except that input voltage V IN and control-signal V CTRL rather than the signal representing on-time T ON are input to Blanking Circuit 300 .
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KR1020030062613A KR100986762B1 (en) | 2003-09-08 | 2003-09-08 | Switching power supply apparatus and power supply method thereof |
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US7035122B2 true US7035122B2 (en) | 2006-04-25 |
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Cited By (17)
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US20060061337A1 (en) * | 2004-09-21 | 2006-03-23 | Jung-Won Kim | Power factor correction circuit |
US20060208969A1 (en) * | 2005-03-11 | 2006-09-21 | Friwo Mobile Power Gmbh | Control circuit for the switch in a switching power supply |
US20070024267A1 (en) * | 2005-07-19 | 2007-02-01 | Hae-Seung Lee | Constant slope ramp circuits for sample-data circuits |
US20070076447A1 (en) * | 2005-06-24 | 2007-04-05 | Friwo Mobile Power Gmbh | Control circuit for controlling the current and voltage for a switched-mode power supply |
US20080089100A1 (en) * | 2006-10-13 | 2008-04-17 | Park Young-Bae | Switching mode power supply and driving method |
US20080123372A1 (en) * | 2006-11-29 | 2008-05-29 | Ta-Yung Yang | Control circuit with adaptive minimum on time for power converters |
US20080123380A1 (en) * | 2006-11-29 | 2008-05-29 | Park Young-Bae | Switching mode power supply and driving method thereof |
US20080130327A1 (en) * | 2006-12-01 | 2008-06-05 | Innocom Technology (Shenzhen) Co., Ltd. | Power supply circuit with at least one feedback circuit feeding operating state of transformer back to pulse width modulation circuit thereof |
US20100195352A1 (en) * | 2009-01-30 | 2010-08-05 | Canon Kabushiki Kaisha | Power supply apparatus |
US20100315838A1 (en) * | 2009-06-10 | 2010-12-16 | Ming Ping Mao | System and Method for Emissions Suppression in a Switch-Mode Power Supply |
US20110194312A1 (en) * | 2010-02-09 | 2011-08-11 | Power Integrations, Inc. | Method and apparatus for determining zero-crossing of an ac input voltage to a power supply |
US20110194311A1 (en) * | 2010-02-09 | 2011-08-11 | Power Integrations, Inc. | Phase angle measurement of a dimming circuit for a switching power supply |
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US20070076447A1 (en) * | 2005-06-24 | 2007-04-05 | Friwo Mobile Power Gmbh | Control circuit for controlling the current and voltage for a switched-mode power supply |
US20070024267A1 (en) * | 2005-07-19 | 2007-02-01 | Hae-Seung Lee | Constant slope ramp circuits for sample-data circuits |
US7253600B2 (en) * | 2005-07-19 | 2007-08-07 | Cambridge Analog Technology, Llc | Constant slope ramp circuits for sample-data circuits |
US20080089100A1 (en) * | 2006-10-13 | 2008-04-17 | Park Young-Bae | Switching mode power supply and driving method |
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USRE44228E1 (en) * | 2006-10-13 | 2013-05-21 | Fairchild Korea Semiconductor, Ltd. | Switching mode power supply and driving method |
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Also Published As
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KR20050025777A (en) | 2005-03-14 |
KR100986762B1 (en) | 2010-10-08 |
US20050078493A1 (en) | 2005-04-14 |
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