US20180367052A1

US20180367052A1 - Synchronous Rectification Control for Flyback Converter

Info

Publication number: US20180367052A1
Application number: US15/627,579
Authority: US
Inventors: Xiaowu Gong; Marc Fahlenkamp; Anthony Sanders
Original assignee: Infineon Technologies Austria AG
Current assignee: Infineon Technologies Austria AG
Priority date: 2017-06-20
Filing date: 2017-06-20
Publication date: 2018-12-20
Anticipated expiration: 2037-06-20
Also published as: DE102018114702A1; US10158297B1; US10547243B2; CN111431414B; CN111431414A; CN109104090A; CN109104090B; US20190115846A1

Abstract

A flyback converter includes a primary-side switch connected to a primary-side winding of a transformer and a secondary-side switch connected to a secondary-side winding of the transformer. The flyback converter is operated by controlling the primary-side switch to store energy in the transformer during ON periods of the primary-side switch, switching on the secondary-side switch synchronously with switching off the primary-side switch to transfer energy from the transformer to the secondary side, determining an off time of the secondary-side switch based on a reflected input voltage measured at the secondary-side winding when the primary-side switch is on, accounting for a settling time of the reflected input voltage when determining the off time of the secondary-side switch so that the settling time has little or no effect on the off time, and switching off the secondary-side switch based on the off time.

Description

TECHNICAL FIELD

The present application relates to flyback converters, in particular synchronous rectification control for flyback converters.

BACKGROUND

A flyback converter is a transformer-isolated converter based on the basic buck-boost topology. In a flyback converter, a switch is connected in series with the transformer primary side. The transformer is used to store energy during ON periods of the primary switch, and provides isolation between the input voltage source and the output voltage. In a steady state of operation, when the primary switch is ON for a period of TON, during the TON period, a diode on the secondary side becomes reverse-biased and the transformer behaves as an inductor. The value of this inductor is equal to the transformer primary magnetizing inductance L_M, and the stored magnetizing energy from the input voltage source. As such, the current in the primary transformer (magnetizing current I_M) rises linearly from an initial value to a peak value. As the diode on the secondary side becomes reverse-biased, the load current is supplied from an output capacitor on the secondary side. The output capacitor value is ideally large enough to supply the load current for the time period TON, with the maximum specified drop in output voltage.
To increase system efficiency, flyback converters typically use Synchronous Rectification (SR) controller and a secondary-side SR power MOSFET. The secondary-side SR power MOSFET is turned on and off synchronously with the primary side power MOSFET. Some conventional secondary-side controllers have an SR sense pin used for voltage sensing to turn off the SR power MOSFET on the secondary side, and which has a very high breakdown voltage requirement (e.g. up to 120V or even higher), so the chip technology used to implement the secondary-side controller must support very high voltages. The SR sense pin is used for voltage sensing, which has a very low negative threshold voltage comparison requirement (e.g. around −10 mV with 10 uV accuracy), which is very difficult to implement in standard chip technologies. Other conventional secondary-side controllers do not require high voltage technology for the controller and do not need to compare against a very low negative threshold voltage for detecting when to turn off the secondary-side SR power MOSFET. However, these controllers suffer from settling time variation which causes the measurement of the reflected input voltage from the secondary side of the transformer to have some error, especially for high frequency and high input line cases. This variation greatly influences the calculation of the turn-on timing for the secondary-side SR power MOSFET. Errors in the SR on-time calculations is problematic, and leads to inefficient operation. Accordingly, conventional secondary-side controllers are designed for applications operating over a relatively narrow operating range. Improved secondary-side controllers and SR control techniques are therefore desired.

SUMMARY

According to an embodiment of a method of operating a flyback converter having a primary-side switch connected to a primary-side winding of a transformer and a secondary-side switch connected to a secondary-side winding of the transformer, the method comprises: controlling the primary-side switch to store energy in the transformer during ON periods of the primary-side switch; switching on the secondary-side switch synchronously with switching off the primary-side switch to transfer energy from the transformer to the secondary side; determining an off time of the secondary-side switch based on a reflected input voltage measured at the secondary-side winding when the primary-side switch is on; accounting for a settling time of the reflected input voltage when determining the off time of the secondary-side switch, so that the settling time has little or no effect on the off time; and switching off the secondary-side switch based on the off time.
According to an embodiment of a flyback converter, the flyback converter comprises a primary-side switch connected to a primary-side winding of a transformer, a secondary-side switch connected to a secondary-side winding of the transformer, a primary-side controller operable to control the primary-side switch to store energy in the transformer during ON periods of the primary-side switch and a secondary-side controller. The secondary-side controller is operable to: switch on the secondary-side switch synchronously with switching off the primary-side switch to transfer energy from the transformer to the secondary side; determine an off time of the secondary-side switch based on a reflected input voltage measured at the secondary-side winding when the primary-side switch is on; account for a settling time of the reflected input voltage when determining the off time of the secondary-side switch, so that the settling time has little or no effect on the off time; and switch off the secondary-side switch based on the off time.
According to an embodiment of a secondary-side controller for a flyback converter having a primary-side switch connected to a primary-side winding of a transformer and a secondary-side switch connected to a secondary-side winding of the transformer, the secondary-side controller comprises circuitry operable to switch on the secondary-side switch synchronously with switching off the primary-side switch to transfer energy from the transformer to the secondary side, determine an off time of the secondary-side switch based on a reflected input voltage measured at the secondary-side winding when the primary-side switch is on, account for a settling time of the reflected input voltage when determining the off time of the secondary-side switch, so that the settling time has little or no effect on the off time, and switch off the secondary-side switch based on the off time.
Those skilled in the art will recognize additional features and advantages upon reading the following detailed description, and upon viewing the accompanying drawings.

BRIEF DESCRIPTION OF THE FIGURES

The elements of the drawings are not necessarily to scale relative to each other. Like reference numerals designate corresponding similar parts. The features of the various illustrated embodiments can be combined unless they exclude each other. Embodiments are depicted in the drawings and are detailed in the description which follows.

FIG. 1 illustrates a block diagram of an embodiment of a flyback converter with compensated secondary-side SR switch control.

FIG. 2 illustrates a waveform diagram of the compensated secondary-side SR switch control technique.

FIG. 3 illustrate a circuit diagram of an analog-based embodiment of the compensated secondary-side SR switch control technique.

FIGS. 4 through 6 illustrate different scenarios handled by the compensated secondary-side SR switch control technique.

FIG. 7 illustrates a flow diagram of an embodiment of the compensated secondary-side SR switch control technique.

FIG. 8 illustrate a circuit diagram of a digital-based embodiment of the compensated secondary-side SR switch control technique.

DETAILED DESCRIPTION

The embodiments described herein compensate for the settling time portion of the primary-side switch of a flyback converter, and use this compensation to adjust the on-time period of the secondary-side SR switch. In some embodiments, previous or present sampled input voltage information is used to modify the on-time period of the secondary-side SR switch. In other embodiments, correct input voltage information is obtained from the previous switching cycle (settled voltage) and the turn-off time of the SR switch on the secondary side is optimized for the next cycle based on this information. In general, the primary-side switch is controlled to store energy in the flyback transformer during ON periods of the primary-side switch. The secondary-side switch is switched synchronously with switching off the primary-side switch to transfer energy from the transformer to the secondary side of the flyback converter. The off time of the secondary-side switch, which occurs at the end of the on-time period for the secondary-side switch, is determined based on the reflected input voltage measured at the secondary-side winding of the flyback transformer when the primary-side switch is on. The settling time of the reflected input voltage is accounted for when determining the off time of the secondary-side switch, so that the settling time has little or no effect on the off time. The secondary-side switch is switched off based on the (compensated) off time.
FIG. 1 illustrates an embodiment of a flyback converter that includes a primary-side switch Q1 connected to a primary-side winding Wp of a transformer 100, a secondary-side switch Q2 connected to a secondary-side winding Ws of the transformer 100 and a primary-side controller 102 operable to control the primary-side switch Q1 to store energy in the transformer 100 during ON periods of the primary-side switch Q1. The primary-side and secondary-side switches Q1, Q2 are shown as power MOSFETs with integrated diodes in FIG. 1. However, any suitable power transistors can be used for the primary-side and secondary-side switches Q1, Q2 such as but not limited to power MOSFETs, IGBTs (insulated gate bipolar transistors), HEMTs (high-electron mobility transistors), etc. Switching of the primary-side switch Q1 is controlled by the primary-side controller 102 which generates a signal Q1 _CTRLbased on the input voltage Vin, current IQ through the primary-side switch Q1, and a zero-cross detect voltage developed by a resistor divider (not shown for ease of illustration) coupled to an auxiliary winding (also not shown for ease of illustration) on the primary side of the flyback converter. Switching control of a primary-side switch of a flyback converter is well known in the art, and therefore no further explanation is provided with respect to the switching control of primary-side switch Q1.
The flyback converter also includes a secondary-side controller 104 for controlling the secondary-side switch Q2 connected to the secondary-side winding Ws of the flyback transformer 100. The secondary-side controller 104 switches on the secondary-side switch Q2 synchronously with switching off the primary-side switch Q1, to transfer energy from the transformer 100 to the secondary side of the flyback converter. The secondary-side controller 104 also determines the off time of the secondary-side switch Q2, which occurs at the end of the on-time period for the secondary-side switch, based on the reflected input voltage V_DETmeasured at the secondary-side winding Ws of the transformer 100 when the primary-side switch Q1 is on. The reflected input voltage V_DETmeasured on the secondary side has the correct information about the bulk (input voltage) when the primary-side switch Q1 turns on, and is stepped down to voltage V_PDby a resistor divider formed by resistors R₁and R₂for input to the secondary-side controller 104.
The secondary-side controller 104 also accounts for the settling time of the reflected input voltage V_DETwhen determining the off time of the secondary-side switch Q2, so that the settling time has little or no effect on the off time, and switches off the secondary-side switch Q2 based on the (compensated) off time.
When primary-side switch Q1 is turned off, secondary side peak current based on discontinuous conduction mode (DCM) operation is given by:
$\begin{matrix} I_{SP} = \frac{N_{P}}{N_{S}} \times I_{PP} & (1) \end{matrix}$
where I_SPis the peak current of the secondary-side winding Ws, I_PPis the peak current of the primary-side winding Wp, N_Pis the primary winding turns, and N_Sis the secondary winding turns. The peak current I_PPof the primary-side winding Wp and the peak current I_SPof the secondary-side winding Ws are given by:
$\begin{matrix} I_{PP} = \frac{V_{in}}{L_{P}} \times T_{on} and & (2) \\ I_{SP} = \frac{V_{out}}{L_{S}} \times T_{DET} & (3) \end{matrix}$
where L_Pis the primary-side winding inductance, V_inis the primary-side input voltage, V_outis the system output voltage, T_onis the turn-on period for the primary-side switch Q1, and T_DETis the timing for secondary-side winding demagnetization, which should also be the turn-on period T_onof the secondary-side switch Q2.
Inserting equations (2) and (3) into equation (1) yields:
$\begin{matrix} \frac{V_{out}}{L_{S}} \times T_{DET} = \frac{N_{P}}{N_{S}} \times \frac{V_{in}}{L_{P}} \times T_{on}, & (4) \\ \frac{N_{P}}{N_{S}} = \sqrt{\frac{L_{P}}{L_{S}}} = n and & (5) \\ \frac{V_{in} \times T_{on}}{n} = V_{out} \times T_{DET} & (6) \end{matrix}$
From equation (6), the inductor average voltage is zero during a switching period in steady state, so the product of charge-voltage and charge-time is equal to the product of discharge-voltage and discharge-time, which is referred to as the volt-second balance equation.
Equation (6) can be used to predict a solution for the on-time period and thus off time of the secondary-side switch Q2, but because of reflected input measurement error and parasitic parameters in the system, equation (6) may not be followed closely. The secondary-side controller 104 calculates the secondary-side winding demagnetization time T_DEr for the previous switching cycle and the present product of charge-voltage and charge-time, cancelling errors introduced by the measurement error and parasitic parameters.
For the n^thswitching cycle, the charge balance equation is given by:
$\begin{matrix} \frac{[V_{in} (n) + ɛ] \times T_{on} (n)}{n} = V_{out} (n) \times T_{DET} (n) & (7) \end{matrix}$
where ε is the measurement error for the reflected input voltage V_DET. For the (n+1)^thswitching cycle, the charge balance equation is given by:
$\begin{matrix} \frac{[V_{in} (n + 1) + ɛ] \times T_{on} (n + 1)}{n} = V_{out} (n + 1) \times T_{DET} (n + 1) & (8) \end{matrix}$
Dividing equations (7) and (8) yields:
$\begin{matrix} T_{DET} (n + 1) = \frac{\frac{[V_{in} (n + 1) + ɛ] \times T_{on} (n + 1)}{n \times V_{out} (n + 1)}}{\frac{[V_{in} (n) + ɛ] \times T_{on} (n)}{n \times V_{out} (n)}} \times T_{DET} (n) & (9) \end{matrix}$
Because the output capacitor Co of the flyback converter is relatively large, and for the two consecutive switching cycles (n) and (n+1), the output voltage will be the same and therefore V_out(n)=V_out(n+1). Equation (9) can be simplified as given by:
$\begin{matrix} T_{DET} (n + 1) = \frac{\frac{[V_{in} (n + 1) + ɛ] \times T_{on} (n + 1)}{n}}{\frac{[V_{in} (n) + ɛ] \times T_{on} (n)}{n}} \times T_{DET} (n) & (10) \end{matrix}$
Based on the previous switching cycle demagnetization time and the calculated turn-on period for the secondary-side switch Q2, the secondary-side controller 104 updates the calculation and corrects the volt-second equation to yield an accurate turn-on period and thus off time for the secondary-side switch Q2 for the next switching cycle. The secondary-side controller 104 can tune the turn-on period and thus off time for the secondary-side switch Q2 based on the difference between the calculated turn-on time and the measured turn-on time, to yield more accurate results for turning on and turning off the secondary-side switch Q2.
FIG. 2 illustrates a waveform that shows how the secondary-side controller 104 tunes the calculated turn-on period and turn off time for the secondary-side switch Q2 as a function of the reflected input voltage V_DETmeasured at the secondary-side winding Ws of the flyback transformer, where T_onPrimaryis the on-time period of the primary-side switch Q1, T_SRmaxis the maximum allowed turn-on period for the secondary-side switch Q2, T_SRonis the compensated (adjusted) on-time period for switch Q2, and T_deadis the time for switch Q2 to be turned off before approaching T_SRmax.
FIG. 3 illustrates a block diagram of an analog-based implementation of the control technique implemented by the secondary-side controller 104. V-I (voltage-current) converter A₃converts voltage V_CDinto current I_DISCHR, where V_CDis the resistor divided output voltage provided by resistors R₃and R₄for input to the secondary-side controller 104. When the primary-side switch Q1 turns off, voltage V_PDgoes negative. V-I converter A₃discharges internal capacitor C_T, which means the secondary-side switch Q2 is turned on. V-I converter A₁converts voltage V_PDinto current I_CHR, where V_PDis the resistor divided reflected input voltage provided by resistors R₁and R₂and measured by the secondary-side controller 104. V-I converter A₁is on when the primary-side switch Q1 is on and voltage V_PDis at a high voltage.
The secondary-side controller 104 uses the difference current I_CHR−I_DISCHRto charge internal capacitor C_Tfrom a default voltage level V_ref1during the turn-on period of the primary-side switch Q1. Current I_CHRis given by:
$\begin{matrix} I_{CHR} = \frac{\frac{R_{2}}{R_{1} + R_{2}} \times (\frac{V_{in}}{n} + V_{out})}{R_{int 1}} & (12) \end{matrix}$
where R_int1is an internal resistor for converting voltage V_PDinto current. Current I_DISCHRis given by:
$\begin{matrix} I_{DISCHR} = \frac{\frac{R_{4}}{R_{3} + R_{4}} \times V_{out}}{R_{int 2}} & (13) \end{matrix}$
where R_int2is an internal resistor for converting voltage V_CDinto current. From equations (12) and (13), the difference current I_CHR−I_DISCHRis given by:
$\begin{matrix} I_{CHR} - I_{DISCHR} = \frac{\frac{R_{2}}{R_{1} + R_{2}} \times (\frac{V_{in}}{n} + V_{out})}{R_{int 1}} - \frac{\frac{R_{4}}{R_{3} + R_{4}} \times V_{out}}{R_{int 2}} & (14) \end{matrix}$
If R_int1=R_int2and
$\frac{R_{2}}{R_{1}} = \frac{R_{4}}{R_{3}},$
the difference current I_CHR−I_DISCHRbecomes:
$\begin{matrix} I_{CHR} - I_{DISCHR} = \frac{\frac{R_{5}}{R_{4} + R_{5}} \times (\frac{V_{in}}{n})}{R_{int 1}} & (15) \end{matrix}$
From equation (15), the internal capacitor C_Tis charged up only by the reflected input voltage, not output voltage.
Comparator A₄compares voltage V_PDwith reference voltage V_ref2. When voltage V_PDis lower than reference V_ref2, one short pulse is generated by pulse generator A₂. This short pulse sets SR (set-reset) flip-flop A₅, and turns on the secondary-side switch Q2 through buffer block A₆.
During the secondary-side winding demagnetization time, which should be the turn-on period for the secondary-side switch Q2, the secondary-side controller 104 uses current sink A₈to discharge (I_DISCHR+I_error) internal capacitor C_T, where I_erroris a programmable current that can be positive or negative. When the capacitor C_Tvoltage discharges to V_ref3level, the secondary-side switch Q2 is turned off through comparator A₇, SR flip-flop A₅and buffer A₆. SR flip-flop A₅is reset via logic block A₁₂when both T_SRmaxand the output of comparator A₇is positive. When the capacitor C_Tvoltage discharges to V_ref1level as indicated by comparator A₉, after some delay time T_deadprovided by logic block A₁₃and delay block A₁₀to get t_cal, time t_calis compared with the falling edge t_maxof T_SRmaxand the secondary-side controller 104 performs some judgement and adjustment through logic block A₁₁.
For high system frequencies or high line (AC input) conditions, the turn-on period T_ONPrimaryof the primary-side switch Q1 is reduced, and the reflected input voltage V_PDmeasured by the secondary-side controller 104 is not accurate. Under these conditions, voltage V_PDsettles. During the settling time, V-I converter A₁is operating but not at the right level. As a result, V-I converter A₁charges capacitor C_Tto an improper level (the voltage information is not correct during the settling time). When this voltage is converted to current for charging capacitor C_T, some error exists in I_CHR. Ideally, voltage V_PDhas no settling time and capacitor C_Tis charged at the input voltage level Vin for the full on-time period (rectangular voltage signal) of the secondary-side switch Q2. However, capacitor C_Tmay be charged lower than what it should ideally be charged to. This means that the on-time period and thus the off time for the secondary-side switch Q2 may be set shorter than what it ideally should be, lowering system efficiency. From equation (6), the calculated turn-on period and off time for the secondary-side switch Q2 may be adversely affected.
The secondary-side controller 104 corrects this error by compensating for the shape of voltage V_PD, to account for the settling time so that V_PDhas a rectangular or quasi-rectangular shape. The circuit shown in FIG. 3 charges capacitor C_Tand makes the voltage look like a rectangular or quasi-rectangular voltage signal, by compensating the V_PDsignal. Pulse generator A₂, SR flip-flop A₅and buffer block A₆sample and hold voltage V_PDat the proper level and the secondary-side controller 104 uses this voltage to calculate the charge current I_CHRfor charging capacitor C_Tduring the next switching cycle.
As shown in FIG. 2, the target turn-on period and thus turn off time for the secondary-side switch Q2 should be given by:
T _SRon =T _SRmax −T _dead (11)
where T_SRmaxis the maximum allowed turn-on period for the secondary-side switch Q2, and can be measured by a comparator included in or associated with the secondary-side controller 104.
From equation (11), if T_SRonis shorter than T_SRmax−T_dead, the secondary-side controller 104 prolongs the turn-on period and thus delays the turn off time of switch Q2 for the next switching cycle, and makes the next switching cycle turn-on period equal to T_SRmax−T_dead. If T_SRonis longer than T_SRmax−T_dead, the secondary-side controller 104 shortens the calculated turn-on period and thus pulls in the turn off time of switch Q2 for the next switching cycle, and makes next switching cycle turn-on period equal to T_SRmax−T_dead. If T_SRonis equal to T_SRmax−T_dead, the secondary-side controller 104 keeps the calculated turn-on period and thus off time of switch Q2 time for the next switching cycle, and makes the next switching cycle turn-on period equal to T_SRmax−T_dead.
FIGS. 4 through 6 illustrate the scenarios described above and handled by the secondary-side controller 104. Ideally, time t_calshould happen at the same time as t_maxfor the present switching cycle. If time t_calhappens before time t_maxas shown in FIG. 4, which means that the discharge time for capacitor C_Tis too short for the present switching cycle, the secondary-side controller 104 reduces discharge current I_errorby ΔI so that t_calapproaches t_maxfor the next switching cycle.
If time t_calhappens at the same time as tax as shown in FIG. 5, the discharge time for capacitor C_Tis ideal for the present switching cycle. The secondary-side controller 104 maintains the discharge current I_DISCHR+I_errorat the present level, so that t_calwill be at the same time as t_maxfor the next switching cycle.
If time t_calhappens after t_maxas shown in FIG. 6, t_calhappens after t_max, which means that the discharge time for capacitor C_Tis too long for the present switching cycle. The secondary-side controller 104 increases the discharge current I_errore.g. by 5×ΔI, 10×ΔI, or even higher so that t_calwill be earlier than t_maxfor the next switching cycle.
FIG. 7 illustrates an embodiment of the control technique implemented by the secondary-side controller 104. The control technique can be used for both DCM and CCM (continuous conduction mode) operation of the secondary-side switch Q2. The secondary-side controller 104 converts voltage V_PDinto current I_CHRand voltage V_CDinto current I_DISCHR(Block 200). During the turn-on period of the primary-side switch Q1, the secondary-side controller 104 uses difference current I_CHR−I_DISCHRto charge internal capacitor C_T(Block 202). After the primary-side switch Q1 is turned off, the secondary-side controller 104 turns on the secondary-side switch Q2 when V_PDis lower than threshold voltage V_ref2(Block 204). For the first switching pulse of the secondary-side switch Q2, the secondary-side controller 104 uses one current I_DISCHRto discharge internal capacitor C_Tduring the turn-off period of the secondary-side switch Q2 (Block 206). The secondary-side controller 104 uses one programmable current I_DISCHR+I_errorto discharge internal capacitor C_Tduring the turn-on period of the secondary-side switch Q2 for the subsequent switching cycles (Block 208). When the voltage across internal capacitor C_Tis discharged to V_ref3, the secondary-side controller 104 turns off the secondary-side switch Q2 (Block 210). Further, when the voltage across internal capacitor C_Tdischarges to V_ref1, with one fixed delay time T_deadto get time t_cal, which is compared with the maximum allowed T_SRmaxfalling edge t_max(Block 212), the secondary-side controller 104 performs the following evaluations and adjustments (Block 214):

- t_calhappens before t_max, which means that discharge time for capacitor C_Tis too short for the present switching cycle. For the optimal result, t_calshould happen the same time as t_max. For the next switching cycle, the secondary-side controller 104 reduces discharge current I_errorby ΔI, and t_calwill be approach to t_maxfor the next switching cycle;
- t_calhappens the same time as t_max, which means that discharge time for capacitor C_Tis already optimal for the present switching cycle. The secondary-side controller 104 maintains the discharge current I_error, and t_calwill be the same as t_maxfor the next switching cycle;
- t_calhappens after t_max, which means that discharge time for capacitor C_Tis too long for the present switching cycle. For the optimal result, t_calshould happen the same time as t_max. For the next switching cycle, the secondary-side controller 104 increases the discharge current I_error(for example, by 5×ΔI, 10×ΔI, or even higher), and t_calwill be earlier than t_maxfor the next switching cycle.

With the control technique described above, the turn-on period T_DETand thus turn off time of the secondary-side switch Q2 can be calculated based on the previous switching cycle and the present product of charge-voltage and charge-time, and the errors induced by the measurement of the reflected input voltage and parasitic parameters are cancelled. Also, the discharge current depends on output voltage and therefore is adapted for a jump (sudden increase) in the output voltage. Furthermore, there is no need for high voltage chip technology with very low threshold detection and the control technique can be used for both DCM and CCM operation.
By using the volt-second balance equation, also based on the previous switching cycle demagnetization time and present product of input voltage over turn-on time, the secondary-side controller 104 can correct the volt-second equation and provide accurate transistor turn-on period and thus off time for the next switching cycle. The turn-on period and off time can be tuned based on the difference between calculated turn-on time and measured turn-on time, to yield an optimum result. Errors introduced by the reflected input voltage measurement and parasitic parameters are also cancelled by the control technique described herein.
FIG. 8 illustrates a block diagram of a digital-based implementation of the SR control technique implemented by the secondary-side controller 104. According to this embodiment, capacitor C_Tis not used and the secondary-side controller 104 does not necessarily need the previous cycle information. At the end of the present on-time period for the primary-side switch Q1, the secondary-side controller 104 needs to sample the reflected input voltage measured at the secondary-side winding Ws. However, the secondary-side controller 104 does not know the end of the primary-side switch Q1 on-time period once the primary-side switch Q1 is turned on. In one embodiment, the secondary-side controller 104 includes a sample-and-hold unit 300 which samples the stepped down version V_PDof the reflected input voltage V_DETmeasured at the secondary-side winding Ws over an open window that always samples, and captures the value when the primary-side switch Q1 turns off. The falling edge of the turn-off event of primary-side switch Q1 is detected by an integrated capture compare unit (CCU) 302, which triggers the sample and hold unit 300 for the capturing event of the input voltage. Furthermore, the CCU 302 estimates the on-time period of the primary-side switch Q1 based on the captured edges of the sampling window. The captured on-time is fed to a lookup table (LUT) 304 which contains the associated error figures for very small on-time values when the reflected voltage is not yet settled during primary-side switch Q1 turn-on phase (see FIG. 2). The corresponding error figure is fed to a calculation unit 306 for determining the on-time of the secondary-side switch Q2, which is based on the volt-second theorem equation previously described herein. By considering the error figure from the LUT 304 within the calculation for the on-time of the secondary-side switch Q2, the sampled deviated input voltage is compensated for very small on-time periods of the primary-side switch Q1. The secondary-side switch Q2 turns on immediately when the primary-side switch Q1 turns off. The secondary-side controller 104 provides a minimum on-time period for the secondary-side switch Q2, and calculates the off-time during this period.
Terms such as “first”, “second”, and the like, are used to describe various elements, regions, sections, etc. and are also not intended to be limiting. Like terms refer to like elements throughout the description.
As used herein, the terms “having”, “containing”, “including”, “comprising” and the like are open ended terms that indicate the presence of stated elements or features, but do not preclude additional elements or features. The articles “a”, “an” and “the” are intended to include the plural as well as the singular, unless the context clearly indicates otherwise.
It is to be understood that the features of the various embodiments described herein may be combined with each other, unless specifically noted otherwise.
Although specific embodiments have been illustrated and described herein, it will be appreciated by those of ordinary skill in the art that a variety of alternate and/or equivalent implementations may be substituted for the specific embodiments shown and described without departing from the scope of the present invention. This application is intended to cover any adaptations or variations of the specific embodiments discussed herein. Therefore, it is intended that this invention be limited only by the claims and the equivalents thereof.

Claims

1. A method of operating a flyback converter having a primary-side switch connected to a primary-side winding of a transformer and a secondary-side switch connected to a secondary-side winding of the transformer, the method comprising:

controlling the primary-side switch to store energy in the transformer during ON periods of the primary-side switch;

switching on the secondary-side switch synchronously with switching off the primary-side switch to transfer energy from the transformer to the secondary side;

determining an off time of the secondary-side switch based on a reflected input voltage measured at the secondary-side winding when the primary-side switch is on;

accounting for a settling time of the reflected input voltage when determining the off time of the secondary-side switch, so that the settling time has little or no effect on the off time; and

switching off the secondary-side switch based on the off time,

wherein the flyback converter comprises a current source configured to provide a charge current for charging a capacitor on the secondary side when the primary-side switch is on and a current sink configured to sink a discharge current for discharging the capacitor when the secondary-side switch is on, and wherein accounting for the settling time of the reflected input voltage when determining the off time of the secondary-side switch comprises:

adjusting the discharge current for a present switching cycle of the secondary-side switch by an error current which is based on a comparison of the off time determined for a previous switching cycle of the secondary-side switch to a maximum off time calculated for the secondary-side switch.

2. (canceled)

3. The method of claim 1, wherein switching off the secondary-side switch based on the off time comprises:

switching off the secondary-side switch when the voltage across the capacitor decreases to a first reference value.

4. The method of claim 1, wherein adjusting the discharge current for the present switching cycle of the secondary-side switch based on the reflected input voltage as measured at steady-state after the settling time lapses during the previous switching cycle comprises:

comparing the off time determined for the previous switching cycle of the secondary-side switch to a maximum off time calculated for the secondary-side switch; and

decreasing the error current for the present switching cycle of the secondary-side switch if the off time determined for the previous switching cycle is less than the maximum off time.

5. The method of claim 1, wherein adjusting the discharge current for the present switching cycle of the secondary-side switch based on the reflected input voltage as measured at steady-state after the settling time lapses during the previous switching cycle comprises:

increasing the error current for the present switching cycle of the secondary-side switch if the off time determined for the previous switching cycle is greater than the maximum off time.

6. The method of claim 1, wherein adjusting the discharge current for the present switching cycle of the secondary-side switch based on the reflected input voltage as measured at steady-state after the settling time lapses during the previous switching cycle comprises:

maintaining the same error current for the present switching cycle of the secondary-side switch as the previous switching cycle if the off time determined for the previous switching cycle is the same as the maximum off time.

7. The method of claim 1, wherein adjusting the discharge current for the present switching cycle of the secondary-side switch based on the reflected input voltage as measured at steady-state after the settling time lapses during the previous switching cycle comprises:

sampling values of the reflected input voltage during the previous switching cycle of the secondary-side switch and holding one of the values sampled at steady-state; and

using the value of the reflected input voltage sampled at steady-state during the previous switching cycle of the secondary-side switch in determining the off time of the secondary-side switch for the present switching cycle of the secondary-side switch.

8-10. (canceled)

11. A flyback converter, comprising:

a primary-side switch connected to a primary-side winding of a transformer;

a secondary-side switch connected to a secondary-side winding of the transformer;

a primary-side controller operable to control the primary-side switch to store energy in the transformer during ON periods of the primary-side switch;

a secondary-side controller operable to:

switch on the secondary-side switch synchronously with switching off the primary-side switch to transfer energy from the transformer to the secondary side;

determine an off time of the secondary-side switch based on a reflected input voltage measured at the secondary-side winding when the primary-side switch is on;

account for a settling time of the reflected input voltage when determining the off time of the secondary-side switch, so that the settling time has little or no effect on the off time; and

switch off the secondary-side switch based on the off time;

a current source configured to provide a charge current for charging a capacitor on the secondary side when the primary-side switch is on; and

a current sink configured to sink a discharge current for discharging the capacitor when the secondary-side switch is on,

wherein the secondary-side controller is operable to adjust the discharge current for a present switching cycle of the secondary-side switch by an error current which is based on a comparison of the off time determined for a previous switching cycle of the secondary-side switch to a maximum off time calculated for the secondary-side switch.

12. (canceled)

13. The flyback converter of claim 11, wherein the secondary-side controller is operable to switch off the secondary-side switch when the voltage across the capacitor decreases to a first reference value.

14. The flyback converter of claim 11, wherein the secondary-side controller is operable to:

compare the off time determined for the previous switching cycle of the secondary-side switch to a maximum off time calculated for the secondary-side switch; and

decrease the error current for the present switching cycle of the secondary-side switch if the off time determined for the previous switching cycle is less than the maximum off time.

15. The flyback converter of claim 1, wherein the secondary-side controller is operable to:

increase the error current for the present switching cycle of the secondary-side switch if the off time determined for the previous switching cycle is greater than the maximum off time.

16. The flyback converter of claim 11, wherein the secondary-side controller is operable to:

maintain the same error current for the present switching cycle of the secondary-side switch as the previous switching cycle if the off time determined for the previous switching cycle is the same as the maximum off time.

17. The flyback converter of claim 11, wherein the secondary-side controller is operable to:

sample values of the reflected input voltage during the previous switching cycle of the secondary-side switch and hold one of the values sampled at steady-state; and

use the value of the reflected input voltage sampled at steady-state during the previous switching cycle of the secondary-side switch in determining the off time of the secondary-side switch for the present switching cycle of the secondary-side switch.

18-21. (canceled)