US11716012B2 - Controlling an electronic switching unit for supplying power to an inductive power load - Google Patents

Controlling an electronic switching unit for supplying power to an inductive power load Download PDF

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US11716012B2
US11716012B2 US17/798,372 US202117798372A US11716012B2 US 11716012 B2 US11716012 B2 US 11716012B2 US 202117798372 A US202117798372 A US 202117798372A US 11716012 B2 US11716012 B2 US 11716012B2
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capacitors
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US20230066463A1 (en
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Baptiste Rol
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Vitesco Technologies GmbH
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    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L53/00—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles
    • B60L53/20—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles characterised by converters located in the vehicle
    • B60L53/22—Constructional details or arrangements of charging converters specially adapted for charging electric vehicles
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H02M1/143—Arrangements for reducing ripples from dc input or output using compensating arrangements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/36—Means for starting or stopping converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L2210/00—Converter types
    • B60L2210/40—DC to AC converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P2201/00—Indexing scheme relating to controlling arrangements characterised by the converter used
    • H02P2201/15—Power factor Correction [PFC] circuit generating the DC link voltage for motor driving inverter
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/64—Electric machine technologies in electromobility
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/70—Energy storage systems for electromobility, e.g. batteries
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/7072—Electromobility specific charging systems or methods for batteries, ultracapacitors, supercapacitors or double-layer capacitors
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/72—Electric energy management in electromobility
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T90/00—Enabling technologies or technologies with a potential or indirect contribution to GHG emissions mitigation
    • Y02T90/10—Technologies relating to charging of electric vehicles
    • Y02T90/14—Plug-in electric vehicles

Definitions

  • the invention relates to the field of electronic switching circuits supplying power to inductive power loads from an electrical accumulator.
  • inductive power loads such as electric motors
  • inductive power loads require bridges of switches such as inverters, H-bridges, DC-to-DC converters, etc. to control them.
  • an electrical accumulator for example a battery, thus supplies power to the inductive power load via a switching circuit comprising a bridge of switches.
  • Inductive power loads comprise coils which generate a high inrush current during certain operating phases.
  • An electric motor for example, will generate an inrush of current when the motor is started, or during sharp acceleration, which may be very high.
  • filter capacitors generally of electrochemical type, to be added between the electric power supply and the ground of the electronic switching circuits. These capacitors are used to stabilize the voltage bus of the battery each time there is a large inrush of current for the power functions of the electronic switching circuit.
  • the bank of capacitors which is provided between the electric power supply and ground consists of an oversized number of capacitors, and the capacitance of these capacitors is also oversized.
  • Operating safety is obtained at an extra cost in manufacturing the electronic switching units, as well as additional bulk on the printed circuits of these units, this going against the trend, in particular in the automotive industry, of lowering manufacturing costs and decreasing the size of computers.
  • An aspect of the invention is electronic switching units for supplying electric power to an inductive power load of the prior art.
  • an aspect of the invention aims for a method for controlling an electronic switching unit for supplying electric power to an inductive power load, this electronic switching unit comprising:
  • This method comprises the following steps:
  • the method comprises the following steps:
  • the method comprises the following steps:
  • the method according to an aspect of the invention makes it possible to protect the electrochemical filter capacitors. This protection may be exploited to size the electrochemical capacitors as accurately as possible for a particular electronic switching unit. Accurately sizing the electrochemical capacitors may reduce the cost thereof.
  • the electrochemical capacitors are bulky components, reducing their number and their capacitance allows a substantial gain in terms of bulk on the printed circuit of the electronic unit, and therefore a general reduction in the size of this electronic unit.
  • this protection makes it possible to increase the reliability of the electronic switching unit.
  • the method according to an aspect of the invention may comprise the following additional features, alone or in combination:
  • FIG. 1 schematically shows an electronic switching unit according to an aspect of the invention
  • FIG. 2 is a diagram illustrating the method according to an aspect of the invention
  • FIG. 3 shows an operating curve of a filter capacitor of the electronic unit of FIG. 1 .
  • FIG. 1 schematically illustrates an electronic switching unit 1 according to an aspect of the invention.
  • the electronic unit 1 is an inverter intended to supply power to and control a three-phase electric motor 2 within a motor vehicle.
  • the electronic unit 1 is supplied with power by a battery of the motor vehicle, the power supply line 3 of which, at the potential of +12 V, is shown.
  • the electronic unit 1 comprises an electric power supply connector 4 making it possible in particular to connect the electronic unit 1 to this electric power supply line 3 .
  • the electronic unit 1 comprises a bridge 5 of switches which is adapted, in the present example, to supply power to the three-phase motor 2 .
  • a microcontroller 6 forming part of the equipment of the vehicle transmits the control setpoints to be implemented for controlling the motor 2 to the bridge 5 of switches.
  • the bridge 5 of switches is controlled by a pulse-width modulated (PWM) signal delivered by the microcontroller 6 .
  • PWM pulse-width modulated
  • the motor 2 is an inductive power load comprising high-inductance coils
  • the electronic unit 1 has a bank 7 of input filter capacitors.
  • This bank 7 of capacitors consists of a predefined number of capacitors C 1 to C n which are high-capacitance (for example, more than 1 ⁇ F) electrochemical capacitors. These capacitors C 1 to C n protect the electronic unit 1 against the large variations in electrical energy caused by the high inrushes of current which take place during certain operating phases of the motor 2 , such as starting or acceleration.
  • the capacitors C 1 to C n are intended to be connected between the power supply line 3 (+12 V) and ground.
  • the number of capacitors C 1 to C n is chosen according to the power of the installation.
  • the electronic unit 1 in addition comprises a device 8 for connecting capacitors.
  • This device 8 comprises, for each of the capacitors C 1 to C n , a switch 9 making it possible to open or to close the circuit between one electrode of the capacitor and ground, the other electrode of each capacitor being connected to the power supply line 3 .
  • the device 8 for connecting capacitors is controlled by a control module 10 which is adapted to close and open the switches 9 .
  • the switches 9 are, for example, transistors and the module 10 may be a module of driver type.
  • the control module 10 moreover receives the pulse-width modulated signal from the microcontroller 6 .
  • the module 10 thus has the information relating to the working frequency and to the duty cycle given as a setpoint by the microcontroller 6 for controlling the motor 2 .
  • the control module 6 transfers this signal to the switch bridge 5 in order to effectively control the bridge 5 of switches and therefore control the motor 2 , and is able to modify this signal.
  • the device 8 for connecting capacitors in addition comprises a means for measuring the current flowing through each capacitor C 1 to C n , this means being schematically depicted by an ammeter 11 .
  • this means being schematically depicted by an ammeter 11 .
  • the control module 10 thus has a measurement of the current for each capacitor C 1 to C n .
  • the control method according to an aspect of the invention makes it possible for the bank 7 of capacitors to fulfill its filtering function by protecting the electronic unit 1 from the load inrush current, which may transiently be very high.
  • the method also guarantees optimal operation of the capacitors C 1 to C n and their durability, and consequently improves the general reliability of the electronic unit 1 .
  • This method is described with reference to the diagram of FIG. 2 , which schematically illustrates the steps successively implemented by the control module 10 controlling the device 8 for connecting capacitors.
  • a first step A 1 relates to the initial programming of the control module 10 when it is brought into operation. During this step A 1 , the following data are stored in the control module 10 :
  • step A 2 then relates to initializing the choice of the initial filter capacitor, which will be the only capacitor activated when the method starts.
  • the first capacitor C 1 is designated as the initial filter capacitor.
  • Step A 3 the initial capacitor (C 1 , in this first iteration of the method) is activated and all the other capacitors C 2 to C n are deactivated.
  • the capacitors are activated or deactivated by the switches 9 (see FIG. 1 ).
  • Step A 3 therefore consists, during this first iteration, in closing the switch 9 relating to the first capacitor C 1 and in opening all the other switches 9 relating to the other capacitors C 2 to C n .
  • the current flowing through the initial capacitor is measured using the ammeter 11 (see FIG. 1 ). If the current measured through the initial capacitor is above the nominal current threshold I RMS_T0 , then the method proceeds to the following step A 5 . Otherwise, the method loops back to step A 4 .
  • the value of the nominal current threshold I RMS_T0 is a predetermined value which depends on the filter capacitors used. This value corresponds to the maximum current which a capacitor (here the capacitor C 1 in its role as initial filter capacitor) is intended to safely withstand at the nominal working frequency F T0 .
  • the nominal working frequency F T0 is the frequency of the pulse-width modulated signal sent by the microcontroller 6 and which the control module 10 transmits identically to the bridge 5 of switches.
  • the method therefore remains at step A 4 as long as the current flowing through the initial capacitor (which is in this first iteration the capacitor C 1 , and which is the only active capacitor of the bank of capacitors) remains below the nominal current threshold I RMS_T0 .
  • Step A 5 corresponds to a situation where the current flowing through the initial capacitor C 1 is above the nominal current threshold I RMS_T0 , and this current is considered too high for the initial capacitor C 1 .
  • Step A 5 consists in activating an additional filter capacitor in the bank 7 of capacitors.
  • the following capacitor C 2 will thus be activated in step A 5 , that is to say that its switch 9 will be closed by the control module 10 .
  • the bank 7 of capacitors will therefore consist of two capacitors C 1 and C 2 in parallel and the current will therefore be distributed over these two capacitors.
  • step A 6 a new current measurement is carried out.
  • the current flowing through the two activated capacitors C 1 , C 2 is measured for each of these capacitors.
  • the device then proceeds to step A 7 , in which a new check relating to the current takes place.
  • step A 7 the current values measured for each capacitor C 1 , C 2 (which are therefore below the nominal current threshold I RMS_T0 ) are in addition evaluated to determine whether these current measurements are furthermore below a floor threshold.
  • the floor threshold is equal to half of the nominal current threshold I RMS_T0 . If these two current measurements are above the floor threshold, the method loops back to step A 6 . Conversely, when the current through the two capacitors C 1 , C 2 is below the floor threshold (half of the nominal current threshold I RMS_T0 ), the method then proceeds to step A 8 , in which the second capacitor C 2 is deactivated. This situation corresponds to returning to a current judged sufficiently low to require only a single capacitor in the bank 7 of filter capacitors.
  • step A 9 consists in determining whether or not the power function is completed, that is to say whether the filtering function fulfilled by the bank 7 of capacitors is still required, taking into account the operating phase of the motor 2 . If this power function is not completed, the method then loops back to step A 4 . Conversely, if the power function is completed, the method proceeds to step A 10 , in which a new initial capacitor will be designated for the next iteration of the method. In this first iteration of the method, the following capacitor C 2 is now designated as the initial capacitor. During the next iteration of step A 3 and the following steps, it is this capacitor C 2 which will begin by forming the bank 7 of filter capacitors alone.
  • step A 10 The method then loops back, after step A 10 , to step A 3 , during which this new initial capacitor C 2 will therefore be activated while all the other capacitors will be deactivated, and the method then launches a new iteration of step A 3 and the following steps as described above.
  • step A 6 of this first iteration if, during this step, unlike above, the current measured in each capacitor C 1 , C 2 is above the nominal current threshold I RMS_T0 , the method then does not continue with step A 7 , but this time proceeds to step B 1 , where the following capacitor of the bank 7 of capacitors is activated. In this first iteration, the capacitors C 1 , C 2 , C 3 are therefore activated in step B 1 while all the other capacitors are deactivated.
  • steps B 2 and B 3 which are similar to steps A 6 and A 7 , but which this time involve the three capacitors C 1 , C 2 , C 3 .
  • step B 2 the current flowing through each of the capacitors C 1 to C 3 is measured and compared with the nominal current threshold I RMS_T0 . If this current through each capacitor is below the nominal current threshold I RMS_T0 , the method proceeds to step B 3 , in which this current value is compared with the floor current threshold (here, also, half of the nominal threshold current I RMS_T0 ). Step B 3 loops back to step B 2 if the current through each capacitor is above the floor current threshold. Conversely, the method proceeds to step B 4 if the current through each capacitor is below the floor current threshold. In step B 4 , the capacitor which has just been activated (C 3 ) is then deactivated.
  • step B 5 consists in determining whether or not the power function is completed. If this power function is not completed, the method then loops back to step A 6 . Conversely, if the power function is completed, the method proceeds to step B 6 , in which a new initial capacitor will be designated for the next iteration of the method. In this first iteration of the method, the following capacitor C 2 is now designated as the initial capacitor. The method then loops back, after step B 6 , to step A 3 , during which this new initial capacitor C 2 will therefore be activated while all the other capacitors will be deactivated, and the method then launches a new iteration of step A 3 and the following steps as described above.
  • step B 2 If, in step B 2 , the current measured through each of the capacitors C 1 , C 2 , C 3 is above the nominal current threshold I RMS_T0 , the method proceeds to step C 1 , in which an additional capacitor is activated. The following capacitor is then activated and is added to the capacitors C 1 , C 2 , C 3 to form the bank 7 of filter capacitors. The method is thus repeated for each of the capacitors of the bank of capacitors (this being schematically depicted by the dotted line 13 in this FIG. 2 ), so that, as long as the current through each capacitor is above the nominal current threshold I RMS_T0 , a new capacitor is added to the bank 7 , up to the last capacitor C n .
  • Step C 1 relates to adding this capacitor C n and thus consists in activating the last capacitor C n which is available within the bank 7 of filter capacitors.
  • Step C 3 loops back to step C 2 if the current through each capacitor is above the floor current threshold. Conversely, the method proceeds to step C 4 if the current through each capacitor is below the floor current threshold. In step C 4 , the capacitor which has just been activated (C n ) is then deactivated.
  • step C 5 consists in determining whether or not the power function is completed. If this power function is not completed, the method then loops back to step B 2 , in accordance with the dotted line 16 (if the capacitor Cn is the fourth and last capacitor of the bank of filter capacitors) or to the step which is equivalent to step B 2 for the capacitor which precedes C n . Conversely, if the power function is completed, the method proceeds to step C 6 , in which a new initial capacitor will be designated for the next iteration of the method.
  • the method is thus looped back between steps A 3 and C 6 , so that the number of capacitors used within the bank of capacitors is always optimal.
  • the method always starts on a single capacitor but, by virtue of steps A 10 , B 6 and C 6 , this capacitor is rotating, that is to say that each capacitor C 1 to C n will therefore in turn play the role of first capacitor to be activated within the bank of capacitors.
  • This arrangement allows regular wear of the capacitors by balancing the usage times of all the capacitors, whatever their position within the bank of capacitors.
  • the capacitors are activated in a rotating fixed order.
  • step C 2 if the measurements of current flowing through each capacitor C 1 to C n are above the nominal current threshold I RMS_T0 , the method then proceeds to a step D 1 in which the working frequency of the pulse-width modulated signal will be modified.
  • This situation corresponds to detecting overuse of the capacitors at the initially intended working frequency F T0 .
  • it is judged necessary to take an additional measure because, despite the maximum capacitance of the bank of capacitors being used, the current flowing through these capacitors is despite everything above the nominal current threshold I RMS_T0 .
  • the working frequency of the pulse-width modulated signal is increased to a first protection frequency F T1 .
  • the frequency of the pulse-width modulated signal may be modified at the control module 10 or directly at the microcontroller 6 .
  • the capacitors C 1 to C n of the bank of capacitors therefore accept a larger current, taking into account the specifications which are specific to electrochemical capacitors (see FIG. 3 ).
  • a current which is above the nominal current threshold I RMS_T0 no longer poses a risk to the filter capacitors.
  • the current threshold posing a risk to the bank of filter capacitors is now the first predetermined current threshold I RMS_T1 (which is therefore above I RMS_T0 ), see FIG. 3 .
  • step D 2 then consists in determining whether the current flowing through each of the capacitors C 1 to C n is above this first predetermined current threshold I RMS_T1 . If this is not the case, the method proceeds to step D 3 , in which the current flowing through each of the capacitors C 1 to C n is this time compared with the nominal current threshold I RMS_T0 . If, during step D 3 , this current is still above I RMS_T0 , the method loops back to step D 2 . Conversely, if, in step D 3 , the current measured through the capacitors is now below I RMS_T0 , the method proceeds to step D 4 , in which the working frequency is again brought back to the initial working frequency F T0 . This situation corresponds to the case where increasing the working frequency is no longer judged useful and the method then proceeds to step D 5 .
  • step D 5 consists, similarly to steps A 9 , B 5 and C 5 , in determining whether the power function is completed. If this power function is not completed, the method then loops back to step C 2 . Conversely, if the power function is completed, the method proceeds to step D 6 , in which a new initial capacitor will be designated for the next iteration of the method (C 2 is now designated as the initial capacitor, in this first iteration).
  • step E 1 the working frequency will this time be increased to a second protection frequency F T2 .
  • this portion of the method starting at step E 1 will then increase the working frequency to the new frequency F T2 , which is greater than F T1 and which thus makes it possible to further increase the capacity of the bank of capacitors C 1 to C n , all the capacitors of which are activated here.
  • step E 1 the sequence is the same as for steps D 1 to D 6 and is therefore not described in more detail here (this method portion is schematically depicted by the dotted line 17 ).
  • This gradation in the increase in the working frequency of the pulse-width modulated signal ends with a maximum frequency F TM also defined during the initialization step A 1 .
  • the method proceeds to step F 1 when the last frequency stage has been reached and the current through the capacitors is still above the predetermined current threshold corresponding to this last frequency stage.
  • the method then proceeds to a final increase in the working frequency to the maximum frequency F TM (in step F 1 ) so as to implement the maximum capacity of the bank of capacitors for this maximum protection frequency F TM .
  • Step F 1 and the following steps unfold in the same way as step D 1 and the following steps or step E 1 and the following steps (which are not shown).
  • Step F 2 then consists in determining whether the current flowing through each of the capacitors C 1 to C n is above the last current threshold I RMS_TM . If this is not the case, the method proceeds to step F 3 , in which the current flowing through each of the capacitors C 1 to C n is this time compared with the current threshold corresponding to the frequency applied just before the maximum frequency F TM (in this example, this is the frequency applied during step E 1 and the following steps). If, during step F 3 , this current is still above the current threshold corresponding to the frequency applied just before the maximum frequency F TM , the method loops back to step F 2 .
  • step F 3 the current measured through the capacitors is now below the current threshold corresponding to the frequency applied just before the maximum frequency F TM , the method proceeds to step F 4 , in which the working frequency is again brought back to the frequency applied just before (in this example, during step E 1 and the following steps). This situation corresponds to the case where increasing the working frequency is no longer judged useful and the method then proceeds to step F 5 .
  • step F 5 consists, similarly to steps A 9 , B 5 , C 5 and D 5 , in determining whether the power function is completed. If this power function is not completed, the method then loops back to the method portion of step E 1 and the following steps (dotted line 18 ). Conversely, if the power function is completed, the method proceeds to step F 6 , in which a new initial capacitor will be designated for the next iteration of the method (as before, C 2 is then designated as the initial capacitor, in this first iteration).
  • step A 3 and step F 6 the bank of filter capacitors is implemented while being protected from current peaks without interfering with the operation of the electronic switching unit.
  • step F 2 if the measurement of current through each capacitor indicates that this current is above the last predetermined current threshold I RMS_TM , which corresponds to the maximum admissible current at the maximum protection frequency F TM , then the method proceeds to step G 1 , in which a new measure will be implemented for protecting the capacitor bank.
  • This measure relates to lowering the duty cycle of the pulse-width modulated signal. The method then here enters a degraded mode in which the duty cycle is lowered and thus affects the operation of the controlled capacitive load with the aim of protecting the bank of filter capacitors.
  • step G 1 the duty cycle is thus lowered by a predetermined value, and, in step G 2 , it is checked whether the measurement of current through each of the capacitors C 1 to C n has returned to below the last predetermined current threshold I RMS_TM . If this is indeed the case, the method loops back to step F 2 , and, if this is not the case, the method loops back to step G 1 in order to lower the duty cycle again.
  • the duty cycle of the pulse-width modulated signal is thus lowered, in one or more iterations of step G 1 , until the current flowing through the capacitors returns to below the last predetermined current threshold I RMS_TM .
  • an alert flag may be activated by the control module 10 in order to warn other equipment of the vehicle, or the user, of a limitation in the control of the motor 2 with a view to protecting the capacitors of the capacitor bank 7 .
  • these phases of limiting the duty cycle have a short duration and ultimately have little influence on the overall operation of the motor 2 .
  • the curve of FIG. 3 shows the change in the capacity i cap of a capacitor of the bank of filter capacitors, that is to say the current which may be admitted by the capacitor, as a function of its working frequency f.
  • This curve is valid for a given temperature, here 25° C., and for a defined voltage.
  • the working frequency is the frequency of the pulse-width modulated signal controlling the switch bridge 5 .
  • FIG. 3 illustrates the context in which the various working frequencies of the pulse-width modulated signal change, and the associated currents within a capacitor of the bank 7 of capacitors.
  • FIG. 3 results from a characteristic curve of an electrochemical capacitor used in the present example.
  • FIG. 3 which is characteristic of an electrochemical capacitor, has a rectilinear first portion having a positive gradient which relates to a phase where the increase in the working frequency applied to the capacitor goes together with an increase in its capacity, that is to say in the current which it is capable of withstanding.
  • This rectilinear first portion is bounded by the maximum frequency F max which may be admitted by the capacitor.
  • the frequency F max is the frequency beyond which the capacitor may be destroyed.
  • FIG. 3 in addition depicts the frequencies F T0 , F T1 , F T2 , . . . F TM which are chosen and initialized in the method which has just been described.
  • the frequency F TM is the maximum frequency to which the capacitor will be subjected during the method. This frequency F TM is preferably less than F max to guarantee the durability of the capacitor.
  • the method starts with a pulse-width modulated signal at the working frequency F T0 corresponding to a maximum current threshold I RMS_T0 for the capacitor.
  • a new capacitor is activated within the bank 7 of capacitors.
  • the working frequency is then modified and is increased to the value F T1 corresponding to a new maximum current I RMS_T1 flowing through the capacitor. This operation of increasing the working frequency is repeated by successively increasing the frequency to the predetermined frequency stages F T1 , F T2 . . .
  • the number of predetermined current thresholds I RMS_T0 , I RMS_T1 , I RMS_T2 . . . I RMS_TM may be adapted for a particular application and specific capacitors, as well as the corresponding working frequency F T0 , F T1 , F T2 . . . F TM .
  • the duty cycle may be lowered continuously or in stages.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Transportation (AREA)
  • Mechanical Engineering (AREA)
  • Inverter Devices (AREA)
  • Dc-Dc Converters (AREA)
  • Emergency Protection Circuit Devices (AREA)
  • Control Of Voltage And Current In General (AREA)
US17/798,372 2020-04-06 2021-03-26 Controlling an electronic switching unit for supplying power to an inductive power load Active US11716012B2 (en)

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FRFR2003400 2020-04-06
FR2003400A FR3108991B1 (fr) 2020-04-06 2020-04-06 Commande d’une unité électronique de commutation pour l’alimentation électrique d’une charge inductive de puissance.
FR2003400 2020-04-06
PCT/EP2021/057876 WO2021204561A1 (fr) 2020-04-06 2021-03-26 Commande d'une unite electronique de commutation pour l'alimentation electrique d'une charge inductive de puissance

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FR3143461A1 (fr) * 2022-12-16 2024-06-21 Psa Automobiles Sa Vehicule automobile comprenant un moyen de chauffage de cellules de batterie sur la base d’un courant alternatif d’onduleur, et procede et programme sur la base d’un tel vehicule
CN115912957A (zh) * 2023-03-09 2023-04-04 深圳市拓普泰克技术股份有限公司 微型逆变器的工作方法、装置、微型逆变器和存储介质

Citations (12)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS57183273A (en) 1981-04-30 1982-11-11 Mitsubishi Electric Corp Starting circuit for high frequency inverter
US20030063481A1 (en) * 2001-10-02 2003-04-03 Kojori Hassan A. Soft-start of DC link capacitors for power electronics and drive systems
JP3992242B1 (ja) 2006-05-29 2007-10-17 株式会社パワーシステム 交流電動機の制御装置
JP2010213510A (ja) 2009-03-11 2010-09-24 Ebara Corp ドライ真空ポンプ用電源装置、及びその運転方法
US20130094262A1 (en) 2011-10-18 2013-04-18 Tigo Energy, Inc. System and Method for Exchangeable Capacitor Modules for High Power Inverters and Converters
US20140339918A1 (en) 2012-01-17 2014-11-20 Massachusetts Institute Of Technology Enhanced Stacked Switched Capacitor Energy Buffer Circuit
US20150171763A1 (en) 2012-07-19 2015-06-18 Mitsubishi Electric Corporation Power conversion device
EP2930839A2 (fr) 2014-03-26 2015-10-14 Solaredge Technologies Ltd. Onduleur à niveaux multiples
WO2016103325A1 (fr) 2014-12-22 2016-06-30 三菱電機株式会社 Dispositif de conversion de puissance
US20160268797A1 (en) * 2015-03-12 2016-09-15 Eaton Corporation Variable frequency drive circuit with overvoltage protection
WO2018155073A1 (fr) 2017-02-24 2018-08-30 工機ホールディングス株式会社 Outil électrique
US20210218359A1 (en) * 2020-01-10 2021-07-15 Yaskawa America, Inc. Variable frequency drive dc bus capacitor configuration to limit dc bus short circuit current

Family Cites Families (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102244955B (zh) * 2010-05-14 2015-12-30 皇家飞利浦电子股份有限公司 自适应电路
RU2687049C1 (ru) * 2018-01-10 2019-05-07 Акционерное общество "Электроавтоматика" Способ управления электроагрегатом с асинхронным генератором

Patent Citations (13)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS57183273A (en) 1981-04-30 1982-11-11 Mitsubishi Electric Corp Starting circuit for high frequency inverter
US20030063481A1 (en) * 2001-10-02 2003-04-03 Kojori Hassan A. Soft-start of DC link capacitors for power electronics and drive systems
JP3992242B1 (ja) 2006-05-29 2007-10-17 株式会社パワーシステム 交流電動機の制御装置
JP2010213510A (ja) 2009-03-11 2010-09-24 Ebara Corp ドライ真空ポンプ用電源装置、及びその運転方法
US20130094262A1 (en) 2011-10-18 2013-04-18 Tigo Energy, Inc. System and Method for Exchangeable Capacitor Modules for High Power Inverters and Converters
US20140339918A1 (en) 2012-01-17 2014-11-20 Massachusetts Institute Of Technology Enhanced Stacked Switched Capacitor Energy Buffer Circuit
US20150171763A1 (en) 2012-07-19 2015-06-18 Mitsubishi Electric Corporation Power conversion device
EP2930839A2 (fr) 2014-03-26 2015-10-14 Solaredge Technologies Ltd. Onduleur à niveaux multiples
US10700588B2 (en) 2014-03-26 2020-06-30 Solaredge Technologies Ltd. Multi-level inverter
WO2016103325A1 (fr) 2014-12-22 2016-06-30 三菱電機株式会社 Dispositif de conversion de puissance
US20160268797A1 (en) * 2015-03-12 2016-09-15 Eaton Corporation Variable frequency drive circuit with overvoltage protection
WO2018155073A1 (fr) 2017-02-24 2018-08-30 工機ホールディングス株式会社 Outil électrique
US20210218359A1 (en) * 2020-01-10 2021-07-15 Yaskawa America, Inc. Variable frequency drive dc bus capacitor configuration to limit dc bus short circuit current

Non-Patent Citations (3)

* Cited by examiner, † Cited by third party
Title
English Translation of the Written Opinion for International Application No. PCT/EP2021/057876, dated Apr. 30, 2021, 6 pages.
International Search Report and Written Opinion for International Application No. PCT/EP2021/057876, dated Apr. 30, 2021, 13 pages (French).
International Search Report and Written Opinion for International Application No. PCT/EP2021/057876, dated Apr. 30, 2021, with partial translation, 10 pages.

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CN115335257A (zh) 2022-11-11
US20230066463A1 (en) 2023-03-02
FR3108991A1 (fr) 2021-10-08
WO2021204561A1 (fr) 2021-10-14

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