TWI509969B - Switched power supply with resonant converter and its control method - Google Patents
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Description
本發明是關於一種具有諧振型轉換器的交換式電源供應器及其控制方法,尤指一種可以讓諧振型轉換器的切換頻率準確趨近諧振頻率的相關技術。The present invention relates to a switching power supply with a resonant converter and a control method thereof, and more particularly to a related art that allows a switching frequency of a resonant converter to accurately approach a resonant frequency.
已知的一種具有諧振型轉換器的交換式電源供應器是如圖12所示,其包括一交流對直流轉換器70和一由諧振型轉換器構成的直流對直流轉換器80;該交流對直流轉換器70是將交流電源轉換為一高壓的直流電源(例如380伏特),再由直流對直流轉換器80將該高壓的直流電源轉換為所需電壓的直流電源。A known switching power supply with a resonant converter is shown in FIG. 12, which includes an AC-to-DC converter 70 and a DC-to-DC converter 80 composed of a resonant converter; The DC converter 70 converts the AC power to a high voltage DC power source (for example, 380 volts), and the DC-DC converter 80 converts the high-voltage DC power to a DC power source of a desired voltage.
該直流對直流轉換器80可由LLC轉換器構成,如圖13所示是一種LLC轉換器90的電路構造,主要是由一半橋電路91、一諧振電路92、一變壓器93及一輸出電路94;其中:該半橋電路91是透過諧振電路92與變壓器93的一次側連接;又變壓器93二次側連接該輸出電路94;該諧振電路92包括一諧振電容Cr、一激磁電感Lm及變壓器93的諧振電感Lr;又諧振電路92具有兩個諧振頻率,第一個諧振頻率Fr1則由諧振電容Cr、激磁電感Lm及變壓器93的諧振電感Lr所決定,第二個諧振 頻率Fr2是由諧振電容Cr及變壓器93的諧振電感Lr所決定。The DC-to-DC converter 80 can be constituted by an LLC converter. As shown in FIG. 13, the circuit configuration of the LLC converter 90 is mainly composed of a half bridge circuit 91, a resonant circuit 92, a transformer 93 and an output circuit 94. The half bridge circuit 91 is connected to the primary side of the transformer 93 through the resonant circuit 92; the secondary side of the transformer 93 is connected to the output circuit 94; the resonant circuit 92 includes a resonant capacitor Cr, a magnetizing inductance Lm, and a transformer 93. The resonant inductor Lr; the resonant circuit 92 has two resonant frequencies, and the first resonant frequency Fr1 is determined by the resonant capacitor Cr, the exciting inductor Lm, and the resonant inductor Lr of the transformer 93, and the second resonant The frequency Fr2 is determined by the resonant capacitor Cr and the resonant inductance Lr of the transformer 93.
前述交換式電源供應器在負載為輕載或LLC轉換器90的輸入電壓過高時,是使其切換頻率Fs大於諧振頻率Fr2,其輸出對輸入的增益G將會降低;而在負載為重載或LLC轉換器90的輸入電壓過低時,諧振型轉換器90會降低其切換頻率Fs,以相對提高其增益G,而滿足負載的需求,在此狀況下,切換頻率Fs小於諧振頻率Fr2。When the input voltage of the light load or the LLC converter 90 is too high, the switching power supply has a switching frequency Fs greater than the resonant frequency Fr2, and the output gain G of the input is reduced; and the load is heavy. When the input voltage of the carrier or LLC converter 90 is too low, the resonant converter 90 lowers its switching frequency Fs to relatively increase its gain G to meet the load demand. In this case, the switching frequency Fs is smaller than the resonant frequency Fr2. .
根據上述可知,LLC轉換器90會根據負載或輸入電壓的變化調整其切換頻率,但一般認為當切換頻率Fs趨近或等於諧振頻率Fr2時,交換式電源供應器具有較佳的工作效率。而如前揭所述,LLC轉換器90的諧振頻率主要是由諧振電容Cr、諧振電感Lr等諧振元件所決定,意即諧振頻率是根據上述諧振元件的規格計算產生的預設值,切換頻率則是根據該預設值而調整。然而實際狀況的是:前述諧振元件在生產時即存在規格誤差,因此根據其規格運算產生的諧振頻率無法完全準確,在此狀況下,LLC轉換器90即使透過精確的控制,使其切換頻率趨近或等於諧振頻率,仍無法達到有效提升工作效率的目的。According to the above, the LLC converter 90 adjusts its switching frequency according to the change of the load or the input voltage, but it is generally considered that the switching power supply has better working efficiency when the switching frequency Fs approaches or equals the resonant frequency Fr2. As described above, the resonant frequency of the LLC converter 90 is mainly determined by a resonant component such as a resonant capacitor Cr and a resonant inductor Lr, that is, the resonant frequency is a preset value calculated according to the specifications of the resonant component, and the switching frequency is It is adjusted according to the preset value. However, the actual situation is that the aforementioned resonant element has a specification error at the time of production, and therefore the resonant frequency generated according to its specification operation cannot be completely accurate. Under this condition, the LLC converter 90 has its switching frequency even after precise control. Near or equal to the resonant frequency, it is still unable to achieve the purpose of effectively improving work efficiency.
由上述可知,LLC轉換器90在切換頻率趨近或等於諧振頻率時具有較佳工作效率,但諧振頻率因諧振元件的規格誤差,無法事先準確計算,因而即使控制切換頻率趨近或等於諧振頻率,仍無法達到有效提升工作效率的目的。As can be seen from the above, the LLC converter 90 has better operating efficiency when the switching frequency approaches or equals the resonant frequency, but the resonant frequency cannot be accurately calculated in advance due to the specification error of the resonant component, and thus even if the control switching frequency approaches or equals the resonant frequency. , still can not achieve the purpose of effectively improving work efficiency.
因此本發明主要目的在提供一種具有諧振型轉換器的交換式電源供應器及其控制方法,其將根據實測數據判斷交換式電源供應器的工作狀態,再根據實際工作狀態調整切換頻率,使其趨近實際的諧振頻率,進而達到提升工作效率的目的。Therefore, the main object of the present invention is to provide a switching power supply with a resonant converter and a control method thereof, which will judge the working state of the switched power supply based on the measured data, and then adjust the switching frequency according to the actual working state, so that Approaching the actual resonant frequency, thereby achieving the goal of improving work efficiency.
為達成前述目的採取的主要技術手段係令前述具有諧振型轉換器的交換式電源供應器包括:一交流對直流轉換器,具有一交流電源輸入端、一直流電源輸出端和一控制端;一直流對直流轉換器,具有一諧振型轉換器、一諧振控制器及一相位檢測器;該相位檢測器分別與諧振型轉換器、諧振控制器連接,以分別取得一變壓器電壓波形和一驅動訊號波形,並據以產生一轉換電壓訊號,再由諧振控制器根據轉換電壓訊號產生一回授電壓控制訊號送至交流對直流轉換器的控制端,以調整交流對直流轉換器的直流電源電壓,進而控制諧振型轉換器的切換頻率。The main technical means for achieving the foregoing objective is that the above-mentioned switching power supply having a resonant converter includes: an AC-to-DC converter having an AC power input terminal, a DC power output terminal, and a control terminal; a DC-to-DC converter having a resonant converter, a resonant controller and a phase detector; the phase detector is respectively connected to the resonant converter and the resonant controller to respectively obtain a transformer voltage waveform and a driving signal Waveform, and accordingly, generates a converted voltage signal, and then the resonant controller generates a feedback voltage control signal according to the converted voltage signal to be sent to the control end of the AC to DC converter to adjust the DC power voltage of the AC to DC converter. Further, the switching frequency of the resonance type converter is controlled.
前述交換式電源供應器是由相位檢測器分別由諧振型轉換器、諧振控制器分別取得變壓器電壓波形及驅動訊號波形,並據以運算取得一反應即時工作狀態的轉換電壓訊號,當轉換電壓訊號不為零,表示切換頻率大於或小於諧振頻率;而由諧振控制器根據該轉換電壓訊號與交流對直流轉換器輸出的直流電源電壓運算後產生一回授電壓控制訊號送至交流對直流轉換器,以調整其輸出電壓,亦即調整諧振型轉換器的輸入電壓,當諧振型轉換器的輸入電壓改變,其切換頻率隨之改變,進而得使切換頻 率趨近或等於諧振頻率。The switching power supply device is obtained by the phase detector respectively obtaining the transformer voltage waveform and the driving signal waveform by the resonant converter and the resonant controller, and calculating a converted voltage signal according to the operation to obtain a real-time working state, when converting the voltage signal Non-zero, indicating that the switching frequency is greater than or less than the resonant frequency; and the resonant controller generates a feedback voltage control signal to the AC-to-DC converter according to the converted voltage signal and the DC power supply voltage outputted by the AC-DC converter. In order to adjust its output voltage, that is, adjust the input voltage of the resonant converter. When the input voltage of the resonant converter changes, the switching frequency changes accordingly, and the switching frequency is changed. The rate approaches or equals the resonant frequency.
為達成前述目的採取的又一技術手段係令前述方法包括:取得一諧振型轉換器的一變壓器電壓波形及一驅動訊號波形,據以產生一本次轉換電壓訊號;判斷本次轉換電壓訊號是否為零;若本次轉換電壓訊號不為零,判斷本次轉換電壓訊號與一前次轉換電壓訊號的差值是否小於零;該前次轉換電壓訊號是根據先前取得的變壓器電壓波形及驅動訊號波形所產生;若前述差值小於零,接著判斷切換頻率是否降低,若是,降低切換頻率,若否,則提高切換頻率;前述方法主要是先降低或提高諧振型轉換器的切換頻率,再根據實測諧振轉換器的變壓器電壓波形及驅動訊號波形判斷交換式電源供應器目前的工作狀態,當變壓器電壓波形及驅動訊號波形運算產生的本次轉換電壓訊號不為零,表示諧振型轉換器目前的切換頻率與諧振頻率不一致,接著判斷轉換電壓訊號是否小於先前取得的轉換電壓訊號,若是,表示調整方向正確,依原方式進一步降低或提高切換頻率,直到轉換電壓訊號為零,即達成使切換頻率與諧振頻率趨於一致的目的。Another technical means for achieving the foregoing objective is that the method includes: obtaining a transformer voltage waveform and a driving signal waveform of a resonant type converter, thereby generating a current converted voltage signal; determining whether the current converted voltage signal is Zero; if the current conversion voltage signal is not zero, it is judged whether the difference between the current conversion voltage signal and a previous conversion voltage signal is less than zero; the previous conversion voltage signal is based on the previously obtained transformer voltage waveform and the driving signal If the difference is less than zero, then determine whether the switching frequency is reduced, and if so, reduce the switching frequency, if not, increase the switching frequency; the foregoing method mainly reduces or increases the switching frequency of the resonant converter, and then according to The transformer voltage waveform and the driving signal waveform of the measured resonant converter determine the current working state of the switching power supply. When the transformer voltage waveform and the driving signal waveform operation generate the converted voltage signal is not zero, it indicates the current resonant converter. The switching frequency is inconsistent with the resonant frequency, and then the switching voltage is judged. Voltage converter is smaller than the number previously obtained, if, in the right direction represents the adjustment to further reduce or increase the switching frequency according to the original mode until the voltage converter is zero, i.e., to achieve the switching frequency of the resonant frequency convergence purposes.
10‧‧‧交流對直流轉換器10‧‧‧AC to DC converter
100‧‧‧控制模組100‧‧‧Control Module
101‧‧‧疊加電路101‧‧‧Superimposed circuit
102‧‧‧控制器102‧‧‧ Controller
20‧‧‧直流對直流轉換器20‧‧‧DC to DC converter
21‧‧‧全橋電路21‧‧‧Full bridge circuit
22‧‧‧諧振電路22‧‧‧Resonance circuit
23‧‧‧變壓器23‧‧‧Transformers
24‧‧‧輸出電路24‧‧‧Output circuit
25‧‧‧諧振控制器25‧‧‧Resonance controller
251‧‧‧運算器251‧‧‧Operator
252‧‧‧控制單元252‧‧‧Control unit
30‧‧‧相位檢測器30‧‧‧ phase detector
31‧‧‧比較器31‧‧‧ Comparator
32‧‧‧邏輯閘32‧‧‧Logic gate
33‧‧‧低通濾波器33‧‧‧Low-pass filter
70‧‧‧交流對直流轉換器70‧‧‧AC to DC converter
80‧‧‧直流對直流轉換器80‧‧‧DC to DC converter
90‧‧‧LLC轉換器90‧‧‧LLC Converter
91‧‧‧半橋電路91‧‧‧Half-bridge circuit
92‧‧‧諧振電路92‧‧‧Resonance circuit
93‧‧‧變壓器93‧‧‧Transformers
94‧‧‧輸出電路94‧‧‧Output circuit
圖1是本發明交換式電源供應器一較佳實施例的電路圖。BRIEF DESCRIPTION OF THE DRAWINGS Figure 1 is a circuit diagram of a preferred embodiment of a switched power supply of the present invention.
圖2是本發明交換式電源供應器又一較佳實施例的電路圖。2 is a circuit diagram of still another preferred embodiment of the switched power supply of the present invention.
圖3是本發明交換式電源供應器再一較佳實施例的電路圖。3 is a circuit diagram of still another preferred embodiment of the switched power supply of the present invention.
圖4是諧振電路在切換頻率小於諧振頻率時的工作波形圖。Fig. 4 is a diagram showing the operation waveform of the resonance circuit when the switching frequency is smaller than the resonance frequency.
圖5是諧振電路切換頻率大於諧振頻率時的工作波形圖。Fig. 5 is a diagram showing an operation waveform when the switching frequency of the resonance circuit is larger than the resonance frequency.
圖6是本發明直流對直流轉換器中相位檢測器的電路圖。Figure 6 is a circuit diagram of a phase detector in a DC-to-DC converter of the present invention.
圖7是本發明相位檢測器在輕載下取得的變壓器電壓波形及驅動訊號波形圖。7 is a waveform diagram of a transformer voltage waveform and a driving signal obtained by the phase detector of the present invention under light load.
圖8是本發明相位檢測器在重載下取得的變壓器電壓波形及驅動訊號波形圖。8 is a waveform diagram of a transformer voltage waveform and a driving signal obtained by the phase detector of the present invention under heavy load.
圖9是本發明一較佳實施例的方法流程圖。9 is a flow chart of a method in accordance with a preferred embodiment of the present invention.
圖10是本發明又一較佳實施例的方法流程圖。10 is a flow chart of a method in accordance with still another preferred embodiment of the present invention.
圖11是本發明一較佳實施例的交流對直流轉換器內設控制模組的一電路圖。11 is a circuit diagram of a control module built in an AC-to-DC converter according to a preferred embodiment of the present invention.
圖12是已知交換式電源供應器的電路方塊圖。Figure 12 is a circuit block diagram of a known switched power supply.
圖13是已知交換式電源供應器中所設LLC電路的電路圖。Figure 13 is a circuit diagram of an LLC circuit provided in a known switched power supply.
關於本發明交換式電源供應器的一較佳實施例,請參閱圖1所示,包括一交流對直流轉換器10、一直流對直流轉換器20;其中: 該交流對直流轉換器10具有一交流電源輸入端AC IN、一直流電源輸出端DC OUT和一控制端BC,用以將由交流電源輸入端AC IN輸入的交流市電轉換為相對高壓的直流電壓Vbulk,並由直流電源輸出端DC OUT輸出,其控制端BC將影響直流電源輸出端DC OUT上的直流電壓Vbulk。A preferred embodiment of the switching power supply of the present invention, as shown in FIG. 1, includes an AC to DC converter 10, a DC to DC converter 20, wherein: The AC-to-DC converter 10 has an AC power input terminal AC IN, a DC power output terminal DC OUT and a control terminal BC for converting the AC mains input from the AC power input terminal AC IN into a relatively high voltage DC voltage Vbulk. And by the DC power output DC OUT output, its control terminal BC will affect the DC voltage Vbulk on the DC power output DC OUT.
在本實施例中,該直流對直流轉換器20具有諧振轉換器、一諧振控制器25及一相位檢測器30所組成,其中,該諧振轉換器是由LLC轉換器所構成,其具有一全橋電路21、一諧振電路22、一變壓器23及一輸出電路24;該全橋電路21具有多個成對且交替導通的電子開關QA~QD,各電子開關QA~QD分別與諧振控制器25連接,由諧振控制器25提供的驅動訊號(Driving Signal)控制各電子開關QA~QD的導通與否;該諧振電路22主要係由一諧振電容Cr、一激磁電感Lm及變壓器23的諧振電感Lr所組成;該諧振電路22連接於交流對直流轉換器10的直流電源輸出端和變壓器23的一次側之間,變壓器23的二次側與輸出電路24連接。In this embodiment, the DC-DC converter 20 has a resonant converter, a resonant controller 25, and a phase detector 30, wherein the resonant converter is composed of an LLC converter, and has a full a bridge circuit 21, a resonant circuit 22, a transformer 23 and an output circuit 24; the full bridge circuit 21 has a plurality of pairs of electronic switches QA~QD that are alternately turned on, and the electronic switches QA~QD and the resonant controller 25, respectively The driving signal (Driving Signal) provided by the resonant controller 25 controls whether the electronic switches QA to QD are turned on or not. The resonant circuit 22 is mainly composed of a resonant capacitor Cr, a magnetizing inductor Lm, and a resonant inductor Lr of the transformer 23. The resonant circuit 22 is connected between the DC power output end of the AC-DC converter 10 and the primary side of the transformer 23, and the secondary side of the transformer 23 is connected to the output circuit 24.
在本實施例中,該變壓器23提供一個以上的變壓器電壓波形擷取點,其可為變壓器23二次側耦合線圈處(如圖1所示)、一次側的耦合線圈處(如圖2所示)或二次側(如圖3所示),以提供一變壓器電壓波形Vtr予相位檢測器30,供相位檢測器30根據變壓器電壓波形Vtr和諧振控制器25的驅動訊號(Driving Signal,本實施例是取電子開關QB的閘、源極電壓波形Vgs_QB)判斷目前的工作狀態, 並產生一轉換電壓訊號Vturn。本實施例中,係由變壓器23的二次側耦合線圈處取得變壓器電壓波形。In this embodiment, the transformer 23 provides one or more transformer voltage waveform extraction points, which may be at the secondary side coupling coil of the transformer 23 (as shown in FIG. 1) and the primary side coupling coil (as shown in FIG. 2). Shown or secondary side (as shown in FIG. 3) to provide a transformer voltage waveform Vtr to the phase detector 30 for the phase detector 30 to drive the signal according to the transformer voltage waveform Vtr and the resonant controller 25 (Driving Signal, present) In the embodiment, the gate and source voltage waveforms Vgs_QB of the electronic switch QB are taken to determine the current working state. And generate a conversion voltage signal Vturn. In this embodiment, the transformer voltage waveform is obtained from the secondary side coupling coil of the transformer 23.
前述轉換電壓訊號Vturn將被用來判斷目前的工作狀態,具體而言是判斷諧振型轉換器22的切換頻率Fs與諧振頻率Fr是否相同,其原理係如以下所述:根據實測結果,當LLC電路的切換頻率Fs與諧振頻率Fr不一致時,量測到全橋電路21中電子開關和變壓器23的波形是如圖4所示,由變壓器電壓波形Vtr波形可以看出,切換頻率Fs小於諧振頻率Fr2,在此工作狀態下,應提高電子開關QA~QD的切換頻率。又如圖5所示,則是顯示切換頻率Fs大於諧振頻率Fr2,在此工作狀態下,則應降低電子開關QA~QD的切換頻率。The converted voltage signal Vturn will be used to determine the current operating state, specifically, whether the switching frequency Fs of the resonant converter 22 is the same as the resonant frequency Fr, and the principle is as follows: according to the measured result, when LLC When the switching frequency Fs of the circuit is inconsistent with the resonant frequency Fr, the waveforms of the electronic switch and the transformer 23 in the full bridge circuit 21 are measured as shown in FIG. 4. It can be seen from the waveform of the transformer voltage waveform Vtr that the switching frequency Fs is smaller than the resonant frequency. Fr2, in this working state, the switching frequency of the electronic switch QA~QD should be increased. As shown in FIG. 5, the display switching frequency Fs is greater than the resonance frequency Fr2. In this operating state, the switching frequency of the electronic switches QA to QD should be lowered.
而根據圖4、圖5所示波形可以看出,不論切換頻率Fs大於或小於諧振頻率Fr2,只要諧振頻率Fr2與切換頻率Fs不一致時,變壓器電壓波形Vtr與驅動訊號間即會出現相位差,因此本發明利用相位檢測器30實測該變壓器電壓波形Vtr與驅動訊號的波形,以判斷諧振頻率Fr2與切換頻率Fs是否有不一致的情況,進而由諧振控制器25對切換頻率Fs進行補償。According to the waveforms shown in FIG. 4 and FIG. 5, whether the switching frequency Fs is greater than or less than the resonant frequency Fr2, if the resonant frequency Fr2 does not coincide with the switching frequency Fs, a phase difference occurs between the transformer voltage waveform Vtr and the driving signal. Therefore, the present invention uses the phase detector 30 to measure the waveform of the transformer voltage waveform Vtr and the driving signal to determine whether the resonant frequency Fr2 and the switching frequency Fs are inconsistent, and the resonant controller 25 compensates the switching frequency Fs.
關於前述相位檢測器30請參閱圖6所示,其主要係由一比較器31和一邏輯閘32組成,在本實施例中,進一步包括一低通濾波器33;該比較器31的輸入端和變壓器23上的任一電壓擷取點,以取得變壓器電壓波形Vtr,比較器31的參考端則連接一直流電源,作為參考訊號。比較器31的輸出端與邏輯閘32的一輸入端連接; 在本實施例中,該邏輯閘32是由一互斥或閘(XOR)構成,其另一輸入端是連接諧振控制器25以取得驅動訊號(Driving Signal),在本實施例中,是取得電子開關QB的閘、源極電壓波形(Vgs_QB)。因此,相位檢測器30是將變壓器電壓波形Vtr與直流位準比較後產生的電壓訊號VPHASE ,送至邏輯閘32與驅動訊號(Vgs_QB)波形作互斥或邏輯判斷(請配合參閱圖7、圖8所示,其中圖7為輕載時的波形圖,圖8為重載時的波形圖),並產生一脈波訊號Vx,為確保訊號準確,進一步經過低通濾波器33濾波後,以取得一轉換電壓訊號Vturn送至諧振控制器25,供諧振控制器25判斷是否出現諧振頻率Fr2與切換頻率Fs不一致的狀況,據以決定是否進行補償,使諧振頻率Fr2與切換頻率Fs趨於一致。必須說明的是:所謂「趨於一致」的定義,依交換式電源供應器的工作狀態,可能是使切換頻率Fs趨近諧振頻率Fr2,也可能是使切換頻率Fs與諧振頻率Fr2相同。Referring to FIG. 6 , the phase detector 30 is mainly composed of a comparator 31 and a logic gate 32. In this embodiment, a low pass filter 33 is further included; the input end of the comparator 31 And any voltage on the transformer 23 draws a point to obtain the transformer voltage waveform Vtr, and the reference end of the comparator 31 is connected to the DC power source as a reference signal. The output of the comparator 31 is connected to an input of the logic gate 32. In this embodiment, the logic gate 32 is formed by a mutual exclusion or gate (XOR), and the other input terminal is connected to the resonance controller 25. The driving signal (Driving Signal) is obtained. In the present embodiment, the gate and source voltage waveforms (Vgs_QB) of the electronic switch QB are obtained. Therefore, the phase detector 30 is a voltage signal V PHASE generated by comparing the transformer voltage waveform Vtr with the DC level, and sent to the logic gate 32 and the driving signal (Vgs_QB) waveform for mutual exclusion or logical judgment (please refer to FIG. 7 , 8 is a waveform diagram at the time of light load, and FIG. 8 is a waveform diagram at the time of heavy load, and generates a pulse signal Vx. To ensure accurate signal, further filtered by the low-pass filter 33, A resonant voltage signal Vturn is sent to the resonant controller 25 for the resonant controller 25 to determine whether the resonant frequency Fr2 does not coincide with the switching frequency Fs, thereby determining whether to compensate, such that the resonant frequency Fr2 and the switching frequency Fs tend to Consistent. It must be stated that the definition of "consistent" depends on the operating state of the switching power supply, which may cause the switching frequency Fs to approach the resonant frequency Fr2, or the switching frequency Fs to be the same as the resonant frequency Fr2.
在本實施例中,該諧振控制器25包括一運算器251和一控制單元252,該運算器251係將前述轉換電壓訊號Vturn與一參考電壓VREF 進行差值運算,並將運算產生的差值Verror送至控制單元252,由控制單元252決定是否進行補償,該控制單元252一可行的判斷流程,請參閱圖9所示,其包括:判斷差值Verror是否為零(701);若差值Verror為零,表示諧振頻率Fr2趨近或等於切換頻率Fs,即結束判斷; 若差值Verror不為零,表示諧振頻率Fr2與切換頻率Fs不一致,接著判斷本次差值與前次差值的差(△Verror)是否大於零(702);當本次差值小於前次差值,接著判斷本次切換頻率是否小於前次切換頻率(703),若本次切換頻率Fs(n)小於前次切換頻率Fs(n-1),表示切換頻率Fs大於諧振頻率Fr2,因此降低切換頻率Fs(704),並回到步驟(701);若本次切換頻率Fs(n)未小於前次切換頻率Fs(n-1),表示切換頻率Fs小於諧振頻率Fr2,因此提高切換頻率Fs(705),並回到步驟(701)。In this embodiment, the resonant controller 25 includes an arithmetic unit 251 and a control unit 252. The arithmetic unit 251 performs a difference operation between the converted voltage signal Vturn and a reference voltage V REF , and the difference generated by the operation. The value Verror is sent to the control unit 252, and the control unit 252 determines whether to perform compensation. The control unit 252 determines a feasible determination process, as shown in FIG. 9, which includes: determining whether the difference Verror is zero (701); The value Verror is zero, indicating that the resonant frequency Fr2 approaches or equals the switching frequency Fs, that is, the end judgment; if the difference Verror is not zero, it indicates that the resonant frequency Fr2 is inconsistent with the switching frequency Fs, and then the current difference and the previous difference are judged. Whether the difference (ΔVerror) is greater than zero (702); when the current difference is less than the previous difference, then it is determined whether the current switching frequency is less than the previous switching frequency (703), if the current switching frequency Fs(n) is less than The previous switching frequency Fs(n-1) indicates that the switching frequency Fs is greater than the resonant frequency Fr2, thus lowering the switching frequency Fs (704), and returns to step (701); if the current switching frequency Fs(n) is not less than the previous time Switching frequency Fs(n-1), indicating switching frequency Fs The resonant frequency Fr2, thus increasing the switching frequency Fs (705), and returns to step (701).
在前述步驟(702)中,若本次差值與前次差值的差(△Verror)大於零,即接著判斷本次切換頻率是否小於前次切換頻率(706),本次切換頻率Fs(n)若小於前次切換頻率Fs(n-1),表示切換頻率Fs小於諧振頻率Fr2,將提高切換頻率Fs(705),並回到步驟(701)。In the foregoing step (702), if the difference (ΔVerror) between the current difference and the previous difference is greater than zero, then it is determined whether the current switching frequency is less than the previous switching frequency (706), and the current switching frequency Fs ( n) If it is smaller than the previous switching frequency Fs(n-1), indicating that the switching frequency Fs is smaller than the resonance frequency Fr2, the switching frequency Fs is increased (705), and the process returns to the step (701).
若本次切換頻率Fs(n)未小於前次切換頻率Fs(n-1),表示切換頻率Fs大於諧振頻率Fr2,因此降低切換頻率Fs(704),並回到步驟(701)。If the current switching frequency Fs(n) is not less than the previous switching frequency Fs(n-1), it indicates that the switching frequency Fs is greater than the resonance frequency Fr2, so the switching frequency Fs is lowered (704), and the process returns to the step (701).
前述補償動作回到步驟(701)後,將重新執行步驟(702)、步驟(703)和步驟(704)或(705),直到步驟(701)判斷差值Verror為零,表示切換頻率Fs與諧振頻率Fr2一致。After the foregoing compensation operation returns to step (701), step (702), step (703), and step (704) or (705) will be re-executed until step (701) determines that the difference Verror is zero, indicating the switching frequency Fs and The resonance frequency Fr2 is uniform.
前述控制單元252又一可行的判斷流程,請參閱圖10所示,其包括:判斷差值Verror是否為零(801);若差值Verror為零,表示諧振頻率Fr2趨近或等於切換頻率Fs,即結束 判斷;若差值Verror不為零,表示諧振頻率Fr2與切換頻率Fs不一致,接著判斷本次差值與前次差值的差(△Verror)是否等於零(802);當本次差值與前次差值的差(△Verror)不等於零,進一步判斷是否大於零(803),接著以下的步驟(804)~(807)與前一可行判斷流程的步驟(703)至(706)相同。而在降低或提高切換頻率Fs後,並回到步驟(801);在前述步驟(802)中,若本次差值與前次差值的差(△Verror)等於零,則對切換頻率進行一預調整(808)後,回到步驟(801)。Another feasible determination process of the foregoing control unit 252, as shown in FIG. 10, includes: determining whether the difference Verror is zero (801); if the difference Verror is zero, indicating that the resonant frequency Fr2 approaches or equals the switching frequency Fs End Judging; if the difference Verror is not zero, indicating that the resonant frequency Fr2 is inconsistent with the switching frequency Fs, and then determining whether the difference between the current difference and the previous difference (ΔVerror) is equal to zero (802); when the current difference is before The difference (ΔVerror) of the second difference is not equal to zero, and further judges whether it is greater than zero (803), and then the following steps (804) to (807) are the same as steps (703) to (706) of the previous feasible judgment flow. After the switching frequency Fs is decreased or increased, the process returns to step (801). In the foregoing step (802), if the difference between the current difference and the previous difference (ΔVerror) is equal to zero, the switching frequency is performed. After pre-adjustment (808), return to step (801).
接著判斷差值Verror是否為零(801);若差值Verror不為零,表示諧振頻率Fr2與切換頻率Fs不一致,接著判斷本次差值與前次差值的差(△Verror)是否等於零(802);當本次差值與前次差值的差(△Verror)不等於零,進一步判斷是否大於零(803),若大於零,表示先前預調整的補償方向錯誤,即接著判斷本次切換頻率是否小於前次切換頻率(807),由於補償方向相反,因此本次切換頻率Fs(n)若小於前次切換頻率Fs(n-1),表示切換頻率Fs小於諧振頻率Fr2,將提高切換頻率Fs(806),並回到步驟(801)。Then, it is judged whether the difference Verror is zero (801); if the difference Verror is not zero, it indicates that the resonance frequency Fr2 is inconsistent with the switching frequency Fs, and then it is judged whether the difference (ΔVerror) between the current difference and the previous difference is equal to zero ( 802); when the difference between the current difference and the previous difference (ΔVerror) is not equal to zero, further determining whether it is greater than zero (803), if greater than zero, indicating that the compensation direction of the previous pre-adjustment is wrong, that is, then determining the current handover Whether the frequency is less than the previous switching frequency (807), because the compensation direction is opposite, if the switching frequency Fs(n) is smaller than the previous switching frequency Fs(n-1), it indicates that the switching frequency Fs is smaller than the resonant frequency Fr2, which will improve the switching. Frequency Fs (806) and return to step (801).
若本次切換頻率Fs(n)未小於前次切換頻率Fs(n-1),表示切換頻率Fs大於諧振頻率Fr2,因此降低切換頻率Fs(805),並回到步驟(801)。If the current switching frequency Fs(n) is not less than the previous switching frequency Fs(n-1), it indicates that the switching frequency Fs is greater than the resonance frequency Fr2, so the switching frequency Fs is lowered (805), and the process returns to step (801).
前述步驟(803)若不大於零,表示補償方向正確,則進一步判斷本次切換頻率Fs(n)是否小於前次切換頻 率Fs(n-1)(804),若本次切換頻率Fs(n)小於前次切換頻率Fs(n-1),表示切換頻率Fs大於諧振頻率Fr2,因此降低切換頻率Fs(805),並回到步驟(801)。若本次切換頻率Fs(n)未小於前次切換頻率Fs(n-1),表示切換頻率Fs小於諧振頻率Fr2,將提高切換頻率Fs(806),並回到步驟(801)。直到步驟(801)判斷差值Verror為零,表示切換頻率Fs與諧振頻率Fr2一致。If the step (803) is not greater than zero, indicating that the compensation direction is correct, it is further determined whether the current switching frequency Fs(n) is smaller than the previous switching frequency. The rate Fs(n-1)(804), if the current switching frequency Fs(n) is smaller than the previous switching frequency Fs(n-1), indicating that the switching frequency Fs is greater than the resonance frequency Fr2, thus lowering the switching frequency Fs(805), And return to step (801). If the current switching frequency Fs(n) is not less than the previous switching frequency Fs(n-1), indicating that the switching frequency Fs is smaller than the resonance frequency Fr2, the switching frequency Fs is increased (806), and the process returns to the step (801). Until step (801) determines that the difference Verror is zero, indicating that the switching frequency Fs coincides with the resonant frequency Fr2.
至於前述切換頻率Fs的調整可為以下幾種方式:由於切換頻率Fs與輸出電壓和輸入電壓的比值(Vo/Vin)有關,亦即與增益(Gain)有關,因此調整輸出電壓和輸入電壓,都可以改變切換頻率Fs;進一步而言,在開迴路模式下,係採固定的輸入電壓,經由控制輸出電壓大小,以調整切換頻率Fs。而在閉迴路模式下,則是控制輸入電壓大小,以調整該切換頻率Fs。The adjustment of the switching frequency Fs may be as follows: since the switching frequency Fs is related to the ratio of the output voltage to the input voltage (Vo/Vin), that is, related to the gain (Gain), the output voltage and the input voltage are adjusted. The switching frequency Fs can be changed; further, in the open loop mode, a fixed input voltage is adopted, and the switching frequency Fs is adjusted by controlling the magnitude of the output voltage. In the closed loop mode, the input voltage is controlled to adjust the switching frequency Fs.
根據圖1所示的實施例,直流對直流轉換器20的輸入電壓由交流對直流轉換器10提供,當交流對直流轉換器10的輸出電壓改變,直流對直流轉換器20的切換頻率Fs也將隨之改變,因此可由直流對直流轉換器20的諧振控制器25產生一回授電壓控制訊號(Bulk Control),送至交流對直流轉換器10的控制端BC,以改變該交流對直流轉換器10的輸出電壓,而經由改變直流對直流轉換器20的輸入電壓,以調整切換頻率Fs。對於所屬技術領域具有通常知識者可以理解的是:交流對直流轉換器10是根據其回授的直流電壓Vbulk和前述回授電壓控制訊號(Bulk Control),共同作為調整交流對直流轉換器10輸出電壓的 依據,一具體的實現技術係如以下所述。According to the embodiment shown in Fig. 1, the input voltage of the DC-DC converter 20 is supplied from the AC-DC converter 10. When the output voltage of the AC-DC converter 10 changes, the switching frequency Fs of the DC-DC converter 20 is also It will change accordingly, so a feedback control signal (Bulk Control) can be generated from the resonant controller 25 of the DC-to-DC converter 20, and sent to the control terminal BC of the AC-to-DC converter 10 to change the AC-to-DC conversion. The output voltage of the device 10 is adjusted by changing the input voltage of the DC-to-DC converter 20 to adjust the switching frequency Fs. It can be understood by those skilled in the art that the AC-to-DC converter 10 is used to adjust the output of the AC-to-DC converter 10 according to the DC voltage Vbulk and the aforementioned feedback voltage control signal (Bulk Control). Voltage According to a specific implementation technology, as described below.
請參閱圖1,該交流對直流轉換器10中具有一控制模組100,該控制模組100的一可行實施例是如圖11所示,該控制模組100包括一疊加電路101及一控制器102,該疊加電路101具有兩輸入端和一輸出端,兩輸入端分別連接交流對直流轉換器10的直流電源輸出端DC OUT和控制端BC,以取得回授的直流電壓Vbulk和前述回授電壓控制訊號(Bulk Control),並經疊加後送至控制器102的輸入端,由控制器102產生一驅動訊號,據以調整交流對直流轉換器10直流電源輸出端DC OUT上的直流電壓Vbulk。Referring to FIG. 1 , the AC-DC converter 10 has a control module 100. A possible embodiment of the control module 100 is as shown in FIG. 11 . The control module 100 includes a superimposing circuit 101 and a control. The superimposing circuit 101 has two input ends and an output end, and the two input ends are respectively connected to the DC power output terminal DC OUT and the control terminal BC of the AC to DC converter 10 to obtain the feedback DC voltage Vbulk and the foregoing The voltage control signal (Bulk Control) is superimposed and sent to the input end of the controller 102, and a driving signal is generated by the controller 102 to adjust the DC voltage on the DC output of the DC-to-DC converter 10 DC power supply output terminal. Vbulk.
由上述可知,本發明鑒於LLC電路因諧振元件的生產誤差,以致無法預先準確地計算諧振頻率Fr2,而因諧振頻率Fr2不確定,以致無法有效地調整切換頻率Fs與諧振頻率Fr2的對應關係;而本發明不以預設的諧振頻率Fr2作為調整基準,而是以實測數值判斷切換頻率Fs與諧振頻率Fr2的實際狀態,進而在進入穩態後動態地調整切換頻率Fs,以提升運作效率,並解決因諧振元件誤差無法準確計算諧振頻率所衍生的問題。As can be seen from the above, the present invention is in view of the production error of the LLC circuit due to the resonance element, so that the resonance frequency Fr2 cannot be accurately calculated in advance, and the resonance frequency Fr2 is uncertain, so that the correspondence relationship between the switching frequency Fs and the resonance frequency Fr2 cannot be effectively adjusted; However, the present invention does not use the preset resonant frequency Fr2 as the adjustment reference, but determines the actual state of the switching frequency Fs and the resonant frequency Fr2 by the measured value, and then dynamically adjusts the switching frequency Fs after entering the steady state to improve the operating efficiency. And solve the problem caused by the inability to accurately calculate the resonant frequency due to the error of the resonant component.
10‧‧‧交流對直流轉換器10‧‧‧AC to DC converter
100‧‧‧控制模組100‧‧‧Control Module
20‧‧‧直流對直流轉換器20‧‧‧DC to DC converter
21‧‧‧全橋電路21‧‧‧Full bridge circuit
22‧‧‧諧振電路22‧‧‧Resonance circuit
23‧‧‧變壓器23‧‧‧Transformers
24‧‧‧輸出電路24‧‧‧Output circuit
25‧‧‧諧振控制器25‧‧‧Resonance controller
30‧‧‧相位檢測器30‧‧‧ phase detector
Claims (10)
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TW102125921A TWI509969B (en) | 2013-07-19 | 2013-07-19 | Switched power supply with resonant converter and its control method |
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TW102125921A TWI509969B (en) | 2013-07-19 | 2013-07-19 | Switched power supply with resonant converter and its control method |
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TWI780983B (en) * | 2021-11-12 | 2022-10-11 | 國立臺灣科技大學 | Resonant converter using pre-conduction mechanism to realize wide output voltage range |
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JP6630536B2 (en) * | 2015-10-23 | 2020-01-15 | 日立グローバルライフソリューションズ株式会社 | Power supply |
TWI568163B (en) * | 2015-12-22 | 2017-01-21 | 財團法人工業技術研究院 | Isolated converter and isolated converter? control method |
CN108736727B (en) | 2017-04-14 | 2020-02-21 | 台达电子工业股份有限公司 | Power converter and control method thereof |
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TW201121223A (en) * | 2009-10-30 | 2011-06-16 | Delta Electronics Inc | Method and apparatus for regulating gain within a resonant converter |
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TWI780983B (en) * | 2021-11-12 | 2022-10-11 | 國立臺灣科技大學 | Resonant converter using pre-conduction mechanism to realize wide output voltage range |
US11831244B2 (en) | 2021-11-12 | 2023-11-28 | National Taiwan University Of Science And Technology | Resonant converter having pre-conduction mechanism for realizing wide output voltage range |
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