TWI482411B - Current fed single load switch series resonant converter doubler - Google Patents
Current fed single load switch series resonant converter doubler Download PDFInfo
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
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本發明係有關於一種電流饋給單開關串聯負載共振式倍壓型轉換器，特別係設有輸入電源連接扼流電感串聯功率開關，再於功率開關上並聯分流電容及一組共振槽，共振槽係由共振電感串聯共振電容所組成，該共振槽連接全波整流倍壓電路，最後並聯濾波電容及負載；如此，利用單一個功率開關在零電壓或零電流切換下，可降低其切換損失，並具有柔性切換的特性，同時提高轉換器的操作效率。The invention relates to a current feeding single switch series load resonance type double voltage type converter, in particular, an input power supply is connected with a choke inductor series power switch, and then a shunt capacitor and a group of resonance grooves are connected in parallel on the power switch, and the resonance The slot system is composed of a resonant inductor series resonant capacitor connected to the full-wave rectification voltage doubler circuit, and finally parallel filter capacitor and load; thus, the single power switch can be switched under zero voltage or zero current switching. Loss, and has the characteristics of flexible switching, while improving the operating efficiency of the converter.
長久以來人類對於地球上的自然資源過度開發，導致地球上的自然資源日漸匱乏，近年來人類開始意識到這個問題的嚴重性，且因科技與經濟迅速的發展，使人們的日常生活與電子產品有著密不可分的關係，但由於人類大量的使用石油、天然氣和煤炭，更造成全球的溫室效應與暖化，為了減緩全球溫室效應，並且管制二氧化碳的排放量，於是在1997年日本京都通過京都議定書，用以規定工業國家之二氧化碳減量責任。基於法令以及環保意識的抬頭，在發展電子科技的同時必須要解決日益嚴重的環保問題，然而造成環保問題的原因之一為電子產品的轉換效率低落而造成能源不必要的浪費。因此，如何提升能源的轉換技術，藉此提高電源的利用率，已成為現在與未來的科技發展重點，故在電力電子領域中，提高電路轉換效率變成當今重要的主題。For a long time, human beings have over-exploited the natural resources on the earth, resulting in the lack of natural resources on the earth. In recent years, human beings have begun to realize the seriousness of this problem, and because of the rapid development of technology and economy, people's daily life and electronic products. Inseparable relationship, but due to the large use of oil, natural gas and coal by humans, it has caused global greenhouse effect and warming. In order to mitigate the global greenhouse effect and regulate carbon dioxide emissions, it passed the Kyoto Protocol in Kyoto, Japan in 1997. To stipulate the responsibility for carbon dioxide reduction in industrial countries. Based on the rise of laws and environmental awareness, it is necessary to solve the increasingly serious environmental problems while developing electronic technology. However, one of the causes of environmental problems is the low efficiency of conversion of electronic products and unnecessary waste of energy. Therefore, how to improve the energy conversion technology and thereby improve the utilization rate of power supply has become the focus of current and future technological development. Therefore, in the field of power electronics, improving circuit conversion efficiency has become an important topic today.
電子產品所使用的轉換器，通常是以硬式切換的方式為主，且功率開關操作於高頻切換下，會造成電子產品的轉換效率低落，若使用具有柔性切換特性之轉換器，就能改善上述之問題，而共振式轉換器即為具有柔性切換特性之轉換器，此電路利用電感與電容所組成之共振電路，使功率開關上的電壓或電流降至零時進行切換，且當電路上之電容、電感以及切換頻率參數選擇適當，就可使功率開關操作在零電壓或零電流切換下，使功率開關切換損失降低，提高轉換器整體之效率；緣此，本發明人有鑑於習知存在有如上述之缺失，乃潛心研究、改良，遂得以首先發明本發明。The converters used in electronic products are usually hard-switched, and the power switch operates under high-frequency switching, which causes the conversion efficiency of electronic products to be low. If a converter with flexible switching characteristics is used, it can be improved. The above problem, and the resonant converter is a converter with flexible switching characteristics, which uses a resonant circuit composed of an inductor and a capacitor to switch the voltage or current on the power switch to zero, and when on the circuit When the capacitance, inductance and switching frequency parameters are properly selected, the power switch operation can be switched under zero voltage or zero current, the power switch switching loss is reduced, and the overall efficiency of the converter is improved. Therefore, the inventors have There is a deficiency as described above, and it has been painstakingly studied and improved, and the present invention has been first invented.
本發明之主要目的，係在提供一種利用單一個功率開關在零電壓或零電流切換下，可降低其切換損失，並具有柔性切換的特性，同時提高轉換器的操作效率之電流饋給單開關串聯負載共振式倍壓型轉換器。The main object of the present invention is to provide a current-feeding single switch that can reduce the switching loss by using a single power switch under zero voltage or zero current switching, and has the characteristics of flexible switching while improving the operating efficiency of the converter. Series load resonant type double voltage converter.
本發明之特徵係在：輸入電源連接扼流電感串聯功率開關，再於功率開關上並聯分流電容及一組共振槽，共振槽係由共振電感串聯共振電容所組成，該共振槽連接全波整流倍壓電路，最後並聯濾波電容及負載。The invention is characterized in that: the input power is connected to the choke inductor series power switch, and then the shunt capacitor and a set of resonant slots are connected in parallel on the power switch, and the resonant tank is composed of a resonant inductor series resonant capacitor, and the resonant tank is connected to the full wave rectification. Double voltage circuit, and finally parallel filter capacitor and load.
有關本發明為達上述之使用目的與功效，所採用之技術手段，茲舉出較佳可行之實施例，並配合圖式所示，詳述如下：本發明之實施例，請參閱第一圖所示，主要係設有輸入電源VDC 連接扼流電感Lm 串聯功率開關S，再於功率開關S上並聯分流電容C及一組共振槽1，共振槽1係由共振電感Ls 串聯共振電容Cs 所組成，該共振槽1連接全波整流倍壓電路2，全波整流倍壓電路2係由二極體D1 、D2 連接電容C1 、C2 所組成，該二極體D1 、D2 係為快速恢復(Fast Recovery)二極體或蕭特基(Schittky)二極體，最後並聯濾波電容Co 及負載R。For the purpose of the present invention, the preferred embodiments of the present invention are set forth in the accompanying drawings. As shown, the main system is provided with an input power supply V DC connected to the choke inductor L m series power switch S, and then a shunt capacitor C and a set of resonant tank 1 are connected in parallel with the power switch S, and the resonant tank 1 is resonantly resonated by the resonant inductor L s The capacitor C s is composed of the resonant tank 1 connected to the full-wave rectifying voltage doubler circuit 2, and the full-wave rectifying voltage doubler circuit 2 is composed of diodes D 1 and D 2 connected to capacitors C 1 and C 2 . The polar bodies D 1 and D 2 are fast recovery diodes or Schittky diodes, and finally parallel filter capacitors C o and loads R.
使用時，請參閱第一、二圖所示，在輸入電源VDC (電源側)輸入一直流電壓，經過扼流電感Lm後將直流電壓轉換成直流電流源(扼流電感電流iLm )，其電流漣波很小，再驅動功率開關S切換導通，功率開關S係選擇MOSFET電晶體開關，其內寄生之反向二極體可配合電路動作時流經功率開關S之逆向電流，再經分流電容C，而共振槽1係由共振電感LS 串聯共振電容CS 所組成，其輸入端由功率開關S作高頻切換得到弦波，負載R側的直流電壓是利用全波整流倍壓電路2串聯於共振槽1，將高頻交流電壓轉換成直流電壓而得，負載R端電壓是經由濾波電容C0 濾波穩壓後提供給負載R，其輸出端是經高頻整流過後，所得的漣波率會比在低頻整流過後小的很多，因此可以得到更趨近於直流的電壓給負載R，而濾波電容C0 的電容值大小，可經由電路設計計算出來，通常濾波電容C0 的電容值越大，電路特性會越更加明顯。When using, please refer to the first and second figures, input the DC voltage on the input power V DC (power supply side), and convert the DC voltage into a DC current source (the choke inductor current i Lm ) after the choke inductor Lm. The current ripple is small, and then the power switch S is switched to conduct. The power switch S selects the MOSFET transistor switch, and the parasitic reverse diode can cooperate with the reverse current flowing through the power switch S when the circuit is operated, and then shunt. Capacitor C, and the resonant tank 1 is composed of a resonant inductor L S series resonant capacitor C S , the input end of which is switched by the power switch S for high frequency to obtain a sine wave, and the DC voltage of the load R side is a full wave rectifying piezoelectric The circuit 2 is connected in series to the resonant tank 1 to convert the high-frequency alternating current voltage into a direct current voltage. The voltage at the load R terminal is filtered and regulated by the filter capacitor C 0 and supplied to the load R, and the output end thereof is subjected to high-frequency rectification. The chopping rate will be much smaller than that after the low frequency rectification, so that the voltage closer to DC can be obtained for the load R, and the capacitance value of the filter capacitor C 0 can be calculated through the circuit design. Usually, the filter capacitor C 0 Electricity The larger the capacitance, the more obvious the circuit characteristics will be.
本發明相關元件之波形，如第三圖所示，依其工作模式一～六可得第四～九圖，而此六個工作模式分別為：The waveforms of the related components of the present invention, as shown in the third figure, can be obtained from the fourth to the ninth diagram according to the working modes 1-6, and the six working modes are:
一、工作模式一(ωt 0 ωt <ωt 1 )，如第四圖所示：在ωt0 時，驅動電壓Vgs 由低電位變為高電位，此時功率開關S切換導通，因共振電感電流iLs 大於扼流電感電流iLm ，iLm -iLs 小於零，所以電流反向流經功率開關S，功率開關電流iS 由小於零漸漸上升，而分流電容C無電流通過，共振電感電流iLs 為正值，流經共振電容CS 並對共振電容CS 充電，共振電容電壓VCs 上升，當iLm -iLs 等於零的同時，功率開關電流iS 也上升至等於零，此時共振電感電流iLs 大於零，二極體D1 導通，當功率開關S升至等於零時，進入工作模式二。First, the working mode one (ω t 0 ω t <ω t 1 ), as shown in the fourth figure: at ωt 0 , the driving voltage V gs changes from a low potential to a high potential, at which time the power switch S is switched on, because the resonant inductor current i Ls is greater than the choke inductor The current i Lm , i Lm -i Ls is less than zero, so the current flows backward through the power switch S, the power switch current i S gradually rises from less than zero, and the shunt capacitor C has no current, and the resonant inductor current i Ls is positive. Flowing through the resonant capacitor C S and charging the resonant capacitor C S , the resonant capacitor voltage V Cs rises. When i Lm -i Ls is equal to zero, the power switch current i S also rises to equal zero, and the resonant inductor current i Ls is greater than zero. The diode D 1 is turned on, and when the power switch S rises to be equal to zero, it enters the working mode 2.
二、工作模式二(ωt 1 ωt <ωt 2 )，如第五圖所示：Second, the working mode two (ω t 1 ω t <ω t 2 ), as shown in the fifth figure:
在ωt1 時，功率開關S仍為導通，此時iLm -iLs 大於零，電流流經功率開關S，功率開關電流iS 為大於零，分流電容C仍無電流通過，共振電感電流iLs 仍為正值且持續下降，在流經共振電容CS 並對共振電容CS 充電，共振電容電壓VCs 上升，當共振電容電壓VCs 上升達到峰值時，共振電感電流iLs 降至零點，因此共振電感電流iLs 大於零，此時二極體D1 仍維持繼續導通，當共振電感電流iLs 降至零時，進入工作模式三。At ωt 1 , the power switch S is still on. At this time, i Lm -i Ls is greater than zero, the current flows through the power switch S, the power switch current i S is greater than zero, the shunt capacitor C still has no current, and the resonant inductor current i Ls is still positive and continues to decrease. When flowing through the resonant capacitor C S and charging the resonant capacitor C S , the resonant capacitor voltage V Cs rises. When the resonant capacitor voltage V Cs rises to a peak, the resonant inductor current i Ls falls to zero. Therefore, the resonant inductor current i Ls is greater than zero. At this time, the diode D 1 remains continuously turned on, and when the resonant inductor current i Ls falls to zero, it enters the operational mode three.
三、工作模式三(ωt 2 ωt <ωt 3 )，如第六圖所示：Third, the working mode three (ω t 2 ω t <ω t 3 ), as shown in the sixth figure:
在ωt2 時，功率開關S仍為導通，此時共振電感電流iLs 由零開始下降，共振電容電壓VCs 由峰值開始下降，因共振電感電流iLs 小於扼流電感電流iLm ，iLm -iLs 仍維持大於零，所以電流流經功率開關S，功率開關電流iS 為正值且漸漸上升，分流電容C上仍無電流流過，由於共振電感電流iLs 小於零，共振電流換向流經二極體D2 ，當驅動電壓Vgs 由高電位變為低電位時，進入工作模式四。At ωt 2 , the power switch S is still conducting. At this time, the resonant inductor current i Ls starts to decrease from zero, and the resonant capacitor voltage V Cs decreases from the peak value because the resonant inductor current i Ls is smaller than the turbulent inductor current i Lm , i Lm -i Ls still maintains greater than zero, so the current flows through the power switch S, the power switch current i S is positive and gradually rises, no current flows through the shunt capacitor C, because the resonant inductor current i Ls is less than zero, the resonant current is changed The current flows through the diode D 2 and enters the operation mode four when the driving voltage V gs changes from a high potential to a low potential.
四、工作模式四(ωt 3 ωt <ωt 4 )，如第七圖所示：Fourth, the working mode four (ω t 3 ω t <ω t 4 ), as shown in the seventh figure:
在ωt3 時，驅動電壓Vgs 由高電位變為低電位，共振電感電流iLs 仍小於扼流電感電流iLm ，iLm -iLs 仍大於零，因此功率開關S截止，所以電流流經分流電容C，所以分流電容電流iC 為正值，共振電容電壓VCs 由正值降為負值，共振電感電流iLs 由負值開始上升，由於共振電感電流iLs 小於零，此時二極體D2 為導通，當共振電感電流iLs 升至零點時，進入工作模式五。At ωt 3 , the driving voltage V gs changes from high potential to low potential, the resonant inductor current i Ls is still less than the choke inductor current i Lm , i Lm -i Ls is still greater than zero, so the power switch S is turned off, so the current flows through The shunt capacitor C, so the shunt capacitor current i C is positive, the resonant capacitor voltage V Cs is reduced from a positive value to a negative value, the resonant inductor current i Ls starts to rise from a negative value, because the resonant inductor current i Ls is less than zero, at this time two The polar body D 2 is turned on, and when the resonant inductor current i Ls rises to zero, it enters the operating mode five.
五、工作模式五(ωt 4 ωt <ωt 5 )，如第八圖所示：Five, working mode five (ω t 4 ω t <ω t 5 ), as shown in the eighth figure:
在ωt4 時，功率開關S仍為截止，共振電感電流iLs 仍小於扼流電感電流iLm ，iLm -iLs 大於零，電流流經分流電容C，所以分流電容電流iC 仍為正值，共振電容電壓VCs 由負值上升至正值，共振電感電流iLs 由零開始上升，由於共振電感電流iLs 大於零，此時二極體D2 仍維持繼續導通，當共振電感電iLs 上升至等於扼流電感iLm 電流，也就是iLm -iLs 等於零時，進入工作模式六。At ωt 4 , the power switch S is still off, the resonant inductor current i Ls is still less than the choke inductor current i Lm , i Lm -i Ls is greater than zero, and the current flows through the shunt capacitor C, so the shunt capacitor current i C is still positive The value of the resonant capacitor voltage V Cs rises from a negative value to a positive value, and the resonant inductor current i Ls rises from zero. Since the resonant inductor current i Ls is greater than zero, the diode D 2 remains energized and continues to conduct. i Ls rises to equal the current of the choke inductor i Lm , that is, when i Lm -i Ls is equal to zero, it enters the operating mode six.
六、工作模式六(ωt 5 ωt <ωt 6 )，如第九圖所示：Sixth, working mode six (ω t 5 ω t <ω t 6 ), as shown in the ninth:
在ωt5 時，功率開關S仍為截止，共振電感電流iLs 大於扼流電感電流iLm ，iLm -iLs 小於零，電流反向流經分流電容C，所以分流電容電流iC 為負值，共振電感電流iLs 為正值，對共振電容Cs 充電，共振電容電壓VCs 上升，由負值轉為正值，此時二極體D1 導通，當功率開關電壓Vds 跨壓降至為零時，功率開關S切換至導通，電路動作重新進入工作模式一。At ωt 5 , the power switch S is still off, the resonant inductor current i Ls is greater than the choke inductor current i Lm , i Lm -i Ls is less than zero, and the current flows backward through the shunt capacitor C, so the shunt capacitor current i C is negative The value, the resonant inductor current i Ls is a positive value, charging the resonant capacitor C s , the resonant capacitor voltage V Cs rises from a negative value to a positive value, at which time the diode D 1 is turned on, when the power switching voltage V ds crosses the voltage When it drops to zero, the power switch S switches to conduction, and the circuit action re-enters the operating mode one.
而驅動電壓Vgs 與功率開關電壓Vds 實測波形圖，如第十圖所示，在驅動電壓Vgs 於高電位時，功率開關S為導通，功率開關電壓Vds 為零，驅動電壓Vgs 為低電位時，功率開關電壓Vds 由零開始上升，在驅動電壓Vgs 由低電位轉為高電位時，功率開關電壓Vds 降至為零，由此可知功率開關S操作於零電壓切換，其CH1：X軸：5μs/div、Y軸：10V/div；CH2：X軸：5μs/div、Y軸：100V/div。The driving voltage V gs and the power switching voltage V ds measured waveform diagram, as shown in the tenth figure, when the driving voltage V gs is at a high potential, the power switch S is turned on, the power switching voltage V ds is zero, and the driving voltage V gs When the potential is low, the power switching voltage V ds rises from zero. When the driving voltage V gs changes from low to high, the power switching voltage V ds falls to zero, so that the power switch S operates at zero voltage switching. , CH1: X axis: 5 μs/div, Y axis: 10 V/div; CH2: X axis: 5 μs/div, Y axis: 100 V/div.
而驅動電壓Vgs 與功率開關電流iS 實測波形圖，如第十一圖所示，當功率開關S導通瞬間，因共振電感電流iLs 大於扼流電感電流iLm ，電流反向流經功率開關S，故功率開關電流iS 為負值時切換導通，另當功率開關S截止時，功率開關電流iS 為零，其CH1：X軸：5μs/div、Y軸：100V/div；CH2：X軸：5μs/div、Y軸：500mA/div。The driving voltage V gs and the power switching current i S measured waveform diagram, as shown in the eleventh figure, when the power switch S is turned on, because the resonant inductor current i Ls is greater than the choke inductor current i Lm , the current flows backward through the power Switch S, so the power switch current i S is negative when the switch is turned on, and when the power switch S is turned off, the power switch current i S is zero, its CH1: X axis: 5μs / div, Y axis: 100V / div; CH2 : X axis: 5 μs/div, Y axis: 500 mA/div.
而分流電容電壓Vc 與分流電容電流iC 實測波形圖，如第十二圖所示，當功率開關S截止時，分流電容電壓VC 上升，上升至最高點時，共振電感電流iLs 大於扼流電感電流iLm ，電流反向流經分流電容C，另當功率開關S導通時，iLm -iLs 流經功率開關S，分流電容C上並無電流，其CH1：X軸：5μs/div、Y軸：100V/div；CH2：X軸：5μs/div、Y軸：1A/div。The shunt capacitor voltage V c and the shunt capacitor current i C are measured waveform diagrams. As shown in the twelfth diagram, when the power switch S is turned off, the shunt capacitor voltage V C rises, and when it rises to the highest point, the resonant inductor current i Ls is greater than The choke inductor current i Lm , the current flows backward through the shunt capacitor C. When the power switch S is turned on, i Lm -i Ls flows through the power switch S, and there is no current on the shunt capacitor C. Its CH1:X axis: 5μs /div, Y axis: 100V/div; CH2: X axis: 5μs/div, Y axis: 1A/div.
而共振電容電壓VCS 與共振電感電流iLS 實測波形圖，如第十三圖所示，由圖中可看出共振電容電壓VCS 與共振電感電流iLS 所呈現的交流弦波，其CH1：X軸：5μs/div、Y軸：50V/div；CH2：X軸：5μs/div、Y軸：1A/div。The resonant capacitor voltage V CS and the resonant inductor current i LS measured waveform diagram, as shown in the thirteenth figure, the resonant capacitor voltage V CS and the resonant inductor current i LS appearing in the figure can be seen as the AC sine wave, its CH1 : X axis: 5 μs/div, Y axis: 50 V/div; CH2: X axis: 5 μs/div, Y axis: 1 A/div.
而共振電感電壓VLS 與共振電感電流iLS 實測波形圖，如第十四圖所示，當共振電感電壓VLs 大於零時，共振電感Ls 開始儲存能量，共振電感電流iLs 上升，當共振電感電壓VLs 小於零時，共振電感Ls 釋放能量，共振電感電流iLs 下降，而共振電感電壓VLs 上的突波，是因為輸出端整流二極體(D1 、D2 )在切換時所造成的現象，其CH1：X軸：5μs/div、Y軸：100V/div；CH2：X軸：5μs/div、Y軸：1A/div。The resonant inductor voltage V LS and the resonant inductor current i LS measured waveform diagram, as shown in FIG. 14 , when the resonant inductor voltage V Ls is greater than zero, the resonant inductor L s begins to store energy, and the resonant inductor current i Ls rises when When the resonant inductor voltage V Ls is less than zero, the resonant inductor L s releases energy, the resonant inductor current i Ls decreases, and the surge on the resonant inductor voltage V Ls is because the output rectifying diode (D 1 , D 2 ) is The phenomenon caused by switching, CH1: X axis: 5μs/div, Y axis: 100V/div; CH2: X axis: 5μs/div, Y axis: 1A/div.
而共振電容電壓VCS 與共振電容電流iCS 實測波形圖，如第十五圖所示，當共振電容電流iCs 大於零時，共振電容CS 開始儲存能量，共振電容電壓VCs 上升，反之共振電容電流iCs 小於零時，共振電容CS 釋放能量，共振電容電壓VCs 下降，其CH1：X軸：5μs/div、Y軸：50V/div；CH2：X軸：5μs/div、Y軸：1A/div。And the resonant capacitor voltage V CS and the resonant capacitor current i CS measured waveform diagram, as shown in the fifteenth figure, when the resonant capacitor current i Cs is greater than zero, the resonant capacitor C S begins to store energy, the resonant capacitor voltage V Cs rises, and vice versa. When the resonant capacitor current i Cs is less than zero, the resonant capacitor C S releases energy, and the resonant capacitor voltage V Cs decreases. Its CH1:X axis: 5 μs/div, Y axis: 50 V/div; CH2: X axis: 5 μs/div, Y Axis: 1A/div.
而共振槽輸入電壓Va 與共振槽輸出電壓Vb 實測波形圖，如第十六圖所示，共振槽輸入電壓Va 就是等於並聯分流電容C上的電壓，共振槽輸出電壓Vb 為經由共振槽1共振後所得的交流方波電壓，其CH1：X軸：5μs/div、Y軸：100V/div；CH2：X軸：5μs/div、Y軸：50V/div。The resonant tank input voltage V a and the resonant tank output voltage V b are measured waveform diagrams. As shown in FIG. 16 , the resonant tank input voltage V a is equal to the voltage across the parallel shunt capacitor C, and the resonant tank output voltage V b is via The AC square wave voltage obtained after resonance of the resonance groove 1 has CH1: X axis: 5 μs/div, Y axis: 100 V/div, CH2: X axis: 5 μs/div, and Y axis: 50 V/div.
而共振槽輸出電壓Vb 與共振電容電流iCS 實測波形圖，如第十七圖所示，由圖中可看出共振槽輸入電壓Va 經由共振槽1共振，所得到的交流輸出電壓與輸出電流，其CH1：X軸：5μs/div、Y軸：50V/div；CH2：X軸：5μs/div、Y軸：1A/div。The resonant tank output voltage V b and the resonant capacitor current i CS measured waveform diagram, as shown in FIG. 17, it can be seen from the figure that the resonant tank input voltage V a resonates via the resonant tank 1 and the obtained AC output voltage is Output current, CH1: X axis: 5 μs/div, Y axis: 50 V/div; CH2: X axis: 5 μs/div, Y axis: 1 A/div.
而輸出電壓Vout 與輸出電流iout 實測波形圖，如第十八圖所示，其CH1：X軸：5μs/div、Y軸：50V/div；CH2：X軸：5μs/div、Y軸：500mA/div。The output voltage V out and the output current i out are measured waveforms, as shown in Fig. 18, the CH1: X axis: 5 μs/div, the Y axis: 50 V/div; CH2: X axis: 5 μs/div, Y axis : 500mA/div.
本發明利用單一個功率開關在零電壓或零電流切換下，可降低其切換損失，並具有柔性切換的特性，同時提高轉換器的操作效率。The invention utilizes a single power switch to reduce switching loss under zero voltage or zero current switching, and has the characteristics of flexible switching while improving the operating efficiency of the converter.
綜上所述，本發明實施例確實已能達到所預期之目的及使用功效，且未見有相同結構特徵公知、公用在先者，故本發明當能符合發明專利之申請要件，爰依法提出申請，懇請早日審結，並核賜專利，實深任感荷。In summary, the embodiments of the present invention have indeed achieved the intended purpose and the efficacy of use, and the same structural features are not known and commonly used, so the present invention can meet the requirements of the invention patent, and is proposed according to law. Apply, please apply for an early conclusion, and grant a patent, and I am deeply impressed.
1．．．共振槽1. . . Resonant slot
2．．．全波整流倍壓電路2. . . Full-wave rectification voltage doubler circuit
VDC 、Vin ．．．輸入電源V DC , V in . . . Input power
iin ．．．輸入電流i in . . . Input Current
Lm ．．．扼流電感L m . . . Choke inductor
iLm ．．．扼流電感電流i Lm . . . Choke inductor current
VLm ．．．扼流電感電壓V Lm . . . Choke inductor voltage
S．．．功率開關S. . . Power switch
iS ．．．功率開關電流i S . . . Power switch current
Vds ．．．功率開關電壓V ds . . . Power switch voltage
Vgs ．．．驅動電壓V gs . . . Driving voltage
C．．．分流電容C. . . Shunt capacitor
iC ．．．分流電容電流i C . . . Shunt capacitor current
Vc ．．．分流電容電壓V c . . . Shunt capacitor voltage
Va ．．．共振槽輸入電壓V a . . . Resonant tank input voltage
Ls ．．．共振電感L s . . . Resonance inductor
iLS ．．．共振電感電流i LS . . . Resonant inductor current
VLS ．．．共振電感電壓V LS. . . Resonant inductor voltage
Cs ．．．共振電容C s . . . Resonant capacitor
iCS ．．．共振電容電流i CS . . . Resonant capacitor current
VCS ．．．共振電容電壓V CS . . . Resonant capacitor voltage
Vb ．．．共振槽輸出電壓V b . . . Resonant tank output voltage
D1 、D2 ．．．二極體D 1 , D 2 . . . Dipole
iD1 、iD2 ．．．二極體電流i D1 , i D2 . . . Diode current
VD1 、VD2 ．．．二極體電壓V D1 , V D2 . . . Diode voltage
C1 、C2 ．．．電容C 1 , C 2 . . . capacitance
ic1 、ic2 ．．．電容電流i c1 , i c2 . . . Capacitance current
Vc1 、Vc2 ．．．電容電壓V c1 , V c2 . . . Capacitor voltage
Co ．．．濾波電容C o . . . Filter capacitor
ico ．．．濾波電容電流i co . . . Filter capacitor current
Vco ．．．濾波電容電壓V co . . . Filter capacitor voltage
R．．．負載R. . . load
iout ．．．輸出電流i out . . . Output current
Vout ．．．輸出電壓V out . . . The output voltage
第一圖所示係為本發明實施例之電路圖。The first figure is a circuit diagram of an embodiment of the present invention.
第二圖所示係為本發明實施例之方塊圖。The second figure is a block diagram of an embodiment of the present invention.
第三圖所示係為本發明實施例之波形圖。The third figure is a waveform diagram of an embodiment of the present invention.
第四圖所示係為本發明實施例工作模式一之等效電路圖。The fourth figure is an equivalent circuit diagram of the working mode 1 of the embodiment of the present invention.
第五圖所示係為本發明實施例工作模式二之等效電路圖。The fifth figure is an equivalent circuit diagram of the working mode 2 of the embodiment of the present invention.
第六圖所示係為本發明實施例工作模式三之等效電路圖。The sixth figure shows an equivalent circuit diagram of the working mode 3 of the embodiment of the present invention.
第七圖所示係為本發明實施例工作模式四之等效電路圖。The seventh figure is an equivalent circuit diagram of the working mode 4 of the embodiment of the present invention.
第八圖所示係為本發明實施例工作模式五之等效電路圖。The eighth figure is an equivalent circuit diagram of the working mode 5 of the embodiment of the present invention.
第九圖所示係為本發明實施例工作模式六之等效電路圖。The ninth figure is an equivalent circuit diagram of the working mode 6 of the embodiment of the present invention.
第十圖所示係為本發明實施例驅動電壓Vgs 與功率開關電壓Vds 實測波形圖。The tenth figure shows the measured waveforms of the driving voltage Vgs and the power switching voltage Vds in the embodiment of the present invention.
第十一圖所示係為本發明實施例驅動電壓Vgs 與功率開關電流iS 實測波形圖。The eleventh figure shows the measured waveforms of the driving voltage V gs and the power switching current i S according to the embodiment of the present invention.
第十二圖所示係為本發明實施例分流電容電壓Vc 與分流電容電流iC 實測波形圖。FIG. 12 is a waveform diagram of the shunt capacitor voltage V c and the shunt capacitor current i C according to an embodiment of the present invention.
第十三圖所示係為本發明實施例共振電容電壓VCS 與共振電感電流iLS 實測波形圖。Figure 13 is a waveform diagram of the resonant capacitor voltage V CS and the resonant inductor current i LS according to an embodiment of the present invention.
第十四圖所示係為本發明實施例共振電感電壓VLS 與共振電感電流iLS 實測波形圖。FIG. 14 is a waveform diagram of the resonant inductor voltage V LS and the resonant inductor current i LS according to an embodiment of the present invention.
第十五圖所示係為本發明實施例共振電容電壓VCS 與共振電容電流iCS 實測波形圖。The fifteenth figure is a measured waveform diagram of the resonant capacitor voltage V CS and the resonant capacitor current i CS according to the embodiment of the present invention.
第十六圖所示係為本發明實施例共振槽輸入電壓Va 與共振槽輸出電壓Vb 實測波形圖。Figure 16 is a waveform diagram of the resonant tank input voltage V a and the resonant tank output voltage V b according to the embodiment of the present invention.
第十七圖所示係為本發明實施例共振槽輸出電壓Vb 與共振電容電流icS 實測波形圖。Figure 17 is a waveform diagram of the resonant tank output voltage V b and the resonant capacitor current i cS according to an embodiment of the present invention.
第十八圖所示係為本發明實施例輸出電壓Vout 與輸出電流iout 實測波形圖。FIG. 18 is a waveform diagram of the output voltage V out and the output current i out according to an embodiment of the present invention.
1．．．共振槽1. . . Resonant slot
2．．．全波整流倍壓電路2. . . Full-wave rectification voltage doubler circuit
VDC ．．．輸入電源V DC . . . Input power
Lm ．．．扼流電感L m . . . Choke inductor
iLm ．．．扼流電感電流i Lm . . . Choke inductor current
S．．．功率開關S. . . Power switch
iS ．．．功率開關電流i S . . . Power switch current
Vgs ．．．驅動電壓V gs . . . Driving voltage
C．．．分流電容C. . . Shunt capacitor
iC ．．．分流電容電流i C. . . Shunt capacitor current
Ls ．．．共振電感L s . . . Resonance inductor
Cs ．．．共振電容C s . . . Resonant capacitor
Vb ．．．共振槽輸出電壓V b . . . Resonant tank output voltage
D1 、D2 ．．．二極體D 1 , D 2 . . . Dipole
C1 、C2 ．．．電容C 1 , C 2 . . . capacitance
Co ．．．濾波電容C o . . . Filter capacitor
R．．．負載R. . . load
iout ．．．輸出電流i out . . . Output current
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| CN105322785B (en) * | 2014-06-25 | 2018-01-19 | 台达电子工业股份有限公司 | Flexible suitching type bidirectional power converters and its operating method |
| TWI509972B (en) * | 2014-06-25 | 2015-11-21 | Delta Electronics Inc | Soft-switching bi-directional power converter and method of operating the same |
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| JP2007104747A (en) * | 2005-09-30 | 2007-04-19 | Sony Corp | Switching power circuit |
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| JP2007104747A (en) * | 2005-09-30 | 2007-04-19 | Sony Corp | Switching power circuit |
| TW200824219A (en) * | 2006-11-20 | 2008-06-01 | Kun Shan University Of Technology | A solar power boost charger of series connected load resonance type |
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| US10103647B2 (en) | 2016-08-17 | 2018-10-16 | Industrial Technology Research Institute | Sensorless measurement method and device for filter capacitor current by using a state observer |
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