TWI406485B - An interleaving converter - Google Patents
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Description
一種交錯式轉換器，尤指一種利用單電容來緩和切換開關上的電壓上升速度，進而降低切換損失之交錯式轉換器。An interleaved converter, especially an interleaved converter that utilizes a single capacitor to mitigate the voltage rise rate on the switch, thereby reducing switching losses.
一般轉換器已廣泛應用於直流-直流轉換器中，同時朝向輕、薄、短、小方向發展。為了降低轉換器的體積及重量，提高它的切換頻率已經成為解決此問題的主要途徑之一。然因提高轉換器的切換頻率會增加功率開關之切換損失，降低系統的轉換效率，甚至影響到轉換器的性能。General converters have been widely used in DC-DC converters, and are moving toward light, thin, short, and small directions. In order to reduce the size and weight of the converter, increasing its switching frequency has become one of the main ways to solve this problem. However, increasing the switching frequency of the converter increases the switching loss of the power switch, reduces the conversion efficiency of the system, and even affects the performance of the converter.
為了降低換損失，許多軟切換電路被應用於切換式轉換器中。依據軟切換電路的電路架構，可將其區分成被動式及主動式兩種。由於被動式軟切轉換器只需要採用被動元件，即在導通轉態時達到零電流轉態(ZCT)或在截止轉態時達到零電壓轉態(ZVT)的軟切(Soft Switch)功能。而主動式軟切換電路除了使用被動件之外，還須增加輔助開關，導致成本增加，因此被動式軟切電路常被使用在轉換器中。In order to reduce the switching loss, many soft switching circuits are used in the switching converter. According to the circuit architecture of the soft switching circuit, it can be divided into passive and active. Since the passive soft-switching converter only needs passive components, it is a zero current transition (ZCT) when the conduction state is turned on or a zero voltage transition (ZVT) soft switch function when the transition state is turned off. In addition to the use of passive components, active soft-switching circuits must add auxiliary switches, resulting in increased costs, so passive soft-cut circuits are often used in converters.
參考第一圖，為傳統被動式降壓轉換器之電路架構示意圖。如第一圖所示，以降壓轉換器為例，單組降壓轉換器1可採用無損耗截止型緩震電路10，來降低功率開關M1截止轉態期間的切換損失。為了進一步降低截止轉態期間的切換損失，降壓轉換器1***作於連續導通模式(CCM)與不連續導通模式(DCM)的邊界條件。然而，降壓轉換器1操作於邊界條件下，其電感電流的振幅變化範圍增大，將會 導致輸出電壓的漣波增加，同時限制了輸出功率的大小。Referring to the first figure, it is a schematic diagram of the circuit structure of a conventional passive buck converter. As shown in the first figure, taking the buck converter as an example, the single-group buck converter 1 can employ the lossless cut-off type cushioning circuit 10 to reduce the switching loss during the turn-off state of the power switch M1. In order to further reduce the switching loss during the off-state transition, the buck converter 1 is operated in a boundary condition of a continuous conduction mode (CCM) and a discontinuous conduction mode (DCM). However, the buck converter 1 operates under boundary conditions and its amplitude of the inductor current varies. This causes an increase in the output voltage ripple and limits the amount of output power.
參考第二圖，為傳統交錯式降壓轉換器之電路架構示意圖。如第二圖所示，為了降低截止轉態期間的切換損失，提高降壓轉換器1的功率處理能力以及降低降壓轉換器1的輸出電壓漣波，一種交錯式降壓轉換器2設置二組無損耗截止型緩震電路20、22遂被使用。雖然交錯式降壓轉換器2能達到軟切的效果，然而所需的元件數量及成本卻明顯的增加。Referring to the second figure, it is a schematic diagram of the circuit architecture of a conventional interleaved buck converter. As shown in the second figure, in order to reduce the switching loss during the off-state transition, improve the power handling capability of the buck converter 1 and reduce the output voltage chopping of the buck converter 1, an interleaved buck converter 2 is provided. The group lossless cutoff type cushioning circuits 20, 22 are used. Although the interleaved buck converter 2 can achieve a soft cut effect, the number of components required and the cost are significantly increased.
有鑑於此，為了解決上述的問題，本發明提供一種交錯式轉換器，係藉由單一電容來取代交錯式轉換器中的兩組截止型緩震電路，進而達到零電壓轉態的效果，並且減少元件的使用數目。In view of the above, in order to solve the above problems, the present invention provides an interleaved converter that replaces two sets of cut-off type cushioning circuits in an interleaved converter by a single capacitor, thereby achieving a zero voltage transition effect, and Reduce the number of components used.
本發明第一實施例揭示了一種交錯式轉換器，用以提供一負載用電，該種交錯式轉換器主要由一直流電源、一第一開關、一第二開關、一緩震電容、一第一儲能元件、一第二儲能元件、一第一飛輪二極體、一第二飛輪二極體及一輸出電容等元件連接組成。在本發明中，將前述各元件的連接關係加以調整，再重新組合，即可分別得到各種不同類型的該種交錯式轉換器，例如交錯式降壓轉換器、交錯式昇降壓轉換器及交錯式昇壓轉換器。The first embodiment of the present invention discloses an interleaved converter for providing a load power. The interleaved converter mainly includes a DC power supply, a first switch, a second switch, a cushioning capacitor, and a The first energy storage component, a second energy storage component, a first flywheel diode, a second flywheel diode, and an output capacitor are connected. In the present invention, the connection relationship of the foregoing components is adjusted and recombined to obtain various types of interleaved converters, such as an interleaved buck converter, an interleaved buck-boost converter, and an interleaving. Boost converter.
本發明第二實施例揭示了另外一種交錯式轉換器，用以提供一負載用電，該另外一種交錯式轉換器主要由一直流電源、一第一開關、一第二開關、一緩震電容、一第一儲能元件、一第二儲能元件、一第三儲能元件、一第四儲能元件、一第一電容、一第二電容、一第一飛輪二極體、 一第二飛輪二極體及一輸出電容等元件連接組成。在本發明中，將前述各元件的連接關係加以調整，再重新組合，即可分別得到各種不同類型的該另一種交錯式轉換器，例如交錯式Zeta轉換器、交錯式‘CUK轉換器及交錯式Sepic轉換器。A second embodiment of the present invention discloses another interleaved converter for providing a load power. The other interleaved converter is mainly composed of a DC power supply, a first switch, a second switch, and a cushioning capacitor. a first energy storage component, a second energy storage component, a third energy storage component, a fourth energy storage component, a first capacitor, a second capacitor, a first flywheel diode, A second flywheel diode and an output capacitor are connected to each other. In the present invention, the connection relationship of the foregoing components is adjusted and recombined to obtain different types of the other interleaved converters, such as an interleaved Zeta converter, an interleaved 'CUK converter, and an interleaving. Sepic converter.
本發明第三實施例揭示了一種交錯式轉換器，用以提供一負載用電，該交錯式轉換器包括有一電流型切換電路、一電力轉換單元、一第一飛輪二極體、一第二飛輪二極體、一緩震電容及一輸出電容。電流型切換電路用以輸出一交變輸入電壓，其具有一直流電源、一儲能元件及一切換單元。電力轉換單元具有一主級側與一次級側，該主級側耦接於電流型切換電路，電力轉換單元接收交變輸入電壓，以及從次級側輸出一交變輸出電壓，其中，次級側具有一第一輸出端、一第二輸出端及一中間抽頭端。第一飛輪二極體之第一陽極端連接於次級側之第一輸出端。第二飛輪二極體之第二陽極端連接於次級側之第二輸出端，第二飛輪二極體之第二陰極端連接於第一飛輪二極體之第一陰極端。緩震電容連接於次級側之第一輸出端與次級側之第二輸出端。輸出電容連接於第一陰極端與次級側之中間抽頭端之間，以及與負載並聯連接。A third embodiment of the present invention discloses an interleaved converter for providing a load power. The interleaved converter includes a current mode switching circuit, a power conversion unit, a first flywheel diode, and a second Flywheel diode, a cushioning capacitor and an output capacitor. The current mode switching circuit is configured to output an alternating input voltage having a DC power source, an energy storage component, and a switching unit. The power conversion unit has a main stage side and a primary stage side, the main stage side is coupled to the current mode switching circuit, the power conversion unit receives the alternating input voltage, and outputs an alternating output voltage from the secondary side, wherein the secondary The side has a first output end, a second output end and a middle tap end. The first anode end of the first flywheel diode is coupled to the first output of the secondary side. The second anode end of the second flywheel diode is connected to the second output end of the secondary side, and the second cathode end of the second flywheel diode is connected to the first cathode end of the first flywheel diode. The cushioning capacitor is connected to the first output end of the secondary side and the second output end of the secondary side. The output capacitor is connected between the first cathode end and the intermediate tap end of the secondary side, and is connected in parallel with the load.
綜上所述，本發明提供之交錯式轉換器主要是利用單一緩震電容來取代傳統交錯式轉換器中的兩組截止型緩震電路，以達到零電壓(ZVT)轉態的效果。同時，本發明提供之交錯式轉換器能夠減少元件的使用數目，進而改善了傳統技術中，因為元件數量所導致成本增加的問題。In summary, the interleaved converter provided by the present invention mainly replaces two sets of cut-off type cushioning circuits in the conventional interleaved converter with a single cushioning capacitor to achieve a zero voltage (ZVT) transition state. At the same time, the interleaved converter provided by the present invention can reduce the number of components used, thereby improving the problem of the increase in cost due to the number of components in the conventional art.
以上的概述與接下來的詳細說明皆為示範性質，是為 了進一步說明本發明的申請專利範圍。而有關本發明的其他目的與優點，將在後續的說明與圖示加以闡述。The above summary and the following detailed description are exemplary and are The scope of the patent application of the present invention is further explained. Other objects and advantages of the present invention will be described in the following description and drawings.
本發明提供之交錯式轉換器之實施例適用於各種不同的基本交錯式轉換器，例如交錯式buck轉換器所衍生的轉換器包含有交錯式降壓轉換器、交錯式昇降壓轉換器及交錯式Zeta轉換器。交錯式boost轉換器所衍生之轉換器包含有交錯式昇壓轉換器、交錯式`CUK轉換器及交錯式Sepic轉換器。為了提高交錯式轉換器的輸出能力及轉換效率，本發明將單一個緩震電容設置在基本交錯式轉換器中，作為其緩震電路之應用。The embodiment of the present invention provides an interleaved converter suitable for use in a variety of different basic interleaved converters, such as interleaved buck converters, converters including interleaved buck converters, interleaved buck-boost converters, and interleaving Type Zeta converter. The converter derived from the interleaved boost converter includes an interleaved boost converter, an interleaved `CUK converter, and an interleaved Sepic converter. In order to improve the output capability and conversion efficiency of the interleaved converter, the present invention sets a single cushioning capacitor in a basic interleaved converter as its cushioning circuit application.
以下就單一個緩震電容取代傳統交錯式轉換器中的兩組截止型緩震電路的衍生過程做說明。同時為了簡化說明每一種交錯式轉換器的衍生過程，在此係以交錯式降壓轉換器作為例子說明，以下將詳細說明其推導過程。The following is a description of the derivation process of two sets of cut-off type cushioning circuits in a conventional interleaved converter instead of a single cushioning capacitor. At the same time, in order to simplify the description of the derivation process of each of the interleaved converters, an interleaved buck converter is taken as an example, and the derivation process will be described in detail below.
參考第三A圖，係為具兩組無損失截止型緩震電路之交錯式降壓轉換器之電路示意圖。在第三A圖中所示，虛線部分為無損失截止型緩震電路20、22。在緩震電路20、22中，若電容Cr2及Cr4上的跨壓以電壓源Vcr2及Vcr4來取代，則可用第三B圖的電路圖來取代第三A圖。由第三B圖中可觀察得知，電壓源Vcr2及Vcr4因不用充放電，因此二極體D3及D6可以被省略。當第三B圖中的電壓源Vcr2及Vcr4等於輸出電壓Vo時，節點B及F的電位等於節點H的電位，因此電路可簡化成第三C圖所示之電路圖。Referring to the third A diagram, it is a circuit diagram of an interleaved buck converter with two sets of lossless cut-off type cushioning circuits. As shown in the third A diagram, the broken line portions are lossless cutoff type cushioning circuits 20, 22. In the cushioning circuits 20, 22, if the voltage across the capacitors Cr2 and Cr4 is replaced by the voltage sources Vcr2 and Vcr4, the circuit diagram of the third B diagram can be used instead of the third diagram A. It can be observed from the third B diagram that the voltage sources Vcr2 and Vcr4 are not charged and discharged, so the diodes D3 and D6 can be omitted. When the voltage sources Vcr2 and Vcr4 in the third B diagram are equal to the output voltage Vo, the potentials of the nodes B and F are equal to the potential of the node H, so the circuit can be simplified to the circuit diagram shown in the third C diagram.
依據交錯式降壓轉換器2及截止型緩震電路20、22的動作原理，在一個切換週期期間，二極體D1及D8(或D2 及D5)動作除了在截止型緩震電路20、22諧振期間動作有所不同，其他時間皆相同。此外，由於諧振時間遠小於轉換器切換週期的時間，因此將節點A及G(或C及E)連接在一起，不影響交錯式降壓轉換器2的動作狀態，其電路圖如第三D圖所示。由第三D圖中可看出，二極體D1及D8為並聯，可將此兩個二極體D1、D8合併成單一個二極體D18，同理二極體D2及D5可合併成單一個二極體D25。According to the operation principle of the interleaved buck converter 2 and the cut-off type cushioning circuits 20, 22, the diodes D1 and D8 (or D2) during one switching period The operation of D5) is different except that during the resonance of the cut-off type damping circuits 20 and 22, the other times are the same. In addition, since the resonance time is much shorter than the switching period of the converter, the nodes A and G (or C and E) are connected together without affecting the operating state of the interleaved buck converter 2, and the circuit diagram is as shown in the third D-picture. Shown. As can be seen from the third D picture, the diodes D1 and D8 are connected in parallel, and the two diodes D1 and D8 can be combined into a single diode D18, and the same diodes D2 and D5 can be combined into one. Single diode D25.
此外，電容Cr1及Cr3為並聯連接，因此可將電容Cr1及Cr3合併成電容Cs，其電路圖如第三E圖所示。在第三E圖所示的電路中，將交錯式降壓轉換器2操作於連續導通模式(CCM)或不連續導通模式(DCM)時，流過電感L1及電感L2的電流皆是單方向性，同時，此電流與電感Lr1及Lr2的電流皆為單方向性，並且，電感L1與二極體D7及電感Lr2迴路並聯，因此可採用電感L1r取代。同理，電感L2與二極體D4及電感Lr1可用電感L2r取代，其電路圖如第三F圖所示。In addition, the capacitors Cr1 and Cr3 are connected in parallel, so that the capacitors Cr1 and Cr3 can be combined into a capacitor Cs, and the circuit diagram is as shown in the third E diagram. In the circuit shown in FIG. E, when the interleaved buck converter 2 is operated in continuous conduction mode (CCM) or discontinuous conduction mode (DCM), the current flowing through the inductor L1 and the inductor L2 is one direction. At the same time, the current and the currents of the inductors Lr1 and Lr2 are unidirectional, and the inductor L1 is connected in parallel with the diode D7 and the inductor Lr2, so that the inductor L1r can be used instead. Similarly, the inductor L2 and the diode D4 and the inductor Lr1 can be replaced by the inductor L2r, and the circuit diagram is as shown in the third F diagram.
由第三F圖中可得知，交錯式降壓轉換器3只需設置單一緩震電容Cs作為緩震電路之應用，即可達到無損失截止型緩震電路的功能，並且，同時也簡化了緩震電路之架構，以降低整體之元件使用數目。As can be seen from the third F picture, the interleaved buck converter 3 only needs to provide a single cushioning capacitor Cs as a cushioning circuit to achieve the function of the lossless cut-off type cushioning circuit, and at the same time simplify The architecture of the cushioning circuit is used to reduce the overall number of components used.
復參考第三F圖。本發明之交錯式降壓轉換器3用以提供一負載RL用電，其電路架構包含一直流電源Vs、一第一開關M1、一第二開關M2、一緩震電容Cs、一第一儲能元件L1r、一第二儲能元件L2r、一第一飛輪二極體D18、一第二飛輪二極體D25及一輸出電容Co。其中，第一開關M1之第一汲/源極端與第二開關M2之第一汲/源極端共同 連接於直流電源Vs之第一電源端。緩震電容Cs連接於第一開關M1之第二汲/源極端與第二開關M2之第二汲/源極端之間。Refer to the third F diagram. The interleaved buck converter 3 of the present invention is used to provide a load RL power, and the circuit structure thereof includes a DC power source Vs, a first switch M1, a second switch M2, a cushioning capacitor Cs, and a first storage. The energy component L1r, the second energy storage component L2r, a first flywheel diode D18, a second flywheel diode D25, and an output capacitor Co. Wherein the first 源/source terminal of the first switch M1 is common to the first 汲/source terminal of the second switch M2 Connected to the first power terminal of the DC power source Vs. The snubber capacitor Cs is connected between the second 汲/source terminal of the first switch M1 and the second 源/source terminal of the second switch M2.
此外，第一開關M1之第二汲/源極端更連接於第一儲能元件L1r之第一儲能端與第一飛輪二極體D18之陰極端，第二開關M2之第二汲/源極端更連接於第二儲能元件L2r之第一儲能端與第二飛輪二極體D25之陰極端。同時，第一儲能元件L1r之第二儲能端與第二儲能元件L2r之第二儲能端共同連接，並且，第一飛輪二極體D18之陽陰極端與第二飛輪二極體D25之陽極端共同連接於直流電源Vs之第二電源端。同時，輸出電容Co連接於第一儲能元件L1r之第二儲能端與直流電源Vs之第二電源端之間，以及與負載RL並聯連接。前述之第一儲能元件L1r與第二儲能元件L2r皆為一諧振電感。In addition, the second 源/source terminal of the first switch M1 is further connected to the first energy storage end of the first energy storage element L1r and the cathode end of the first flywheel diode D18, and the second 汲/source of the second switch M2 The pole is connected to the first energy storage end of the second energy storage element L2r and the cathode end of the second flywheel diode D25. At the same time, the second energy storage end of the first energy storage element L1r is connected in common with the second energy storage end of the second energy storage element L2r, and the anode and the second flywheel diode of the first flywheel diode D18 The anode terminal of D25 is commonly connected to the second power terminal of the DC power source Vs. At the same time, the output capacitor Co is connected between the second energy storage end of the first energy storage element L1r and the second power supply end of the DC power source Vs, and is connected in parallel with the load RL. The first energy storage element L1r and the second energy storage element L2r are both a resonant inductor.
復參考第三F圖，配合第三G圖所示電路之各重要元件的電壓及電流波形示意圖。以下，本發明係以交錯式降壓轉換器3之電路作為說明，其操作原理可區分成下述之操作模式。Referring to the third F diagram, the voltage and current waveforms of the important components of the circuit shown in the third G diagram are combined. Hereinafter, the present invention is described by the circuit of the interleaved buck converter 3, and its operation principle can be divided into the following operation modes.
模式1[t0≦t<t1]：在t0之前，第二飛輪二極體D18處於飛輪狀態，第二諧振電感電流IL2等於第二飛輪二極體電流ID2。當t=t0時，第一開關M1導通，第二諧振電感電流IL2為第二飛輪二極體電流1D2與緩震電容電流1C1的總和。由於，t0~t1的時間非常短暫，所以第一諧振電感電流IL1幾乎等於0A，緩震電容電壓VC1也接近於0V，因此，第一開關電流IDS1幾乎等於緩震電容電流IC1。在此期間內，緩震電容電流IC1瞬間增加至第二諧振電感電 流IL2，而第二飛輪二極體電流ID2瞬間減至0A。Mode 1 [t0≦t<t1]: Before t0, the second flywheel diode D18 is in the flywheel state, and the second resonant inductor current IL2 is equal to the second flywheel diode current ID2. When t=t0, the first switch M1 is turned on, and the second resonant inductor current IL2 is the sum of the second flywheel diode current 1D2 and the cushioning capacitor current 1C1. Since the time of t0~t1 is very short, the first resonant inductor current IL1 is almost equal to 0A, and the buffer capacitor voltage VC1 is also close to 0V. Therefore, the first switch current IDS1 is almost equal to the cushioning capacitor current IC1. During this period, the cushioning capacitor current IC1 is instantaneously increased to the second resonant inductor Flow IL2, while the second flywheel diode current ID2 is instantaneously reduced to 0A.
模式2[t1≦t<t2]：在t=t1時，緩震電容電流IC1等於第二諧振電感電流IL2，而第二飛輪二極體D25處於逆向偏壓。在此狀態中，緩震電容Cs與第二諧振電感L2r發生諧振，而第一開關電流IDS1等於諧振電感電流IL2(=IC1)和第一諧振電感電流IL1之電流總和。由電路原理之分析，此諧振時間tg1(t1~t2)可由下面公式(1)得知：
前述公式(1)中，L1為第一諧振電感L1r之電感值；L2為第二諧振電感L2r之電感值；C1為緩震電容Cs之電容值。In the above formula (1), L1 is an inductance value of the first resonance inductor L1r; L2 is an inductance value of the second resonance inductor L2r; and C1 is a capacitance value of the cushioning capacitor Cs.
模式3[t2≦t<t3]：當t=t2時，緩震電容電壓VC1等於直流電源Vs，由於第二諧振電感L2r的作用，第二飛輪二極體D25處於飛輪狀態，而第一開關M1一直保持在導通狀態。此時第一開關電流IDS1等於第一諧振電感電流IL1。在此期間，第一諧振電感電流IL1呈線性增加，而第二諧振電感電流IL2則呈線性減少。Mode 3 [t2≦t<t3]: When t=t2, the cushioning capacitor voltage VC1 is equal to the DC power source Vs, and the second flywheel diode D25 is in the flywheel state due to the action of the second resonant inductor L2r, and the first switch M1 remains in the on state. At this time, the first switching current IDS1 is equal to the first resonant inductor current IL1. During this period, the first resonant inductor current IL1 increases linearly, while the second resonant inductor current IL2 decreases linearly.
模式4[t3≦t<t4]：在t3時，第一開關M1截止。由於第一諧振電感電流IL1必須保持連續，因此強迫緩震電容Cs開始放電，使得第一開關M1具有零電壓轉態(ZVT)的特性。Mode 4 [t3≦t<t4]: At t3, the first switch M1 is turned off. Since the first resonant inductor current IL1 must remain continuous, the forced snubber capacitor Cs starts to discharge, so that the first switch M1 has a characteristic of zero voltage transition (ZVT).
模式5[t4≦t<t5]：當t=t4時，跨於緩震電容Cs的電壓VC1放電至零，此時第一飛輪二極體D18處於飛輪狀態。在此期間內，第一飛輪二極體D18與第二飛輪二極體D25都處於飛輪狀態。Mode 5 [t4≦t<t5]: When t=t4, the voltage VC1 across the cushioning capacitor Cs is discharged to zero, at which time the first flywheel diode D18 is in the flywheel state. During this period, both the first flywheel diode D18 and the second flywheel diode D25 are in a flywheel state.
模式6[t5≦t<t6]：在t5時，第一飛輪二極體D18處於飛輪狀態，由於第二諧振電感電流IL2降為零，使得第二飛輪二極體D25停止飛輪狀態。在此同時，第二開關M2開始導通，第一諧振電感電流IL1等於第一飛輪二極體電流ID1與負的緩震電容電流-IC1的總和。此外，由於第二開關電流IDS2會流經緩震電容Cs的低阻抗路徑，因此，第二飛輪二極體電流ID2將會受到第二開關電流IDS2的支配。此時，負的緩震電容電流-IC1很接近第二開關電流IDS2。在此狀態中，負的緩震電容電流-IC1突增至第一諧振電感電流IL1，而第一飛輪二極體電流ID1則急遽的降為0A。Mode 6 [t5≦t<t6]: At t5, the first flywheel diode D18 is in the flywheel state, and the second flywheel diode D25 stops the flywheel state because the second resonant inductor current IL2 falls to zero. At the same time, the second switch M2 starts to conduct, and the first resonant inductor current IL1 is equal to the sum of the first flywheel diode current ID1 and the negative cushioning capacitor current -IC1. In addition, since the second switch current IDS2 will flow through the low impedance path of the cushioning capacitor Cs, the second flywheel diode current ID2 will be dominated by the second switch current IDS2. At this time, the negative cushioning capacitor current -IC1 is very close to the second switching current IDS2. In this state, the negative cushioning capacitor current -IC1 suddenly increases to the first resonant inductor current IL1, and the first flywheel diode current ID1 drops sharply to 0A.
模式7[t6≦t<t7]：在t=t6時，第一飛輪二極體D18變成反向偏壓，而緩震電容Cs與第一諧振電感L1r形成緩震網路，並且開始諧振。此時第二開關電流IDS2等於第一諧振電感電流IL1(=-IC1)與第二諧振電感電流IL2的總和。由於緩震電容電流-IC1為負電流，故此緩震電容Cs為反向充電。Mode 7 [t6≦t<t7]: At t=t6, the first flywheel diode D18 becomes reverse biased, and the cushioning capacitor Cs forms a cushioning network with the first resonant inductor L1r and begins to resonate. At this time, the second switching current IDS2 is equal to the sum of the first resonant inductor current IL1 (=-IC1) and the second resonant inductor current IL2. Since the snubber capacitor current - IC1 is a negative current, the snubber capacitor Cs is reversely charged.
模式8[t7≦t<t8]：在t=t7時，緩震電容電壓VC1下降至負的直流電源-Vs，在此時負的緩震電容電流-IC1會達到最大負電流值。在此模式中，第一飛輪二極體D18處於飛輪狀態，而第二諧振電感電流IL2則呈現線性增加的趨勢。Mode 8 [t7≦t<t8]: At t=t7, the cushioning capacitor voltage VC1 drops to the negative DC power supply -Vs, at which time the negative cushioning capacitor current -IC1 will reach the maximum negative current value. In this mode, the first flywheel diode D18 is in the flywheel state, and the second resonant inductor current IL2 is in a linearly increasing trend.
模式9[t8≦t<t9]：在t8時，第二開關M2截止。由於第二諧振電感電流IL2必須保持連續，因而使緩震電容Cs開始放電。在此期間，緩震電容電壓VC1逐漸下降，當t=t9時，緩震電容電壓VC1會下降至零。Mode 9 [t8≦t<t9]: At t8, the second switch M2 is turned off. Since the second resonant inductor current IL2 must be kept continuous, the snubber capacitor Cs is started to discharge. During this period, the buffer capacitor voltage VC1 gradually decreases. When t=t9, the buffer capacitor voltage VC1 drops to zero.
模式10[t9≦t<t10]：在此期間，第一飛輪二極體D18 與第二飛輪二極體D25皆處於飛輪狀態，此時第一開關電流IDS1與第二開關電流IDS2呈現線性下降之趨勢。當t=t10時，第一開關M1再次導通，則完成一完整切換週期的操作。Mode 10 [t9≦t<t10]: During this period, the first flywheel diode D18 Both the second flywheel diode D25 and the second flywheel diode D25 are in a flywheel state, and the first switch current IDS1 and the second switch current IDS2 exhibit a linear decreasing trend. When t=t10, the first switch M1 is turned on again, and the operation of a complete switching cycle is completed.
依據前述以單一緩震電容取代傳統交錯式轉換器中的兩組截止型緩震電路的衍生過程說明。其他交錯式buck轉換器所衍生的交錯式昇降壓轉換器可根據此過程，衍生出使用單一緩震電容Cs作為緩震電路應用之交錯式昇降壓轉換器4，如第四A圖所示。另外，交錯式Zeta轉換器也可根據此過程，衍生出使用單一緩震電容Cs作為緩震電路應用之交錯式Zeta轉換器5，如第四B圖所示。In accordance with the foregoing description of a derivative process for replacing two sets of cut-off type cushioning circuits in a conventional interleaved converter with a single cushioning capacitor. According to this process, an interleaved buck-boost converter derived from other interleaved buck converters can derive an interleaved buck-boost converter 4 using a single cushioning capacitor Cs as a cushioning circuit application, as shown in FIG. In addition, the interleaved Zeta converter can also derive an interleaved Zeta converter 5 using a single cushioning capacitor Cs as a cushioning circuit application, as shown in FIG. 4B.
在第四A圖中。本發明之交錯式昇降壓轉換器4用以提供一負載RL用電，其電路架構包含一直流電源Vs、一第一開關M1、一第二開關M2、一緩震電容Cs、一第一儲能元件L1r、一第二儲能元件L2r、一第一飛輪二極體D18、一第二飛輪二極體D25及一輸出電容Co。其中，第一開關M1之第一汲/源極端與第二開關M2之第一汲/源極端共同連接於直流電源Vs之第一電源端。緩震電容Cs連接於第一開關M1之第二汲/源極端與第二開關M2之第二汲/源極端之間。In the fourth A picture. The interleaved buck-boost converter 4 of the present invention is used to provide a load RL power, and the circuit structure thereof includes a DC power source Vs, a first switch M1, a second switch M2, a cushioning capacitor Cs, and a first storage. The energy component L1r, the second energy storage component L2r, a first flywheel diode D18, a second flywheel diode D25, and an output capacitor Co. The first 源/source terminal of the first switch M1 and the first 汲/source terminal of the second switch M2 are commonly connected to the first power terminal of the DC power source Vs. The snubber capacitor Cs is connected between the second 汲/source terminal of the first switch M1 and the second 源/source terminal of the second switch M2.
此外，第一開關M1之第二汲/源極端更連接第一飛輪二極體D18之陰極端與第一儲能元件L1r之第一儲能端，第二開關M2之第二汲/源極端更連接第二飛輪二極體D25之陰極端與第二儲能元件L2r之第一儲能端。同時，第一飛輪二極體D18之陽極端與第二飛輪二極體D25之陽極端共同連接。並且，第一儲能元件L1r之第二儲能端與第二 儲能元件L2r之第二儲能端共同連接於直流電源VS之第二電源端。同時，輸出電容Co連接於第一飛輪二極體D18之陽極端與直流電源Vs之第二電源端之間，以及與負載RL並聯連接。In addition, the second 源/source terminal of the first switch M1 is further connected to the cathode end of the first flywheel diode D18 and the first energy storage end of the first energy storage element L1r, and the second 汲/source terminal of the second switch M2 The cathode end of the second flywheel diode D25 and the first energy storage end of the second energy storage element L2r are further connected. At the same time, the anode end of the first flywheel diode D18 is commonly connected to the anode end of the second flywheel diode D25. And, the second energy storage end of the first energy storage component L1r and the second The second energy storage end of the energy storage component L2r is commonly connected to the second power supply end of the DC power supply VS. At the same time, the output capacitor Co is connected between the anode terminal of the first flywheel diode D18 and the second power terminal of the DC power source Vs, and is connected in parallel with the load RL.
在第四B圖中。本發明之交錯式Zeta壓轉換器5用以提供一負載RL用電，其電路架構包含一直流電源Vs、一第一開關M1、一第二開關M2、一緩震電容Cs、一第一儲能元件L11、一第二儲能元件L21、一第三儲能元件L12、一第四儲能元件L22、一第一電容C1、一第二電容C2、一第一飛輪二極體D18、一第二飛輪二極體D25及一輸出電容Co。In the fourth B picture. The interleaved Zeta voltage converter 5 of the present invention is used to provide a load RL power, and the circuit structure thereof includes a DC power source Vs, a first switch M1, a second switch M2, a cushioning capacitor Cs, and a first storage. The energy component L11, the second energy storage component L21, the third energy storage component L12, the fourth energy storage component L22, a first capacitor C1, a second capacitor C2, a first flywheel diode D18, and a first flywheel diode D18 The second flywheel diode D25 and an output capacitor Co.
其中，第一開關M1之第一汲/源極端與第二開關M2之第一汲/源極端共同連接於直流電源Vs之第一電源端。第一開關M1之第二汲/源極端連接第一儲能元件L11之第一儲能端，並且經由第一電容C1連接第三儲能元件L12之第一儲能端。第二開關M2之第二汲/源極端連接第二儲能元件L21之第一儲能端，並且經由第二電容C2連接第四儲能元件L22之第一儲能端。同時，第三儲能元件L12之第二儲能端與第四儲能元件L22之第二儲能端共同連接。並且，第一儲能元件L11之第二儲能端與第二儲能元件L21之第二儲能端共同連接於直流電源Vs之第二電源端。The first 源/source terminal of the first switch M1 and the first 汲/source terminal of the second switch M2 are commonly connected to the first power terminal of the DC power source Vs. The second 源/source terminal of the first switch M1 is connected to the first energy storage end of the first energy storage element L11, and is connected to the first energy storage end of the third energy storage element L12 via the first capacitor C1. The second 源/source terminal of the second switch M2 is connected to the first energy storage end of the second energy storage element L21, and is connected to the first energy storage end of the fourth energy storage element L22 via the second capacitor C2. At the same time, the second energy storage end of the third energy storage element L12 is connected in common with the second energy storage end of the fourth energy storage element L22. Moreover, the second energy storage end of the first energy storage element L11 and the second energy storage end of the second energy storage element L21 are connected in common to the second power supply end of the DC power source Vs.
此外，緩震電容Cs連接於第三儲能元件L12之第一儲能端與第四儲能元件L22之第一儲能端之間。同時，第一飛輪二極體D18之陰極端連接於第三儲能元件L12之第一儲能端，第二飛輪二極體D25之陰極端連接於第四儲能元件L22之第一儲能端。並且，第一飛輪二極體D18之陽極 端與第二飛輪二極體D25之陽極端共同連接於直流電源Vs之第二電源端。同時，輸出電容Co連接於第三儲能元件L12之第二儲能端與直流電源Vs之第二電源端之間，以及與負載RL並聯連接。In addition, the cushioning capacitor Cs is connected between the first energy storage end of the third energy storage element L12 and the first energy storage end of the fourth energy storage element L22. At the same time, the cathode end of the first flywheel diode D18 is connected to the first energy storage end of the third energy storage component L12, and the cathode end of the second flywheel diode D25 is connected to the first energy storage of the fourth energy storage component L22. end. And, the anode of the first flywheel diode D18 The end is connected to the anode end of the second flywheel diode D25 to the second power terminal of the DC power source Vs. At the same time, the output capacitor Co is connected between the second energy storage end of the third energy storage element L12 and the second power supply end of the DC power source Vs, and is connected in parallel with the load RL.
同樣依據前述以單一緩震電容取代傳統交錯式轉換器中的兩組截止型緩震電路的衍生過程說明。其他交錯式boost轉換器所衍生之交錯式昇壓轉換器可根據此過程，衍生出使用單一緩震電容Cs作為緩震電路應用之交錯式昇壓轉換器6，如第五A圖所示。另外，交錯式`CUK轉換器也可根據此過程，衍生出使用單一緩震電容Cs作為緩震電路應用之交錯式`CUK轉換器7，如第五B圖所示。另外，交錯式Sepic轉換器也可根據此過程，衍生出使用單一緩震電容Cs作為緩震電路應用之交錯式Sepic轉換器8，如第五C圖所示。Also in accordance with the foregoing description of the derivative process of replacing the two sets of cut-off type cushioning circuits in the conventional interleaved converter with a single cushioning capacitor. According to this process, an interleaved boost converter derived from other interleaved boost converters can derive an interleaved boost converter 6 using a single buffer capacitor Cs as a cushioning circuit application, as shown in FIG. In addition, the interleaved `CUK converter can also derive an interleaved `CUK converter 7 using a single cushioning capacitor Cs as a cushioning circuit application according to this process, as shown in FIG. In addition, the interleaved Sepic converter can also derive an interleaved Sepic converter 8 using a single cushioning capacitor Cs as a cushioning circuit application, as shown in FIG. 5C.
在第五A圖中。本發明之交錯式昇壓轉換器6用以提供一負載RL用電，其電路架構包含一直流電源Vs、一第一開關M1、一第二開關M2、一緩震電容Cs、一第一儲能元件L1r、一第二儲能元件L2r、一第一飛輪二極體D18、一第二飛輪二極體D25及一輸出電容Co。其中，第一儲能元件L1r之第一儲能端與第二儲能元件L2r之第一儲能端共同連接於直流電源Vs之第一電源端。緩震電容Cs連接於第一儲能元件L1r之第二儲能端與第二儲能元件L2r之第二儲能端之間。In the fifth A picture. The interleaved boost converter 6 of the present invention is used to provide a load RL power. The circuit structure includes a DC power source Vs, a first switch M1, a second switch M2, a cushioning capacitor Cs, and a first storage. The energy component L1r, the second energy storage component L2r, a first flywheel diode D18, a second flywheel diode D25, and an output capacitor Co. The first energy storage end of the first energy storage component L1r and the first energy storage end of the second energy storage component L2r are commonly connected to the first power supply end of the DC power source Vs. The cushioning capacitor Cs is connected between the second energy storage end of the first energy storage element L1r and the second energy storage end of the second energy storage element L2r.
此外，第一儲能元件L1r之第二儲能端更連接第一飛輪二極體D18之陽極端與第一開關M1之第一汲/源極端，第二儲能元件L2r之第二儲能端更連接第二飛輪二極體 D25之陽極端與第二開關M2之第一汲/源極端。同時，第一飛輪二極體D18之陰極端與第二飛輪二極體D25之陰極端共同連接。並且，第一開關M1之第二汲/源極端與第二開關M2之第二汲/源極端共同連接於直流電源VS之第二電源端。同時，輸出電容Co連接於第一飛輪二極體D18之陰極端與直流電源Vs之第二電源端之間，以及與負載RL並聯連接。In addition, the second energy storage end of the first energy storage component L1r is further connected to the anode end of the first flywheel diode D18 and the first 汲/source terminal of the first switch M1, and the second energy storage of the second energy storage component L2r The second end is connected to the second flywheel diode The anode end of D25 and the first 汲/source terminal of the second switch M2. At the same time, the cathode end of the first flywheel diode D18 is commonly connected to the cathode end of the second flywheel diode D25. Moreover, the second 汲/source terminal of the first switch M1 and the second 汲/source terminal of the second switch M2 are commonly connected to the second power terminal of the DC power source VS. At the same time, the output capacitor Co is connected between the cathode end of the first flywheel diode D18 and the second power terminal of the DC power source Vs, and is connected in parallel with the load RL.
在第五B圖中。本發明之交錯式`CUK壓轉換器7用以提供一負載RL用電，其電路架構包含一直流電源Vs、一第一開關M1、一第二開關M2、一緩震電容Cs、一第一儲能元件L11、一第二儲能元件L21、一第三儲能元件L12、一第四儲能元件L22、一第一電容C1、一第二電容C2、一第一飛輪二極體D18、一第二飛輪二極體D25及一輸出電容Co。In the fifth B picture. The interleaved `CUK voltage converter 7 of the present invention is used to provide a load RL power, and the circuit structure thereof includes a DC power source Vs, a first switch M1, a second switch M2, a cushioning capacitor Cs, and a first An energy storage component L11, a second energy storage component L21, a third energy storage component L12, a fourth energy storage component L22, a first capacitor C1, a second capacitor C2, a first flywheel diode D18, A second flywheel diode D25 and an output capacitor Co.
其中，第一儲能元件L11之第一儲能端與第二儲能元件L21之第一儲能端共同連接於直流電源Vs之第一電源端。第一儲能元件L11之第二儲能端連接於第一開關M1之第一汲/源極端，並且經由第一電容C1連接第三儲能元件L12之第一儲能端。第二儲能元件L21之第二儲能端連接於第二開關M2之第一汲/源極端，並且經由第二電容C2連接第四儲能元件L22之第一儲能端。同時，第三儲能元件L12之第二儲能端與第四儲能元件L22之第二儲能端共同連接。並且，第一開關M1之第二汲/源極端與第二開關M2之第二汲/源極端共同連接於直流電源Vs之第二電源端。The first energy storage end of the first energy storage component L11 and the first energy storage end of the second energy storage component L21 are commonly connected to the first power supply end of the DC power source Vs. The second energy storage end of the first energy storage element L11 is connected to the first 汲/source terminal of the first switch M1, and is connected to the first energy storage end of the third energy storage element L12 via the first capacitor C1. The second energy storage end of the second energy storage element L21 is connected to the first 汲/source terminal of the second switch M2, and is connected to the first energy storage end of the fourth energy storage element L22 via the second capacitor C2. At the same time, the second energy storage end of the third energy storage element L12 is connected in common with the second energy storage end of the fourth energy storage element L22. Moreover, the second 源/source terminal of the first switch M1 and the second 汲/source terminal of the second switch M2 are commonly connected to the second power terminal of the DC power source Vs.
此外，緩震電容Cs連接於第三儲能元件L12之第一儲 能端與第四儲能元件L22之第一儲能端之間。同時，第一飛輪二極體D18之陽極端連接於第三儲能元件L12之第一儲能端，第二飛輪二極體D25之陽極端連接於第四儲能元件L22之第一儲能端，並且，第一飛輪二極體D18之陰極端與第二飛輪二極體D25之陰極端共同連接於直流電源Vs之第二電源端。同時，輸出電容Co連接於第三儲能元件L12之第二儲能端與直流電源Vs之第二電源端之間，以及與負載RL並聯連接。In addition, the cushioning capacitor Cs is connected to the first storage of the third energy storage component L12. The energy end is between the first energy storage end of the fourth energy storage element L22. At the same time, the anode end of the first flywheel diode D18 is connected to the first energy storage end of the third energy storage component L12, and the anode end of the second flywheel diode D25 is connected to the first energy storage of the fourth energy storage component L22. And the cathode end of the first flywheel diode D18 and the cathode end of the second flywheel diode D25 are commonly connected to the second power terminal of the DC power source Vs. At the same time, the output capacitor Co is connected between the second energy storage end of the third energy storage element L12 and the second power supply end of the DC power source Vs, and is connected in parallel with the load RL.
在第五C圖中。本發明之交錯式Sepic轉換器8用以提供一負載RL用電，其電路架構包含一直流電源Vs、一第一開關M1、一第二開關M2、一緩震電容Cs、一第一儲能元件L11、一第二儲能元件L21、一第三儲能元件L12、一第四儲能元件L22、一第一電容C1、一第二電容C2、一第一飛輪二極體D18、一第二飛輪二極體D25及一輸出電容Co。In the fifth C picture. The interleaved Sepic converter 8 of the present invention is used to provide a load RL power, and the circuit structure includes a DC power source Vs, a first switch M1, a second switch M2, a cushioning capacitor Cs, and a first energy storage. The component L11, a second energy storage component L21, a third energy storage component L12, a fourth energy storage component L22, a first capacitor C1, a second capacitor C2, a first flywheel diode D18, and a first Two flywheel diode D25 and an output capacitor Co.
其中，第一儲能元件L11之第一儲能端與第二儲能元件L21之第一儲能端共同連接於直流電源Vs之第一電源端。第一儲能元件L11之第二儲能端連接於第一開關M1之第一汲/源極端，並且經由第一電容C1連接第一飛輪二極體D18之陽極端。第二儲能元件L21之第二儲能端連接於第二開關M2之第一汲/源極端，並且經由第二電容C2連接第二飛輪二極體D25之陽極端。同時，第一飛輪二極體D18之陰極端與第二飛輪二極體D25之陰極端共同連接。並且，第一開關M1之第二汲/源極端與第二開關M2之第二汲/源極端共同連接於直流電源Vs之第二電源端。The first energy storage end of the first energy storage component L11 and the first energy storage end of the second energy storage component L21 are commonly connected to the first power supply end of the DC power source Vs. The second energy storage end of the first energy storage element L11 is connected to the first 汲/source terminal of the first switch M1, and is connected to the anode end of the first flywheel diode D18 via the first capacitor C1. The second energy storage end of the second energy storage element L21 is connected to the first 汲/source terminal of the second switch M2, and is connected to the anode end of the second flywheel diode D25 via the second capacitor C2. At the same time, the cathode end of the first flywheel diode D18 is commonly connected to the cathode end of the second flywheel diode D25. Moreover, the second 源/source terminal of the first switch M1 and the second 汲/source terminal of the second switch M2 are commonly connected to the second power terminal of the DC power source Vs.
此外，緩震電容Cs連接於第一飛輪二極體D18之陽極 端與第二飛輪二極體D25之陽極端之間。同時，第三儲能元件L12之第一儲能端連接於第一飛輪二極體D18之陽極端，第四儲能元件L22之第一儲能端連接於第二飛輪二極體D25之陽極端，並且，第三儲能元件L12之第二儲能端與第四儲能元件L22之第二儲能端共同連接於直流電源Vs之第二電源端。同時，輸出電容Co連接於第一飛輪二極體D18之陰極端與直流電源Vs之第二電源端之間，以及與負載RL並聯連接。In addition, the cushioning capacitor Cs is connected to the anode of the first flywheel diode D18 The end is between the anode end of the second flywheel diode D25. At the same time, the first energy storage end of the third energy storage component L12 is connected to the anode end of the first flywheel diode D18, and the first energy storage end of the fourth energy storage component L22 is connected to the anode of the second flywheel diode D25. In an extreme, the second energy storage end of the third energy storage element L12 and the second energy storage end of the fourth energy storage element L22 are connected in common to the second power supply end of the DC power source Vs. At the same time, the output capacitor Co is connected between the cathode end of the first flywheel diode D18 and the second power terminal of the DC power source Vs, and is connected in parallel with the load RL.
再者，在切換式電源轉換器架構中的半橋式轉換器、全橋式轉換器、推挽式轉換器、順向式轉換器以及反馳式轉換器皆可視為一種交錯式轉換器，因此，同樣皆可採用單一緩震電容作為截止型緩震電路之應用，以提高轉換器的效率。由於轉換器種類繁多，在此僅以半橋式轉換器、全橋式轉換器及推挽式轉換器等三種轉換器作為說明，同時，此舉例說明，不影響本發明實際上的範圍。Furthermore, the half-bridge converter, the full-bridge converter, the push-pull converter, the forward converter, and the flyback converter in the switched power converter architecture can be regarded as an interleaved converter. Therefore, a single cushioning capacitor can also be used as the cut-off type cushioning circuit to improve the efficiency of the converter. Since there are many types of converters, only three types of converters, such as a half bridge converter, a full bridge converter, and a push-pull converter, are described here, and this example does not affect the actual range of the present invention.
第六A圖所示為一種使用單一緩震電容Cs作為緩震電路應用之半橋式轉換器9。第六B圖所示為一種使用單一緩震電容Cs作為緩震電路應用之全橋式轉換器10。第六C圖所示為一種使用單一緩震電容Cs作為緩震電路應用之推挽式轉換器11。Figure 6A shows a half-bridge converter 9 using a single cushioning capacitor Cs as a cushioning circuit. Figure 6B shows a full bridge converter 10 using a single cushioning capacitor Cs as a cushioning circuit application. The sixth C diagram shows a push-pull converter 11 using a single cushioning capacitor Cs as a cushioning circuit application.
在第六A圖中。半橋式轉換器9提供一負載RL用電，其包括有一電流型切換電路90、一電力轉換單元T1、一第一飛輪二極體D1、一第二飛輪二極體D2、一緩震電容Cs及一輸出電容Co。電流型切換電路90由一直流電源Vi、一儲能元件L1及一切換單元902組成，係將直流電源Vi的直流電轉成一交變輸入電壓AC1，並加以輸出，其中， 該電流型切換電路90為一半橋式開關電路，電力轉換單元T1為一變壓器。In the sixth picture A. The half bridge converter 9 provides a load RL power, which includes a current mode switching circuit 90, a power conversion unit T1, a first flywheel diode D1, a second flywheel diode D2, and a cushioning capacitor. Cs and an output capacitor Co. The current-type switching circuit 90 is composed of a DC power source Vi, an energy storage component L1, and a switching unit 902. The DC power of the DC power source Vi is converted into an AC input voltage AC1 and output. The current mode switching circuit 90 is a half bridge switching circuit, and the power conversion unit T1 is a transformer.
復參考第六A圖。電力轉換單元T1之主級側耦接於電流型切換電路90，用以接收交變輸入電壓AC1，且將交變輸入電壓AC1轉成一交變輸出電壓AC2，進而從電力轉換單元T1之次級側輸出。前述之電力轉換單元T1之次級側包含一第一輸出端TE1、一第二輸出端TE2及一中間抽頭端TM，緩震電容Cs連接於電力轉換單元T1之次級側之第一輸出端TE1與第二輸出端TE2之間。第一飛輪二極體D1之陽極端連接於電力轉換單元T1之次級側之第一輸出端TE1，第二飛輪二極體D2之陽極端連接於電力轉換單元T1之次級側之第二輸出端TE2，同時，第一飛輪二極體D1之陰極端與第二飛輪二極體D2之陰極端共同連接。輸出電容Co連接於第一飛輪二極體D1之陰極端與電力轉換單元T1之次級側之中間抽頭端TM之間，以及與負載RL並聯連接。Refer to Figure 6A for details. The main-stage side of the power conversion unit T1 is coupled to the current-type switching circuit 90 for receiving the alternating input voltage AC1 and converting the alternating input voltage AC1 into an alternating output voltage AC2, and then from the power conversion unit T1. Stage side output. The secondary side of the power conversion unit T1 includes a first output terminal TE1, a second output terminal TE2, and a middle tap terminal TM. The buffer capacitor Cs is connected to the first output end of the secondary side of the power conversion unit T1. Between TE1 and the second output terminal TE2. The anode end of the first flywheel diode D1 is connected to the first output terminal TE1 on the secondary side of the power conversion unit T1, and the anode end of the second flywheel diode D2 is connected to the second side of the secondary side of the power conversion unit T1. The output terminal TE2 is simultaneously connected to the cathode end of the first flywheel diode D1 and the cathode end of the second flywheel diode D2. The output capacitor Co is connected between the cathode terminal of the first flywheel diode D1 and the intermediate tap terminal TM of the secondary side of the power conversion unit T1, and is connected in parallel with the load RL.
配合第六A圖。在第六B圖中，全橋式轉換器10與前述半橋式轉換器9之電路結構主要差異處，乃在於不同元件組成的切換單元。全橋式轉換器10的電流型切換電路100中，切換單元1002主要由四個切換開關M1至M4相互連接所組合而成，而半橋式轉換器9的電流型切換電路90中，切換單元902則是由二個切換開關M1制M2與二個電容C1至C2相互連接所組合而成。Cooperate with Figure 6A. In the sixth diagram B, the main difference between the full-bridge converter 10 and the circuit configuration of the aforementioned half-bridge converter 9 lies in the switching unit composed of different elements. In the current type switching circuit 100 of the full bridge converter 10, the switching unit 1002 is mainly composed of four switching switches M1 to M4 connected to each other, and in the current type switching circuit 90 of the half bridge converter 9, the switching unit The 902 is formed by combining two M2s of the switch M1 and two capacitors C1 to C2.
配合第六A圖。在第六C圖中，推挽式轉換器11與前述半橋式轉換器9之電路結構主要差異處，乃在於不同元件組成的切換單元。推挽式轉換器11的電流型切換電路110中，切換單元1102主要由二個切換開關M1至M2相互連 接所組合而成，而半橋式轉換器9的電流型切換電路90中，切換單元902則是由二個切換開關M1制M2與二個電容C1至C2相互連接所組合而成。Cooperate with Figure 6A. In the sixth C diagram, the main difference between the structure of the push-pull converter 11 and the aforementioned half-bridge converter 9 lies in the switching unit composed of different elements. In the current mode switching circuit 110 of the push-pull converter 11, the switching unit 1102 is mainly connected to each other by two switching switches M1 to M2. In the current mode switching circuit 90 of the half bridge converter 9, the switching unit 902 is formed by combining two M2s of two switching switches M1 and two capacitors C1 to C2.
復參考第六C圖，配合第七圖所示電路之各重要元件的電壓及電流波形示意圖。以下，本發明係以推挽式轉換器11之電路作為說明，其操作原理可區分成下述之操作模式。Referring to the sixth C diagram, the voltage and current waveforms of the important components of the circuit shown in the seventh figure are combined. Hereinafter, the present invention is described by the circuit of the push-pull converter 11, and its operation principle can be divided into the following operation modes.
模式1(t0≦t<t1)：在t0之前開關M1截止而M2處於導通狀態中，此時一次側的能量會經由變壓器T1之一次側繞組NP2經由變壓器T1鐵心傳送到二次側繞組NS2，再經由二極體D2送至負載端RL。當t=t0時，開關M2導通，在此狀態中，由於開關M1及M2同時導通，使得流入變壓器T1之一次側的電流分別流入繞組NP1及NP2，並且其電流方向相反，使得變壓器T1二次側繞組NS2之跨壓從Vo慢慢降至0。當繞組電壓低於Vo時，二極體D2截止，此時負載功率由輸出電容Co來提供。而緩震電容Cs上的跨壓也從-2VO慢慢降至0，由於緩震電容Cs的電壓慢慢做變化，因此二極體D2上的電壓變化會緩慢變化，促使二極體D2截止有零電壓轉態(zero-voltage transition：ZVT)。Mode 1 (t0≦t<t1): before T0, switch M1 is turned off and M2 is in the on state. At this time, the energy of the primary side is transmitted to the secondary winding NS2 via the transformer T1 core via the primary winding NP2 of the transformer T1. Then, it is sent to the load terminal RL via the diode D2. When t=t0, the switch M2 is turned on. In this state, since the switches M1 and M2 are simultaneously turned on, the current flowing to the primary side of the transformer T1 flows into the windings NP1 and NP2, respectively, and the current direction thereof is opposite, so that the transformer T1 is twice. The voltage across the side winding NS2 slowly drops from Vo to zero. When the winding voltage is lower than Vo, the diode D2 is turned off, and the load power is supplied from the output capacitor Co. The voltage across the cushioning capacitor Cs also slowly drops from -2VO to 0. Since the voltage of the cushioning capacitor Cs changes slowly, the voltage change on the diode D2 changes slowly, causing the diode D2 to be cut off. There is zero-voltage transition (ZVT).
模式2(t1≦t<t2)：當t=t1時，開關電流IDS1等於IDS2，並且其電流值等於電感電流IL1的一半，此時緩震電容Cs上跨的電壓為0。在此模式中，變壓器T1中的每個繞組電壓為0，而負載之功率由輸出電容Co來提供。Mode 2 (t1≦t<t2): When t=t1, the switch current IDS1 is equal to IDS2, and its current value is equal to half of the inductor current IL1, and the voltage across the buffer capacitor Cs is zero. In this mode, each winding voltage in transformer T1 is zero and the power of the load is provided by the output capacitance Co.
模式3(t2≦t<t3)：在t=t2時開關M2截止，此時電感電流IL1的電流全部流經繞組NP1，因此變壓器T1繞組NP1的電壓慢慢往上增加，並且電感電流IL1會經由二次 側繞組NS1及NS2，將緩震電容Cs的電壓從0往2Vo增加，由於緩震電容Cs的作用，促使開關M2在截止狀態時，有ZVT的特性。Mode 3 (t2≦t<t3): At t=t2, the switch M2 is turned off. At this time, the current of the inductor current IL1 flows through the winding NP1, so the voltage of the winding NP1 of the transformer T1 gradually increases upward, and the inductor current IL1 will Via the second time The side windings NS1 and NS2 increase the voltage of the cushioning capacitor Cs from 0 to 2Vo. Due to the action of the cushioning capacitor Cs, the switch M2 is in the off state and has the characteristics of ZVT.
模式4(t3≦t<t4)：當t=t3時，緩震電容Cs的跨壓達到2Vo，此時二極體D1導通，變壓器T1二次側繞組NS1被箝制到輸出電壓Vo在此操作模式中，輸入能量藉由變壓器T1一次側繞組NP1及二次側繞組NS1及二極體D1送至負載端RL，以提供負載RL所需電源。Mode 4 (t3≦t<t4): When t=t3, the voltage across the cushioning capacitor Cs reaches 2Vo. At this time, the diode D1 is turned on, and the secondary winding NS1 of the transformer T1 is clamped to the output voltage Vo. In the mode, the input energy is sent to the load terminal RL through the transformer T1 primary winding NP1 and the secondary winding NS1 and the diode D1 to provide the power required for the load RL.
模式5(t4≦t<t5)：當t=t4時，開關M2導通，在此狀態中由於開關M1及M2同時導通使得流入變壓器T1一次側的電流分別流入繞組NP1及NP2，並且其電流方向相反，使得變壓器T1二次側繞組NP2之跨壓從0慢慢升至Vo。當繞組電壓高於Vo時，二極體D1截止此時負載功率由輸出電容Co來提供。而緩震電容Cs上的跨壓也從2Vo慢慢降至0，由於緩震電容Cs的電壓慢慢做變化，因此二極體D1上的電壓會緩慢變化促使二極體D1截止有零電壓轉態(zero-voltage transition：ZVT)。Mode 5 (t4≦t<t5): When t=t4, the switch M2 is turned on. In this state, since the switches M1 and M2 are simultaneously turned on, the current flowing into the primary side of the transformer T1 flows into the windings NP1 and NP2, respectively, and the current direction thereof. On the contrary, the voltage across the secondary winding NP2 of the transformer T1 is gradually increased from 0 to Vo. When the winding voltage is higher than Vo, the diode D1 is turned off and the load power is supplied from the output capacitor Co. The voltage across the cushioning capacitor Cs also slowly drops from 2Vo to 0. Since the voltage of the cushioning capacitor Cs changes slowly, the voltage on the diode D1 changes slowly, causing the diode D1 to have zero voltage at the cutoff. Zero-voltage transition (ZVT).
模式6(t5≦t<t6)：當t=t5時，開關電流IDS1等於IDS2，並且其電流值等於電感電流IL1的一半，此時緩震電容Cs上跨的電壓為0。在此模式中變壓器T1中的每個繞組電壓為0而負載之功率由輸出電容Co來提供。Mode 6 (t5≦t<t6): When t=t5, the switch current IDS1 is equal to IDS2, and its current value is equal to half of the inductor current IL1, and the voltage across the buffer capacitor Cs is zero. In this mode each winding voltage in transformer T1 is zero and the power of the load is provided by output capacitor Co.
模式7(t6≦t<t7)：在t=t6時開關M2截止，此時電感電流IL1的電流全部流經繞組NP2，因此變壓器T1繞組NP2的電壓慢慢往下增加，並且電感電流IL1會經由二次側繞組NS1及NS2，將緩震電容Cs的電壓從0往-2Vo增加。由於緩震電容Cs的作用，促使開關M1在截止狀態時， 有ZVT的特性。Mode 7 (t6≦t<t7): At t=t6, the switch M2 is turned off. At this time, the current of the inductor current IL1 flows through the winding NP2, so the voltage of the winding NP2 of the transformer T1 gradually increases downward, and the inductor current IL1 will The voltage of the snubber capacitor Cs is increased from 0 to -2Vo via the secondary side windings NS1 and NS2. Due to the action of the cushioning capacitor Cs, the switch M1 is caused to be in the off state. There are features of ZVT.
模式8(t7≦t<t8)：當t=t7時，緩震電容Cs的跨壓達到-2Vo，此時二極體D2導通，變壓器T1二次側繞組NS2被箝制到輸出電壓Vo在此操作模式中，輸入能量藉由變壓器T1一次側繞組NP2及二次側繞組NS2及二極體D1送至負載端RL，以提供負載RL所需電源。當t=t8時，開關M1再次導通即完成一完整切換週期的操作。Mode 8 (t7≦t<t8): When t=t7, the voltage across the cushioning capacitor Cs reaches -2Vo, at which time the diode D2 is turned on, and the secondary winding NS2 of the transformer T1 is clamped to the output voltage Vo. In the operation mode, the input energy is sent to the load terminal RL through the transformer T1 primary winding NP2 and the secondary winding NS2 and the diode D1 to provide the power required for the load RL. When t=t8, the switch M1 is turned on again to complete the operation of a complete switching cycle.
綜上所述，本發明之交錯式轉換器之實施例適用於各種不同的基本非隔離型交錯式轉換器或隔離型交錯式轉換器，係藉由單一緩震電容來緩和轉換器中開關上的電壓上升速度，以達到1.具有簡單的電路架構、2.使用較少的元件、3.高的轉換效率及4.可降低電路的設計流程等優點。In summary, the embodiment of the interleaved converter of the present invention is applicable to a variety of different basic non-isolated interleaved converters or isolated interleaved converters, with a single cushioning capacitor to mitigate the switches in the converter. The voltage rise speed is up to 1. It has the advantages of simple circuit architecture, 2. use fewer components, 3. high conversion efficiency and 4. lower circuit design flow.
惟，以上所述，僅為本發明最佳之一的具體實施例之詳細說明與圖式，任何熟悉該項技藝者在本發明之領域內，可輕易思及之變化或修飾皆可涵蓋在以下本案之專利範圍。However, the above description is only a detailed description of the specific embodiments of the present invention, and any one skilled in the art can easily conceive changes or modifications in the field of the present invention. The scope of the patent in this case below.
1‧‧‧降壓轉換器1‧‧‧Buck Converter
10‧‧‧截止型緩震電路10‧‧‧ Cutoff type cushioning circuit
2‧‧‧交錯式降壓轉換器2‧‧‧Interleaved Buck Converter
20、22‧‧‧截止型緩震電路20, 22‧‧‧ Cutoff type cushioning circuit
3‧‧‧交錯式降壓轉換器3‧‧‧Interleaved Buck Converter
RL‧‧‧負載RL‧‧ load
Vs‧‧‧直流電源Vs‧‧‧DC power supply
M1‧‧‧第一開關M1‧‧‧ first switch
M2‧‧‧第二開關M2‧‧‧ second switch
Cs‧‧‧緩震電容Cs‧‧‧ cushioning capacitor
L1r‧‧‧第一儲能元件L1r‧‧‧ first energy storage component
L2r‧‧‧第二儲能元件L2r‧‧‧Second energy storage component
D18‧‧‧第一飛輪二極體D18‧‧‧First flywheel diode
D25‧‧‧第二飛輪二極體D25‧‧‧Second flywheel diode
Co‧‧‧輸出電容Co‧‧‧ output capacitor
IL1‧‧‧第一諧振電感電流IL1‧‧‧First Resonant Inductor Current
IL2‧‧‧第二諧振電感電流IL2‧‧‧Second resonant inductor current
ID1‧‧‧第一飛輪二極體電流ID1‧‧‧First Flywheel Diode Current
ID2‧‧‧第二飛輪二極體電流ID2‧‧‧Second flywheel diode current
IC1‧‧‧緩震電容電流IC1‧‧‧ cushioning capacitor current
VC1‧‧‧緩震電容電壓VC1‧‧‧ cushioning capacitor voltage
IDS1‧‧‧第一開關電流IDS1‧‧‧ first switch current
4‧‧‧交錯式昇降壓轉換器4‧‧‧Interleaved buck-boost converter
5‧‧‧交錯式Zeta壓轉換器5‧‧‧Interleaved Zeta Pressure Converter
L11‧‧‧第一儲能元件L11‧‧‧ first energy storage component
L21‧‧‧第二儲能元件L21‧‧‧Second energy storage component
L12‧‧‧第三儲能元件L12‧‧‧ third energy storage component
L22‧‧‧第四儲能元件L22‧‧‧ fourth energy storage component
C1‧‧‧第一電容C1‧‧‧first capacitor
C2‧‧‧第二電容C2‧‧‧second capacitor
6‧‧‧交錯式昇壓轉換器6‧‧‧Interleaved Boost Converter
7‧‧‧交錯式`CUK壓轉換器7‧‧‧Interleaved `CUK voltage converter
8‧‧‧交錯式Scpic轉換器8‧‧‧Interleaved Scpic Converter
9‧‧‧半橋式轉換器9‧‧‧Half-bridge converter
90、100、110‧‧‧電流型切換電路90, 100, 110‧‧‧ current mode switching circuit
T1‧‧‧電力轉換單元T1‧‧‧Power Conversion Unit
D1‧‧‧第一飛輪二極體D1‧‧‧First flywheel diode
D2‧‧‧第二飛輪二極體D2‧‧‧Second flywheel diode
Vi‧‧‧直流電源Vi‧‧‧DC power supply
L1‧‧‧儲能元件L1‧‧‧ energy storage components
902、1002、1102‧‧‧切換單元902, 1002, 1102‧‧‧ Switching unit
AC1‧‧‧交變輸入電壓AC1‧‧‧Alternating input voltage
AC2‧‧‧交變輸出電壓AC2‧‧‧Alternating output voltage
TE1‧‧‧第一輸出端TE1‧‧‧ first output
TE2‧‧‧第二輸出端TE2‧‧‧ second output
TM‧‧‧中間抽頭端TM‧‧‧Intermediate tap
第一圖為傳統被動式降壓轉換器之電路架構示意圖；第二圖為傳統交錯式降壓轉換器之電路架構示意圖；第三A圖至第三F圖為本發明第一實施例之交錯式降壓轉換器之衍生過程電路示意圖；第三G圖為本發明第一實施例之電路各重要元件的電壓及電流波形示意圖；第四A圖為本發明第二實施例之交錯式昇降壓轉換器電路示意圖；第四B圖為本發明第三實施例之交錯式Zeta轉換器電 路示意圖；第五A圖為本發明第四實施例之交錯式昇壓轉換器電路示意圖；第五B圖為本發明第五實施例之交錯式‘CUK轉換器電路示意圖；第五C圖為本發明第六實施例之交錯式Sepic轉換器電路示意圖；第六A圖為本發明第七實施例之半橋式轉換器電路示意圖；第六B圖為本發明第八實施例之全橋式轉換器電路示意圖；第六C圖為本發明第九實施例之推挽式轉換器電路示意圖；及第七圖為本發明第九實施例之電路各重要元件的電壓及電流波形示意圖。The first figure is a schematic diagram of a circuit structure of a conventional passive buck converter; the second figure is a schematic diagram of a circuit structure of a conventional interleaved buck converter; and the third to third F diagrams are interlaced according to the first embodiment of the present invention; Schematic diagram of a derivative process circuit of a buck converter; a third G diagram is a schematic diagram of voltage and current waveforms of various important components of the circuit of the first embodiment of the present invention; and FIG. 4A is an interleaved buck-boost conversion of the second embodiment of the present invention Schematic diagram of the circuit; fourth B is an interleaved Zeta converter according to a third embodiment of the present invention FIG. 5 is a schematic diagram of a circuit of an interleaved boost converter according to a fourth embodiment of the present invention; FIG. 5B is a schematic diagram of a circuit of an interleaved 'CUK converter according to a fifth embodiment of the present invention; A schematic diagram of a circuit of an interleaved Sepic converter according to a sixth embodiment of the present invention; a sixth diagram is a circuit diagram of a half bridge converter according to a seventh embodiment of the present invention; and a sixth diagram is a full bridge type according to the eighth embodiment of the present invention. FIG. 6 is a schematic diagram of a push-pull converter circuit according to a ninth embodiment of the present invention; and FIG. 7 is a schematic diagram showing voltage and current waveforms of various important components of the circuit according to the ninth embodiment of the present invention.
3‧‧‧交錯式降壓轉換器3‧‧‧Interleaved Buck Converter
RL‧‧‧負載RL‧‧ load
Vs‧‧‧直流電源Vs‧‧‧DC power supply
M1‧‧‧第一開關M1‧‧‧ first switch
M2‧‧‧第二開關M2‧‧‧ second switch
Cs‧‧‧緩震電容Cs‧‧‧ cushioning capacitor
L1r‧‧‧第一儲能元件L1r‧‧‧ first energy storage component
L2r‧‧‧第二儲能元件L2r‧‧‧Second energy storage component
D18‧‧‧第一飛輪二極體D18‧‧‧First flywheel diode
D25‧‧‧第二飛輪二極體D25‧‧‧Second flywheel diode
Co‧‧‧輸出電容Co‧‧‧ output capacitor
IL1‧‧‧第一諧振電感電流IL1‧‧‧First Resonant Inductor Current
IL2‧‧‧第二諧振電感電流IL2‧‧‧Second resonant inductor current
ID1‧‧‧第一飛輪二極體電流ID1‧‧‧First Flywheel Diode Current
ID2‧‧‧第二飛輪二極體電流ID2‧‧‧Second flywheel diode current
IC1‧‧‧緩震電容電流IC1‧‧‧ cushioning capacitor current
VC1‧‧‧緩震電容電壓VC1‧‧‧ cushioning capacitor voltage
IDS1‧‧‧第一開關電流IDS1‧‧‧ first switch current
IDS2‧‧‧第二開關電流IDS2‧‧‧Second switch current
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| TWI452815B (en) * | 2011-09-16 | 2014-09-11 | Univ Hungkuang | High performance staggered boost converter |
| TWI452812B (en) * | 2011-09-16 | 2014-09-11 | Univ Hungkuang | High Efficiency Staggered Boost Converter |
| TWI427912B (en) * | 2012-03-13 | 2014-02-21 | Univ Kun Shan | Interleaved dc-dc zero-voltage switching converter |
| CN102638221A (en) * | 2012-04-26 | 2012-08-15 | 南京航空航天大学 | Front end buck convertor lossless buffer circuit for controlling superpower high-speed motor |
| TWI575859B (en) * | 2015-10-29 | 2017-03-21 | 光寶電子（廣州）有限公司 | Interleaved buck converter |
| TWI625922B (en) * | 2017-04-12 | 2018-06-01 | 國立中山大學 | Wide-range voltage conversion ratios dc-dc converter |
| CN111987909A (en) * | 2020-08-05 | 2020-11-24 | 安徽工程大学 | Interleaved parallel DC/DC converter and control method thereof |
| TWI777735B (en) * | 2021-08-19 | 2022-09-11 | 亞源科技股份有限公司 | Boost converting apparatus with passive lossless snubber |
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| US5838558A (en) * | 1997-05-19 | 1998-11-17 | Trw Inc. | Phase staggered full-bridge converter with soft-PWM switching |
| TW200826456A (en) * | 2006-12-06 | 2008-06-16 | Sheng-You Ceng | Interleaving converter with the snubber of single-capacitor |
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| US5838558A (en) * | 1997-05-19 | 1998-11-17 | Trw Inc. | Phase staggered full-bridge converter with soft-PWM switching |
| TW200826456A (en) * | 2006-12-06 | 2008-06-16 | Sheng-You Ceng | Interleaving converter with the snubber of single-capacitor |
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