TW202207599A - Interleaved high voltage conversion ratio dc/dc converter - Google Patents

Interleaved high voltage conversion ratio dc/dc converter Download PDF

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TW202207599A
TW202207599A TW109126531A TW109126531A TW202207599A TW 202207599 A TW202207599 A TW 202207599A TW 109126531 A TW109126531 A TW 109126531A TW 109126531 A TW109126531 A TW 109126531A TW 202207599 A TW202207599 A TW 202207599A
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diode
auxiliary
inductor
power switch
switching
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TW109126531A
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TWI752579B (en
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楊松霈
陳信助
謝承道
林資祐
邱韋丞
林加耀
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崑山科技大學
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    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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Abstract

The invention discloses interleaved high voltage conversion ratio dc/dc converter, which obtains very high boost gain, reduces input current ripple, and reduces the volume of inductance. At the same time, there is no need to operate at very large conduction ratios, but has low voltage stress that is lower than output voltage, which reduces conduction losses and improve overall efficiency. Further, the invention can share the input current and effectively reduce the current stress of the storage unit and switching unit in the circuit, which is suitable for high power applications.

Description

交錯型高電壓轉換比直流轉換器Interleaved High Voltage Conversion Ratio DC Converter

本發明係有關於一種交錯型高電壓轉換比直流轉換器，尤其是指一種可得到極高的升壓增益，且可使輸入電流漣波降低，降低電感的體積，同時不必操作在極大的導通比，具有低於輸出電壓的低電壓應力，可降低導通損失，提升整體效率，並可分擔輸入電流，能有效降低電路中儲能元件及開關元件之電流應力，適合應用於高功率的場合，而在其整體施行使用上更增實用功效特性者。The present invention relates to an interleaved high voltage conversion ratio DC converter, in particular to a kind of high boost gain, which can reduce the input current ripple and reduce the volume of the inductance, and at the same time, it does not need to operate in a large conduction It has a low voltage stress lower than the output voltage, which can reduce the conduction loss, improve the overall efficiency, and can share the input current, which can effectively reduce the current stress of the energy storage elements and switching elements in the circuit, and is suitable for high-power applications. And in its overall implementation and use, it has more practical efficacy characteristics.

按，對於直流升壓目的而言，理論上，操作在極高導通比的傳統升壓型〔boost〕轉換器能夠得到高電壓增益，但是實務上受到寄生元件的影響，電壓轉換比受限在約5倍以下，因此當電壓增益高達10倍左右的實務需求時，研發嶄新的高升壓轉換器拓樸是必要的。因此，於近幾年來，高升壓DC-DC轉換器是電力電子工程領域中常見的研究主題之一。Press, for the purpose of DC boosting, in theory, a conventional boost converter operating at a very high conduction ratio can obtain high voltage gain, but in practice it is affected by parasitic components, and the voltage conversion ratio is limited to It is necessary to develop a new high boost converter topology when the voltage gain is as high as about 10 times practical requirements. Therefore, in recent years, high boost DC-DC converters are one of the common research topics in the field of power electronics engineering.

實務上操作在極大導通比的傳統升壓型轉換器其電壓增益是有所限制，而且轉換效率不佳。另一方面，操作在極大導通比的升壓型轉換器衍生了以下問題：容易產生很大的輸入電流漣波，使得太陽能電池模組輸出端的電解電容數量必須增加，減少燃料電池的使用壽命；另一方面，輸出二極體的反向恢復問題造成嚴重的反向恢復損失及EMI雜訊問題。In practice, conventional boost converters operating at extremely large turn-on ratios have limited voltage gain and poor conversion efficiency. On the other hand, the boost converter operating at a very large conduction ratio has the following problems: it is easy to generate a large input current ripple, so that the number of electrolytic capacitors at the output of the solar cell module must be increased, reducing the service life of the fuel cell; On the other hand, the reverse recovery problem of the output diode causes serious reverse recovery losses and EMI noise problems.

另，在轉換效率考量方面，由於環保意識高漲，節能減碳是各國的重要政策，轉換器的效率要求日益嚴苛，功率電子開關造成的功率損失必須善加考量。典型交錯式升壓型轉換器之功率開關與輸出二極體之電壓應力均為高壓的輸出電壓，由於高耐壓的MOSFET，一般都具有高導通電阻RDS(ON)的特性，導致較高的導通損失。In addition, in terms of conversion efficiency, due to the rising awareness of environmental protection, energy saving and carbon reduction are important policies of various countries, and the efficiency requirements of converters are becoming more and more stringent, and the power loss caused by power electronic switches must be carefully considered. The voltage stress of the power switch and the output diode of a typical interleaved boost converter is a high-voltage output voltage. Due to the high-voltage MOSFET, generally has the characteristics of high on-resistance RDS(ON), resulting in higher voltage. conduction loss.

緣是，發明人有鑑於此，秉持多年該相關行業之豐富設計開發及實際製作經驗，針對現有之結構及缺失再予以研究改良，提供一種交錯型高電壓轉換比直流轉換器，以期達到更佳實用價值性之目的者。The reason is that, in view of this, the inventor, adhering to years of rich experience in design, development and actual production in the related industry, researches and improves the existing structure and defects, and provides an interleaved high-voltage conversion ratio DC converter, in order to achieve a better The purpose of practical value.

本發明之主要目的在於提供一種交錯型高電壓轉換比直流轉換器，主要係可得到極高的升壓增益，且可使輸入電流漣波降低，降低電感的體積，同時不必操作在極大的導通比，具有低於輸出電壓的低電壓應力，可降低導通損失，提升整體效率，並可分擔輸入電流，能有效降低電路中儲能元件及開關元件之電流應力，適合應用於高功率的場合，而在其整體施行使用上更增實用功效特性者。The main purpose of the present invention is to provide an interleaved high voltage conversion ratio DC converter, which can obtain extremely high boost gain, reduce the input current ripple, and reduce the size of the inductor, and at the same time, it is not necessary to operate at a very large turn-on It has a low voltage stress lower than the output voltage, which can reduce the conduction loss, improve the overall efficiency, and can share the input current, which can effectively reduce the current stress of the energy storage elements and switching elements in the circuit, and is suitable for high-power applications. And in its overall implementation and use, it has more practical efficacy characteristics.

為令本發明所運用之技術內容、發明目的及其達成之功效有更完整且清楚的揭露，茲於下詳細說明之，並請一併參閱所揭之圖式及圖號：In order to make the technical content used in the present invention, the purpose of the invention and the effect achieved by the present invention more completely and clearly disclosed, it is explained in detail below, and please refer to the disclosed drawings and drawing numbers together:

首先，請參閱第一圖本發明之電路圖所示，本發明之轉換器(1)主要於輸入電壓

Figure 02_image001
之正極分別連接第一輸入濾波電感
Figure 02_image003
之第一端、輸入濾波電容
Figure 02_image103
之負極及第二輸入濾波電感
Figure 02_image005
之第一端，而該輸入電壓
Figure 02_image104
之負極則進行接地，該第一輸入濾波電感
Figure 02_image003
之第二端分別連接第10二極體
Figure 02_image025
之正極及第11二極體
Figure 02_image027
之正極，該輸入濾波電容
Figure 02_image009
之正極分別連接第一耦合電感一次側
Figure 02_image035
之第一端、第13二極體
Figure 02_image031
之負極、第二耦合電感一次側
Figure 02_image039
之第一端及該第11二極體
Figure 02_image027
之負極，該第一耦合電感一次側
Figure 02_image035
形成有第一磁化電感
Figure 02_image043
，該第二耦合電感一次側
Figure 02_image039
形成有第二磁化電感
Figure 02_image045
，該第二輸入濾波電感
Figure 02_image005
之第二端分別連接第12二極體
Figure 02_image029
之正極及該第13二極體
Figure 02_image031
之正極，該第10二極體
Figure 02_image025
之負極分別連接第二功率開關
Figure 02_image053
之第一端、該第二耦合電感一次側
Figure 02_image039
之第二端、第一箝位二極體
Figure 02_image105
之正極及第二輔助二極體
Figure 02_image017
之正極，於該第10二極體
Figure 02_image025
之負極與該第二耦合電感一次側
Figure 02_image039
之第二端之間形成有第二漏電感
Figure 02_image049
，該第二功率開關
Figure 02_image053
之第二端則予以接地，該第12二極體
Figure 02_image029
之負極分別連接第一功率開關
Figure 02_image051
之第一端、第二箝位二極體
Figure 02_image013
之正極、第一輔助二極體
Figure 02_image015
之正極及該第一耦合電感一次側
Figure 02_image035
之第二端，於該第12二極體
Figure 02_image029
之負極與該第一耦合電感一次側
Figure 02_image035
之第二端之間形成有第一漏電感
Figure 02_image047
，該第一功率開關
Figure 02_image051
之第二端則予以接地，該第一箝位二極體
Figure 02_image105
之負極分別連接第二切換二極體
Figure 02_image023
之正極、第三輔助二極體
Figure 02_image019
之負極、該第二箝位二極體
Figure 02_image013
之負極、箝位電容
Figure 02_image057
之第一端及第二切換電容
Figure 02_image106
之負極，該箝位電容
Figure 02_image107
之第二端予以接地，該第二輔助二極體
Figure 02_image017
之負極分別連接該第一輔助二極體
Figure 02_image015
之負極及輔助電感
Figure 02_image007
之第一端，該輔助電感
Figure 02_image108
之第二端分別連接該第三輔助二極體
Figure 02_image019
之正極及輔助開關
Figure 02_image055
之第一端，該輔助開關
Figure 02_image109
之第二端則予以接地，該第二切換二極體
Figure 02_image023
之負極分別連接第二耦合電感二次側
Figure 02_image041
之第一端及第一切換電容
Figure 02_image110
之負極，該第二耦合電感二次側
Figure 02_image111
之第二端連接第一耦合電感二次側
Figure 02_image037
之第一端，該第一耦合電感二次側
Figure 02_image112
之第二端分別連接該第二切換電容
Figure 02_image106
之正極及第一切換二極體
Figure 02_image021
之正極，該第一切換電容
Figure 02_image110
之正極及該第一切換二極體
Figure 02_image113
之負極一併連接至輸出二極體
Figure 02_image033
之正極，該輸出二極體
Figure 02_image114
之負極分別連接至輸出電容
Figure 02_image063
之第一端與輸出負載
Figure 02_image065
之第一端，而該輸出電容
Figure 02_image115
之第二端與該輸出負載
Figure 02_image065
之第二端則予以接地。First of all, please refer to the first circuit diagram of the present invention, the converter (1) of the present invention is mainly based on the input voltage
Figure 02_image001
The positive poles are respectively connected to the first input filter inductor
Figure 02_image003
The first end, the input filter capacitor
Figure 02_image103
The negative pole and the second input filter inductor
Figure 02_image005
the first terminal, and the input voltage
Figure 02_image104
The negative pole is grounded, the first input filter inductor
Figure 02_image003
The second ends are respectively connected to the 10th diode
Figure 02_image025
The positive electrode and the 11th diode
Figure 02_image027
positive, the input filter capacitor
Figure 02_image009
The positive poles are respectively connected to the primary side of the first coupled inductor
Figure 02_image035
The first end, the 13th diode
Figure 02_image031
the negative pole, the primary side of the second coupled inductor
Figure 02_image039
the first end and the 11th diode
Figure 02_image027
the negative pole, the primary side of the first coupled inductor
Figure 02_image035
A first magnetizing inductance is formed
Figure 02_image043
, the primary side of the second coupled inductor
Figure 02_image039
A second magnetizing inductance is formed
Figure 02_image045
, the second input filter inductor
Figure 02_image005
The second ends are respectively connected to the 12th diode
Figure 02_image029
the positive electrode and the 13th diode
Figure 02_image031
the positive electrode, the 10th diode
Figure 02_image025
The negative poles are respectively connected to the second power switch
Figure 02_image053
the first end, the primary side of the second coupled inductor
Figure 02_image039
the second end, the first clamping diode
Figure 02_image105
the positive electrode and the second auxiliary diode
Figure 02_image017
The positive electrode of the 10th diode
Figure 02_image025
the negative pole and the primary side of the second coupled inductor
Figure 02_image039
A second leakage inductance is formed between the second ends
Figure 02_image049
, the second power switch
Figure 02_image053
The second terminal is grounded, the 12th diode
Figure 02_image029
The negative poles are respectively connected to the first power switch
Figure 02_image051
the first end, the second clamping diode
Figure 02_image013
The positive electrode, the first auxiliary diode
Figure 02_image015
the positive pole and the primary side of the first coupled inductor
Figure 02_image035
the second end of the 12th diode
Figure 02_image029
the negative pole and the primary side of the first coupled inductor
Figure 02_image035
A first leakage inductance is formed between the second ends of the
Figure 02_image047
, the first power switch
Figure 02_image051
The second terminal is grounded, the first clamping diode
Figure 02_image105
The negative poles are respectively connected to the second switching diodes
Figure 02_image023
The positive electrode, the third auxiliary diode
Figure 02_image019
the negative electrode, the second clamping diode
Figure 02_image013
negative pole, clamp capacitor
Figure 02_image057
the first terminal and the second switched capacitor
Figure 02_image106
the negative pole of the clamp capacitor
Figure 02_image107
The second terminal of the second auxiliary diode is grounded, the second auxiliary diode
Figure 02_image017
The negative poles are respectively connected to the first auxiliary diode
Figure 02_image015
The negative pole and auxiliary inductance
Figure 02_image007
the first end of the auxiliary inductor
Figure 02_image108
the second ends are respectively connected to the third auxiliary diode
Figure 02_image019
positive and auxiliary switch
Figure 02_image055
the first end of the auxiliary switch
Figure 02_image109
The second terminal is grounded, the second switching diode
Figure 02_image023
The negative poles are respectively connected to the secondary side of the second coupling inductor
Figure 02_image041
the first terminal and the first switched capacitor
Figure 02_image110
the negative pole, the secondary side of the second coupled inductor
Figure 02_image111
The second end is connected to the secondary side of the first coupled inductor
Figure 02_image037
the first end, the second side of the first coupled inductor
Figure 02_image112
The second ends are respectively connected to the second switching capacitor
Figure 02_image106
the positive electrode and the first switching diode
Figure 02_image021
the positive pole of the first switched capacitor
Figure 02_image110
the positive electrode and the first switching diode
Figure 02_image113
The negative poles are also connected to the output diode
Figure 02_image033
the positive pole of the output diode
Figure 02_image114
The negative poles are respectively connected to the output capacitors
Figure 02_image063
the first terminal and the output load
Figure 02_image065
the first terminal, and the output capacitor
Figure 02_image115
the second terminal and the output load
Figure 02_image065
The second end is grounded.

而該轉換器(1)在使用過程中，根據各開關切換和各二極體導通與否，可以將該轉換器(1)在一個切換週期

Figure 02_image116
的動作，分成十六個線性階段，請再參閱第二圖本發明之時序圖所示，以下將本發明分為十六個工作模式進行分析討論：In the process of using the converter (1), according to the switching of each switch and the conduction of each diode, the converter (1) can be switched in one switching cycle.
Figure 02_image116
The action is divided into sixteen linear stages. Please refer to the timing diagram of the present invention in Figure 2. The present invention is divided into sixteen working modes for analysis and discussion below:

第一階段［

Figure 02_image118
］：［第一功率開關
Figure 02_image051
、第二功率開關
Figure 02_image053
：ON，輔助開關
Figure 02_image055
：OFF，第11二極體
Figure 02_image027
、第13二極體
Figure 02_image031
、第一箝位二極體
Figure 02_image105
、第二箝位二極體
Figure 02_image013
、第一切換二極體
Figure 02_image021
、第二切換二極體
Figure 02_image023
、第一輔助二極體
Figure 02_image015
、第二輔助二極體
Figure 02_image017
、第三輔助二極體
Figure 02_image019
、輸出二極體
Figure 02_image114
：OFF，第10二極體
Figure 02_image025
、第12二極體
Figure 02_image029
：ON］：請再一併參閱第三圖本發明之第一階段等效線性電路圖所示，第一階段開始於
Figure 02_image120
，第一功率開關
Figure 02_image051
與第二功率開關
Figure 02_image053
皆為ON。兩個耦合電感的初級側跨壓均為輸入電壓
Figure 02_image001
，即第一磁化電感
Figure 02_image043
、第一漏電感
Figure 02_image047
、第二磁化電感
Figure 02_image045
、第二漏電感
Figure 02_image049
的跨壓為
Figure 02_image001
，其電流呈線性上升，斜率同為
Figure 02_image122
。當
Figure 02_image124
，第二功率開關
Figure 02_image053
切換為OFF時，本階段結束。The first stage[
Figure 02_image118
]: [First power switch
Figure 02_image051
, the second power switch
Figure 02_image053
: ON, auxiliary switch
Figure 02_image055
: OFF, 11th diode
Figure 02_image027
, the 13th diode
Figure 02_image031
, the first clamp diode
Figure 02_image105
, the second clamp diode
Figure 02_image013
, the first switching diode
Figure 02_image021
, the second switching diode
Figure 02_image023
, the first auxiliary diode
Figure 02_image015
, the second auxiliary diode
Figure 02_image017
, the third auxiliary diode
Figure 02_image019
, output diode
Figure 02_image114
: OFF, 10th diode
Figure 02_image025
, the 12th diode
Figure 02_image029
:ON]: Please refer to the third figure again, as shown in the first-stage equivalent linear circuit diagram of the present invention, the first stage starts at
Figure 02_image120
, the first power switch
Figure 02_image051
with second power switch
Figure 02_image053
All are ON. The primary side voltage across the two coupled inductors is the input voltage
Figure 02_image001
, the first magnetizing inductance
Figure 02_image043
, the first leakage inductance
Figure 02_image047
, the second magnetizing inductance
Figure 02_image045
, the second leakage inductance
Figure 02_image049
The cross pressure is
Figure 02_image001
, the current increases linearly, and the slope is the same as
Figure 02_image122
. when
Figure 02_image124
, the second power switch
Figure 02_image053
When switched to OFF, this phase ends.

第二階段［

Figure 02_image126
］：［第一功率開關
Figure 02_image051
：ON、第二功率開關
Figure 02_image053
：ON
Figure 02_image128
OFF，輔助開關
Figure 02_image055
：OFF，第10二極體
Figure 02_image025
、第13二極體
Figure 02_image031
、第一箝位二極體
Figure 02_image105
、第二箝位二極體
Figure 02_image013
、第一切換二極體
Figure 02_image021
、第二切換二極體
Figure 02_image023
、第一輔助二極體
Figure 02_image015
、第二輔助二極體
Figure 02_image017
、第三輔助二極體
Figure 02_image019
、輸出二極體
Figure 02_image114
：OFF，第11二極體
Figure 02_image027
、第12二極體
Figure 02_image029
：ON］：請再一併參閱第四圖本發明之第二階段等效線性電路圖所示，第二階段開始於
Figure 02_image130
，第二功率開關
Figure 02_image053
切換成OFF。第二漏電感電流
Figure 02_image131
對第二功率開關
Figure 02_image053
的輸出［寄生］電容
Figure 02_image133
充電，第二功率開關
Figure 02_image053
的跨壓
Figure 02_image135
由零電壓開始上升，耦合電感二次側總電壓
Figure 02_image137
也隨之上升。因為第二功率開關
Figure 02_image053
的輸出電容
Figure 02_image133
很小，所以本階段時間很短，第二漏電感電流
Figure 02_image131
視為常數。當
Figure 02_image139
，第二功率開關
Figure 02_image053
的跨壓
Figure 02_image141
等於箝位電容
Figure 02_image057
的電壓
Figure 02_image142
時，即
Figure 02_image144
時，第二箝位二極體
Figure 02_image013
及第一切換二極體
Figure 02_image021
和第二切換二極體
Figure 02_image023
轉態成ON，本階段結束。second stage[
Figure 02_image126
]: [First power switch
Figure 02_image051
: ON, second power switch
Figure 02_image053
: ON
Figure 02_image128
OFF, auxiliary switch
Figure 02_image055
: OFF, 10th diode
Figure 02_image025
, the 13th diode
Figure 02_image031
, the first clamp diode
Figure 02_image105
, the second clamp diode
Figure 02_image013
, the first switching diode
Figure 02_image021
, the second switching diode
Figure 02_image023
, the first auxiliary diode
Figure 02_image015
, the second auxiliary diode
Figure 02_image017
, the third auxiliary diode
Figure 02_image019
, output diode
Figure 02_image114
: OFF, 11th diode
Figure 02_image027
, the 12th diode
Figure 02_image029
: ON]: Please also refer to the second-stage equivalent linear circuit diagram of the present invention in Figure 4. The second stage starts at
Figure 02_image130
, the second power switch
Figure 02_image053
Switch to OFF. second leakage inductance current
Figure 02_image131
to the second power switch
Figure 02_image053
The output [parasitic] capacitance of
Figure 02_image133
charging, second power switch
Figure 02_image053
cross pressure
Figure 02_image135
Rising from zero voltage, the total voltage on the secondary side of the coupled inductor
Figure 02_image137
also rose. Because the second power switch
Figure 02_image053
The output capacitance of
Figure 02_image133
is very small, so the time of this stage is very short, the second leakage inductance current
Figure 02_image131
regarded as a constant. when
Figure 02_image139
, the second power switch
Figure 02_image053
cross pressure
Figure 02_image141
equal to the clamp capacitance
Figure 02_image057
voltage
Figure 02_image142
when, that is
Figure 02_image144
, the second clamp diode
Figure 02_image013
and the first switching diode
Figure 02_image021
and the second switching diode
Figure 02_image023
Transition to ON, the end of this stage.

第三階段［

Figure 02_image146
］：［第一功率開關
Figure 02_image051
：ON、第二功率開關
Figure 02_image053
、輔助開關
Figure 02_image055
：OFF，第二箝位二極體
Figure 02_image013
、第一切換二極體
Figure 02_image021
、第二切換二極體
Figure 02_image023
：OFF
Figure 02_image128
ON，第10二極體
Figure 02_image025
、第13二極體
Figure 02_image031
、第一箝位二極體
Figure 02_image105
、第一輔助二極體
Figure 02_image015
、第二輔助二極體
Figure 02_image017
、第三輔助二極體
Figure 02_image019
、輸出二極體
Figure 02_image114
：OFF，第11二極體
Figure 02_image027
、第12二極體
Figure 02_image029
：ON］：請再一併參閱第五圖本發明之第三階段等效線性電路圖所示，第三階段開始於
Figure 02_image148
， 第二箝位二極體
Figure 02_image013
、第一切換二極體
Figure 02_image021
、第二切換二極體
Figure 02_image023
轉態為ON。第二耦合電感一次側
Figure 02_image039
跨壓
Figure 02_image149
，第二漏電感電流
Figure 02_image131
下降，第二漏電感電流
Figure 02_image131
經由第二箝位二極體
Figure 02_image013
對箝位電容
Figure 02_image057
充電。儲存在第二磁化電感
Figure 02_image045
的能量藉由耦合電感傳送至二次側，經由第一切換二極體
Figure 02_image021
和第二切換二極體
Figure 02_image023
對第一切換電容
Figure 02_image151
和第二切換電容
Figure 02_image106
充電。另一方面，因為耦合電感二次側電流感應至第一組耦合電感的理想變壓器一次側，使得第一組耦合電感的漏電感電流可表示為
Figure 02_image153
。當
Figure 02_image155
， 第二漏電感電流
Figure 02_image131
下降至零時，第二箝位二極體
Figure 02_image013
以零電流切換［ZCS］自然轉態成OFF，本階段結束。因為第二箝位二極體
Figure 02_image013
以ZCS轉態成OFF，因此沒有反向恢復損失。The third phase[
Figure 02_image146
]: [First power switch
Figure 02_image051
: ON, second power switch
Figure 02_image053
, auxiliary switch
Figure 02_image055
: OFF, second clamp diode
Figure 02_image013
, the first switching diode
Figure 02_image021
, the second switching diode
Figure 02_image023
: OFF
Figure 02_image128
ON, 10th diode
Figure 02_image025
, the 13th diode
Figure 02_image031
, the first clamp diode
Figure 02_image105
, the first auxiliary diode
Figure 02_image015
, the second auxiliary diode
Figure 02_image017
, the third auxiliary diode
Figure 02_image019
, output diode
Figure 02_image114
: OFF, 11th diode
Figure 02_image027
, the 12th diode
Figure 02_image029
:ON]: Please also refer to the third-stage equivalent linear circuit diagram of the present invention in Figure 5. The third stage starts at
Figure 02_image148
, the second clamp diode
Figure 02_image013
, the first switching diode
Figure 02_image021
, the second switching diode
Figure 02_image023
Transition to ON. The primary side of the second coupled inductor
Figure 02_image039
cross pressure
Figure 02_image149
, the second leakage inductance current
Figure 02_image131
falling, the second leakage inductance current
Figure 02_image131
via the second clamp diode
Figure 02_image013
pair clamp capacitor
Figure 02_image057
Charge. stored in the second magnetizing inductance
Figure 02_image045
The energy is transferred to the secondary side through the coupled inductor, through the first switching diode
Figure 02_image021
and the second switching diode
Figure 02_image023
on the first switched capacitor
Figure 02_image151
and the second switched capacitor
Figure 02_image106
Charge. On the other hand, since the secondary side current of the coupled inductor is induced to the ideal transformer primary side of the first set of coupled inductors, the leakage inductance current of the first set of coupled inductors can be expressed as
Figure 02_image153
. when
Figure 02_image155
, the second leakage inductance current
Figure 02_image131
drops to zero, the second clamp diode
Figure 02_image013
With zero current switching [ZCS], the state is naturally turned to OFF, and this stage ends. because the second clamp diode
Figure 02_image013
Transitions to OFF with ZCS, so there is no reverse recovery penalty.

第四階段［

Figure 02_image157
］：［第一功率開關
Figure 02_image051
：ON、第二功率開關
Figure 02_image053
、輔助開關
Figure 02_image055
：OFF，第二箝位二極體
Figure 02_image013
：ON
Figure 02_image128
OFF，第一切換二極體
Figure 02_image021
、第二切換二極體
Figure 02_image023
：ON，第10二極體
Figure 02_image025
、第13二極體
Figure 02_image031
、第一箝位二極體
Figure 02_image105
、第一輔助二極體
Figure 02_image015
、第二輔助二極體
Figure 02_image017
、第三輔助二極體
Figure 02_image019
、輸出二極體
Figure 02_image114
：OFF，第11二極體
Figure 02_image027
、第12二極體
Figure 02_image029
：ON］：請再一併參閱第六圖本發明之第四階段等效線性電路圖所示，第四階段開始於
Figure 02_image159
，第二箝位二極體
Figure 02_image013
轉態成OFF。第二磁化電感
Figure 02_image045
的電流
Figure 02_image160
完全由耦合電感一次側感應到二次側，經由第一切換二極體
Figure 02_image021
和第二切換二極體
Figure 02_image023
持續對第一切換電容
Figure 02_image151
和第二切換電容
Figure 02_image106
充電。在本階段第二磁化電感電流
Figure 02_image160
和流經第一功率開關
Figure 02_image051
的電流分別為
Figure 02_image162
、
Figure 02_image164
。當
Figure 02_image166
，輔助開關
Figure 02_image055
切換成ON時，本階段結束。the fourth stage
Figure 02_image157
]: [First power switch
Figure 02_image051
: ON, second power switch
Figure 02_image053
, auxiliary switch
Figure 02_image055
: OFF, second clamp diode
Figure 02_image013
: ON
Figure 02_image128
OFF, first switching diode
Figure 02_image021
, the second switching diode
Figure 02_image023
: ON, 10th diode
Figure 02_image025
, the 13th diode
Figure 02_image031
, the first clamp diode
Figure 02_image105
, the first auxiliary diode
Figure 02_image015
, the second auxiliary diode
Figure 02_image017
, the third auxiliary diode
Figure 02_image019
, output diode
Figure 02_image114
: OFF, 11th diode
Figure 02_image027
, the 12th diode
Figure 02_image029
: ON]: Please refer to the fourth stage equivalent linear circuit diagram of the present invention in Figure 6. The fourth stage starts at
Figure 02_image159
, the second clamp diode
Figure 02_image013
Transition to OFF. second magnetizing inductance
Figure 02_image045
the current
Figure 02_image160
Fully sensed from the primary side of the coupled inductor to the secondary side via the first switching diode
Figure 02_image021
and the second switching diode
Figure 02_image023
continuously on the first switched capacitor
Figure 02_image151
and the second switched capacitor
Figure 02_image106
Charge. The second magnetizing inductor current at this stage
Figure 02_image160
and flows through the first power switch
Figure 02_image051
The currents are
Figure 02_image162
,
Figure 02_image164
. when
Figure 02_image166
, auxiliary switch
Figure 02_image055
When switched ON, this phase ends.

第五階段［

Figure 02_image168
］：［第一功率開關
Figure 02_image051
：ON，第二功率開關
Figure 02_image053
：OFF，輔助開關
Figure 02_image055
：OFF
Figure 02_image128
ON，第二輔助二極體
Figure 02_image017
：OFF
Figure 02_image128
ON，第一切換二極體
Figure 02_image021
、第二切換二極體
Figure 02_image023
：ON，第10二極體
Figure 02_image025
、第13二極體
Figure 02_image031
、第一箝位二極體
Figure 02_image105
、第二箝位二極體
Figure 02_image013
、第一輔助二極體
Figure 02_image015
、第三輔助二極體
Figure 02_image019
、輸出二極體
Figure 02_image114
：OFF，第11二極體
Figure 02_image027
、第12二極體
Figure 02_image029
：ON］：請再一併參閱第七圖本發明之第五階段等效線性電路圖所示，第五階段開始於
Figure 02_image170
，輔助開關
Figure 02_image055
切換為ON，第二輔助二極體
Figure 02_image017
轉態為ON。因為輔助電感
Figure 02_image007
的存在，輔助電感電流
Figure 02_image171
由零開始上升，所以輔助開關
Figure 02_image055
和第二輔助二極體
Figure 02_image017
能夠以ZCS切換為ON。第二漏電感電流
Figure 02_image173
從0開始上升，因此第二磁化電感電流
Figure 02_image160
流入為理想變壓器之第二耦合電感一次側
Figure 02_image039
的電流減小，導致耦合電感二次側的電流開始下降，使得第一切換二極體
Figure 02_image021
之電流
Figure 02_image174
和第二切換二極體
Figure 02_image023
之電流
Figure 02_image176
下降。當
Figure 02_image178
， 第二漏電感電流
Figure 02_image180
上升至滿足
Figure 02_image181
，此時第一切換二極體電流
Figure 02_image174
和第二切換二極體電流
Figure 02_image176
會下降到0，第一切換二極體
Figure 02_image021
和第二切換二極體
Figure 02_image023
以ZCS自然轉態成OFF，本階段結束。The fifth stage [
Figure 02_image168
]: [First power switch
Figure 02_image051
: ON, the second power switch
Figure 02_image053
: OFF, auxiliary switch
Figure 02_image055
: OFF
Figure 02_image128
ON, second auxiliary diode
Figure 02_image017
: OFF
Figure 02_image128
ON, the first switching diode
Figure 02_image021
, the second switching diode
Figure 02_image023
: ON, 10th diode
Figure 02_image025
, the 13th diode
Figure 02_image031
, the first clamp diode
Figure 02_image105
, the second clamp diode
Figure 02_image013
, the first auxiliary diode
Figure 02_image015
, the third auxiliary diode
Figure 02_image019
, output diode
Figure 02_image114
: OFF, 11th diode
Figure 02_image027
, the 12th diode
Figure 02_image029
:ON]: Please refer to Figure 7, which is the equivalent linear circuit diagram of the fifth stage of the present invention. The fifth stage starts at
Figure 02_image170
, auxiliary switch
Figure 02_image055
switched ON, the second auxiliary diode
Figure 02_image017
Transition to ON. Because of the auxiliary inductance
Figure 02_image007
The presence of auxiliary inductor current
Figure 02_image171
rising from zero, so the auxiliary switch
Figure 02_image055
and the second auxiliary diode
Figure 02_image017
Can be switched ON with ZCS. second leakage inductance current
Figure 02_image173
Rising from 0, so the second magnetizing inductor current
Figure 02_image160
The inflow is the primary side of the second coupled inductor of an ideal transformer
Figure 02_image039
The current decreases, causing the current on the secondary side of the coupled inductor to begin to drop, making the first switching diode
Figure 02_image021
the current
Figure 02_image174
and the second switching diode
Figure 02_image023
the current
Figure 02_image176
decline. when
Figure 02_image178
, the second leakage inductance current
Figure 02_image180
rise to contentment
Figure 02_image181
, at this time the first switching diode current
Figure 02_image174
and the second switching diode current
Figure 02_image176
will drop to 0, the first switching diode
Figure 02_image021
and the second switching diode
Figure 02_image023
When ZCS naturally transitions to OFF, this stage ends.

第六階段［

Figure 02_image183
］：［第一功率開關
Figure 02_image051
、輔助開關
Figure 02_image055
：ON，第二功率開關
Figure 02_image053
：OFF，第一切換二極體
Figure 02_image021
、第二切換二極體
Figure 02_image023
：ON
Figure 02_image128
OFF，第二輔助二極體
Figure 02_image017
：ON，第10二極體
Figure 02_image025
、第13二極體
Figure 02_image031
、第一箝位二極體
Figure 02_image105
、第二箝位二極體
Figure 02_image013
、第一輔助二極體
Figure 02_image015
、第三輔助二極體
Figure 02_image019
、輸出二極體
Figure 02_image114
：OFF，第11二極體
Figure 02_image027
、第12二極體
Figure 02_image029
：ON］：請再一併參閱第八圖本發明之第六階段等效線性電路圖所示，第六階段開始於
Figure 02_image185
，第一切換二極體
Figure 02_image021
和第二切換二極體
Figure 02_image023
轉態為OFF。輔助電感
Figure 02_image007
和第二功率開關
Figure 02_image053
的輸出電容
Figure 02_image133
形成共振電路，因為輔助電感
Figure 02_image007
和第二功率開關
Figure 02_image053
的輸出電容
Figure 02_image133
都很小，共振頻率很大，所以輔助電感電流
Figure 02_image171
以共振形式快速上升，第二功率開關
Figure 02_image053
的跨壓
Figure 02_image135
以共振形式快速下降。第二功率開關
Figure 02_image053
的輸出電容
Figure 02_image133
所儲存的能量轉移至輔助電感
Figure 02_image007
儲存。當第二功率開關
Figure 02_image053
的跨壓
Figure 02_image135
下降至零，第二功率開關
Figure 02_image053
的內部本體二極體［body diode］導通，第二功率開關
Figure 02_image053
的跨壓
Figure 02_image135
箝制在零，第二功率開關
Figure 02_image053
之ZVS切換的條件成立。當
Figure 02_image186
，第二功率開關
Figure 02_image053
以ZVS切換為ON，本階段結束。The sixth stage [
Figure 02_image183
]: [First power switch
Figure 02_image051
, auxiliary switch
Figure 02_image055
: ON, the second power switch
Figure 02_image053
: OFF, first switching diode
Figure 02_image021
, the second switching diode
Figure 02_image023
: ON
Figure 02_image128
OFF, second auxiliary diode
Figure 02_image017
: ON, 10th diode
Figure 02_image025
, the 13th diode
Figure 02_image031
, the first clamp diode
Figure 02_image105
, the second clamp diode
Figure 02_image013
, the first auxiliary diode
Figure 02_image015
, the third auxiliary diode
Figure 02_image019
, output diode
Figure 02_image114
: OFF, 11th diode
Figure 02_image027
, the 12th diode
Figure 02_image029
: ON]: Please refer to Figure 8, which is the equivalent linear circuit diagram of the sixth stage of the present invention. The sixth stage starts at
Figure 02_image185
, the first switching diode
Figure 02_image021
and the second switching diode
Figure 02_image023
Transition to OFF. Auxiliary inductance
Figure 02_image007
and the second power switch
Figure 02_image053
The output capacitance of
Figure 02_image133
form a resonant circuit because the auxiliary inductance
Figure 02_image007
and the second power switch
Figure 02_image053
The output capacitance of
Figure 02_image133
are very small, the resonance frequency is large, so the auxiliary inductor current
Figure 02_image171
Rapid rise in resonance form, second power switch
Figure 02_image053
cross pressure
Figure 02_image135
Rapid decline in resonance form. second power switch
Figure 02_image053
The output capacitance of
Figure 02_image133
The stored energy is transferred to the auxiliary inductor
Figure 02_image007
store. When the second power switch
Figure 02_image053
cross pressure
Figure 02_image135
down to zero, the second power switch
Figure 02_image053
The internal body diode of , conducts, the second power switch
Figure 02_image053
cross pressure
Figure 02_image135
clamped at zero, the second power switch
Figure 02_image053
The conditions for ZVS switching are satisfied. when
Figure 02_image186
, the second power switch
Figure 02_image053
When ZVS is switched to ON, this stage ends.

第七階段［

Figure 02_image188
］：［第一功率開關
Figure 02_image051
、輔助開關
Figure 02_image055
：ON，第二功率開關
Figure 02_image053
：OFF
Figure 02_image128
ON，第二輔助二極體
Figure 02_image017
：ON，第11二極體
Figure 02_image027
、第13二極體
Figure 02_image031
、第一箝位二極體
Figure 02_image105
、第二箝位二極體
Figure 02_image013
、第一切換二極體
Figure 02_image021
、第二切換二極體
Figure 02_image023
、第一輔助二極體
Figure 02_image015
、第三輔助二極體
Figure 02_image019
、輸出二極體
Figure 02_image114
：OFF，第10二極體
Figure 02_image025
、第12二極體
Figure 02_image029
：ON］：請再一併參閱第九圖本發明之第七階段等效線性電路圖所示，第七階段開始於
Figure 02_image190
，第二功率開關
Figure 02_image053
以ZVS切換為ON。本階段輔助電感
Figure 02_image007
之電壓
Figure 02_image191
，輔助電感電流
Figure 02_image171
保持常數。耦合電感一次側受到輸入電壓
Figure 02_image001
充磁。當
Figure 02_image193
，輔助開關
Figure 02_image055
切換為OFF時，本階段結束。the seventh stage
Figure 02_image188
]: [First power switch
Figure 02_image051
, auxiliary switch
Figure 02_image055
: ON, the second power switch
Figure 02_image053
: OFF
Figure 02_image128
ON, second auxiliary diode
Figure 02_image017
: ON, 11th diode
Figure 02_image027
, the 13th diode
Figure 02_image031
, the first clamp diode
Figure 02_image105
, the second clamp diode
Figure 02_image013
, the first switching diode
Figure 02_image021
, the second switching diode
Figure 02_image023
, the first auxiliary diode
Figure 02_image015
, the third auxiliary diode
Figure 02_image019
, output diode
Figure 02_image114
: OFF, 10th diode
Figure 02_image025
, the 12th diode
Figure 02_image029
: ON]: Please refer to Figure 9, which is the equivalent linear circuit diagram of the seventh stage of the present invention. The seventh stage starts at
Figure 02_image190
, the second power switch
Figure 02_image053
Toggle ON with ZVS. Auxiliary inductor at this stage
Figure 02_image007
voltage
Figure 02_image191
, the auxiliary inductor current
Figure 02_image171
keep it constant. The primary side of the coupled inductor is subjected to the input voltage
Figure 02_image001
Magnetizing. when
Figure 02_image193
, auxiliary switch
Figure 02_image055
When switched to OFF, this phase ends.

第八階段［

Figure 02_image195
］：［第一功率開關
Figure 02_image051
、第二功率開關
Figure 02_image053
：ON，輔助開關
Figure 02_image055
：ON
Figure 02_image128
OFF，第11二極體
Figure 02_image027
、第13二極體
Figure 02_image031
、第一箝位二極體
Figure 02_image105
、第二箝位二極體
Figure 02_image013
、第一切換二極體
Figure 02_image021
、第二切換二極體
Figure 02_image023
、第一輔助二極體
Figure 02_image015
、輸出二極體
Figure 02_image114
：OFF，第二輔助二極體
Figure 02_image017
、第三輔助二極體
Figure 02_image019
：ON，第10二極體
Figure 02_image025
、第12二極體
Figure 02_image029
：ON］：請再一併參閱第十圖本發明之第八階段等效線性電路圖所示，第八階段開始於
Figure 02_image197
，輔助開關
Figure 02_image055
切換為OFF，因為輔助電感電流
Figure 02_image171
的連續性，使得第三輔助二極體
Figure 02_image019
轉態為ON，輔助電感電壓
Figure 02_image198
，輔助電感電流
Figure 02_image171
線性下降，輔助電感
Figure 02_image007
儲存的能量傳送至箝位電容
Figure 02_image107
，而輸入電壓
Figure 02_image200
繼續對兩個耦合電感一次側充磁。當
Figure 02_image202
，輔助電感電流
Figure 02_image171
下降至零，第二輔助二極體
Figure 02_image017
、第三輔助二極體
Figure 02_image019
以ZCS自然轉態成OFF，本階段結束。接著，進入後半切換週期的8個階段。eighth stage
Figure 02_image195
]: [First power switch
Figure 02_image051
, the second power switch
Figure 02_image053
: ON, auxiliary switch
Figure 02_image055
: ON
Figure 02_image128
OFF, 11th diode
Figure 02_image027
, the 13th diode
Figure 02_image031
, the first clamp diode
Figure 02_image105
, the second clamp diode
Figure 02_image013
, the first switching diode
Figure 02_image021
, the second switching diode
Figure 02_image023
, the first auxiliary diode
Figure 02_image015
, output diode
Figure 02_image114
: OFF, second auxiliary diode
Figure 02_image017
, the third auxiliary diode
Figure 02_image019
: ON, 10th diode
Figure 02_image025
, the 12th diode
Figure 02_image029
: ON]: Please also refer to Figure 10, as shown in the equivalent linear circuit diagram of the eighth stage of the present invention, the eighth stage starts at
Figure 02_image197
, auxiliary switch
Figure 02_image055
switched OFF because the auxiliary inductor current
Figure 02_image171
continuity, such that the third auxiliary diode
Figure 02_image019
transition to ON, auxiliary inductor voltage
Figure 02_image198
, the auxiliary inductor current
Figure 02_image171
Linear drop, auxiliary inductance
Figure 02_image007
The stored energy is delivered to the clamping capacitor
Figure 02_image107
, while the input voltage
Figure 02_image200
Continue to magnetize the primary side of both coupled inductors. when
Figure 02_image202
, the auxiliary inductor current
Figure 02_image171
down to zero, the second auxiliary diode
Figure 02_image017
, the third auxiliary diode
Figure 02_image019
When ZCS naturally transitions to OFF, this stage ends. Next, the eight stages of the second half switching cycle are entered.

第九階段［

Figure 02_image204
］：［第一功率開關
Figure 02_image051
、第二功率開關
Figure 02_image053
：ON，輔助開關
Figure 02_image055
：OFF，第11二極體
Figure 02_image027
、第13二極體
Figure 02_image031
、第一箝位二極體
Figure 02_image105
、第二箝位二極體
Figure 02_image013
、第一切換二極體
Figure 02_image021
、第二切換二極體
Figure 02_image023
、第一輔助二極體
Figure 02_image015
、輸出二極體
Figure 02_image114
：OFF，第二輔助二極體
Figure 02_image017
、第三輔助二極體
Figure 02_image019
：ON
Figure 02_image128
OFF，第10二極體
Figure 02_image025
、第12二極體
Figure 02_image029
：ON］：請再一併參閱第十一圖本發明之第九階段等效線性電路圖所示，第九階段開始於
Figure 02_image206
，第一功率開關
Figure 02_image051
與第二功率開關
Figure 02_image053
皆為ON。兩個耦合電感的初級側跨壓均為輸入電壓
Figure 02_image001
，即第一磁化電感
Figure 02_image043
、第一漏電感
Figure 02_image047
、第二磁化電感
Figure 02_image045
、第二漏電感
Figure 02_image049
的跨壓為
Figure 02_image001
，第一漏電感電流
Figure 02_image207
和第二漏電感電流
Figure 02_image173
都呈線性上升，斜率同為
Figure 02_image209
。當
Figure 02_image211
，第一功率開關
Figure 02_image051
切換為OFF時，本階段結束。The ninth stage [
Figure 02_image204
]: [First power switch
Figure 02_image051
, the second power switch
Figure 02_image053
: ON, auxiliary switch
Figure 02_image055
: OFF, 11th diode
Figure 02_image027
, the 13th diode
Figure 02_image031
, the first clamp diode
Figure 02_image105
, the second clamp diode
Figure 02_image013
, the first switching diode
Figure 02_image021
, the second switching diode
Figure 02_image023
, the first auxiliary diode
Figure 02_image015
, output diode
Figure 02_image114
: OFF, second auxiliary diode
Figure 02_image017
, the third auxiliary diode
Figure 02_image019
: ON
Figure 02_image128
OFF, 10th diode
Figure 02_image025
, the 12th diode
Figure 02_image029
: ON]: Please refer to Figure 11, which is the equivalent linear circuit diagram of the ninth stage of the present invention. The ninth stage starts at
Figure 02_image206
, the first power switch
Figure 02_image051
with second power switch
Figure 02_image053
All are ON. The primary side voltage across the two coupled inductors is the input voltage
Figure 02_image001
, the first magnetizing inductance
Figure 02_image043
, the first leakage inductance
Figure 02_image047
, the second magnetizing inductance
Figure 02_image045
, the second leakage inductance
Figure 02_image049
The cross pressure is
Figure 02_image001
, the first leakage inductance current
Figure 02_image207
and the second leakage inductance current
Figure 02_image173
both rise linearly, with the same slope as
Figure 02_image209
. when
Figure 02_image211
, the first power switch
Figure 02_image051
When switched to OFF, this phase ends.

第十階段［

Figure 02_image213
］：［第一功率開關
Figure 02_image051
：ON
Figure 02_image128
OFF，第二功率開關
Figure 02_image053
：ON，輔助開關
Figure 02_image055
：OFF，第11二極體
Figure 02_image027
、第12二極體
Figure 02_image029
、第一箝位二極體
Figure 02_image105
、第二箝位二極體
Figure 02_image013
、第一切換二極體
Figure 02_image021
、第二切換二極體
Figure 02_image023
、第一輔助二極體
Figure 02_image015
、第二輔助二極體
Figure 02_image017
、第三輔助二極體
Figure 02_image019
、輸出二極體
Figure 02_image114
：OFF，第10二極體
Figure 02_image025
、第13二極體
Figure 02_image031
：ON］：請再一併參閱第十二圖本發明之第十階段等效線性電路圖所示，第十階段開始於
Figure 02_image215
，第一功率開關
Figure 02_image051
切換成OFF。第一漏電感電流
Figure 02_image216
對第一功率開關
Figure 02_image051
的輸出［寄生］電容
Figure 02_image217
充電，第一功率開關
Figure 02_image051
的跨壓
Figure 02_image219
由零電壓開始上升，耦合電感二次側總電壓
Figure 02_image221
也上升。輸出二極體
Figure 02_image114
電壓
Figure 02_image223
也隨之上升。因為第一功率開關
Figure 02_image051
的輸出電容
Figure 02_image217
很小，所以本階段時間很短，當
Figure 02_image225
，第一功率開關
Figure 02_image227
的跨壓
Figure 02_image228
上升至箝位電容電壓
Figure 02_image142
時，即
Figure 02_image229
時，第一箝位二極體
Figure 02_image231
及輸出二極體
Figure 02_image114
轉態成ON，本階段結束。tenth stage
Figure 02_image213
]: [First power switch
Figure 02_image051
: ON
Figure 02_image128
OFF, the second power switch
Figure 02_image053
: ON, auxiliary switch
Figure 02_image055
: OFF, 11th diode
Figure 02_image027
, the 12th diode
Figure 02_image029
, the first clamp diode
Figure 02_image105
, the second clamp diode
Figure 02_image013
, the first switching diode
Figure 02_image021
, the second switching diode
Figure 02_image023
, the first auxiliary diode
Figure 02_image015
, the second auxiliary diode
Figure 02_image017
, the third auxiliary diode
Figure 02_image019
, output diode
Figure 02_image114
: OFF, 10th diode
Figure 02_image025
, the 13th diode
Figure 02_image031
: ON]: Please also refer to Figure 12, which is the equivalent linear circuit diagram of the tenth stage of the present invention. The tenth stage starts at
Figure 02_image215
, the first power switch
Figure 02_image051
Switch to OFF. first leakage inductance current
Figure 02_image216
to the first power switch
Figure 02_image051
The output [parasitic] capacitance of
Figure 02_image217
charging, first power switch
Figure 02_image051
cross pressure
Figure 02_image219
Rising from zero voltage, the total voltage on the secondary side of the coupled inductor
Figure 02_image221
also rise. output diode
Figure 02_image114
Voltage
Figure 02_image223
also rose. Because the first power switch
Figure 02_image051
The output capacitance of
Figure 02_image217
is very small, so this stage is very short, when
Figure 02_image225
, the first power switch
Figure 02_image227
cross pressure
Figure 02_image228
rise to the clamping capacitor voltage
Figure 02_image142
when, that is
Figure 02_image229
, the first clamp diode
Figure 02_image231
and output diode
Figure 02_image114
Transition to ON, the end of this stage.

第十一階段［

Figure 02_image232
］：［第一功率開關
Figure 02_image051
、輔助開關
Figure 02_image055
：OFF，第二功率開關
Figure 02_image053
：ON，第一箝位二極體
Figure 02_image105
、輸出二極體
Figure 02_image114
：OFF
Figure 02_image128
ON，第11二極體
Figure 02_image027
、第12二極體
Figure 02_image029
、第二箝位二極體
Figure 02_image013
、第一切換二極體
Figure 02_image021
、第二切換二極體
Figure 02_image023
、第一輔助二極體
Figure 02_image015
、第二輔助二極體
Figure 02_image017
、第三輔助二極體
Figure 02_image019
：OFF，第10二極體
Figure 02_image025
、第13二極體
Figure 02_image031
：ON］：請再一併參閱第十三圖本發明之第十一階段等效線性電路圖所示，第十一階段開始於
Figure 02_image234
，第一功率開關
Figure 02_image051
為OFF，且第一箝位二極體
Figure 02_image105
和輸出二極體
Figure 02_image114
為ON。部分的第一漏電感電流
Figure 02_image216
對箝位電容
Figure 02_image057
充電，第一漏電感電流
Figure 02_image235
下降，第一磁化電感
Figure 02_image236
的電流
Figure 02_image238
流入第一組耦合電感之理想變壓器的電流上升，第一磁化電感
Figure 02_image240
所儲存的能量經由耦合電感及輸出二極體
Figure 02_image114
傳遞至輸出負載
Figure 02_image065
，輸出二極體
Figure 02_image114
之電流
Figure 02_image241
上升，其電流增加速率受第一漏電感
Figure 02_image047
限制。在本階段中，當
Figure 02_image243
時，箝位電容
Figure 02_image057
開始對輸出側放電，耦合電感的二次側及第一切換電容
Figure 02_image151
和第二切換電容
Figure 02_image106
可視為電壓源，以提升輸出電壓增益。當
Figure 02_image245
， 第一漏電感電流
Figure 02_image247
下降至零，第一箝位二極體
Figure 02_image248
以零電流切換［ZCS］自然轉態為OFF，本階段結束。the eleventh stage
Figure 02_image232
]: [First power switch
Figure 02_image051
, auxiliary switch
Figure 02_image055
: OFF, the second power switch
Figure 02_image053
: ON, first clamp diode
Figure 02_image105
, output diode
Figure 02_image114
: OFF
Figure 02_image128
ON, 11th diode
Figure 02_image027
, the 12th diode
Figure 02_image029
, the second clamp diode
Figure 02_image013
, the first switching diode
Figure 02_image021
, the second switching diode
Figure 02_image023
, the first auxiliary diode
Figure 02_image015
, the second auxiliary diode
Figure 02_image017
, the third auxiliary diode
Figure 02_image019
: OFF, 10th diode
Figure 02_image025
, the 13th diode
Figure 02_image031
: ON]: Please also refer to Figure 13, which is the equivalent linear circuit diagram of the eleventh stage of the present invention. The eleventh stage starts at
Figure 02_image234
, the first power switch
Figure 02_image051
is OFF, and the first clamp diode
Figure 02_image105
and output diode
Figure 02_image114
is ON. part of the first leakage inductance current
Figure 02_image216
pair clamp capacitor
Figure 02_image057
charging, the first leakage inductor current
Figure 02_image235
falling, the first magnetizing inductance
Figure 02_image236
the current
Figure 02_image238
The current flowing into the ideal transformer of the first set of coupled inductances rises, the first magnetizing inductance
Figure 02_image240
The stored energy passes through the coupled inductor and output diode
Figure 02_image114
pass to the output load
Figure 02_image065
, the output diode
Figure 02_image114
the current
Figure 02_image241
rise, the rate of current increase is limited by the first leakage inductance
Figure 02_image047
limit. In this stage, when
Figure 02_image243
, the clamping capacitor
Figure 02_image057
Begin to discharge the output side, coupling the secondary side of the inductor and the first switched capacitor
Figure 02_image151
and the second switched capacitor
Figure 02_image106
Can be regarded as a voltage source to increase the output voltage gain. when
Figure 02_image245
, the first leakage inductance current
Figure 02_image247
down to zero, the first clamp diode
Figure 02_image248
With zero current switching [ZCS], the natural transition state is OFF, and this stage ends.

第十二階段［

Figure 02_image249
］：［第一功率開關
Figure 02_image051
、輔助開關
Figure 02_image055
：OFF，第二功率開關
Figure 02_image053
：ON，第一箝位二極體
Figure 02_image105
：ON
Figure 02_image128
OFF，輸出二極體
Figure 02_image114
：ON，第11二極體
Figure 02_image027
、第12二極體
Figure 02_image029
、第二箝位二極體
Figure 02_image013
、第一切換二極體
Figure 02_image021
、第二切換二極體
Figure 02_image023
、第一輔助二極體
Figure 02_image015
、第二輔助二極體
Figure 02_image017
、第三輔助二極體
Figure 02_image019
：OFF，第10二極體
Figure 02_image025
、第13二極體
Figure 02_image031
：ON］：請再一併參閱第十四圖本發明之第十二階段等效線性電路圖所示，第十二階段開始於
Figure 02_image251
，第一箝位二極體
Figure 02_image252
轉態成OFF。磁化電感儲存的能量完全藉由耦合電感傳遞至二次側，經由輸出二極體
Figure 02_image114
對輸出電容
Figure 02_image063
及輸出負載
Figure 02_image065
放電。當
Figure 02_image253
，輔助開關
Figure 02_image055
切換成ON時，本階段結束。the twelfth stage
Figure 02_image249
]: [First power switch
Figure 02_image051
, auxiliary switch
Figure 02_image055
: OFF, the second power switch
Figure 02_image053
: ON, first clamp diode
Figure 02_image105
: ON
Figure 02_image128
OFF, output diode
Figure 02_image114
: ON, 11th diode
Figure 02_image027
, the 12th diode
Figure 02_image029
, the second clamp diode
Figure 02_image013
, the first switching diode
Figure 02_image021
, the second switching diode
Figure 02_image023
, the first auxiliary diode
Figure 02_image015
, the second auxiliary diode
Figure 02_image017
, the third auxiliary diode
Figure 02_image019
: OFF, 10th diode
Figure 02_image025
, the 13th diode
Figure 02_image031
: ON]: Please also refer to Figure 14, which is the equivalent linear circuit diagram of the twelfth stage of the present invention. The twelfth stage starts at
Figure 02_image251
, the first clamp diode
Figure 02_image252
Transition to OFF. The energy stored in the magnetizing inductance is completely transferred to the secondary side through the coupled inductance, through the output diode
Figure 02_image114
to the output capacitor
Figure 02_image063
and output load
Figure 02_image065
discharge. when
Figure 02_image253
, auxiliary switch
Figure 02_image055
When switched ON, this phase ends.

第十三階段［

Figure 02_image255
］：［第一功率開關
Figure 02_image051
：OFF，第二功率開關
Figure 02_image053
：ON，輔助開關
Figure 02_image055
：OFF
Figure 02_image128
ON，第一輔助二極體
Figure 02_image015
：OFF
Figure 02_image128
ON，第11二極體
Figure 02_image027
、第12二極體
Figure 02_image029
、第一箝位二極體
Figure 02_image105
、第二箝位二極體
Figure 02_image013
、第一切換二極體
Figure 02_image021
、第二切換二極體
Figure 02_image023
、第二輔助二極體
Figure 02_image017
、第三輔助二極體
Figure 02_image019
：OFF，輸出二極體
Figure 02_image114
：ON，第10二極體
Figure 02_image025
、第13二極體
Figure 02_image031
：ON］：請再一併參閱第十五圖本發明之第十三階段等效線性電路圖所示，第十三階段開始於
Figure 02_image257
，輔助開關
Figure 02_image055
切換為ON，第一輔助二極體
Figure 02_image258
轉態為ON，因為輔助電感電流
Figure 02_image171
的初始值為零，所以輔助開關
Figure 02_image055
和第一輔助二極體
Figure 02_image259
能夠以ZCS切換為ON。第一漏電感電流
Figure 02_image260
從零開始上升，輸出二極體
Figure 02_image114
之電流
Figure 02_image261
開始下降。當
Figure 02_image263
， 輸出二極體電流
Figure 02_image261
下降至零，第一磁化電感
Figure 02_image043
所儲存的能量藉由耦合電感傳遞至輸出負載
Figure 02_image065
的動作結束，此時
Figure 02_image265
，輸出二極體
Figure 02_image114
以ZCS自然轉態成OFF，本階段結束。Thirteenth stage [
Figure 02_image255
]: [First power switch
Figure 02_image051
: OFF, the second power switch
Figure 02_image053
: ON, auxiliary switch
Figure 02_image055
: OFF
Figure 02_image128
ON, the first auxiliary diode
Figure 02_image015
: OFF
Figure 02_image128
ON, 11th diode
Figure 02_image027
, the 12th diode
Figure 02_image029
, the first clamp diode
Figure 02_image105
, the second clamp diode
Figure 02_image013
, the first switching diode
Figure 02_image021
, the second switching diode
Figure 02_image023
, the second auxiliary diode
Figure 02_image017
, the third auxiliary diode
Figure 02_image019
: OFF, output diode
Figure 02_image114
: ON, 10th diode
Figure 02_image025
, the 13th diode
Figure 02_image031
: ON]: Please also refer to Figure 15, which is the equivalent linear circuit diagram of the thirteenth stage of the present invention. The thirteenth stage starts at
Figure 02_image257
, auxiliary switch
Figure 02_image055
switched ON, the first auxiliary diode
Figure 02_image258
transition to ON because the auxiliary inductor current
Figure 02_image171
The initial value of is zero, so the auxiliary switch
Figure 02_image055
and the first auxiliary diode
Figure 02_image259
Can be switched ON with ZCS. first leakage inductance current
Figure 02_image260
Rising from zero, output diode
Figure 02_image114
the current
Figure 02_image261
begin to drop. when
Figure 02_image263
, the output diode current
Figure 02_image261
drops to zero, the first magnetizing inductance
Figure 02_image043
The stored energy is transferred to the output load through the coupled inductor
Figure 02_image065
action ends, at this time
Figure 02_image265
, the output diode
Figure 02_image114
When ZCS naturally transitions to OFF, this stage ends.

第十四階段［

Figure 02_image267
］：［第一功率開關
Figure 02_image051
：OFF，第二功率開關
Figure 02_image053
、輔助開關
Figure 02_image055
：ON，輸出二極體
Figure 02_image114
：ON
Figure 02_image128
OFF，第11二極體
Figure 02_image027
、第12二極體
Figure 02_image029
、第一箝位二極體
Figure 02_image105
、第二箝位二極體
Figure 02_image013
、第一切換二極體
Figure 02_image021
、第二切換二極體
Figure 02_image023
、第二輔助二極體
Figure 02_image017
、第三輔助二極體
Figure 02_image019
：OFF，第10二極體
Figure 02_image025
、第13二極體
Figure 02_image031
、第一輔助二極體
Figure 02_image015
：ON］：請再一併參閱第十六圖本發明之第十四階段等效線性電路圖所示，第十四階段開始於
Figure 02_image269
，輸出二極體
Figure 02_image114
轉態為OFF。輔助電感
Figure 02_image007
和第一功率開關
Figure 02_image270
的輸出電容
Figure 02_image271
形成共振電路，因為輔助電感
Figure 02_image007
和第一功率開關
Figure 02_image272
的輸出電容
Figure 02_image273
都很小，共振頻率很大，所以輔助電感電流
Figure 02_image171
以共振形式快速上升，第一功率開關
Figure 02_image274
的跨壓
Figure 02_image275
以共振形式快速下降。第一功率開關
Figure 02_image272
的輸出電容
Figure 02_image273
所儲存的能量轉移至輔助電感
Figure 02_image007
儲存。當第一功率開關
Figure 02_image276
的跨壓
Figure 02_image277
下降至零，第一功率開關
Figure 02_image276
的內部本體二極體［body diode］導通，第一功率開關
Figure 02_image276
的跨壓
Figure 02_image275
箝制在零，第一功率開關
Figure 02_image276
之ZVS切換的條件成立。當
Figure 02_image278
，第一功率開關
Figure 02_image276
以ZVS切換為ON，本階段結束。fourteenth stage
Figure 02_image267
]: [First power switch
Figure 02_image051
: OFF, the second power switch
Figure 02_image053
, auxiliary switch
Figure 02_image055
: ON, output diode
Figure 02_image114
: ON
Figure 02_image128
OFF, 11th diode
Figure 02_image027
, the 12th diode
Figure 02_image029
, the first clamp diode
Figure 02_image105
, the second clamp diode
Figure 02_image013
, the first switching diode
Figure 02_image021
, the second switching diode
Figure 02_image023
, the second auxiliary diode
Figure 02_image017
, the third auxiliary diode
Figure 02_image019
: OFF, 10th diode
Figure 02_image025
, the 13th diode
Figure 02_image031
, the first auxiliary diode
Figure 02_image015
:ON]: Please also refer to Figure 16, as shown in the equivalent linear circuit diagram of the fourteenth stage of the present invention, the fourteenth stage starts at
Figure 02_image269
, the output diode
Figure 02_image114
Transition to OFF. Auxiliary inductance
Figure 02_image007
and the first power switch
Figure 02_image270
The output capacitance of
Figure 02_image271
form a resonant circuit because the auxiliary inductance
Figure 02_image007
and the first power switch
Figure 02_image272
The output capacitance of
Figure 02_image273
are very small, the resonance frequency is large, so the auxiliary inductor current
Figure 02_image171
Rapid rise in resonance form, first power switch
Figure 02_image274
cross pressure
Figure 02_image275
Rapid decline in resonance form. first power switch
Figure 02_image272
The output capacitance of
Figure 02_image273
The stored energy is transferred to the auxiliary inductor
Figure 02_image007
store. When the first power switch
Figure 02_image276
cross pressure
Figure 02_image277
down to zero, the first power switch
Figure 02_image276
The internal body diode of , turns on, the first power switch
Figure 02_image276
cross pressure
Figure 02_image275
clamped at zero, the first power switch
Figure 02_image276
The conditions for ZVS switching are satisfied. when
Figure 02_image278
, the first power switch
Figure 02_image276
When ZVS is switched to ON, this stage ends.

第十五階段［

Figure 02_image280
］：［第二功率開關
Figure 02_image053
、輔助開關
Figure 02_image055
：ON，第一功率開關
Figure 02_image051
：OFF
Figure 02_image128
ON，第11二極體
Figure 02_image027
、第13二極體
Figure 02_image282
、第一箝位二極體
Figure 02_image105
、第二箝位二極體
Figure 02_image013
、第一切換二極體
Figure 02_image021
、第二切換二極體
Figure 02_image023
、第二輔助二極體
Figure 02_image017
、第三輔助二極體
Figure 02_image019
、輸出二極體
Figure 02_image114
：OFF，第10二極體
Figure 02_image025
、第12二極體
Figure 02_image283
、第一輔助二極體
Figure 02_image015
：ON］：請再一併參閱第十七圖本發明之第十五階段等效線性電路圖所示，第十五階段開始於
Figure 02_image285
，第一功率開關
Figure 02_image286
以ZVS切換為ON。本階段輔助電感
Figure 02_image007
之電壓
Figure 02_image191
，輔助電感電流
Figure 02_image171
保持常數。耦合電感一次側受到輸入電壓
Figure 02_image001
充磁。當
Figure 02_image287
，輔助開關
Figure 02_image055
切換為OFF時，本階段結束。the fifteenth stage
Figure 02_image280
]: [Second power switch
Figure 02_image053
, auxiliary switch
Figure 02_image055
: ON, the first power switch
Figure 02_image051
: OFF
Figure 02_image128
ON, 11th diode
Figure 02_image027
, the 13th diode
Figure 02_image282
, the first clamp diode
Figure 02_image105
, the second clamp diode
Figure 02_image013
, the first switching diode
Figure 02_image021
, the second switching diode
Figure 02_image023
, the second auxiliary diode
Figure 02_image017
, the third auxiliary diode
Figure 02_image019
, output diode
Figure 02_image114
: OFF, 10th diode
Figure 02_image025
, the 12th diode
Figure 02_image283
, the first auxiliary diode
Figure 02_image015
: ON]: Please also refer to Figure 17, as shown in the equivalent linear circuit diagram of the fifteenth stage of the present invention, the fifteenth stage starts at
Figure 02_image285
, the first power switch
Figure 02_image286
Toggle ON with ZVS. Auxiliary inductor at this stage
Figure 02_image007
voltage
Figure 02_image191
, the auxiliary inductor current
Figure 02_image171
keep it constant. The primary side of the coupled inductor is subjected to the input voltage
Figure 02_image001
Magnetizing. when
Figure 02_image287
, auxiliary switch
Figure 02_image055
When switched to OFF, this phase ends.

第十六階段［

Figure 02_image289
］：［第一功率開關
Figure 02_image051
、第二功率開關
Figure 02_image053
：ON，輔助開關
Figure 02_image055
：ON
Figure 02_image128
OFF，第11二極體
Figure 02_image027
、第13二極體
Figure 02_image291
、第一箝位二極體
Figure 02_image105
、第二箝位二極體
Figure 02_image013
、第一切換二極體
Figure 02_image021
、第二切換二極體
Figure 02_image023
、第二輔助二極體
Figure 02_image017
、輸出二極體
Figure 02_image114
：OFF，第10二極體
Figure 02_image025
、第12二極體
Figure 02_image292
、第一輔助二極體
Figure 02_image015
、第三輔助二極體
Figure 02_image019
：ON］：請再一併參閱第十八圖本發明之第十六階段等效線性電路圖所示，第十六階段開始於
Figure 02_image293
，輔助開關
Figure 02_image055
切換為OFF，因為輔助電感電流
Figure 02_image171
的連續性，使得第三輔助二極體
Figure 02_image019
轉態為ON，輔助電感電壓
Figure 02_image198
，輔助電感電流
Figure 02_image171
線性下降，輔助電感
Figure 02_image007
儲存的能量傳送至箝位電容
Figure 02_image107
，而輸入電壓
Figure 02_image200
繼續對兩個耦合電感一次側充磁。當
Figure 02_image294
，輔助電感電流
Figure 02_image171
下降至零，第一輔助二極體
Figure 02_image296
、第三輔助二極體
Figure 02_image019
以ZCS自然轉態成OFF，本階段結束。The sixteenth stage [
Figure 02_image289
]: [First power switch
Figure 02_image051
, the second power switch
Figure 02_image053
: ON, auxiliary switch
Figure 02_image055
: ON
Figure 02_image128
OFF, 11th diode
Figure 02_image027
, the 13th diode
Figure 02_image291
, the first clamp diode
Figure 02_image105
, the second clamp diode
Figure 02_image013
, the first switching diode
Figure 02_image021
, the second switching diode
Figure 02_image023
, the second auxiliary diode
Figure 02_image017
, output diode
Figure 02_image114
: OFF, 10th diode
Figure 02_image025
, the 12th diode
Figure 02_image292
, the first auxiliary diode
Figure 02_image015
, the third auxiliary diode
Figure 02_image019
: ON]: Please also refer to Figure 18, as shown in the equivalent linear circuit diagram of the sixteenth stage of the present invention, the sixteenth stage starts at
Figure 02_image293
, auxiliary switch
Figure 02_image055
switched OFF because the auxiliary inductor current
Figure 02_image171
continuity, such that the third auxiliary diode
Figure 02_image019
transition to ON, auxiliary inductor voltage
Figure 02_image198
, the auxiliary inductor current
Figure 02_image171
Linear drop, auxiliary inductance
Figure 02_image007
The stored energy is delivered to the clamping capacitor
Figure 02_image107
, while the input voltage
Figure 02_image200
Continue to magnetize the primary side of both coupled inductors. when
Figure 02_image294
, the auxiliary inductor current
Figure 02_image171
down to zero, the first auxiliary diode
Figure 02_image296
, the third auxiliary diode
Figure 02_image019
When ZCS naturally transitions to OFF, this stage ends.

依據上述電路動作分析結果，使用IsSpice模擬軟體驗證其電路理論分析、電氣規格以及上述所及之優點［請再一併參閱第十九圖本發明之模擬電路示意圖所示］。設定該轉換器(1)之相關參數如下表1所示： 輸入電壓Vin 24 V 導通比D 0.52 輸出電壓Vo 400 V 電感L i1 、L i2 、Lm 1 、Lm 2

Figure 02_image297
輸出功率Po 200 W 輸出電容C o
Figure 02_image299
 切換頻率fs 50 kHz 電容C A 、C c 、C 1 、C 2
Figure 02_image301
 表1電氣規格與元件參數According to the above circuit action analysis results, the IsSpice simulation software is used to verify its circuit theoretical analysis, electrical specifications, and the above-mentioned advantages [please also refer to the schematic diagram of the simulation circuit of the present invention in Figure 19]. Set the relevant parameters of the converter (1) as shown in Table 1 below: Input voltage V in 24V Conduction ratio D 0.52 Output voltage V o 400V Inductances L i1 , L i2 , L m 1 , L m 2
Figure 02_image297
 Output power P o 200W Output capacitor C o
Figure 02_image299
 Switching frequency f s 50kHz Capacitors C A , C c , C 1 , C 2
Figure 02_image301
 Table 1 Electrical Specifications and Component Parameters

以下將介紹輸出功率

Figure 02_image302
之下相關模擬結果，模擬波形將驗正項目如下：The following will describe the output power
Figure 02_image302
The relevant simulation results below, the simulation waveform will be verified as follows:

A.電氣規格驗證：輸入電壓

Figure 02_image071
、輸出電壓
Figure 02_image073
、導通比
Figure 02_image304
A. Electrical Specification Verification: Input Voltage
Figure 02_image071
,The output voltage
Figure 02_image073
, conduction ratio
Figure 02_image304

請再一併參閱第二十圖本發明之開關驅動信號

Figure 02_image067
、
Figure 02_image069
與輸入電壓
Figure 02_image071
及輸出電壓
Figure 02_image073
的模擬波形圖所示，由該第二十圖可知，輸入電壓
Figure 02_image306
、輸出電壓
Figure 02_image308
，滿足電氣之需求規格。Please also refer to the switch driving signal of the present invention in FIG. 20
Figure 02_image067
,
Figure 02_image069
with input voltage
Figure 02_image071
and output voltage
Figure 02_image073
As shown in the analog waveform diagram of the twentieth diagram, the input voltage
Figure 02_image306
,The output voltage
Figure 02_image308
, to meet the requirements of electrical specifications.

B.輸入電流漣波相消：

Figure 02_image310
、
Figure 02_image311
、
Figure 02_image312
、
Figure 02_image313
、
Figure 02_image315
、
Figure 02_image316
、
Figure 02_image317
B. Input current ripple cancellation:
Figure 02_image310
,
Figure 02_image311
,
Figure 02_image312
,
Figure 02_image313
,
Figure 02_image315
,
Figure 02_image316
,
Figure 02_image317

因為該轉換器(1)以交錯180度依序導通的驅動方式操作，因此，輸入濾波電感電流

Figure 02_image318
和
Figure 02_image319
漣波相差180度，又
Figure 02_image320
，因此
Figure 02_image318
、
Figure 02_image319
及
Figure 02_image322
、
Figure 02_image323
之漣波可以相消以降低輸入電流
Figure 02_image312
之漣波。請再一併參閱第二十一圖本發明之輸入端電流
Figure 02_image324
、
Figure 02_image325
的模擬波形圖、第二十二圖本發明之輸入端電流
Figure 02_image079
、
Figure 02_image081
的模擬波形圖、第二十三圖本發明之輸入端電流
Figure 02_image083
、
Figure 02_image085
、
Figure 02_image087
的模擬波形圖所示，可以觀察出，當輸入濾波電感電流漣波
Figure 02_image326
和
Figure 02_image328
約為2.5A，輸入電流漣波
Figure 02_image330
約為1.2A。Because the converter (1) operates in a staggered 180-degree turn-on drive mode, the input filter inductor current
Figure 02_image318
and
Figure 02_image319
The ripples differ by 180 degrees, and
Figure 02_image320
,therefore
Figure 02_image318
,
Figure 02_image319
and
Figure 02_image322
,
Figure 02_image323
The ripple can be cancelled to reduce the input current
Figure 02_image312
the ripples. Please also refer to the input current of the present invention in Figure 21
Figure 02_image324
,
Figure 02_image325
The analog waveform diagram of , and the input terminal current of the present invention in Fig. 22
Figure 02_image079
,
Figure 02_image081
The analog waveform diagram of , and the input terminal current of the present invention in Figure 23
Figure 02_image083
,
Figure 02_image085
,
Figure 02_image087
As shown in the simulated waveforms, it can be observed that when the input filter inductor current ripples
Figure 02_image326
and
Figure 02_image328
About 2.5A, input current ripple
Figure 02_image330
About 1.2A.

C.第一功率開關

Figure 02_image051
、第二功率開關
Figure 02_image053
的低電壓應力：
Figure 02_image332
及
Figure 02_image334
C. The first power switch
Figure 02_image051
, the second power switch
Figure 02_image053
The low voltage stress of:
Figure 02_image332
and
Figure 02_image334

因為該轉換器(1)加入升壓電容，因此開關跨壓將會被升壓電容給限制住：

Figure 02_image336
、
Figure 02_image338
，請再一併參閱第二十四圖本發明之第一功率開關
Figure 02_image051
驅動信號
Figure 02_image089
Figure 02_image091
、
Figure 02_image093
及其跨壓
Figure 02_image095
、
Figure 02_image097
的模擬波形圖及第二十五圖本發明之第二功率開關
Figure 02_image053
驅動信號
Figure 02_image089
Figure 02_image091
、
Figure 02_image093
及其跨壓
Figure 02_image095
、
Figure 02_image097
的模擬波形圖所示，開關的跨壓也約為100V，可知開關確實擁有遠低於輸出電壓的低電壓應力。Because the converter (1) adds a boost capacitor, the switch voltage across the switch will be limited by the boost capacitor:
Figure 02_image336
,
Figure 02_image338
, please also refer to the first power switch of the present invention in Figure 24
Figure 02_image051
drive signal
Figure 02_image089
Figure 02_image091
,
Figure 02_image093
and its cross pressure
Figure 02_image095
,
Figure 02_image097
The analog waveform diagram and the twenty-fifth diagram of the second power switch of the present invention
Figure 02_image053
drive signal
Figure 02_image089
Figure 02_image091
,
Figure 02_image093
and its cross pressure
Figure 02_image095
,
Figure 02_image097
As shown in the analog waveform of , the cross voltage of the switch is also about 100V, which shows that the switch does have a low voltage stress much lower than the output voltage.

而本發明之轉換器(1)與文獻中之高升壓比轉換器，在電壓轉換比進行比較，請參閱下表2所示，本發明之轉換器(1)具有極高的電壓轉換比： 高升壓轉換器 文獻［1］ 文獻［2］ 文獻［3］ 本發明 電壓轉換比

Figure 02_image340
Figure 02_image342
Figure 02_image342
Figure 02_image343
 表2參考文獻與本發明之比較表The converter (1) of the present invention is compared with the high boost ratio converter in the literature in terms of voltage conversion ratio, as shown in Table 2 below, the converter (1) of the present invention has a very high voltage conversion ratio : high boost converter Literature [1] Literature [2] Literature [3] this invention Voltage conversion ratio
Figure 02_image340
Figure 02_image342
Figure 02_image342
Figure 02_image343
 Table 2 Comparison table of references and the present invention

請再一併參閱第二十六圖本發明於匝數比

Figure 02_image099
時與文獻［1］之電壓轉換比比較曲線圖及第二十七圖本發明於匝數比
Figure 02_image101
時與文獻［1］之電壓轉換比比較曲線圖所示，由於文獻［1］、文獻［2］、文獻［3］之電壓增益皆相同，取文獻［1］為代表與本發明之轉換器(1)進行比較可知，本發明之轉換器(1)具有最高之電壓增益，且當耦合電感匝數比
Figure 02_image345
越大時，則差距會更加明顯。Please also refer to Figure 26 in the present invention for the turns ratio
Figure 02_image099
When compared with the voltage conversion ratio of the literature [1], and the twenty-seventh graph of the present invention, the turns ratio
Figure 02_image101
When compared with the voltage conversion ratio of document [1], as shown in the graph, since the voltage gain of document [1], document [2], and document [3] are all the same, document [1] is taken as the representative converter of the present invention. (1) It can be seen from the comparison that the converter (1) of the present invention has the highest voltage gain, and when the coupled inductor turns ratio is
Figure 02_image345
The larger the difference, the more obvious the difference will be.

參考文獻：references:

［1］R. N. A. L. S. Aquino, F. L. Tofoli, P. P. Praca, D. S. O. Jr, and L. H. S. C. Barreto, “Soft switching high voltage gain dc-dc interleaved boost converter,” IET Power Electronics, vol. 8, iss. 1, pp. 120-129, 2015[1] RNALS Aquino, FL Tofoli, PP Praca, DSO Jr, and LHSC Barreto, “Soft switching high voltage gain dc-dc interleaved boost converter,” IET Power Electronics, vol. 8, iss. 1, pp. 120-129 , 2015

［2］M. Muhammad, M. Armstrong, and M. Elgendy, “A nonisolated interleaved boost converter for high-voltage gain applications,” IEEE Trans. Power Electronics, vol. 31, no. 2, pp. 352-362, 2016[2] M. Muhammad, M. Armstrong, and M. Elgendy, “A nonisolated interleaved boost converter for high-voltage gain applications,” IEEE Trans. Power Electronics, vol. 31, no. 2, pp. 352-362, 2016

［3］M. Forouzesh, Y. Shen, K. Yari, Y. P. Siwakoti, F. Blaabjerg, “High-efficiency high step-up DC-DC converter with dual coupled inductors for grid-connected  photovoltaic systems,” IEEE Trans. Power Electronics, vol. 33, no. 7, pp. 5967-5982, 2018.[3] M. Forouzesh, Y. Shen, K. Yari, YP Siwakoti, F. Blaabjerg, “High-efficiency high step-up DC-DC converter with dual coupled inductors for grid-connected photovoltaic systems,” IEEE Trans. Power Electronics, vol. 33, no. 7, pp. 5967-5982, 2018.

藉由以上所述，本發明之使用實施說明可知，本發明與現有技術手段相較之下，本發明主要係具有下列優點：From the above, the use and implementation description of the present invention shows that compared with the prior art means, the present invention mainly has the following advantages:

1.高升壓增益：本發明提出交錯型高電壓轉換比直流轉換器，可得到極高的升壓增益。1. High boost gain: The present invention proposes an interleaved high voltage conversion ratio DC converter, which can obtain extremely high boost gain.

2.高電力密度：第一功率開關

Figure 02_image051
及第二功率開關
Figure 02_image053
係以180°的相位差交錯工作，可使輸入電流漣波降低，因此，可以使用電感值較小之輸入濾波電感，降低電感的體積。2. High power density: the first power switch
Figure 02_image051
and second power switch
Figure 02_image053
It works staggered with a phase difference of 180°, which can reduce the input current ripple. Therefore, an input filter inductor with a smaller inductance value can be used to reduce the size of the inductor.

3.低電壓應力：高電壓增益的達成，不必操作在極大的導通比，則功率開關具有低於輸出電壓的低電壓應力，故可使用導通電阻較小的低額定耐壓MOSFET，所以可降低導通損失，提升整體效率。3. Low voltage stress: To achieve high voltage gain, it is not necessary to operate at a very large conduction ratio, and the power switch has a low voltage stress lower than the output voltage, so a low-rated withstand voltage MOSFET with a small on-resistance can be used, so it can be reduced. Conduction loss, improve overall efficiency.

4.高功率應用：提出交錯型高電壓轉換比直流轉換器，由於電路架構仍具有並聯連接特性，故可分擔輸入電流，能有效降低電路中儲能元件及開關元件之電流應力，適合應用於高功率的場合。4. High-power application: The interleaved high-voltage conversion ratio DC converter is proposed. Since the circuit structure still has the characteristics of parallel connection, it can share the input current, which can effectively reduce the current stress of the energy storage elements and switching elements in the circuit. It is suitable for application in High power occasions.

5.高轉換效率：本發明具有電流分流且可選用低導通電阻MOSFET，使電路導通損失有效降低，提升轉換器之整體效率。5. High conversion efficiency: The present invention has current shunt and can choose low on-resistance MOSFET, which can effectively reduce the conduction loss of the circuit and improve the overall efficiency of the converter.

然而前述之實施例或圖式並非限定本發明之產品結構或使用方式，任何所屬技術領域中具有通常知識者之適當變化或修飾，皆應視為不脫離本發明之專利範疇。However, the foregoing embodiments or drawings do not limit the product structure or usage of the present invention, and any appropriate changes or modifications made by those with ordinary knowledge in the technical field should be regarded as not departing from the scope of the present invention.

綜上所述，本發明實施例確能達到所預期之使用功效，又其所揭露之具體構造，不僅未曾見諸於同類產品中，亦未曾公開於申請前，誠已完全符合專利法之規定與要求，爰依法提出發明專利之申請，懇請惠予審查，並賜准專利，則實感德便。To sum up, the embodiment of the present invention can indeed achieve the expected use effect, and the specific structure disclosed is not only not seen in similar products, but also has not been disclosed before the application, which fully complies with the provisions of the patent law In accordance with the requirements, I would like to file an application for an invention patent in accordance with the law, and I urge you to review it and grant the patent.

1:轉換器1: Converter

Figure 02_image001
:輸入電壓
Figure 02_image001
:Input voltage

Figure 02_image003
:第一輸入濾波電感
Figure 02_image003
: first input filter inductor

Figure 02_image005
:第二輸入濾波電感
Figure 02_image005
: The second input filter inductor

Figure 02_image007
:輔助電感
Figure 02_image007
: Auxiliary inductor

Figure 02_image009
:輸入濾波電容
Figure 02_image009
: Input filter capacitor

Figure 02_image011
:第一箝位二極體
Figure 02_image011
: 1st clamp diode

Figure 02_image013
:第二箝位二極體
Figure 02_image013
: Second clamp diode

Figure 02_image015
:第一輔助二極體
Figure 02_image015
: first auxiliary diode

Figure 02_image017
:第二輔助二極體
Figure 02_image017
: second auxiliary diode

Figure 02_image019
:第三輔助二極體
Figure 02_image019
: third auxiliary diode

Figure 02_image021
:第一切換二極體
Figure 02_image021
: first switching diode

Figure 02_image023
:第二切換二極體
Figure 02_image023
: second switching diode

Figure 02_image025
:第10二極體
Figure 02_image025
: 10th diode

Figure 02_image027
:第11二極體
Figure 02_image027
: 11th diode

Figure 02_image029
:第12二極體
Figure 02_image029
: 12th diode

Figure 02_image031
:第13二極體
Figure 02_image031
: 13th diode

Figure 02_image033
:輸出二極體
Figure 02_image033
: output diode

Figure 02_image035
:第一耦合電感一次側
Figure 02_image035
: Primary side of the first coupled inductor

Figure 02_image037
:第一耦合電感二次側
Figure 02_image037
: Secondary side of the first coupled inductor

Figure 02_image039
:第二耦合電感一次側
Figure 02_image039
: Primary side of the second coupled inductor

Figure 02_image041
:第二耦合電感二次側
Figure 02_image041
: Secondary side of the second coupled inductor

Figure 02_image043
:第一磁化電感
Figure 02_image043
: first magnetizing inductance

Figure 02_image045
:第二磁化電感
Figure 02_image045
: Second magnetizing inductance

Figure 02_image047
:第一漏電感
Figure 02_image047
: first leakage inductance

Figure 02_image049
:第二漏電感
Figure 02_image049
: Second leakage inductance

Figure 02_image051
:第一功率開關
Figure 02_image051
: first power switch

Figure 02_image053
:第二功率開關
Figure 02_image053
: Second power switch

Figure 02_image055
:輔助開關
Figure 02_image055
: Auxiliary switch

Figure 02_image057
:箝位電容
Figure 02_image057
: Clamping Capacitor

Figure 02_image059
:第一切換電容
Figure 02_image059
: first switching capacitor

Figure 02_image061
:第二切換電容
Figure 02_image061
: Second switching capacitor

Figure 02_image063
:輸出電容
Figure 02_image063
: output capacitor

Figure 02_image065
:輸出負載
Figure 02_image065
: output load

第一圖：本發明之電路圖The first picture: the circuit diagram of the present invention

第二圖：本發明之時序圖Figure 2: Timing diagram of the present invention

第三圖：本發明之第一階段等效線性電路圖Figure 3: Equivalent linear circuit diagram of the first stage of the present invention

第四圖：本發明之第二階段等效線性電路圖Figure 4: Equivalent linear circuit diagram of the second stage of the present invention

第五圖：本發明之第三階段等效線性電路圖Figure 5: Equivalent linear circuit diagram of the third stage of the present invention

第六圖：本發明之第四階段等效線性電路圖Figure 6: Equivalent linear circuit diagram of the fourth stage of the present invention

第七圖：本發明之第五階段等效線性電路圖Figure 7: Equivalent linear circuit diagram of the fifth stage of the present invention

第八圖：本發明之第六階段等效線性電路圖Figure 8: Equivalent linear circuit diagram of the sixth stage of the present invention

第九圖：本發明之第七階段等效線性電路圖Figure 9: Equivalent linear circuit diagram of the seventh stage of the present invention

第十圖：本發明之第八階段等效線性電路圖Figure 10: Equivalent linear circuit diagram of the eighth stage of the present invention

第十一圖：本發明之第九階段等效線性電路圖Figure 11: Equivalent linear circuit diagram of the ninth stage of the present invention

第十二圖：本發明之第十階段等效線性電路圖Figure 12: Equivalent linear circuit diagram of the tenth stage of the present invention

第十三圖：本發明之第十一階段等效線性電路圖Figure 13: Equivalent linear circuit diagram of the eleventh stage of the present invention

第十四圖：本發明之第十二階段等效線性電路圖Figure 14: Equivalent linear circuit diagram of the twelfth stage of the present invention

第十五圖：本發明之第十三階段等效線性電路圖Figure 15: Equivalent linear circuit diagram of the thirteenth stage of the present invention

第十六圖：本發明之第十四階段等效線性電路圖Figure 16: Equivalent linear circuit diagram of the fourteenth stage of the present invention

第十七圖：本發明之第十五階段等效線性電路圖Figure 17: Equivalent linear circuit diagram of the fifteenth stage of the present invention

第十八圖：本發明之第十六階段等效線性電路圖Figure 18: Equivalent linear circuit diagram of the sixteenth stage of the present invention

第十九圖：本發明之模擬電路示意圖Figure 19: Schematic diagram of the analog circuit of the present invention

第二十圖：本發明之開關驅動信號

Figure 02_image067
、
Figure 02_image069
與輸入電壓
Figure 02_image071
及輸出電壓
Figure 02_image073
的模擬波形圖Figure 20: Switch driving signal of the present invention
Figure 02_image067
,
Figure 02_image069
with input voltage
Figure 02_image071
and output voltage
Figure 02_image073
The analog waveform of

第二十一圖：本發明之輸入端電流

Figure 02_image075
、
Figure 02_image077
的模擬波形圖Figure 21: Input current of the present invention
Figure 02_image075
,
Figure 02_image077
The analog waveform of

第二十二圖：本發明之輸入端電流

Figure 02_image079
、
Figure 02_image081
的模擬波形圖Figure 22: Input current of the present invention
Figure 02_image079
,
Figure 02_image081
The analog waveform of

第二十三圖：本發明之輸入端電流

Figure 02_image083
、
Figure 02_image085
、
Figure 02_image087
的模擬波形圖Figure 23: Input current of the present invention
Figure 02_image083
,
Figure 02_image085
,
Figure 02_image087
The analog waveform of

第二十四圖：本發明之第一功率開關

Figure 02_image051
驅動信號
Figure 02_image089
Figure 02_image091
、
Figure 02_image093
及其跨壓
Figure 02_image095
、
Figure 02_image097
的模擬波形圖Figure 24: The first power switch of the present invention
Figure 02_image051
drive signal
Figure 02_image089
Figure 02_image091
,
Figure 02_image093
and its cross pressure
Figure 02_image095
,
Figure 02_image097
The analog waveform of

第二十五圖：本發明之第二功率開關

Figure 02_image053
驅動信號
Figure 02_image089
Figure 02_image091
、
Figure 02_image093
及其跨壓
Figure 02_image095
、
Figure 02_image097
的模擬波形圖Figure 25: The second power switch of the present invention
Figure 02_image053
drive signal
Figure 02_image089
Figure 02_image091
,
Figure 02_image093
and its cross pressure
Figure 02_image095
,
Figure 02_image097
The analog waveform of

第二十六圖：本發明於匝數比

Figure 02_image099
時與文獻［1］之電壓轉換比比較曲線圖Figure 26: The invention is based on the turns ratio
Figure 02_image099
When compared with the voltage conversion ratio of the literature [1]

第二十七圖：本發明於匝數比

Figure 02_image101
時與文獻［1］之電壓轉換比比較曲線圖The twenty-seventh figure: the invention is based on the turns ratio
Figure 02_image101
When compared with the voltage conversion ratio of the literature [1]

1:轉換器1: Converter

V in :輸入電壓 V in : input voltage

L i 1 :第一輸入濾波電感 L i 1 : the first input filter inductor

L i 2 :第二輸入濾波電感 L i 2 : the second input filter inductor

L a :輔助電感 L a : auxiliary inductance

C A :輸入濾波電容 C A : Input filter capacitor

D c 1 :第一箝位二極體 D c 1 : first clamp diode

D c 2 :第二箝位二極體 D c 2 : second clamp diode

D a 1 :第一輔助二極體 D a 1 : the first auxiliary diode

D a 2 :第二輔助二極體 D a 2 : the second auxiliary diode

D a 3 :第三輔助二極體 D a 3 : the third auxiliary diode

D 1 :第一切換二極體 D 1 : first switching diode

D 2 :第二切換二極體 D 2 : second switching diode

D 10 :第10二極體 D 10 : 10th diode

D 11 :第11二極體 D 11 : 11th diode

D 12 :第12二極體 D 12 : 12th diode

D 13 :第13二極體 D 13 : 13th diode

D o :輸出二極體 D o : output diode

N p 1 :第一耦合電感一次側 N p 1 : the primary side of the first coupled inductor

N s 1 :第一耦合電感二次側 N s 1 : the secondary side of the first coupled inductor

N p 2 :第二耦合電感一次側 N p 2 : the primary side of the second coupled inductor

N s 2 :第二耦合電感二次側 N s 2 : the secondary side of the second coupled inductor

L m 1 :第一磁化電感 L m 1 : the first magnetizing inductance

L m 2 :第二磁化電感 L m 2 : second magnetizing inductance

L k 1 :第一漏電感 L k 1 : first leakage inductance

L k 2 :第二漏電感 L k 2 : second leakage inductance

S 1 :第一功率開關 S 1 : the first power switch

S 2 :第二功率開關 S 2 : Second power switch

S a :輔助開關 S a : Auxiliary switch

C c :箝位電容 C c : clamp capacitor

C 1 :第一切換電容 C 1 : the first switching capacitor

C 2 :第二切換電容 C 2 : Second switching capacitor

C o :輸出電容 C o : output capacitance

R o :輸出負載 R o : output load

Claims (3)

一種交錯型高電壓轉換比直流轉換器，其主要係令轉換器於輸入電壓之正極分別連接第一輸入濾波電感之第一端、輸入濾波電容之負極及第二輸入濾波電感之第一端，而該輸入電壓之負極則進行接地，該第一輸入濾波電感之第二端分別連接第10二極體之正極及第11二極體之正極，該輸入濾波電容之正極分別連接第一耦合電感一次側之第一端、第13二極體之負極、第二耦合電感一次側之第一端及該第11二極體之負極，該第二輸入濾波電感之第二端分別連接第12二極體之正極及該第13二極體之正極，該第10二極體之負極分別連接第二功率開關之第一端、該第二耦合電感一次側之第二端、第一箝位二極體之正極及第二輔助二極體之正極，該第二功率開關之第二端則予以接地，該第12二極體之負極分別連接第一功率開關之第一端、第二箝位二極體之正極、第一輔助二極體之正極及該第一耦合電感一次側之第二端，該第一功率開關之第二端則予以接地，該第一箝位二極體之負極分別連接第二切換二極體之正極、第三輔助二極體之負極、該第二箝位二極體之負極、箝位電容之第一端及第二切換電容之負極，該箝位電容之第二端予以接地，該第二輔助二極體之負極分別連接該第一輔助二極體之負極及輔助電感之第一端，該輔助電感之第二端分別連接該第三輔助二極體之正極及輔助開關之第一端，該輔助開關之第二端則予以接地，該第二切換二極體之負極分別連接第二耦合電感二次側之第一端及第一切換電容之負極，該第二耦合電感二次側之第二端連接第一耦合電感二次側之第一端，該第一耦合電感二次側之第二端分別連接該第二切換電容之正極及第一切換二極體之正極，該第一切換電容之正極及該第一切換二極體之負極一併連接至輸出二極體之正極，該輸出二極體之負極分別連接至輸出電容之第一端與輸出負載之第一端，而該輸出電容之第二端與該輸出負載之第二端則予以接地。An interleaved high-voltage conversion ratio DC converter is mainly used to connect the positive pole of the input voltage to the first terminal of the first input filter inductor, the negative pole of the input filter capacitor and the first terminal of the second input filter inductor, respectively. The negative pole of the input voltage is grounded, the second end of the first input filter inductor is connected to the positive pole of the 10th diode and the positive pole of the 11th diode, respectively, and the positive pole of the input filter capacitor is connected to the first coupling inductor respectively The first end of the primary side, the negative electrode of the 13th diode, the first end of the primary side of the second coupling inductor and the negative electrode of the 11th diode, the second end of the second input filter inductor is connected to the 122nd diode respectively The positive pole of the pole body and the positive pole of the 13th diode, and the negative pole of the 10th diode are respectively connected to the first end of the second power switch, the second end of the primary side of the second coupling inductor, and the first clamp two The positive pole of the pole body and the positive pole of the second auxiliary diode, the second terminal of the second power switch is grounded, and the negative pole of the 12th diode is respectively connected to the first terminal of the first power switch and the second clamp The positive pole of the diode, the positive pole of the first auxiliary diode and the second terminal of the primary side of the first coupling inductor, the second terminal of the first power switch is grounded, and the negative pole of the first clamping diode Connect the positive pole of the second switching diode, the negative pole of the third auxiliary diode, the negative pole of the second clamping diode, the first end of the clamping capacitor and the negative pole of the second switching capacitor, respectively. The second end of the auxiliary diode is grounded, the negative electrode of the second auxiliary diode is respectively connected to the negative electrode of the first auxiliary diode and the first end of the auxiliary inductor, and the second end of the auxiliary inductor is respectively connected to the third auxiliary diode The positive pole of the diode and the first terminal of the auxiliary switch, the second terminal of the auxiliary switch is grounded, and the negative pole of the second switching diode is respectively connected to the first terminal of the secondary side of the second coupling inductor and the first terminal of the first switching capacitor. Negative, the second end of the secondary side of the second coupled inductor is connected to the first end of the secondary side of the first coupled inductor, the second end of the secondary side of the first coupled inductor is respectively connected to the positive electrode and the second end of the second switching capacitor The positive pole of a switching diode, the positive pole of the first switching capacitor and the negative pole of the first switching diode are connected together to the positive pole of the output diode, and the negative pole of the output diode is respectively connected to the second pole of the output capacitor. One end and the first end of the output load, and the second end of the output capacitor and the second end of the output load are grounded. 如請求項1所述交錯型高電壓轉換比直流轉換器，其中，該第一耦合電感一次側形成有第一磁化電感，該第二耦合電感一次側形成有第二磁化電感。The interleaved high voltage conversion ratio DC converter according to claim 1, wherein a first magnetizing inductance is formed on the primary side of the first coupled inductor, and a second magnetizing inductance is formed on the primary side of the second coupled inductor. 如請求項1所述交錯型高電壓轉換比直流轉換器，其中，該第10二極體之負極與該第二耦合電感一次側之第二端之間形成有第二漏電感，該第12二極體之負極與該第一耦合電感一次側之第二端之間形成有第一漏電感。The interleaved high voltage conversion ratio DC converter of claim 1, wherein a second leakage inductance is formed between the negative electrode of the tenth diode and the second end of the primary side of the second coupled inductor, and the 12th A first leakage inductance is formed between the negative electrode of the diode and the second end of the primary side of the first coupled inductor.
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