TW202207599A - Interleaved high voltage conversion ratio dc/dc converter - Google Patents
Interleaved high voltage conversion ratio dc/dc converter Download PDFInfo
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
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本發明係有關於一種交錯型高電壓轉換比直流轉換器,尤其是指一種可得到極高的升壓增益,且可使輸入電流漣波降低,降低電感的體積,同時不必操作在極大的導通比,具有低於輸出電壓的低電壓應力,可降低導通損失,提升整體效率,並可分擔輸入電流,能有效降低電路中儲能元件及開關元件之電流應力,適合應用於高功率的場合,而在其整體施行使用上更增實用功效特性者。The present invention relates to an interleaved high voltage conversion ratio DC converter, in particular to a kind of high boost gain, which can reduce the input current ripple and reduce the volume of the inductance, and at the same time, it does not need to operate in a large conduction It has a low voltage stress lower than the output voltage, which can reduce the conduction loss, improve the overall efficiency, and can share the input current, which can effectively reduce the current stress of the energy storage elements and switching elements in the circuit, and is suitable for high-power applications. And in its overall implementation and use, it has more practical efficacy characteristics.
按,對於直流升壓目的而言,理論上,操作在極高導通比的傳統升壓型〔boost〕轉換器能夠得到高電壓增益,但是實務上受到寄生元件的影響,電壓轉換比受限在約5倍以下,因此當電壓增益高達10倍左右的實務需求時,研發嶄新的高升壓轉換器拓樸是必要的。因此,於近幾年來,高升壓DC-DC轉換器是電力電子工程領域中常見的研究主題之一。Press, for the purpose of DC boosting, in theory, a conventional boost converter operating at a very high conduction ratio can obtain high voltage gain, but in practice it is affected by parasitic components, and the voltage conversion ratio is limited to It is necessary to develop a new high boost converter topology when the voltage gain is as high as about 10 times practical requirements. Therefore, in recent years, high boost DC-DC converters are one of the common research topics in the field of power electronics engineering.
實務上操作在極大導通比的傳統升壓型轉換器其電壓增益是有所限制,而且轉換效率不佳。另一方面,操作在極大導通比的升壓型轉換器衍生了以下問題:容易產生很大的輸入電流漣波,使得太陽能電池模組輸出端的電解電容數量必須增加,減少燃料電池的使用壽命;另一方面,輸出二極體的反向恢復問題造成嚴重的反向恢復損失及EMI雜訊問題。In practice, conventional boost converters operating at extremely large turn-on ratios have limited voltage gain and poor conversion efficiency. On the other hand, the boost converter operating at a very large conduction ratio has the following problems: it is easy to generate a large input current ripple, so that the number of electrolytic capacitors at the output of the solar cell module must be increased, reducing the service life of the fuel cell; On the other hand, the reverse recovery problem of the output diode causes serious reverse recovery losses and EMI noise problems.
另,在轉換效率考量方面,由於環保意識高漲,節能減碳是各國的重要政策,轉換器的效率要求日益嚴苛,功率電子開關造成的功率損失必須善加考量。典型交錯式升壓型轉換器之功率開關與輸出二極體之電壓應力均為高壓的輸出電壓,由於高耐壓的MOSFET,一般都具有高導通電阻RDS(ON)的特性,導致較高的導通損失。In addition, in terms of conversion efficiency, due to the rising awareness of environmental protection, energy saving and carbon reduction are important policies of various countries, and the efficiency requirements of converters are becoming more and more stringent, and the power loss caused by power electronic switches must be carefully considered. The voltage stress of the power switch and the output diode of a typical interleaved boost converter is a high-voltage output voltage. Due to the high-voltage MOSFET, generally has the characteristics of high on-resistance RDS(ON), resulting in higher voltage. conduction loss.
緣是,發明人有鑑於此,秉持多年該相關行業之豐富設計開發及實際製作經驗,針對現有之結構及缺失再予以研究改良,提供一種交錯型高電壓轉換比直流轉換器,以期達到更佳實用價值性之目的者。The reason is that, in view of this, the inventor, adhering to years of rich experience in design, development and actual production in the related industry, researches and improves the existing structure and defects, and provides an interleaved high-voltage conversion ratio DC converter, in order to achieve a better The purpose of practical value.
本發明之主要目的在於提供一種交錯型高電壓轉換比直流轉換器,主要係可得到極高的升壓增益,且可使輸入電流漣波降低,降低電感的體積,同時不必操作在極大的導通比,具有低於輸出電壓的低電壓應力,可降低導通損失,提升整體效率,並可分擔輸入電流,能有效降低電路中儲能元件及開關元件之電流應力,適合應用於高功率的場合,而在其整體施行使用上更增實用功效特性者。The main purpose of the present invention is to provide an interleaved high voltage conversion ratio DC converter, which can obtain extremely high boost gain, reduce the input current ripple, and reduce the size of the inductor, and at the same time, it is not necessary to operate at a very large turn-on It has a low voltage stress lower than the output voltage, which can reduce the conduction loss, improve the overall efficiency, and can share the input current, which can effectively reduce the current stress of the energy storage elements and switching elements in the circuit, and is suitable for high-power applications. And in its overall implementation and use, it has more practical efficacy characteristics.
為令本發明所運用之技術內容、發明目的及其達成之功效有更完整且清楚的揭露,茲於下詳細說明之,並請一併參閱所揭之圖式及圖號:In order to make the technical content used in the present invention, the purpose of the invention and the effect achieved by the present invention more completely and clearly disclosed, it is explained in detail below, and please refer to the disclosed drawings and drawing numbers together:
首先,請參閱第一圖本發明之電路圖所示,本發明之轉換器(1)主要於輸入電壓之正極分別連接第一輸入濾波電感之第一端、輸入濾波電容之負極及第二輸入濾波電感之第一端,而該輸入電壓之負極則進行接地,該第一輸入濾波電感之第二端分別連接第10二極體之正極及第11二極體之正極,該輸入濾波電容之正極分別連接第一耦合電感一次側之第一端、第13二極體之負極、第二耦合電感一次側之第一端及該第11二極體之負極,該第一耦合電感一次側形成有第一磁化電感,該第二耦合電感一次側形成有第二磁化電感,該第二輸入濾波電感之第二端分別連接第12二極體之正極及該第13二極體之正極,該第10二極體之負極分別連接第二功率開關之第一端、該第二耦合電感一次側之第二端、第一箝位二極體之正極及第二輔助二極體之正極,於該第10二極體之負極與該第二耦合電感一次側之第二端之間形成有第二漏電感,該第二功率開關之第二端則予以接地,該第12二極體之負極分別連接第一功率開關之第一端、第二箝位二極體之正極、第一輔助二極體之正極及該第一耦合電感一次側之第二端,於該第12二極體之負極與該第一耦合電感一次側之第二端之間形成有第一漏電感,該第一功率開關之第二端則予以接地,該第一箝位二極體之負極分別連接第二切換二極體之正極、第三輔助二極體之負極、該第二箝位二極體之負極、箝位電容之第一端及第二切換電容之負極,該箝位電容之第二端予以接地,該第二輔助二極體之負極分別連接該第一輔助二極體之負極及輔助電感之第一端,該輔助電感之第二端分別連接該第三輔助二極體之正極及輔助開關之第一端,該輔助開關之第二端則予以接地,該第二切換二極體之負極分別連接第二耦合電感二次側之第一端及第一切換電容之負極,該第二耦合電感二次側之第二端連接第一耦合電感二次側之第一端,該第一耦合電感二次側之第二端分別連接該第二切換電容之正極及第一切換二極體之正極,該第一切換電容之正極及該第一切換二極體之負極一併連接至輸出二極體之正極,該輸出二極體之負極分別連接至輸出電容之第一端與輸出負載之第一端,而該輸出電容之第二端與該輸出負載之第二端則予以接地。First of all, please refer to the first circuit diagram of the present invention, the converter (1) of the present invention is mainly based on the input voltage The positive poles are respectively connected to the first input filter inductor The first end, the input filter capacitor The negative pole and the second input filter inductor the first terminal, and the input voltage The negative pole is grounded, the first input filter inductor The second ends are respectively connected to the 10th diode The positive electrode and the 11th diode positive, the input filter capacitor The positive poles are respectively connected to the primary side of the first coupled inductor The first end, the 13th diode the negative pole, the primary side of the second coupled inductor the first end and the 11th diode the negative pole, the primary side of the first coupled inductor A first magnetizing inductance is formed , the primary side of the second coupled inductor A second magnetizing inductance is formed , the second input filter inductor The second ends are respectively connected to the 12th diode the positive electrode and the 13th diode the positive electrode, the 10th diode The negative poles are respectively connected to the second power switch the first end, the primary side of the second coupled inductor the second end, the first clamping diode the positive electrode and the second auxiliary diode The positive electrode of the 10th diode the negative pole and the primary side of the second coupled inductor A second leakage inductance is formed between the second ends , the second power switch The second terminal is grounded, the 12th diode The negative poles are respectively connected to the first power switch the first end, the second clamping diode The positive electrode, the first auxiliary diode the positive pole and the primary side of the first coupled inductor the second end of the 12th diode the negative pole and the primary side of the first coupled inductor A first leakage inductance is formed between the second ends of the , the first power switch The second terminal is grounded, the first clamping diode The negative poles are respectively connected to the second switching diodes The positive electrode, the third auxiliary diode the negative electrode, the second clamping diode negative pole, clamp capacitor the first terminal and the second switched capacitor the negative pole of the clamp capacitor The second terminal of the second auxiliary diode is grounded, the second auxiliary diode The negative poles are respectively connected to the first auxiliary diode The negative pole and auxiliary inductance the first end of the auxiliary inductor the second ends are respectively connected to the third auxiliary diode positive and auxiliary switch the first end of the auxiliary switch The second terminal is grounded, the second switching diode The negative poles are respectively connected to the secondary side of the second coupling inductor the first terminal and the first switched capacitor the negative pole, the secondary side of the second coupled inductor The second end is connected to the secondary side of the first coupled inductor the first end, the second side of the first coupled inductor The second ends are respectively connected to the second switching capacitor the positive electrode and the first switching diode the positive pole of the first switched capacitor the positive electrode and the first switching diode The negative poles are also connected to the output diode the positive pole of the output diode The negative poles are respectively connected to the output capacitors the first terminal and the output load the first terminal, and the output capacitor the second terminal and the output load The second end is grounded.
而該轉換器(1)在使用過程中,根據各開關切換和各二極體導通與否,可以將該轉換器(1)在一個切換週期的動作,分成十六個線性階段,請再參閱第二圖本發明之時序圖所示,以下將本發明分為十六個工作模式進行分析討論:In the process of using the converter (1), according to the switching of each switch and the conduction of each diode, the converter (1) can be switched in one switching cycle. The action is divided into sixteen linear stages. Please refer to the timing diagram of the present invention in Figure 2. The present invention is divided into sixteen working modes for analysis and discussion below:
第一階段[]:[第一功率開關、第二功率開關:ON,輔助開關:OFF,第11二極體、第13二極體、第一箝位二極體、第二箝位二極體、第一切換二極體、第二切換二極體、第一輔助二極體、第二輔助二極體、第三輔助二極體、輸出二極體:OFF,第10二極體、第12二極體:ON]:請再一併參閱第三圖本發明之第一階段等效線性電路圖所示,第一階段開始於,第一功率開關與第二功率開關皆為ON。兩個耦合電感的初級側跨壓均為輸入電壓,即第一磁化電感、第一漏電感、第二磁化電感、第二漏電感的跨壓為,其電流呈線性上升,斜率同為。當,第二功率開關切換為OFF時,本階段結束。The first stage[ ]: [First power switch , the second power switch : ON, auxiliary switch : OFF, 11th diode , the 13th diode , the first clamp diode , the second clamp diode , the first switching diode , the second switching diode , the first auxiliary diode , the second auxiliary diode , the third auxiliary diode , output diode : OFF, 10th diode , the 12th diode :ON]: Please refer to the third figure again, as shown in the first-stage equivalent linear circuit diagram of the present invention, the first stage starts at , the first power switch with second power switch All are ON. The primary side voltage across the two coupled inductors is the input voltage , the first magnetizing inductance , the first leakage inductance , the second magnetizing inductance , the second leakage inductance The cross pressure is , the current increases linearly, and the slope is the same as . when , the second power switch When switched to OFF, this phase ends.
第二階段[]:[第一功率開關:ON、第二功率開關:ONOFF,輔助開關:OFF,第10二極體、第13二極體、第一箝位二極體、第二箝位二極體、第一切換二極體、第二切換二極體、第一輔助二極體、第二輔助二極體、第三輔助二極體、輸出二極體:OFF,第11二極體、第12二極體:ON]:請再一併參閱第四圖本發明之第二階段等效線性電路圖所示,第二階段開始於,第二功率開關切換成OFF。第二漏電感電流對第二功率開關的輸出[寄生]電容充電,第二功率開關的跨壓由零電壓開始上升,耦合電感二次側總電壓也隨之上升。因為第二功率開關的輸出電容很小,所以本階段時間很短,第二漏電感電流視為常數。當,第二功率開關的跨壓等於箝位電容的電壓時,即時,第二箝位二極體及第一切換二極體和第二切換二極體轉態成ON,本階段結束。second stage[ ]: [First power switch : ON, second power switch : ON OFF, auxiliary switch : OFF, 10th diode , the 13th diode , the first clamp diode , the second clamp diode , the first switching diode , the second switching diode , the first auxiliary diode , the second auxiliary diode , the third auxiliary diode , output diode : OFF, 11th diode , the 12th diode : ON]: Please also refer to the second-stage equivalent linear circuit diagram of the present invention in Figure 4. The second stage starts at , the second power switch Switch to OFF. second leakage inductance current to the second power switch The output [parasitic] capacitance of charging, second power switch cross pressure Rising from zero voltage, the total voltage on the secondary side of the coupled inductor also rose. Because the second power switch The output capacitance of is very small, so the time of this stage is very short, the second leakage inductance current regarded as a constant. when , the second power switch cross pressure equal to the clamp capacitance voltage when, that is , the second clamp diode and the first switching diode and the second switching diode Transition to ON, the end of this stage.
第三階段[]:[第一功率開關:ON、第二功率開關、輔助開關:OFF,第二箝位二極體、第一切換二極體、第二切換二極體:OFFON,第10二極體、第13二極體、第一箝位二極體、第一輔助二極體、第二輔助二極體、第三輔助二極體、輸出二極體:OFF,第11二極體、第12二極體:ON]:請再一併參閱第五圖本發明之第三階段等效線性電路圖所示,第三階段開始於 , 第二箝位二極體、第一切換二極體、第二切換二極體轉態為ON。第二耦合電感一次側跨壓,第二漏電感電流下降,第二漏電感電流經由第二箝位二極體對箝位電容充電。儲存在第二磁化電感的能量藉由耦合電感傳送至二次側,經由第一切換二極體和第二切換二極體對第一切換電容和第二切換電容充電。另一方面,因為耦合電感二次側電流感應至第一組耦合電感的理想變壓器一次側,使得第一組耦合電感的漏電感電流可表示為。當 , 第二漏電感電流下降至零時,第二箝位二極體以零電流切換[ZCS]自然轉態成OFF,本階段結束。因為第二箝位二極體以ZCS轉態成OFF,因此沒有反向恢復損失。The third phase[ ]: [First power switch : ON, second power switch , auxiliary switch : OFF, second clamp diode , the first switching diode , the second switching diode : OFF ON, 10th diode , the 13th diode , the first clamp diode , the first auxiliary diode , the second auxiliary diode , the third auxiliary diode , output diode : OFF, 11th diode , the 12th diode :ON]: Please also refer to the third-stage equivalent linear circuit diagram of the present invention in Figure 5. The third stage starts at , the second clamp diode , the first switching diode , the second switching diode Transition to ON. The primary side of the second coupled inductor cross pressure , the second leakage inductance current falling, the second leakage inductance current via the second clamp diode pair clamp capacitor Charge. stored in the second magnetizing inductance The energy is transferred to the secondary side through the coupled inductor, through the first switching diode and the second switching diode on the first switched capacitor and the second switched capacitor Charge. On the other hand, since the secondary side current of the coupled inductor is induced to the ideal transformer primary side of the first set of coupled inductors, the leakage inductance current of the first set of coupled inductors can be expressed as . when , the second leakage inductance current drops to zero, the second clamp diode With zero current switching [ZCS], the state is naturally turned to OFF, and this stage ends. because the second clamp diode Transitions to OFF with ZCS, so there is no reverse recovery penalty.
第四階段[]:[第一功率開關:ON、第二功率開關、輔助開關:OFF,第二箝位二極體:ONOFF,第一切換二極體、第二切換二極體:ON,第10二極體、第13二極體、第一箝位二極體、第一輔助二極體、第二輔助二極體、第三輔助二極體、輸出二極體:OFF,第11二極體、第12二極體:ON]:請再一併參閱第六圖本發明之第四階段等效線性電路圖所示,第四階段開始於,第二箝位二極體轉態成OFF。第二磁化電感的電流完全由耦合電感一次側感應到二次側,經由第一切換二極體和第二切換二極體持續對第一切換電容和第二切換電容充電。在本階段第二磁化電感電流和流經第一功率開關的電流分別為、。當,輔助開關切換成ON時,本階段結束。the fourth stage ]: [First power switch : ON, second power switch , auxiliary switch : OFF, second clamp diode : ON OFF, first switching diode , the second switching diode : ON, 10th diode , the 13th diode , the first clamp diode , the first auxiliary diode , the second auxiliary diode , the third auxiliary diode , output diode : OFF, 11th diode , the 12th diode : ON]: Please refer to the fourth stage equivalent linear circuit diagram of the present invention in Figure 6. The fourth stage starts at , the second clamp diode Transition to OFF. second magnetizing inductance the current Fully sensed from the primary side of the coupled inductor to the secondary side via the first switching diode and the second switching diode continuously on the first switched capacitor and the second switched capacitor Charge. The second magnetizing inductor current at this stage and flows through the first power switch The currents are , . when , auxiliary switch When switched ON, this phase ends.
第五階段[]:[第一功率開關:ON,第二功率開關:OFF,輔助開關:OFFON,第二輔助二極體:OFFON,第一切換二極體、第二切換二極體:ON,第10二極體、第13二極體、第一箝位二極體、第二箝位二極體、第一輔助二極體、第三輔助二極體、輸出二極體:OFF,第11二極體、第12二極體:ON]:請再一併參閱第七圖本發明之第五階段等效線性電路圖所示,第五階段開始於,輔助開關切換為ON,第二輔助二極體轉態為ON。因為輔助電感的存在,輔助電感電流由零開始上升,所以輔助開關和第二輔助二極體能夠以ZCS切換為ON。第二漏電感電流從0開始上升,因此第二磁化電感電流流入為理想變壓器之第二耦合電感一次側的電流減小,導致耦合電感二次側的電流開始下降,使得第一切換二極體之電流和第二切換二極體之電流下降。當 , 第二漏電感電流上升至滿足,此時第一切換二極體電流和第二切換二極體電流會下降到0,第一切換二極體和第二切換二極體以ZCS自然轉態成OFF,本階段結束。The fifth stage [ ]: [First power switch : ON, the second power switch : OFF, auxiliary switch : OFF ON, second auxiliary diode : OFF ON, the first switching diode , the second switching diode : ON, 10th diode , the 13th diode , the first clamp diode , the second clamp diode , the first auxiliary diode , the third auxiliary diode , output diode : OFF, 11th diode , the 12th diode :ON]: Please refer to Figure 7, which is the equivalent linear circuit diagram of the fifth stage of the present invention. The fifth stage starts at , auxiliary switch switched ON, the second auxiliary diode Transition to ON. Because of the auxiliary inductance The presence of auxiliary inductor current rising from zero, so the auxiliary switch and the second auxiliary diode Can be switched ON with ZCS. second leakage inductance current Rising from 0, so the second magnetizing inductor current The inflow is the primary side of the second coupled inductor of an ideal transformer The current decreases, causing the current on the secondary side of the coupled inductor to begin to drop, making the first switching diode the current and the second switching diode the current decline. when , the second leakage inductance current rise to contentment , at this time the first switching diode current and the second switching diode current will drop to 0, the first switching diode and the second switching diode When ZCS naturally transitions to OFF, this stage ends.
第六階段[]:[第一功率開關、輔助開關:ON,第二功率開關:OFF,第一切換二極體、第二切換二極體:ONOFF,第二輔助二極體:ON,第10二極體、第13二極體、第一箝位二極體、第二箝位二極體、第一輔助二極體、第三輔助二極體、輸出二極體:OFF,第11二極體、第12二極體:ON]:請再一併參閱第八圖本發明之第六階段等效線性電路圖所示,第六階段開始於,第一切換二極體和第二切換二極體轉態為OFF。輔助電感和第二功率開關的輸出電容形成共振電路,因為輔助電感和第二功率開關的輸出電容都很小,共振頻率很大,所以輔助電感電流以共振形式快速上升,第二功率開關的跨壓以共振形式快速下降。第二功率開關的輸出電容所儲存的能量轉移至輔助電感儲存。當第二功率開關的跨壓下降至零,第二功率開關的內部本體二極體[body diode]導通,第二功率開關的跨壓箝制在零,第二功率開關之ZVS切換的條件成立。當,第二功率開關以ZVS切換為ON,本階段結束。The sixth stage [ ]: [First power switch , auxiliary switch : ON, the second power switch : OFF, first switching diode , the second switching diode : ON OFF, second auxiliary diode : ON, 10th diode , the 13th diode , the first clamp diode , the second clamp diode , the first auxiliary diode , the third auxiliary diode , output diode : OFF, 11th diode , the 12th diode : ON]: Please refer to Figure 8, which is the equivalent linear circuit diagram of the sixth stage of the present invention. The sixth stage starts at , the first switching diode and the second switching diode Transition to OFF. Auxiliary inductance and the second power switch The output capacitance of form a resonant circuit because the auxiliary inductance and the second power switch The output capacitance of are very small, the resonance frequency is large, so the auxiliary inductor current Rapid rise in resonance form, second power switch cross pressure Rapid decline in resonance form. second power switch The output capacitance of The stored energy is transferred to the auxiliary inductor store. When the second power switch cross pressure down to zero, the second power switch The internal body diode of , conducts, the second power switch cross pressure clamped at zero, the second power switch The conditions for ZVS switching are satisfied. when , the second power switch When ZVS is switched to ON, this stage ends.
第七階段[]:[第一功率開關、輔助開關:ON,第二功率開關:OFFON,第二輔助二極體:ON,第11二極體、第13二極體、第一箝位二極體、第二箝位二極體、第一切換二極體、第二切換二極體、第一輔助二極體、第三輔助二極體、輸出二極體:OFF,第10二極體、第12二極體:ON]:請再一併參閱第九圖本發明之第七階段等效線性電路圖所示,第七階段開始於,第二功率開關以ZVS切換為ON。本階段輔助電感之電壓,輔助電感電流保持常數。耦合電感一次側受到輸入電壓充磁。當,輔助開關切換為OFF時,本階段結束。the seventh stage ]: [First power switch , auxiliary switch : ON, the second power switch : OFF ON, second auxiliary diode : ON, 11th diode , the 13th diode , the first clamp diode , the second clamp diode , the first switching diode , the second switching diode , the first auxiliary diode , the third auxiliary diode , output diode : OFF, 10th diode , the 12th diode : ON]: Please refer to Figure 9, which is the equivalent linear circuit diagram of the seventh stage of the present invention. The seventh stage starts at , the second power switch Toggle ON with ZVS. Auxiliary inductor at this stage voltage , the auxiliary inductor current keep it constant. The primary side of the coupled inductor is subjected to the input voltage Magnetizing. when , auxiliary switch When switched to OFF, this phase ends.
第八階段[]:[第一功率開關、第二功率開關:ON,輔助開關:ONOFF,第11二極體、第13二極體、第一箝位二極體、第二箝位二極體、第一切換二極體、第二切換二極體、第一輔助二極體、輸出二極體:OFF,第二輔助二極體、第三輔助二極體:ON,第10二極體、第12二極體:ON]:請再一併參閱第十圖本發明之第八階段等效線性電路圖所示,第八階段開始於,輔助開關切換為OFF,因為輔助電感電流的連續性,使得第三輔助二極體轉態為ON,輔助電感電壓,輔助電感電流線性下降,輔助電感儲存的能量傳送至箝位電容,而輸入電壓繼續對兩個耦合電感一次側充磁。當,輔助電感電流下降至零,第二輔助二極體、第三輔助二極體以ZCS自然轉態成OFF,本階段結束。接著,進入後半切換週期的8個階段。eighth stage ]: [First power switch , the second power switch : ON, auxiliary switch : ON OFF, 11th diode , the 13th diode , the first clamp diode , the second clamp diode , the first switching diode , the second switching diode , the first auxiliary diode , output diode : OFF, second auxiliary diode , the third auxiliary diode : ON, 10th diode , the 12th diode : ON]: Please also refer to Figure 10, as shown in the equivalent linear circuit diagram of the eighth stage of the present invention, the eighth stage starts at , auxiliary switch switched OFF because the auxiliary inductor current continuity, such that the third auxiliary diode transition to ON, auxiliary inductor voltage , the auxiliary inductor current Linear drop, auxiliary inductance The stored energy is delivered to the clamping capacitor , while the input voltage Continue to magnetize the primary side of both coupled inductors. when , the auxiliary inductor current down to zero, the second auxiliary diode , the third auxiliary diode When ZCS naturally transitions to OFF, this stage ends. Next, the eight stages of the second half switching cycle are entered.
第九階段[]:[第一功率開關、第二功率開關:ON,輔助開關:OFF,第11二極體、第13二極體、第一箝位二極體、第二箝位二極體、第一切換二極體、第二切換二極體、第一輔助二極體、輸出二極體:OFF,第二輔助二極體、第三輔助二極體:ONOFF,第10二極體、第12二極體:ON]:請再一併參閱第十一圖本發明之第九階段等效線性電路圖所示,第九階段開始於,第一功率開關與第二功率開關皆為ON。兩個耦合電感的初級側跨壓均為輸入電壓,即第一磁化電感、第一漏電感、第二磁化電感、第二漏電感的跨壓為,第一漏電感電流和第二漏電感電流都呈線性上升,斜率同為。當,第一功率開關切換為OFF時,本階段結束。The ninth stage [ ]: [First power switch , the second power switch : ON, auxiliary switch : OFF, 11th diode , the 13th diode , the first clamp diode , the second clamp diode , the first switching diode , the second switching diode , the first auxiliary diode , output diode : OFF, second auxiliary diode , the third auxiliary diode : ON OFF, 10th diode , the 12th diode : ON]: Please refer to Figure 11, which is the equivalent linear circuit diagram of the ninth stage of the present invention. The ninth stage starts at , the first power switch with second power switch All are ON. The primary side voltage across the two coupled inductors is the input voltage , the first magnetizing inductance , the first leakage inductance , the second magnetizing inductance , the second leakage inductance The cross pressure is , the first leakage inductance current and the second leakage inductance current both rise linearly, with the same slope as . when , the first power switch When switched to OFF, this phase ends.
第十階段[]:[第一功率開關:ONOFF,第二功率開關:ON,輔助開關:OFF,第11二極體、第12二極體、第一箝位二極體、第二箝位二極體、第一切換二極體、第二切換二極體、第一輔助二極體、第二輔助二極體、第三輔助二極體、輸出二極體:OFF,第10二極體、第13二極體:ON]:請再一併參閱第十二圖本發明之第十階段等效線性電路圖所示,第十階段開始於,第一功率開關切換成OFF。第一漏電感電流對第一功率開關的輸出[寄生]電容充電,第一功率開關的跨壓由零電壓開始上升,耦合電感二次側總電壓也上升。輸出二極體電壓也隨之上升。因為第一功率開關的輸出電容很小,所以本階段時間很短,當,第一功率開關的跨壓上升至箝位電容電壓時,即時,第一箝位二極體及輸出二極體轉態成ON,本階段結束。tenth stage ]: [First power switch : ON OFF, the second power switch : ON, auxiliary switch : OFF, 11th diode , the 12th diode , the first clamp diode , the second clamp diode , the first switching diode , the second switching diode , the first auxiliary diode , the second auxiliary diode , the third auxiliary diode , output diode : OFF, 10th diode , the 13th diode : ON]: Please also refer to Figure 12, which is the equivalent linear circuit diagram of the tenth stage of the present invention. The tenth stage starts at , the first power switch Switch to OFF. first leakage inductance current to the first power switch The output [parasitic] capacitance of charging, first power switch cross pressure Rising from zero voltage, the total voltage on the secondary side of the coupled inductor also rise. output diode Voltage also rose. Because the first power switch The output capacitance of is very small, so this stage is very short, when , the first power switch cross pressure rise to the clamping capacitor voltage when, that is , the first clamp diode and output diode Transition to ON, the end of this stage.
第十一階段[]:[第一功率開關、輔助開關:OFF,第二功率開關:ON,第一箝位二極體、輸出二極體:OFFON,第11二極體、第12二極體、第二箝位二極體、第一切換二極體、第二切換二極體、第一輔助二極體、第二輔助二極體、第三輔助二極體:OFF,第10二極體、第13二極體:ON]:請再一併參閱第十三圖本發明之第十一階段等效線性電路圖所示,第十一階段開始於,第一功率開關為OFF,且第一箝位二極體和輸出二極體為ON。部分的第一漏電感電流對箝位電容充電,第一漏電感電流下降,第一磁化電感的電流流入第一組耦合電感之理想變壓器的電流上升,第一磁化電感所儲存的能量經由耦合電感及輸出二極體傳遞至輸出負載,輸出二極體之電流上升,其電流增加速率受第一漏電感限制。在本階段中,當時,箝位電容開始對輸出側放電,耦合電感的二次側及第一切換電容和第二切換電容可視為電壓源,以提升輸出電壓增益。當 , 第一漏電感電流下降至零,第一箝位二極體以零電流切換[ZCS]自然轉態為OFF,本階段結束。the eleventh stage ]: [First power switch , auxiliary switch : OFF, the second power switch : ON, first clamp diode , output diode : OFF ON, 11th diode , the 12th diode , the second clamp diode , the first switching diode , the second switching diode , the first auxiliary diode , the second auxiliary diode , the third auxiliary diode : OFF, 10th diode , the 13th diode : ON]: Please also refer to Figure 13, which is the equivalent linear circuit diagram of the eleventh stage of the present invention. The eleventh stage starts at , the first power switch is OFF, and the first clamp diode and output diode is ON. part of the first leakage inductance current pair clamp capacitor charging, the first leakage inductor current falling, the first magnetizing inductance the current The current flowing into the ideal transformer of the first set of coupled inductances rises, the first magnetizing inductance The stored energy passes through the coupled inductor and output diode pass to the output load , the output diode the current rise, the rate of current increase is limited by the first leakage inductance limit. In this stage, when , the clamping capacitor Begin to discharge the output side, coupling the secondary side of the inductor and the first switched capacitor and the second switched capacitor Can be regarded as a voltage source to increase the output voltage gain. when , the first leakage inductance current down to zero, the first clamp diode With zero current switching [ZCS], the natural transition state is OFF, and this stage ends.
第十二階段[]:[第一功率開關、輔助開關:OFF,第二功率開關:ON,第一箝位二極體:ONOFF,輸出二極體:ON,第11二極體、第12二極體、第二箝位二極體、第一切換二極體、第二切換二極體、第一輔助二極體、第二輔助二極體、第三輔助二極體:OFF,第10二極體、第13二極體:ON]:請再一併參閱第十四圖本發明之第十二階段等效線性電路圖所示,第十二階段開始於,第一箝位二極體轉態成OFF。磁化電感儲存的能量完全藉由耦合電感傳遞至二次側,經由輸出二極體對輸出電容及輸出負載放電。當,輔助開關切換成ON時,本階段結束。the twelfth stage ]: [First power switch , auxiliary switch : OFF, the second power switch : ON, first clamp diode : ON OFF, output diode : ON, 11th diode , the 12th diode , the second clamp diode , the first switching diode , the second switching diode , the first auxiliary diode , the second auxiliary diode , the third auxiliary diode : OFF, 10th diode , the 13th diode : ON]: Please also refer to Figure 14, which is the equivalent linear circuit diagram of the twelfth stage of the present invention. The twelfth stage starts at , the first clamp diode Transition to OFF. The energy stored in the magnetizing inductance is completely transferred to the secondary side through the coupled inductance, through the output diode to the output capacitor and output load discharge. when , auxiliary switch When switched ON, this phase ends.
第十三階段[]:[第一功率開關:OFF,第二功率開關:ON,輔助開關:OFFON,第一輔助二極體:OFFON,第11二極體、第12二極體、第一箝位二極體、第二箝位二極體、第一切換二極體、第二切換二極體、第二輔助二極體、第三輔助二極體:OFF,輸出二極體:ON,第10二極體、第13二極體:ON]:請再一併參閱第十五圖本發明之第十三階段等效線性電路圖所示,第十三階段開始於,輔助開關切換為ON,第一輔助二極體轉態為ON,因為輔助電感電流的初始值為零,所以輔助開關和第一輔助二極體能夠以ZCS切換為ON。第一漏電感電流從零開始上升,輸出二極體之電流開始下降。當 , 輸出二極體電流下降至零,第一磁化電感所儲存的能量藉由耦合電感傳遞至輸出負載的動作結束,此時,輸出二極體以ZCS自然轉態成OFF,本階段結束。Thirteenth stage [ ]: [First power switch : OFF, the second power switch : ON, auxiliary switch : OFF ON, the first auxiliary diode : OFF ON, 11th diode , the 12th diode , the first clamp diode , the second clamp diode , the first switching diode , the second switching diode , the second auxiliary diode , the third auxiliary diode : OFF, output diode : ON, 10th diode , the 13th diode : ON]: Please also refer to Figure 15, which is the equivalent linear circuit diagram of the thirteenth stage of the present invention. The thirteenth stage starts at , auxiliary switch switched ON, the first auxiliary diode transition to ON because the auxiliary inductor current The initial value of is zero, so the auxiliary switch and the first auxiliary diode Can be switched ON with ZCS. first leakage inductance current Rising from zero, output diode the current begin to drop. when , the output diode current drops to zero, the first magnetizing inductance The stored energy is transferred to the output load through the coupled inductor action ends, at this time , the output diode When ZCS naturally transitions to OFF, this stage ends.
第十四階段[]:[第一功率開關:OFF,第二功率開關、輔助開關:ON,輸出二極體:ONOFF,第11二極體、第12二極體、第一箝位二極體、第二箝位二極體、第一切換二極體、第二切換二極體、第二輔助二極體、第三輔助二極體:OFF,第10二極體、第13二極體、第一輔助二極體:ON]:請再一併參閱第十六圖本發明之第十四階段等效線性電路圖所示,第十四階段開始於,輸出二極體轉態為OFF。輔助電感和第一功率開關的輸出電容形成共振電路,因為輔助電感和第一功率開關的輸出電容都很小,共振頻率很大,所以輔助電感電流以共振形式快速上升,第一功率開關的跨壓以共振形式快速下降。第一功率開關的輸出電容所儲存的能量轉移至輔助電感儲存。當第一功率開關的跨壓下降至零,第一功率開關的內部本體二極體[body diode]導通,第一功率開關的跨壓箝制在零,第一功率開關之ZVS切換的條件成立。當,第一功率開關以ZVS切換為ON,本階段結束。fourteenth stage ]: [First power switch : OFF, the second power switch , auxiliary switch : ON, output diode : ON OFF, 11th diode , the 12th diode , the first clamp diode , the second clamp diode , the first switching diode , the second switching diode , the second auxiliary diode , the third auxiliary diode : OFF, 10th diode , the 13th diode , the first auxiliary diode :ON]: Please also refer to Figure 16, as shown in the equivalent linear circuit diagram of the fourteenth stage of the present invention, the fourteenth stage starts at , the output diode Transition to OFF. Auxiliary inductance and the first power switch The output capacitance of form a resonant circuit because the auxiliary inductance and the first power switch The output capacitance of are very small, the resonance frequency is large, so the auxiliary inductor current Rapid rise in resonance form, first power switch cross pressure Rapid decline in resonance form. first power switch The output capacitance of The stored energy is transferred to the auxiliary inductor store. When the first power switch cross pressure down to zero, the first power switch The internal body diode of , turns on, the first power switch cross pressure clamped at zero, the first power switch The conditions for ZVS switching are satisfied. when , the first power switch When ZVS is switched to ON, this stage ends.
第十五階段[]:[第二功率開關、輔助開關:ON,第一功率開關:OFFON,第11二極體、第13二極體、第一箝位二極體、第二箝位二極體、第一切換二極體、第二切換二極體、第二輔助二極體、第三輔助二極體、輸出二極體:OFF,第10二極體、第12二極體、第一輔助二極體:ON]:請再一併參閱第十七圖本發明之第十五階段等效線性電路圖所示,第十五階段開始於,第一功率開關以ZVS切換為ON。本階段輔助電感之電壓,輔助電感電流保持常數。耦合電感一次側受到輸入電壓充磁。當,輔助開關切換為OFF時,本階段結束。the fifteenth stage ]: [Second power switch , auxiliary switch : ON, the first power switch : OFF ON, 11th diode , the 13th diode , the first clamp diode , the second clamp diode , the first switching diode , the second switching diode , the second auxiliary diode , the third auxiliary diode , output diode : OFF, 10th diode , the 12th diode , the first auxiliary diode : ON]: Please also refer to Figure 17, as shown in the equivalent linear circuit diagram of the fifteenth stage of the present invention, the fifteenth stage starts at , the first power switch Toggle ON with ZVS. Auxiliary inductor at this stage voltage , the auxiliary inductor current keep it constant. The primary side of the coupled inductor is subjected to the input voltage Magnetizing. when , auxiliary switch When switched to OFF, this phase ends.
第十六階段[]:[第一功率開關、第二功率開關:ON,輔助開關:ONOFF,第11二極體、第13二極體、第一箝位二極體、第二箝位二極體、第一切換二極體、第二切換二極體、第二輔助二極體、輸出二極體:OFF,第10二極體、第12二極體、第一輔助二極體、第三輔助二極體:ON]:請再一併參閱第十八圖本發明之第十六階段等效線性電路圖所示,第十六階段開始於,輔助開關切換為OFF,因為輔助電感電流的連續性,使得第三輔助二極體轉態為ON,輔助電感電壓,輔助電感電流線性下降,輔助電感儲存的能量傳送至箝位電容,而輸入電壓繼續對兩個耦合電感一次側充磁。當,輔助電感電流下降至零,第一輔助二極體、第三輔助二極體以ZCS自然轉態成OFF,本階段結束。The sixteenth stage [ ]: [First power switch , the second power switch : ON, auxiliary switch : ON OFF, 11th diode , the 13th diode , the first clamp diode , the second clamp diode , the first switching diode , the second switching diode , the second auxiliary diode , output diode : OFF, 10th diode , the 12th diode , the first auxiliary diode , the third auxiliary diode : ON]: Please also refer to Figure 18, as shown in the equivalent linear circuit diagram of the sixteenth stage of the present invention, the sixteenth stage starts at , auxiliary switch switched OFF because the auxiliary inductor current continuity, such that the third auxiliary diode transition to ON, auxiliary inductor voltage , the auxiliary inductor current Linear drop, auxiliary inductance The stored energy is delivered to the clamping capacitor , while the input voltage Continue to magnetize the primary side of both coupled inductors. when , the auxiliary inductor current down to zero, the first auxiliary diode , the third auxiliary diode When ZCS naturally transitions to OFF, this stage ends.
依據上述電路動作分析結果,使用IsSpice模擬軟體驗證其電路理論分析、電氣規格以及上述所及之優點[請再一併參閱第十九圖本發明之模擬電路示意圖所示]。設定該轉換器(1)之相關參數如下表1所示:
以下將介紹輸出功率之下相關模擬結果,模擬波形將驗正項目如下:The following will describe the output power The relevant simulation results below, the simulation waveform will be verified as follows:
A.電氣規格驗證:輸入電壓、輸出電壓、導通比 A. Electrical Specification Verification: Input Voltage ,The output voltage , conduction ratio
請再一併參閱第二十圖本發明之開關驅動信號、與輸入電壓及輸出電壓的模擬波形圖所示,由該第二十圖可知,輸入電壓、輸出電壓,滿足電氣之需求規格。Please also refer to the switch driving signal of the present invention in FIG. 20 , with input voltage and output voltage As shown in the analog waveform diagram of the twentieth diagram, the input voltage ,The output voltage , to meet the requirements of electrical specifications.
B.輸入電流漣波相消:、、、、、、 B. Input current ripple cancellation: , , , , , ,
因為該轉換器(1)以交錯180度依序導通的驅動方式操作,因此,輸入濾波電感電流和漣波相差180度,又,因此、及、之漣波可以相消以降低輸入電流之漣波。請再一併參閱第二十一圖本發明之輸入端電流、的模擬波形圖、第二十二圖本發明之輸入端電流、的模擬波形圖、第二十三圖本發明之輸入端電流、、的模擬波形圖所示,可以觀察出,當輸入濾波電感電流漣波和約為2.5A,輸入電流漣波約為1.2A。Because the converter (1) operates in a staggered 180-degree turn-on drive mode, the input filter inductor current and The ripples differ by 180 degrees, and ,therefore , and , The ripple can be cancelled to reduce the input current the ripples. Please also refer to the input current of the present invention in Figure 21 , The analog waveform diagram of , and the input terminal current of the present invention in Fig. 22 , The analog waveform diagram of , and the input terminal current of the present invention in Figure 23 , , As shown in the simulated waveforms, it can be observed that when the input filter inductor current ripples and About 2.5A, input current ripple About 1.2A.
C.第一功率開關、第二功率開關的低電壓應力:及 C. The first power switch , the second power switch The low voltage stress of: and
因為該轉換器(1)加入升壓電容,因此開關跨壓將會被升壓電容給限制住:、,請再一併參閱第二十四圖本發明之第一功率開關驅動信號 、及其跨壓、的模擬波形圖及第二十五圖本發明之第二功率開關驅動信號 、及其跨壓、的模擬波形圖所示,開關的跨壓也約為100V,可知開關確實擁有遠低於輸出電壓的低電壓應力。Because the converter (1) adds a boost capacitor, the switch voltage across the switch will be limited by the boost capacitor: , , please also refer to the first power switch of the present invention in Figure 24 drive signal , and its cross pressure , The analog waveform diagram and the twenty-fifth diagram of the second power switch of the present invention drive signal , and its cross pressure , As shown in the analog waveform of , the cross voltage of the switch is also about 100V, which shows that the switch does have a low voltage stress much lower than the output voltage.
而本發明之轉換器(1)與文獻中之高升壓比轉換器,在電壓轉換比進行比較,請參閱下表2所示,本發明之轉換器(1)具有極高的電壓轉換比:
請再一併參閱第二十六圖本發明於匝數比時與文獻[1]之電壓轉換比比較曲線圖及第二十七圖本發明於匝數比時與文獻[1]之電壓轉換比比較曲線圖所示,由於文獻[1]、文獻[2]、文獻[3]之電壓增益皆相同,取文獻[1]為代表與本發明之轉換器(1)進行比較可知,本發明之轉換器(1)具有最高之電壓增益,且當耦合電感匝數比越大時,則差距會更加明顯。Please also refer to Figure 26 in the present invention for the turns ratio When compared with the voltage conversion ratio of the literature [1], and the twenty-seventh graph of the present invention, the turns ratio When compared with the voltage conversion ratio of document [1], as shown in the graph, since the voltage gain of document [1], document [2], and document [3] are all the same, document [1] is taken as the representative converter of the present invention. (1) It can be seen from the comparison that the converter (1) of the present invention has the highest voltage gain, and when the coupled inductor turns ratio is The larger the difference, the more obvious the difference will be.
參考文獻:references:
[1]R. N. A. L. S. Aquino, F. L. Tofoli, P. P. Praca, D. S. O. Jr, and L. H. S. C. Barreto, “Soft switching high voltage gain dc-dc interleaved boost converter,” IET Power Electronics, vol. 8, iss. 1, pp. 120-129, 2015[1] RNALS Aquino, FL Tofoli, PP Praca, DSO Jr, and LHSC Barreto, “Soft switching high voltage gain dc-dc interleaved boost converter,” IET Power Electronics, vol. 8, iss. 1, pp. 120-129 , 2015
[2]M. Muhammad, M. Armstrong, and M. Elgendy, “A nonisolated interleaved boost converter for high-voltage gain applications,” IEEE Trans. Power Electronics, vol. 31, no. 2, pp. 352-362, 2016[2] M. Muhammad, M. Armstrong, and M. Elgendy, “A nonisolated interleaved boost converter for high-voltage gain applications,” IEEE Trans. Power Electronics, vol. 31, no. 2, pp. 352-362, 2016
[3]M. Forouzesh, Y. Shen, K. Yari, Y. P. Siwakoti, F. Blaabjerg, “High-efficiency high step-up DC-DC converter with dual coupled inductors for grid-connected photovoltaic systems,” IEEE Trans. Power Electronics, vol. 33, no. 7, pp. 5967-5982, 2018.[3] M. Forouzesh, Y. Shen, K. Yari, YP Siwakoti, F. Blaabjerg, “High-efficiency high step-up DC-DC converter with dual coupled inductors for grid-connected photovoltaic systems,” IEEE Trans. Power Electronics, vol. 33, no. 7, pp. 5967-5982, 2018.
藉由以上所述,本發明之使用實施說明可知,本發明與現有技術手段相較之下,本發明主要係具有下列優點:From the above, the use and implementation description of the present invention shows that compared with the prior art means, the present invention mainly has the following advantages:
1.高升壓增益:本發明提出交錯型高電壓轉換比直流轉換器,可得到極高的升壓增益。1. High boost gain: The present invention proposes an interleaved high voltage conversion ratio DC converter, which can obtain extremely high boost gain.
2.高電力密度:第一功率開關及第二功率開關係以180°的相位差交錯工作,可使輸入電流漣波降低,因此,可以使用電感值較小之輸入濾波電感,降低電感的體積。2. High power density: the first power switch and second power switch It works staggered with a phase difference of 180°, which can reduce the input current ripple. Therefore, an input filter inductor with a smaller inductance value can be used to reduce the size of the inductor.
3.低電壓應力:高電壓增益的達成,不必操作在極大的導通比,則功率開關具有低於輸出電壓的低電壓應力,故可使用導通電阻較小的低額定耐壓MOSFET,所以可降低導通損失,提升整體效率。3. Low voltage stress: To achieve high voltage gain, it is not necessary to operate at a very large conduction ratio, and the power switch has a low voltage stress lower than the output voltage, so a low-rated withstand voltage MOSFET with a small on-resistance can be used, so it can be reduced. Conduction loss, improve overall efficiency.
4.高功率應用:提出交錯型高電壓轉換比直流轉換器,由於電路架構仍具有並聯連接特性,故可分擔輸入電流,能有效降低電路中儲能元件及開關元件之電流應力,適合應用於高功率的場合。4. High-power application: The interleaved high-voltage conversion ratio DC converter is proposed. Since the circuit structure still has the characteristics of parallel connection, it can share the input current, which can effectively reduce the current stress of the energy storage elements and switching elements in the circuit. It is suitable for application in High power occasions.
5.高轉換效率:本發明具有電流分流且可選用低導通電阻MOSFET,使電路導通損失有效降低,提升轉換器之整體效率。5. High conversion efficiency: The present invention has current shunt and can choose low on-resistance MOSFET, which can effectively reduce the conduction loss of the circuit and improve the overall efficiency of the converter.
然而前述之實施例或圖式並非限定本發明之產品結構或使用方式,任何所屬技術領域中具有通常知識者之適當變化或修飾,皆應視為不脫離本發明之專利範疇。However, the foregoing embodiments or drawings do not limit the product structure or usage of the present invention, and any appropriate changes or modifications made by those with ordinary knowledge in the technical field should be regarded as not departing from the scope of the present invention.
綜上所述,本發明實施例確能達到所預期之使用功效,又其所揭露之具體構造,不僅未曾見諸於同類產品中,亦未曾公開於申請前,誠已完全符合專利法之規定與要求,爰依法提出發明專利之申請,懇請惠予審查,並賜准專利,則實感德便。To sum up, the embodiment of the present invention can indeed achieve the expected use effect, and the specific structure disclosed is not only not seen in similar products, but also has not been disclosed before the application, which fully complies with the provisions of the patent law In accordance with the requirements, I would like to file an application for an invention patent in accordance with the law, and I urge you to review it and grant the patent.
1:轉換器1: Converter
:輸入電壓 :Input voltage
:第一輸入濾波電感 : first input filter inductor
:第二輸入濾波電感 : The second input filter inductor
:輔助電感 : Auxiliary inductor
:輸入濾波電容 : Input filter capacitor
:第一箝位二極體 : 1st clamp diode
:第二箝位二極體 : Second clamp diode
:第一輔助二極體 : first auxiliary diode
:第二輔助二極體 : second auxiliary diode
:第三輔助二極體 : third auxiliary diode
:第一切換二極體 : first switching diode
:第二切換二極體 : second switching diode
:第10二極體 : 10th diode
:第11二極體 : 11th diode
:第12二極體 : 12th diode
:第13二極體 : 13th diode
:輸出二極體 : output diode
:第一耦合電感一次側 : Primary side of the first coupled inductor
:第一耦合電感二次側 : Secondary side of the first coupled inductor
:第二耦合電感一次側 : Primary side of the second coupled inductor
:第二耦合電感二次側 : Secondary side of the second coupled inductor
:第一磁化電感 : first magnetizing inductance
:第二磁化電感 : Second magnetizing inductance
:第一漏電感 : first leakage inductance
:第二漏電感 : Second leakage inductance
:第一功率開關 : first power switch
:第二功率開關 : Second power switch
:輔助開關 : Auxiliary switch
:箝位電容 : Clamping Capacitor
:第一切換電容 : first switching capacitor
:第二切換電容 : Second switching capacitor
:輸出電容 : output capacitor
:輸出負載 : output load
第一圖:本發明之電路圖The first picture: the circuit diagram of the present invention
第二圖:本發明之時序圖Figure 2: Timing diagram of the present invention
第三圖:本發明之第一階段等效線性電路圖Figure 3: Equivalent linear circuit diagram of the first stage of the present invention
第四圖:本發明之第二階段等效線性電路圖Figure 4: Equivalent linear circuit diagram of the second stage of the present invention
第五圖:本發明之第三階段等效線性電路圖Figure 5: Equivalent linear circuit diagram of the third stage of the present invention
第六圖:本發明之第四階段等效線性電路圖Figure 6: Equivalent linear circuit diagram of the fourth stage of the present invention
第七圖:本發明之第五階段等效線性電路圖Figure 7: Equivalent linear circuit diagram of the fifth stage of the present invention
第八圖:本發明之第六階段等效線性電路圖Figure 8: Equivalent linear circuit diagram of the sixth stage of the present invention
第九圖:本發明之第七階段等效線性電路圖Figure 9: Equivalent linear circuit diagram of the seventh stage of the present invention
第十圖:本發明之第八階段等效線性電路圖Figure 10: Equivalent linear circuit diagram of the eighth stage of the present invention
第十一圖:本發明之第九階段等效線性電路圖Figure 11: Equivalent linear circuit diagram of the ninth stage of the present invention
第十二圖:本發明之第十階段等效線性電路圖Figure 12: Equivalent linear circuit diagram of the tenth stage of the present invention
第十三圖:本發明之第十一階段等效線性電路圖Figure 13: Equivalent linear circuit diagram of the eleventh stage of the present invention
第十四圖:本發明之第十二階段等效線性電路圖Figure 14: Equivalent linear circuit diagram of the twelfth stage of the present invention
第十五圖:本發明之第十三階段等效線性電路圖Figure 15: Equivalent linear circuit diagram of the thirteenth stage of the present invention
第十六圖:本發明之第十四階段等效線性電路圖Figure 16: Equivalent linear circuit diagram of the fourteenth stage of the present invention
第十七圖:本發明之第十五階段等效線性電路圖Figure 17: Equivalent linear circuit diagram of the fifteenth stage of the present invention
第十八圖:本發明之第十六階段等效線性電路圖Figure 18: Equivalent linear circuit diagram of the sixteenth stage of the present invention
第十九圖:本發明之模擬電路示意圖Figure 19: Schematic diagram of the analog circuit of the present invention
第二十圖:本發明之開關驅動信號、與輸入電壓及輸出電壓的模擬波形圖Figure 20: Switch driving signal of the present invention , with input voltage and output voltage The analog waveform of
第二十一圖:本發明之輸入端電流、的模擬波形圖Figure 21: Input current of the present invention , The analog waveform of
第二十二圖:本發明之輸入端電流、的模擬波形圖Figure 22: Input current of the present invention , The analog waveform of
第二十三圖:本發明之輸入端電流、、的模擬波形圖Figure 23: Input current of the present invention , , The analog waveform of
第二十四圖:本發明之第一功率開關驅動信號 、及其跨壓、的模擬波形圖Figure 24: The first power switch of the present invention drive signal , and its cross pressure , The analog waveform of
第二十五圖:本發明之第二功率開關驅動信號 、及其跨壓、的模擬波形圖Figure 25: The second power switch of the present invention drive signal , and its cross pressure , The analog waveform of
第二十六圖:本發明於匝數比時與文獻[1]之電壓轉換比比較曲線圖Figure 26: The invention is based on the turns ratio When compared with the voltage conversion ratio of the literature [1]
第二十七圖:本發明於匝數比時與文獻[1]之電壓轉換比比較曲線圖The twenty-seventh figure: the invention is based on the turns ratio When compared with the voltage conversion ratio of the literature [1]
1:轉換器1: Converter
V in :輸入電壓 V in : input voltage
L i 1 :第一輸入濾波電感 L i 1 : the first input filter inductor
L i 2 :第二輸入濾波電感 L i 2 : the second input filter inductor
L a :輔助電感 L a : auxiliary inductance
C A :輸入濾波電容 C A : Input filter capacitor
D c 1 :第一箝位二極體 D c 1 : first clamp diode
D c 2 :第二箝位二極體 D c 2 : second clamp diode
D a 1 :第一輔助二極體 D a 1 : the first auxiliary diode
D a 2 :第二輔助二極體 D a 2 : the second auxiliary diode
D a 3 :第三輔助二極體 D a 3 : the third auxiliary diode
D 1 :第一切換二極體 D 1 : first switching diode
D 2 :第二切換二極體 D 2 : second switching diode
D 10 :第10二極體 D 10 : 10th diode
D 11 :第11二極體 D 11 : 11th diode
D 12 :第12二極體 D 12 : 12th diode
D 13 :第13二極體 D 13 : 13th diode
D o :輸出二極體 D o : output diode
N p 1 :第一耦合電感一次側 N p 1 : the primary side of the first coupled inductor
N s 1 :第一耦合電感二次側 N s 1 : the secondary side of the first coupled inductor
N p 2 :第二耦合電感一次側 N p 2 : the primary side of the second coupled inductor
N s 2 :第二耦合電感二次側 N s 2 : the secondary side of the second coupled inductor
L m 1 :第一磁化電感 L m 1 : the first magnetizing inductance
L m 2 :第二磁化電感 L m 2 : second magnetizing inductance
L k 1 :第一漏電感 L k 1 : first leakage inductance
L k 2 :第二漏電感 L k 2 : second leakage inductance
S 1 :第一功率開關 S 1 : the first power switch
S 2 :第二功率開關 S 2 : Second power switch
S a :輔助開關 S a : Auxiliary switch
C c :箝位電容 C c : clamp capacitor
C 1 :第一切換電容 C 1 : the first switching capacitor
C 2 :第二切換電容 C 2 : Second switching capacitor
C o :輸出電容 C o : output capacitance
R o :輸出負載 R o : output load
Claims (3)
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TWI792944B (en) * | 2022-03-15 | 2023-02-11 | 崑山科技大學 | High Boost DC Converter Device |
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US20060012348A1 (en) * | 2000-04-27 | 2006-01-19 | Qun Zhao | Coupled inductor DC/DC converter |
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TWI501527B (en) * | 2013-08-09 | 2015-09-21 | Nat Univ Chin Yi Technology | High voltage ratio interleaved converter with soft-switching using single auxiliary switch |
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