201112602 六、發明說明： 【發明所屬之技術領域】 本發明係關於一種設於電力轉換機器之濾波器襄置， 特別是關於一種用以降低起因於開關之共用模式電流及 EMI(電磁干擾）雜訊流出至交流系統之量之主動遽波器裝 置及將主動濾波器裝置設於輸入側之電力轉換裝置。 【先前技術】 隨著電力用半導體元件之特性提升，可實現開關頻率 之高頻化。以無停電電源裝置或通訊用電源裝置為代表之 電力轉換裝置，基於對高速回應或低噪音之要求、濾波器 之小型化要求等，廣泛使用利用PWM(脈寬調變）控制之高 頻開關方式。 ι 隨著開關頻率之高頻化之進展，透過直流連結部或纜 線流至大地之高頻洩漏電流變大。此高頻洩漏電流成為流 入交流系統之雜訊，對連接於交流系統之其他裝置造成不 良影響而成為社會問題。例如，在無停電電源裝置，特別 是將大容量之蓄電池以懸浮方式連接於直流側時，會有大 的高頻洩漏電流從此蓄電池及變長之直流纜線流至大地之 傾向，此高頻洩漏電流對連接於交流系統之其他交流機器 造成不良影響。 作為降低流出至交流系統之高頻洩漏電流之方法，例 如已知有專利文獻丨所揭示之主動濾波器裝置。圖5係專 利文獻1所示之習知雜訊降低裝置及電力轉換裝置的構成 201112602 圖。圖5中，接地別，以』2係、共通之接地，但爲了便於說 明分別賦予不同符號。 圖5中’具備三相交流電源！、電力轉換裝置3、負載 5、及設於三相交流電源i與電力轉換裝置3間之主動瀘波 器裝置7。 ^ 1 ’捲繞有1匝數之電 藉由檢測線20a以檢 作為電流檢測器之電流變壓器2〇 源線1 a〜1 c與N匝數之檢測線2〇a，201112602 VI. Description of the Invention: [Technical Field] The present invention relates to a filter device provided in a power conversion machine, and more particularly to a method for reducing a common mode current and EMI (electromagnetic interference) caused by a switch An active chopper device that flows out to the AC system and a power conversion device that places the active filter device on the input side. [Prior Art] As the characteristics of power semiconductor components are improved, the switching frequency can be increased. A power conversion device represented by an uninterruptible power supply device or a communication power supply device is widely used for high-frequency switching using PWM (pulse width modulation) control based on requirements for high-speed response or low noise, miniaturization of filters, and the like. the way. ι As the high frequency of the switching frequency progresses, the high-frequency leakage current flowing through the DC link or cable to the ground becomes large. This high-frequency leakage current becomes a noise that flows into the AC system, and it is a social problem that adversely affects other devices connected to the AC system. For example, in an uninterruptible power supply device, particularly when a large-capacity battery is connected to the DC side in a floating manner, there is a tendency for a large high-frequency leakage current to flow from the battery and the variable-length DC cable to the ground. Leakage currents adversely affect other AC machines connected to the AC system. As a method of reducing the high-frequency leakage current flowing to the AC system, for example, an active filter device disclosed in the patent document is known. Fig. 5 is a diagram showing the structure of a conventional noise reduction device and a power conversion device shown in Patent Document 1 201112602. In Fig. 5, the grounding is not the same as the "2", common grounding, but different symbols are given for convenience of explanation. In Figure 5, 'has three-phase AC power! The power conversion device 3, the load 5, and the active chopper device 7 provided between the three-phase AC power source i and the power conversion device 3. ^ 1 'A winding of 1 turns of electricity is detected by the detection line 20a as a current transformer of the current detector 2 〇 source line 1 a~1 c and N number of detection lines 2〇a,
測比1/N(N> 1)檢測電力轉換裝置3產生之共用模式電流^ 且輸出為檢測電流io/N。電容器C2具有電容器ci之=_ 1)倍之導納。 由電晶體na，Ub構成之增幅器u之輸入（基極）與輸 出（射極）間連接有檢測線20a，在電容器C1流過與檢測電 流相同之電流io/N。又，在電容器C2流過在電容器以流 過之電流io/N之（N— 1)倍之電流⑺—丨）“…。亦即，在接地 E1流過檢測電流i〇/N之n倍之電流i〇。 由於檢測電流係電力轉換裝置3之共用模式電流沁之 1/N倍’因此流過增幅器U之電流與共用模式電流“相同， 可抵銷流出至交流系統之共用模式電流。藉此，可降低流 出至交流系統之共用模式電流。 ” 然而，圖5所示之電力轉換裝置3中，流過大的補償 電流時’會有電容器C1，C2之端子電壓變高之情形。此端 子電壓超過增幅器U之電源電壓時，增幅器u飽和，無 法獲得共用模式電流之降低效果。為了解決此問題，根據 最大補償電流設計增幅器11之電源電壓。 201112602 圖6及圖7係習知主動遽波器裝置之直流電源之具體 構成例三圖6中，僅以二極體D7及電容器C5使交流系統 之二相交流電源1之交流電壓整流平滑並產生增幅器丨i之 直流電源（動作電源）。圖7中’以二極體D7, D8, D9、電容 器C5，C6、電晶體Q7及電阻13c使交流系統之三相交流電 源1之交流電壓W2電壓整流平滑並產生增幅器u之直流 電源（動作電源）。 專利文獻1 :日本特開2008 — 312429號公報 【發明内容】 · 然而，圖6、圖7所示之構成，對構成增幅器11之電 晶體11a，Ub恆施加直流電源Vc(電容器C5之端子電壓） 之大致-半之電壓，有電晶體lla，m之散熱變大之缺點。 又，電晶體.11a，lib之損耗與增幅器u之電源電壓（及補償 電流）成正比。即使用以補償（抵銷）共用模式電流之補償電 流較小時，亦產生大的增幅器損耗，系統整體之效率變差。 本發明提供-種在補償電流較小時可降低增幅器損耗鲁 之主動濾波器裝置及電力轉換裝置。 第1發明之主動據波器裝置，係設於以三個電源線内 之一個電源線為接地相之三相交流電源與電力轉換裝置之 間，以降低流於該電源線之共用模式電流產生之雜訊，該 電力轉換裝置將從該三相交流電源供應 < 交流電力轉換成 既疋交流電力或直流電力並供應至負載且在筐體具有接地 端子，其特徵在於，具備：可變直流電源，從該電源線獲 6 201112602 :甘 可ι為任意之直流輸出電壓並加以輸出；電流檢 測手段插通有該電源線與檢測線，藉由該檢測線檢測該 共用模式電流並輸出共用模式電流檢測訊號；增幅器，以 該可變直流電源之直流輸出電壓為電源電歷，以增幅度上 將該共用模式電流檢測訊號加以增幅，使電流經由第1電 容器流過該接地相之電源線與接地之間；以及電壓檢測手 段，用以檢測該增幅器之輸出振幅；根據以該電壓檢測手 段檢測之輸出振幅檢測訊號使該可變直流電源之直流輸出 電壓為可變。 第2發明之主動濾波器裝置，係設於以三個電源線内 之個電源線為接地相之三相交流電源與電力轉換裝置之 間’以降低流於該電源線之共用模式電流產生之雜訊，該 電力轉換裝置將從該三相交流電源供應之交流電力轉換成 既定交流電力或直流電力並供應至負載且在筐體具有接地 端子，其特徵在於，具備：可變直流電源，從該電源線獲 仟電力，可變為任思之直流輸出電壓並加以輸出；電流檢 測手段，插通有該電源線與檢測線，藉由該檢測線以1/N(N > 1)之檢測比檢測該共用模式電流並輸出共用模式電流檢 測訊號；增幅器，以該可變直流電源之直流輸出電壓為電 源電壓，以增幅度1將該共用模式電流檢測訊號加以增幅， 使電流經由第1電容器流過該接地相之電源線與接地之 間；第2電容器，具有該第i電容器之（Ν_丨）倍之導納，使 電流從與該增幅器大致相同電位之端子流過該接地相之電 源線與接地之間；以及電壓檢測手段，用以檢測該增幅器 201112602 之輸出振幅；根據以該電壓檢、，目I丨生饥a m w e w壓檢測手段檢測之輪出振幅檢測 讯號使該可變直流電源之直ώ 4且，爪輸出電壓為可變。 第3發明之電力轉換裝置 > ▲ 保將從二相交流電源供應 之父流電力轉換成既定交流雷 ^ # 乂，爪電力或直流電力並供應至負 載’其特徵在於：將第1戋篦 Α第2發明之主動濾波器裝置設 於輸入側。 根據本發明’電壓檢測手段檢測增幅器之輸出振幅， 根據乂電壓檢測手奴檢測之輸出振幅檢測訊號使可變直流 電源之直流輸出電壓為可變’因此在補償電流較小時，增 幅器之電源電壓變小，可降低增幅器損耗。 【實施方式】 、下參…、圖式詳細說明本發明之主動濾波器裝置及 電力轉換裝置之實施形態。 (實施例1) 圖1係實施例1之主動濾波器裝置及電力轉換裝置的 構成圖ϋ 1中具備二相交流電源i、電力轉換裝置3、 負載5、及設於三相夺、;* φ 祁父机電源丨與電力轉換裝置3間之主動 濾波器裝置7 — 1。 在一相乂 ’爪電源1連接R相用電源線la、s相用電源 線ib及τ相用電源線lc，s相用電源線^係接地相之電 源線其接地1：力轉換農置3之僮體（架如係連接於接地 端子E而接地。在雷 €力轉換裝置3與筐體3a之間各處具有 對地間電容，但將此箅斤入 _ 寻‘合顯不成電力轉換裝置3之電容 201112602 器C0之負極與接地端子E之間之對地間電容*。 R相用、s相用、τ相用電源線la〜"、 動滤波器裝置7- i之端子R1，S1，T1。主動澹波器裝置7 —^具有電流變麼器10(電流檢測手段）、由卿電晶體山 與PNP電晶體Ub構成之增幅器u、低頻分離電容器^(第 ^電容器)、二極體D7、電容以5、非絕緣之可變直流電源 30、二極體D8、電容器C3、電阻R1，R2。 非絕緣之可變直流電源3G具備輸人端子、輸出端子、 共通端子、及輸出電壓調整端子，將直流輸入電堡輸入至 輸入端子與共通端子間，根據輸入至輸出電麼調整端子之 訊號將直流輸出電屢輸出至輪出端子與共通端子間。此可 變直流電源30例如係以戴斷型轉換器等構成。 電流變壓器1G捲繞（貫通）有環狀鐵心作為主電源線之 R相用、s相用、τ相用電源線13〜1(；各1&數，且捲繞有 檢測線10al匝數。 -極體D7之陽極係連接於R相用電源線ia，二極體 D7之陰極錢接於可變直流電源％之輸人端子盘電容器 Ο之一端。電容HC5之另一端與接地相之電源線^、電 晶體Ub之集極、可變直流電源3〇之共通端子連接。電容 器C5之二端係、連接於可變直流電源3G之輸人端子與共通 端子之間。可變直流電源3G將電容器q5之直流電壓作為 直流輸入電壓施加。 電晶體11a之集極係連接於可變直流電源3〇之輸出端 子’電晶冑11a之基極係連接於電晶體m之基極、檢測線 201112602 10a之一端、低頻分離電容器ci之一她，你相x ^ 鸲，低頻分離電容器 C1之另一端係連接於接地端子£。 電晶體11a之射極係連接於雷晶辦 较电日日體llb之射極、檢測線 H)a之另-端、二極體08之陽極，二極體則之陰極係連 接於電容器C3之-端與電阻R1之—端。電阻^之另一端 係透過電阻R2連接於電容器^3之另—唑彻 力知與電晶體11 b之 集極。 電阻R1與電阻R2之遠接駄仫嚙从 遲接點係連接於可變直流電源30 之輸出調整端子。由二極體D8、電容器〇、電阻W Μ 構成之電壓檢測手段，將電阻RL與電阻R2之連接點之電 壓檢測為增幅器11之輸出振幅，^ ^ ^ ^ ^ ^ m ^ ^ -T ^ ^ 根據檢測之輸出振幅檢測 號使可變直流電源30之直流輸出電壓vr為可變。 又，在插通電流變壓器10 應串聯抗流線圈L1 L2 L3#“ ，lb’ lc分別對 u L2 L3 H 1力_43具有抗流線圈 3H t aa ^ , 由6個IGBT(絕緣柵雙極The ratio 1/N (N > 1) detects the common mode current ^ generated by the power conversion device 3 and outputs the detected current io/N. Capacitor C2 has an admittance of capacitor ci = _ 1). A detection line 20a is connected between the input (base) and the output (emitter) of the amplifier u composed of the transistors na, Ub, and a current io/N which is the same as the detection current flows through the capacitor C1. Further, in the capacitor C2, a current (7) which is (N-1) times the current flowing through the capacitor io/N (7) - "...", that is, n times the detection current i 〇 / N flows through the ground E1. The current i〇. Since the detection current is 1/N times the common mode current 电力 of the power conversion device 3, the current flowing through the amplifier U is the same as the common mode current, and the common mode current flowing out to the AC system can be offset. . Thereby, the common mode current flowing to the AC system can be reduced. However, in the power conversion device 3 shown in Fig. 5, when a large compensation current flows, the terminal voltage of the capacitors C1 and C2 becomes high. When the terminal voltage exceeds the power supply voltage of the amplifier U, the amplifier u In order to solve this problem, the power supply voltage of the booster 11 is designed according to the maximum compensation current. 201112602 FIG. 6 and FIG. 7 are specific examples of the DC power supply of the conventional active chopper device. In Fig. 6, the AC voltage of the two-phase AC power supply 1 of the AC system is rectified smoothly by the diode D7 and the capacitor C5, and the DC power supply (operation power supply) of the amplifier 丨i is generated. In Fig. 7, the diode D7 is used. , D8, D9, capacitors C5, C6, transistor Q7, and resistor 13c rectify and smooth the AC voltage W2 voltage of the three-phase AC power supply 1 of the AC system and generate a DC power supply (operation power supply) of the amplifier u. Patent Document 1: Japan JP-A-2008-312429 SUMMARY OF THE INVENTION However, in the configuration shown in Figs. 6 and 7, the DC power supply Vc (the end of the capacitor C5) is constantly applied to the transistor 11a constituting the amplifier 11. The voltage of the voltage - roughly half of the voltage has the disadvantage that the heat dissipation of the transistor lla, m becomes large. Moreover, the loss of the transistor .11a, lib is proportional to the power supply voltage (and the compensation current) of the amplifier u. When the compensation current of the compensation (offset) common mode current is small, a large amplifier loss is also generated, and the overall efficiency of the system is deteriorated. The present invention provides an active filter that can reduce the loss of the amplifier when the compensation current is small. The active device according to the first aspect of the present invention is provided between a three-phase AC power source and a power conversion device in which one of the three power supply lines is a ground phase to reduce the flow of the device The noise generated by the common mode current of the power line, the power conversion device converts the three-phase AC power supply <AC power into both AC power and DC power and supplies it to the load and has a ground terminal in the housing, the characteristics of which In addition, it has a variable DC power supply, which is obtained from the power line 6 201112602: Ganke is an arbitrary DC output voltage and is output; the current detecting means is inserted through the power line. And detecting line, detecting the common mode current by the detecting line and outputting the common mode current detecting signal; and increasing the DC output voltage of the variable DC power source to the power supply electric power to increase the amplitude of the common mode current detecting The signal is increased to allow current to flow between the power line of the ground phase and the ground via the first capacitor; and a voltage detecting means for detecting an output amplitude of the amplifier; and detecting an output amplitude signal according to the voltage detecting means The DC output voltage of the variable DC power source is variable. The active filter device of the second invention is disposed between a three-phase AC power source and a power conversion device having three power supply lines as grounding phases. 'To reduce the noise generated by the common mode current flowing through the power line, the power conversion device converts the AC power supplied from the three-phase AC power source into a predetermined AC power or DC power and supplies it to the load and has a ground in the housing The terminal is characterized in that: a variable DC power supply is obtained, and the power is obtained from the power line, and can be changed to a DC input of Ren Si The voltage is outputted and outputted; the current detecting means is inserted into the power line and the detecting line, and the common mode current is detected by the detecting line at a detection ratio of 1/N (N > 1) and the common mode current detecting signal is outputted. And an amplifier, wherein the DC output voltage of the variable DC power source is used as a power supply voltage, and the common mode current detection signal is increased by an amplitude increase 1 to cause a current to flow between the power supply line of the ground phase and the ground through the first capacitor a second capacitor having a (Ν_丨) times admittance of the i-th capacitor, causing a current to flow between the power supply line of the ground phase and the ground from a terminal having substantially the same potential as the amplifier; and a voltage detecting means , for detecting the output amplitude of the amplifier 201112602; according to the voltage detection, the detection of the wheel amplitude detection signal detected by the target I hunger amwew pressure detection means that the variable DC power supply is straight and the claw output The voltage is variable. The power conversion device according to the third aspect of the invention ▲ is configured to convert the parent flow power from the two-phase AC power supply into a predetermined AC mine, the claw power or the DC power, and supply it to the load, which is characterized by: The active filter device of the second invention is provided on the input side. According to the invention, the voltage detecting means detects the output amplitude of the amplifier, and detects the output amplitude detecting signal of the slave slave detecting according to the 乂 voltage, so that the DC output voltage of the variable DC power source is variable'. Therefore, when the compensation current is small, the booster is The power supply voltage is reduced to reduce the amplifier loss. [Embodiment] Embodiments of the active filter device and the power conversion device according to the present invention will be described in detail with reference to the drawings. (Embodiment 1) FIG. 1 is a configuration diagram of an active filter device and a power conversion device according to Embodiment 1. FIG. 1 includes a two-phase AC power supply i, a power conversion device 3, a load 5, and a three-phase capture; The active filter device 7-1 between the φ 祁 parent power source 丨 and the power conversion device 3. In one phase, the 'claw power supply 1 is connected to the R phase power supply line la, the s phase power supply line ib and the τ phase power supply line lc, the s phase power supply line is the grounding phase of the power supply line, the grounding line 1: force conversion The child body of 3 (the frame is connected to the grounding terminal E and grounded. There is a capacitance between the ground between the lightning force conversion device 3 and the casing 3a, but this is not enough to be converted into electricity. Capacitor of the conversion device 3 201112602 The capacitance between the negative electrode of the device C0 and the ground terminal E to the ground. * R phase, s phase, τ phase power supply line la~", dynamic filter device 7-i terminal R1, S1, T1. The active chopper device 7-^ has a current transformer 10 (current detecting means), an amplifier u composed of a crystal transistor mountain and a PNP transistor Ub, and a low frequency separating capacitor ^ ), diode D7, capacitor 5, non-isolated variable DC power supply 30, diode D8, capacitor C3, resistor R1, R2. Non-insulated variable DC power supply 3G with input terminals, output terminals, common The terminal and the output voltage adjustment terminal input the DC input electric power to the input terminal and the common terminal, according to The signal of the adjustment terminal is outputted to the output terminal of the output power to the wheel terminal and the common terminal. The variable DC power source 30 is constituted by a wear-breaking converter, for example. The current transformer 1G is wound (through) The ring core is used as the R phase for the main power supply line, the s phase is used, and the τ phase power supply line 13 to 1 (the number of each 1 & and the detection line 10al is wound. - The anode of the polar body D7 is connected to The R phase uses the power line ia, and the cathode of the diode D7 is connected to one end of the input terminal capacitor Ο of the variable DC power source. The other end of the capacitor HC5 and the grounding phase of the power line ^, the collector of the transistor Ub The common terminal of the variable DC power supply is connected. The two ends of the capacitor C5 are connected between the input terminal of the variable DC power supply 3G and the common terminal. The variable DC power supply 3G uses the DC voltage of the capacitor q5 as the DC input. Voltage application: The collector of the transistor 11a is connected to the output terminal of the variable DC power supply 3'. The base of the transistor 111a is connected to the base of the transistor m, one end of the detection line 201112602 10a, and the low frequency separation capacitor ci One of her, you are x ^ 鸲, The other end of the low-frequency separation capacitor C1 is connected to the ground terminal £. The emitter of the transistor 11a is connected to the emitter of the lightning crystal day llb, the other end of the detection line H)a, and the diode 08 The anode and the cathode of the diode are connected to the end of the capacitor C3 and the end of the resistor R1. The other end of the resistor is connected to the capacitor ^3 through the resistor R2, and the azole is known to the transistor 11 b. The distance between the resistor R1 and the resistor R2 is connected to the output adjustment terminal of the variable DC power source 30 from the late contact point. The voltage detecting means composed of the diode D8, the capacitor 〇, and the resistor W , The voltage at the connection point of the resistor RL and the resistor R2 is detected as the output amplitude of the amplifier 11, ^ ^ ^ ^ ^ ^ ^ ^ ^ -T ^ ^ The DC output voltage of the variable DC power source 30 is determined according to the detected output amplitude detection number. Vr is variable. Also, in the plug-in current transformer 10, the choke coil L1 L2 L3#" should be connected in series, and lb' lc respectively have a choke coil 3H t aa ^ for the u L2 L3 H 1 force _43, which is composed of 6 IGBTs (insulated gate bipolar
!電曰曰體)構成之開關元件Q Q1 ^ ^ V電今益C〇。開關元件 、開關7G件Q2之串聯電路 it# 04 Φ . :一鳊、開關疋件Q3與開關 V4之串聯電路之二端、 之_聯雷心 &開關凡件Q5與開關元件Q6 甲塒電路之二端係連接 v 在-从 安於電4盗C0之二端及負載5。 任開關7〇件Q丨〜q6 $隹 極體叫〜心在-極Λ 射極間分別對應連接二 在一極體〇1盘二搞辦m . 線圈L1，在-β μ /、—和體D2之連接點連接抗流 小闯在—極體d3與二 L2,在-極浐 、 之連接點連接抗流線圈 隹一極體ϋ5與二極體D6 各開關元件Q1〜Q6之…連接點連接抗流線圈乙3。 Q之閉極端子係連接於未圓示之控制電 10 201112602 路，藉由此控制電路控制開關元件Q1〜Q6之導通/斷開， 電力轉換裝置3 ’動作為將從三相交流電源1供應之交流電 力轉換成既定直流電力並供應至負載5之轉換器（交流直流 轉換裝置）。 此外’作為電力轉換裝置，使用將從三相交流電源1 供應之交流電力轉換成既定交流電力並供應至負載5之變 流器亦可。 接著’參照圖1說明實施例1之主動濾波器裝置之動 _ 作。首先’在電流變壓器10，共用模式電流io流過1匝數 之電源線1 a〜1 c時，在1匝數之檢測線10a亦流過與共用 模式電流相同之電流i〇。 增幅器11以增幅度1將流過檢測線丨〇a之i〇加以增 幅，使電流經由低頻分離電容器C1流至接地E卜此時，以 二極體D8及電容器C3使電晶體ila，llb之射極之輸出整 流平滑’將電阻R1與電阻R2之連接點之電壓檢測為增幅 器11之輸出振幅，根據檢測之輸出振幅檢測訊號使可變直 ® 流電源30之直流輸出電壓Vr為可變。是以，用以抵銷共 用模式電流之補償電流較小時’增幅器11之電源電壓變 小，可降低增幅器11損耗。 圖2係顯示與實施例1之主動濾波器裝置之電容器 C3(與電阻R1與電阻R2之連接點之電壓對應）之兩端電壓 對應使可變直流電源3 0之直流輸出電壓yr為可變之情 況。如圖2所示，與電容器C3之電壓成正比，可變直流電 源30之直流輸出電壓vr呈直線變化。 201112602 (實施例2) 圖3係實施例2之主動渡波器裝置及電力轉換裝置的 構成圖。圖3所示之實施例2之主動滤波器裝置7_2，相 對圖1所示之實施例i之主動濾波器裝置㈠，在電流變 壓器20捲繞有N阻數（N>卜例如1〇阻數）之檢測線心。 在電晶體1 la，1 lb之射極與接地端子E之間連接有低 頻分離電容器C2。低頻分離電容器C2具有低頻分離電容 器C1之導納之9倍之導納。亦即，低頻分離電容器C2具 有低頻分離電容器C1之電容之9倍之電容值。 、籲 根據以上述方式構成之實施例2之主動濾波器裝置， 首先，在電流變壓器20,共用模式電流“流過i阻數之電 源線la〜卜時，在10阻數之檢測線2〇a流過共用模式電流 之十分之—之電流ii=io/10。 增幅器11等效於具有以使流過低頻分離電容器c丨之 電流η相等於電流丨。/10之方式控制電壓之增幅部乂丨及具 有與增巾“p V1《電壓相同之電壓、用以使電流 9io/10流過具有低頻分離電容器C1之9倍之電容之低頻分鲁 離電容器C2之增幅部V2。 亦即，增幅部VI以增幅度1將檢測線20a檢測之共用 模式電流之十分之一之電流W10加以增幅，使電流經由低 頻分離電容器C1流至接地E卜又，增幅部V2使流過低頻 分離電容器C1之電流i, ：= io/ΙΟ之9倍之電流i2= 9il = 9i〇/1〇 經由低頻分離電容器C2流至接地E1。 疋以，在接地E1流過與共用模式電流i〇相同值之電流 12 201112602 10 ’因此可降低流出至交流系統之共用模式電流。因此，可 降低產生之雜訊，謀求低價且小型化。 又，以二極體D8及電容器C3使電晶體lla，llb之射 極之輸出整流平滑’將電阻R1與電阻R2之連接點之電壓 檢測為增幅器11之輸出振幅，根據檢測之輸出振幅檢測訊 號使可變直流電源3 〇之直流輸出電$ Vr為可變。是以， 用以抵銷共用模式電流之補償電流較小時，增幅$ u之電 源電壓變小，可降低正常時之增幅器n損耗。 (實施例3) 圖4係實施例3之主動濾波器裝置及電力轉換裝置的 構成圖。圖4所示之實施例3之主動濾波器裝置7_3，相 對圖3所不之實施例2之主動濾波器裝置7 _ 2，取代電容 器Cl，C2設置電阻R3, R4、電容器C4 ,將電阻r3, R4串 聯並連接於電晶體丨la，Ub之基極與射極之間，在電阻R3, R4之連接點與接地端子E之間連接電容器匸4。 電阻R4具有電阻R3之導納（阻抗值之倒數）之9倍之 導納。亦即’電阻R4具有電阻R3之1 /9倍之阻抗值。 根據以上述方式構成之實施例3之主動濾波器裝置， 首先，在電流變壓器2〇，共用模式電流i()流過丨匝數之電 源線la〜lc時’在1〇匝數之檢測線2〇a流過共用模式電流 之十分之一之電流i1= iQ/1〇。 增幅器1 1等效於具有以使流過電阻r3之電流丨丨相等 於電流io/ΙΟ之方式控制電壓之增幅部VI及具有與增幅部 VI之電壓相同之電壓、用以使電流h = = 9i〇/i〇流過具 13 201112602 有電阻R3之1/9倍之阻抗值之電阻R4之增幅部v2。 亦Ρ ί日巾田。p v 1以增幅度1將檢測線2〇a檢測之共用 模式電洲_之十刀之一之電流i〇/1〇加以增幅，使電流經由電 3與電谷器C4流至接地E i。又，增幅部V2使流過電 阻们之電流丨1 = Wl0之9倍之電流9h = 9i〇/10經由電 阻R4與電容器C4流至接地E1。 是以在接地E1流過與共用模式電流io相同值之電流 i。’因此可降低流出至交流系統之共用模式電流。因此，可 降低產生之雜訊，謀求低價且小型化^ 籲 又以一極體D8及電容器C3使電晶體1 ia，nb之射 極之輸出整流平滑，將電阻Rl與電阻Μ之連接點之電壓 檢則為牦幅器1 1之輸出振幅，根據檢測之輸出振幅檢測訊 號使可變直流電源30之直流輸出電壓Vr為可變。是以， 用以抵銷共用模式電流之補償電流較小時，增幅器i i之電 源電壓變小，可降低增幅器1 1損耗。 此外，本發明並不限於實施例丨至實施例3之主動濾 ,器裝置。在實施例2，在電容器c丄串聯電阻R3 '在電容 · 器C2串聯電阻r4之構成亦可。 、本發明可利用於以無停電電源裝置或通訊用電源裝置 為代表之電力轉換裝置。 【圖式簡單說明】 圖1係實施例1之主動濾波器裝置及電力轉換裝置的 構成圖。 14 201112602 圖2係顯示與實施例1之主動濾波器裝置之電容器C3 之兩端電壓對應使可變直流電源之直流輸出電壓為可變之 情況的圖。 圖3係實施例2之主動濾波器裝置及電力轉換裝置的 構成圖。 圖4係實施例3之主動濾波器裝置及電力轉換裝置的 構成圖。 圖5係習知主動濾波器裝置及電力轉換裝置之例1的 籲 構成圖。 圖6係習知主動濾波器裝置之直流電源之具體構成例 1 ° 圖7係習知主動濾波器裝置之直流電源之具體構成例 1。 【主要元件符號說明】 1 三相交流電源 1 a. R相用電源線 lb S相用電源線 1 c T相用電源線 3 電力轉換裝置 4 對地間電容 5 負載 7, 7a, 7b, 7- 1, 7-2, 7- 3 主動濾波器裝置 10, 20 電流變壓器 15 201112602 1 0a，20a 檢測線 30 可變直流電源 11a, lib 電晶體 Rl, R2, R3, R4 電阻 Cl, C2 低頻分離電容器 CO, C3,C4, C5, C6 電容器 Q1〜Q6 開關元件 D1〜D 8 二極體 LI〜L3 抗流線圈!Electrical body) The switching element consisting of Q Q1 ^ ^ V is now available. Switching element, series circuit of switch 7G part Q2 it# 04 Φ . : one end, two ends of the series circuit of switch element Q3 and switch V4, _ 联 雷心 & switch part Q5 and switching element Q6 armor The two-terminal connection of the circuit is at the end of the C0 and the load 5 of the slave. Any switch 7 丨 Q丨~q6 $ 隹 体 〜 心 心 心 心 心 心 心 心 心 心 心 心 心 心 心 心 射 射 射 射 射 射 射 射 射 射 射 线圈 线圈 线圈 线圈 线圈 线圈 线圈 线圈 线圈 线圈 线圈 线圈 线圈 线圈 线圈 线圈 线圈 线圈The connection point of the body D2 is connected with the anti-flow small 闯 in the - body d3 and the two L2, and the connection point of the anti-current coil 隹1 ϋ5 and the diode D6 of the dipole body D6 are connected at the connection point of the - pole 浐Connect the anti-flow coil B to the point. The closed terminal of Q is connected to the control circuit 10 201112602, which is not shown, by which the control circuit controls the on/off of the switching elements Q1 Q Q6, and the power conversion device 3 ' acts to supply the three-phase AC power supply 1 The AC power is converted into a converter of a predetermined DC power and supplied to the load 5 (AC-DC converter). Further, as the power conversion device, a converter that converts AC power supplied from the three-phase AC power supply 1 into predetermined AC power and supplies it to the load 5 may be used. Next, the operation of the active filter device of the first embodiment will be described with reference to Fig. 1 . First, in the current transformer 10, when the common mode current io flows through the power supply lines 1a to 1c of one turn, the current i〇 which is the same as the common mode current flows through the detection line 10a of one turn. The amplifier 11 increases the amplitude of the current flowing through the detection line 丨〇a by increasing the amplitude 1, and causes the current to flow to the ground through the low-frequency separation capacitor C1. At this time, the transistor ila, llb is made by the diode D8 and the capacitor C3. The output of the emitter is rectified and smoothed. The voltage at the junction of the resistor R1 and the resistor R2 is detected as the output amplitude of the amplifier 11, and the DC output voltage Vr of the variable direct current source 30 is made according to the detected output amplitude detection signal. change. Therefore, when the compensation current for canceling the common mode current is small, the power supply voltage of the booster 11 becomes small, and the loss of the amplifier 11 can be reduced. 2 is a diagram showing that the voltage across the capacitor C3 (corresponding to the voltage at the junction of the resistor R1 and the resistor R2) of the active filter device of the first embodiment corresponds to the DC output voltage yr of the variable DC power source 30 being variable. The situation. As shown in Fig. 2, in direct current with the voltage of the capacitor C3, the DC output voltage vr of the variable DC power source 30 changes linearly. 201112602 (Embodiment 2) FIG. 3 is a configuration diagram of an active ferrite device and a power conversion device according to Embodiment 2. The active filter device 7_2 of the embodiment 2 shown in FIG. 3 is wound with an N-resistance number (N> in the current transformer 20 with respect to the active filter device (1) of the embodiment i shown in FIG. ) The detection line. A low frequency separation capacitor C2 is connected between the emitter of the transistor 1 la, 1 lb and the ground terminal E. The low frequency separation capacitor C2 has an admittance of 9 times the admittance of the low frequency separation capacitor C1. That is, the low frequency separation capacitor C2 has a capacitance value nine times that of the low frequency separation capacitor C1. According to the active filter device of the second embodiment constructed in the above manner, first, in the current transformer 20, when the common mode current "flows through the power supply line la to b of the i resistance number, the detection line 2 of the 10 resistance number 〇 a current flowing through the common mode current is ii = io/10. The amplifier 11 is equivalent to having an increase in the control voltage so that the current η flowing through the low frequency separation capacitor c is equal to the current 丨. And a portion V2 having a low-frequency sub-lubrication capacitor C2 having a voltage equal to the voltage of the wafer "p V1" and for causing a current 9io/10 to flow through a capacitor having a capacitance of 9 times that of the low-frequency separation capacitor C1. That is, the amplification unit VI amplifies the current W10 which is one tenth of the common mode current detected by the detection line 20a by the amplification factor 1 so that the current flows to the ground E through the low frequency separation capacitor C1, and the amplification portion V2 flows. The current i of the low frequency separation capacitor C1, 9 times the current i2 = 9 il = 9i 〇 / 1 流 flows through the low frequency separation capacitor C2 to the ground E1. Therefore, the current of the same value as the common mode current i 在 flows through the ground E1 12 201112602 10 ' Therefore, the common mode current flowing out to the AC system can be reduced. Therefore, the noise generated can be reduced, and the price can be reduced and miniaturized. Further, the output of the emitters of the transistors 11a and 11b is rectified by the diode D8 and the capacitor C3. The voltage at the junction of the resistor R1 and the resistor R2 is detected as the output amplitude of the amplifier 11, and the amplitude of the output is detected according to the detection. The signal makes the variable DC power supply 3 〇 DC output power $ Vr variable. Therefore, when the compensation current for offsetting the common mode current is small, the power supply voltage of the increase of $u becomes small, and the amplifier n loss in normal time can be reduced. (Embodiment 3) Fig. 4 is a configuration diagram of an active filter device and a power conversion device according to a third embodiment. The active filter device 7_3 of the embodiment 3 shown in FIG. 4 is different from the active filter device 7 _ 2 of the embodiment 2 shown in FIG. 3, instead of the capacitors C1, C2, the resistors R3, R4, the capacitor C4, and the resistor r3. R4 is connected in series and connected to the transistor 丨la, between the base and the emitter of Ub, and a capacitor 匸4 is connected between the connection point of the resistors R3, R4 and the ground terminal E. Resistor R4 has an admittance of 9 times the admittance of the resistor R3 (the reciprocal of the impedance value). That is, the resistor R4 has an impedance value of 1 / 9 times the resistance R3. According to the active filter device of the third embodiment constructed as described above, first, in the current transformer 2, when the common mode current i() flows through the power supply lines la to lc of the number of turns, the detection line at 1 turns 2〇a flows through one tenth of the common mode current i1=iQ/1〇. The amplifier 1 1 is equivalent to an amplitude increasing portion VI for controlling the voltage so that the current flowing through the resistor r3 is equal to the current io/ΙΟ, and a voltage having the same voltage as that of the amplification portion VI for making the current h = = 9i 〇 / i 〇 13 13 201112602 The resistance portion R2 of the resistance R4 is 1 / 9 times the resistance of the R3. Also Ρ ί day towel field. p v 1 is increased by a magnitude of 1 to increase the current i〇/1〇 of one of the ten modes of the common mode of the detection line 2〇a, so that the current flows to the ground E i via the electric 3 and the electric grid C4. Further, the amplifying portion V2 causes the current flowing through the resistors 丨1 = 9 times the current 9h = 9i 〇/10 to flow through the resistor R4 and the capacitor C4 to the ground E1. It is a current i flowing at the same value as the common mode current io at the ground E1. 'Therefore, the common mode current flowing out to the AC system can be reduced. Therefore, the noise generated can be reduced, and the low-cost and miniaturization can be achieved. The output of the emitters of the transistors 1 ia, nb is rectified smoothly by the one body D8 and the capacitor C3, and the connection point between the resistor R1 and the resistor Μ is made. The voltage detection is the output amplitude of the amplitude modulator 1 1 , and the DC output voltage Vr of the variable DC power source 30 is made variable according to the detected output amplitude detection signal. Therefore, when the compensation current for canceling the common mode current is small, the power supply voltage of the booster i i becomes small, and the amplifier 11 loss can be reduced. Further, the present invention is not limited to the active filter device of the embodiment to the third embodiment. In the second embodiment, the series resistor R3' in the capacitor c丄 is connected to the series resistor r4 in the capacitor C2. The present invention can be utilized in a power conversion device typified by an uninterruptible power supply device or a communication power supply device. BRIEF DESCRIPTION OF THE DRAWINGS Fig. 1 is a configuration diagram of an active filter device and a power conversion device according to a first embodiment. 14 201112602 Fig. 2 is a view showing a state in which the DC output voltage of the variable DC power source is made variable in accordance with the voltage across the capacitor C3 of the active filter device of the first embodiment. Fig. 3 is a view showing the configuration of an active filter device and a power conversion device of the second embodiment. Fig. 4 is a view showing the configuration of an active filter device and a power conversion device of the third embodiment. Fig. 5 is a view showing a configuration of a conventional example of an active filter device and a power conversion device. Fig. 6 shows a specific configuration example of a DC power supply of a conventional active filter device. Fig. 7 is a specific configuration example 1 of a DC power supply of a conventional active filter device. [Main component symbol description] 1 Three-phase AC power supply 1 a. R-phase power supply line lb S-phase power supply line 1 c T-phase power supply line 3 Power conversion device 4 Ground capacitance 5 Load 7, 7a, 7b, 7 - 1, 7-2, 7- 3 Active filter unit 10, 20 Current transformer 15 201112602 1 0a, 20a Detection line 30 Variable DC power supply 11a, lib transistor Rl, R2, R3, R4 Resistance Cl, C2 Low frequency separation Capacitor CO, C3, C4, C5, C6 Capacitor Q1~Q6 Switching element D1~D 8 Diode LI~L3 Coke coil