JPS59122201A - Branching filter - Google Patents
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- Publication number
- JPS59122201A JPS59122201A JP23207282A JP23207282A JPS59122201A JP S59122201 A JPS59122201 A JP S59122201A JP 23207282 A JP23207282 A JP 23207282A JP 23207282 A JP23207282 A JP 23207282A JP S59122201 A JPS59122201 A JP S59122201A
- Authority
- JP
- Japan
- Prior art keywords
- resonant
- elements
- input
- output coupling
- stage
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
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Links
Classifications
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/20—Frequency-selective devices, e.g. filters
- H01P1/201—Filters for transverse electromagnetic waves
- H01P1/205—Comb or interdigital filters; Cascaded coaxial cavities
Landscapes
- Physics & Mathematics (AREA)
- Electromagnetism (AREA)
- Control Of Motors That Do Not Use Commutators (AREA)
Abstract
Description
【発明の詳細な説明】
本発明は、超短波ないしマイクロ波用分波器に関するも
のである。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a duplexer for very high frequency waves or microwaves.
第１図は従来の分波器の一例を示す要部断面図（第２図
のＢ−Ｂ断面図）、第２図は第１図のＡ−Ａ断面図で、
１は導体より成る共通筐体、乙及び２りは共振素子、３
１及び３ａは段間結合ｌｉｔ整素子、４゜及び４コは共
振周波数微細調整素子で、電極板及び０の電極板と共振
素子の開放端との間隙調整ねじより成る。５は共通入出
力結合素子、６は共通入出力端子である。この分波器に
おいては共振素子２１の軸長を共振波長洞のほぼりに定
めると共に、互に逆極性に配設して中心周波数ｆ、のイ
ンタディジタル型帯域通過ろ波器（以下、帯域通過ろ波
器をＢＰＦと略記する）を構成し、共振素子２ａの軸長
を共振波長入ａのほぼ匈に選ぶと共に、互に逆極性に配
設して中心周波数ｆ−のインクディジタル型ＢＰＦ”を
構成しである。したがって各８振素子２．及び２ａの開
放端と筐体壁との間隙が筐体の上下方向に交互に配設ざ
′Ａ’ｔ、共振周波数の微細調整素子４１及び４コにお
ける間隙調整ねじの外端もまた筐体Ｉの土壁及び下要か
ら交互に突出することとなり、 ′全体の
形状が複雑大型となる。又、股間結合調整素子３ｔ＆び
３．が筐体１の側壁から挿入される導体ｔｉｔ以て形成
されでいるため、その挿入用スリットを穿つに当ってフ
ライス加工を要し、したかっで加工工数が多くなり、コ
スト高となるを免れることが出来ず、更に設計製作に際
して理論値と実験値との間の誤差が大なるため構成部品
の寸法、配置間隔等を一々実験的に確めて誤差？補正す
る必要があり、多くの時間と労力を要する。Fig. 1 is a sectional view of the main part (BB sectional view in Fig. 2) showing an example of a conventional duplexer, and Fig. 2 is a sectional view taken along AA in Fig. 1.
1 is a common housing made of a conductor, B and 2 are resonant elements, 3
1 and 3a are interstage coupling lit adjustment elements, 4° and 4 are resonant frequency fine adjustment elements, which are composed of an electrode plate and a gap adjustment screw between the electrode plate 0 and the open end of the resonant element. 5 is a common input/output coupling element, and 6 is a common input/output terminal. In this duplexer, the axial length of the resonant element 21 is determined to be approximately the length of the resonant wavelength cavity, and interdigital band-pass filters (hereinafter referred to as band-pass filters) with a center frequency f are arranged with opposite polarities to each other. The filter is abbreviated as BPF), and the axial length of the resonant element 2a is selected to be approximately the length of the resonant wavelength input a, and they are arranged with opposite polarities to form an ink digital type BPF with a center frequency f-. Therefore, the gaps between the open ends of each of the 8-oscillation elements 2. and 2a and the housing wall are arranged alternately in the vertical direction of the housing. The outer ends of the four gap adjustment screws also protrude alternately from the earthen wall and bottom part of the casing I, making the overall shape complex and large.In addition, the groin joint adjustment elements 3t & 3. Since it is formed by the conductor tit inserted from the side wall of the body 1, milling is required to make the insertion slit, which increases the number of machining steps and increases the cost. Furthermore, since there is a large error between the theoretical value and the experimental value during design and manufacturing, it is necessary to experimentally confirm the dimensions of each component, arrangement spacing, etc. and correct any errors, which requires a lot of time and effort. It takes.
ＢＰＦ’としてコムライン型ＢＰＦを用いるようにすれ
ば共振素子の開放端と筐体間の間隙及び共振周波数微細
調整素子のねじの外端が同一側にそろうように構成され
ているため全体が簡潔小型であるが、従来のコムライン
型ＢＰＦにおいては共振素子の軸長を共振波長のＩよぼ
灼に形成し、各共振素子の開放端に取付けた電極板と筐
体壁間の負荷容量を付加することによって共振を図ると
共に、結合容量を介して股間を結合せしめるように構成
され、前記負荷容量は比較的大きな値を必要とするので
、共振素子の開放端に取付けた電極板と一筐体壁開の間
隙が狭く、耐圧特性が劣ると共に周囲温度の変化に基づ
く間隙の変化に応じて負荷容量が大幅に変化して安定良
好な電気的特性を得ることが困難で、又、電界結合によ
って段間結合を行うように構成しであるので共振素子と
筐体間に誘電体を介在せしめて全体の小型化を図る場合
には、誘電体の誘電率に応じて設問結合係数が変化する
ため設計が極めて困難である。If a combline type BPF is used as the BPF', the gap between the open end of the resonant element and the housing and the outer end of the screw of the resonant frequency fine adjustment element are arranged on the same side, making the whole structure simpler. Although it is small, in the conventional combline type BPF, the axial length of the resonant element is formed to be approximately equal to the resonant wavelength I, and a load capacity is added between the electrode plate attached to the open end of each resonant element and the housing wall. By doing so, resonance is achieved and the crotches are coupled through a coupling capacitance.Since the load capacitance requires a relatively large value, an electrode plate attached to the open end of the resonant element and one housing are used. The gap between the walls is narrow, the voltage resistance is poor, and the load capacity changes significantly as the gap changes due to changes in ambient temperature, making it difficult to obtain stable electrical characteristics. Since the structure is configured to perform interstage coupling, if a dielectric is interposed between the resonant element and the housing to reduce the overall size, the coupling coefficient will change depending on the dielectric constant of the dielectric. Extremely difficult to design.
本発明は、全体の形状が比較的藺潔小型で、耐圧特性に
優れ、周囲温度の変化の影響を受けることなく安定良好
な電気的特性を有し、共振器として誘電体共振器を用い
た場合にも誘電率の影響をほとんど受けることなく設計
製作の容易な超短波ないしマイクロ波用分波器を実現す
ることを目的とする。The present invention has a relatively compact overall shape, excellent voltage resistance characteristics, stable electrical characteristics without being affected by changes in ambient temperature, and uses a dielectric resonator as a resonator. The purpose of the present invention is to realize a duplexer for very short waves or microwaves that is hardly affected by the dielectric constant and is easy to design and manufacture.
第３図は本発明の一実施例を示す断面図（第４図のＢ−
Ｂ断面図）、第４図は第３図のＡ−Ａ断面図で、１は導
体より成る共通筐体、７は導体まＱ成る隔壁、２１ノな
いし２．い２ツないし２工、２，１ないし２３ｎ及び八
、ないし２６や（ｎはＢＰＦの次数ンは、それぞれ棒状
又は筒状導体よＱ成る共振素子で、素子η、ないし２７
．ｆＬの各軸長を電気長で共振波要人、の（ＪぼＡに形
成すると共に適宜間隔を隔てで同−柵性を以て配設し、
筐体１及Ｕ隔壁７と共に中心周波数ｆ、のコムライン型
ＢＰＦ （ＢＰＦＩ）を構成し、ｒ１様に素子筒ないし
２Ｊｎ ” Ｊｌないし２ Ｊ７Ｌ ％ ２ ＠／ない
し２いの各軸長を電気長で共振波要人−２入３、への（
よぼ匈に形成して中心周波数で２、ｆ３、ｆ７のコムラ
イン型ＢＰＦ （ＢＰＦ’＋ｌ、 ＢＰＦ３、ｓｐｐ、
）を構成しである。３１１ないし３ム（ｎ−〇、３．
ｌないし３ツ（７１−ｒハ３３１ないし３３．（ｎ−ｒ
］・３切ないし３９（ＴＬ−Ｉンは段間結合調整素子で
、例えば筐体内への挿入長を変化せしめ得る容量性ねじ
より成る。４，１ないじ４Ｉｎｓ ４．Ｉｌｌないし４
／７Ｌ％ ４λ１ないし４よ。、４□ｌないし４３ｎは
共振周波数微細調整素子で、第１図及び第２図に示した
ものと同様、可動電極板及びその駆動ねじより成る。５
Ｉａ及び５３φは共通入出力結合素子で、それぞれ棒状
又は筒状導体より成り、素子５７．の軸長を電気長でほ
ぼ入ｒＡとはＩ：ｉ入−Ａの平均値に選び、ＢＰＦｔの
初段の共振素子２７．と適宜間隔を隔てて逆極性を以て
対向せしめて入出力結合変成器？構成せしめると共に、
ＢＰＩ”−の初段の共振素子２．。FIG. 3 is a sectional view showing one embodiment of the present invention (B--B in FIG. 4).
B sectional view), FIG. 4 is a sectional view taken along line A-A in FIG. 2 to 2, 2, 1 to 23n, and 8 to 26 (n is the order of the BPF, respectively, is a resonant element consisting of a rod-shaped or cylindrical conductor Q, and the element η to 27
．． The length of each axis of fL is electrical length, and the resonant wave length is formed into J-A, and arranged at appropriate intervals with the same fence characteristics,
Together with the housing 1 and the U partition 7, a combline type BPF (BPFI) with a center frequency f is configured, and the axial lengths of the element tube or 2Jn'' Jl or 2J7L % 2 @/ or 2 are electrical lengths as shown in r1. Resonant wave key person - 2 in 3, to (
Combline type BPF formed in a horizontal shape with center frequencies of 2, f3, f7 (BPF'+l, BPF3, spp,
). 311 to 3m (n-〇, 3.
l to 3 (71-rha331 to 33.(n-r
]・3 Ins to 39 (TL-In is an interstage coupling adjustment element, for example, consisting of a capacitive screw that can change the insertion length into the housing. 4.1 to 4 Ins 4. Ill to 4
/7L% 4λ1 to 4. , 4□l to 43n are resonant frequency fine adjustment elements, which consist of a movable electrode plate and its driving screw, similar to those shown in FIGS. 1 and 2. 5
Ia and 53φ are common input/output coupling elements, each made of a rod-shaped or cylindrical conductor, and element 57. The axial length of the electrical length is selected to be approximately the average value of I:i input-A, and the first stage resonant element 27. of the BPFt is selected. Is it an input/output coupling transformer with opposite polarity at an appropriate interval? In addition to configuring
BPI"-first stage resonant element 2.
と適宜間隔を隔てて逆極性を以て対向せしめて入出力結
合変成器を構成せしめである。同様に素子５Ｊ４の軸長
を電気長でほぼλ３Ａと旭ぼｈｐ／ａの平均値（こ選び
ＢＰＦ３及びＢＰＦ、の各初段共振素子２，７及び２９
．と各適宜間隔を隔てて逆極性を以て対向せしめて共通
入出力結合変成器を構成しである。The input/output coupling transformer is configured by facing the input/output coupling transformer with opposite polarity at an appropriate interval. Similarly, the axial length of element 5J4 is approximately λ3A in terms of electrical length, and the average value of Asahibo hp/a (this is selected for each of the first stage resonant elements 2, 7 and 29 of BPF3 and BPF).
．． A common input/output coupling transformer is constructed by opposing each other at appropriate intervals and having opposite polarities.
６、、ｖ、は共通入出力端子で、共通入出力結合素子５
７、及び５１．／の各開放端を直接接続しである。５Ｉ
ないし５ｑは入出力結合素子で、例えばＢＰＦ、’ない
ｔＢＰＦ９の各終段の共振素子２ノルないし２ｑｒＬと
対向して入出力結合容量を形成する電極より成る。６１
ないし６４４は入出力端子である。尚、ＢＰＦ′ｌない
しＢＰＦ、の各中心周波数ｆ、ないしｆダの周波数差は
比較的小となるように選んである。6, ,v, is a common input/output terminal, and the common input/output coupling element 5
7, and 51. Each open end of / is connected directly. 5I
Reference numerals 5q to 5q designate input/output coupling elements, which are composed of electrodes that face each final stage resonant element 2nor to 2qrL of the BPF or tBPF9 to form an input/output coupling capacitance. 61
644 are input/output terminals. Incidentally, the frequency difference between the center frequencies f and fda of BPF'l to BPF is selected to be relatively small.
このように構成した本発明分波器においては、入出力端
子６１及び６．にｆ、信号及びｆ、信号を同時又は時間
をおいで各別に加えると共振素子２７い又は２工に共振
室、九が流れ、素子２１１又は２工と筐体１役び隔壁７
との開にＴＥＭモード波を生じ、その磁界成分がカット
オフ導波管Ｍを励振して第５図に示す電界成分Ｅと、第
６図に示す磁界成分Ｈとを有するＨ＋＋モード波を生じ
、次段の素子２ｔ、ｔｎ、−ｒ）又は２ を励振す
る。In the duplexer of the present invention configured as described above, the input/output terminals 61 and 6. When f, signal and f, signal are added simultaneously or separately at a later time, the resonance chamber 9 flows to the resonant element 27 or 2, and the element 211 or 2 and the casing 1 serve as partition wall 7.
A TEM mode wave is generated at the opening of the waveguide, and the magnetic field component excites the cutoff waveguide M to generate an H++ mode wave having an electric field component E shown in FIG. 5 and a magnetic field component H shown in FIG. , the next stage element 2t, tn, -r) or 2 is excited.
コ＋（ｎ−り
前記力・ントオフ導波管部は共振素子の対向間隙部分に
おける筐体１及び隔壁７によって形成される部分で、Ｈ
ｕモード波の遮断波長λ。はλｏ＝２Ｗβ
・・・・・・ （１）で定まる。上式においてＷ
は筺体１の横幅（第４図のｖｒ ） 、εは共振素子と
筐体開１こ介在するオオ質で足走る値で、空気の場合ε
＝１、言秀電イ本の場合（まその誘電率である。The force-off waveguide portion is a portion formed by the housing 1 and the partition wall 7 in the opposing gap portion of the resonant element;
Cutoff wavelength λ of u-mode wave. is λo=2Wβ
...... Determined by (1). In the above formula, W
is the width of the housing 1 (vr in Figure 4), ε is the value of the air quality between the resonance element and the housing opening, and in the case of air, ε
= 1, in the case of Kotonshuden Ihon (this is the dielectric constant of Masano).
又、ＴＥＭモード波の磁界成分ｌこよって力・ノドオフ
導波管部が励損される場合、何段の共（辰素子２７，６
又は２ がプローブ、即ちアンテナとしでイ乍用すり几
る。In addition, when the force/nodoff waveguide section is excited by the magnetic field component l of the TEM mode wave, the number of stages (long elements 27, 6
Or 2 can be used as a probe, ie an antenna.
又、各共振素子間のりアクタンス損失Ｌ０に、０＜＋＋
）（ｋ＝１．２、・・ ・・・ｎ）は、
で求められるが、本発明者が行った基礎実験の糸吉果を
分析すると、共振素子の近くで電磁界σン舌りれがある
ため（３）式の実験式σン方すく正確である。In addition, the actance loss L0 between each resonant element is 0<++
)(k=1.2,...n) can be found by Therefore, the empirical formula (3) is much more accurate.
・・ ・ ・ （３ン
但し、Ｃｄ、、、。え。１．は各共振素子相互の中心間
隔ｄは共振素子の直径、である。・ ・ ・ (3) However, Cd... E. 1. The center distance d between each resonant element is the diameter of the resonant element.
共振素子間を伝送すも信号のりアクタンス損失ＬＣＫ、
（１゜、）から共振素子間の磁界結合係数Ｍｌ’＋、ｆ
Ｋ司を求め得るが、磁界の強さは共振電流の大きざに比
例するので各共振素子間のりアクタンス損失ＬＯＨ，（
Ｋ＋ｌｌと磁界結合係数ＭＨ，（ｘｌｌ）の間ニ（１次
式の関係が成立する。Signal actance loss LCK transmitted between resonant elements,
(1°,) to magnetic field coupling coefficient Ml'+, f between resonant elements
However, since the strength of the magnetic field is proportional to the magnitude of the resonant current, the actance loss between each resonant element LOH, (
A linear relationship holds between K+ll and the magnetic field coupling coefficient MH, (xll).
ＬＣＫ、（Ｋや、）＋ｌニー２０アＯｇＪ＜、（１＜＋
＋） ・・・・・（４）筐体１の横幅Ｗ、共振素子
相互の中心間隔ＣｄＫ、（Ｋ＋Ｉ）、共振素子の直径ｄ
１共振素子と筐体間に介在する材質で定まるε及び伝送
信号の波長λ１を与えると上記各式から磁界結合係数ｌ
Ａｇ４、＜＋＋；） を求めることが出来、磁界結合
係数” Ｋ、ｒＫ＋、）を与えると上記各式かも共振素
子相互の中心間隔ＣｄＫ、（１＜、ｒ）を求めるごとが
出来る。以上はＢＰＦ、につし＼で検討したが、ＢＰ−
ないしＢＰＦケについても同様である。LCK, (Kya,)+l knee 20a OgJ<, (1<+
+) ... (4) Width W of the housing 1, center distance between the resonant elements CdK, (K+I), diameter d of the resonant elements
1. Given ε, which is determined by the material interposed between the resonant element and the housing, and the wavelength λ1 of the transmission signal, the magnetic field coupling coefficient l can be calculated from the above equations.
Ag4, <++;) can be obtained, and by giving the magnetic field coupling coefficient "K, rK+,), the center distance between the resonant elements CdK, (1<, r) can be obtained using each of the above equations. BPF, Nitsushi\ was considered, but BP-
The same applies to BPF.
上述のように共振素子部分においては筐体１及（ａＢ）
び隔壁７との開にＴＥＭモード波を生じ、力・ノドオフ
導波管部においでＨ１＋モード波に変換する動作を繰返
して伝送されたｆ、又はｆよ信号は、共通入出力結合素
子５１．と共振素子２１＋及び２５．とより成る共通入
出力変成器を介して共通入出力端子６７〜．から送出さ
れる。そしてこの場合、共通入出力結合素子５ｊｚがス
タブ回路として作用し、ｆｌ及びｆ、信号間の干渉を防
ぐ。As mentioned above, in the resonant element part, a TEM mode wave is generated between the casings 1 and (aB) and the partition wall 7, and the wave is repeatedly converted into an H1+ mode wave in the force/nodoff waveguide section for transmission. The f or f signal is transmitted through the common input/output coupling element 51 . and resonant elements 21+ and 25. Common input/output terminals 67 to 67 through a common input/output transformer consisting of . Sent from In this case, the common input/output coupling element 5jz acts as a stub circuit to prevent interference between fl, f, and signals.
入出力端子６３及び６．にｆ、及びｆ、４信号を同時又
（ま時間をおいて各別に加えた場合にも前記と同様にし
てＢＰＦＪ又はＢＰＦ’Ｑを伝送した信号は共通入出力
結合素子５ｊ（ｌと共振素子２．／及び２仝ｆとから成
る入出力結合変成器を介して共通入出力端子６７．９か
も送出され、共通入出力結合素子５７．がスタブ回路と
しで作用してｆ、及びｆ、信号間の干渉を防ぐ。逆に共
通入出力端子６，４にｆ、なし＼しｆ、信号を同時又（
ｉ時間をおいて加えた場合にも共通入出力結合素子５７
．２又は５バがスタブ回路としで作用し、各信号は各対
応するＢＰＰ ’）介して入出力端子６Ｉないし６ダか
ら送出される。Input/output terminals 63 and 6. Even if f, f, and 4 signals are applied simultaneously (or separately after some time), the signal transmitted through BPFJ or BPF'Q in the same manner as above will be transmitted through the common input/output coupling element 5j (l and the resonant element). The common input/output terminal 67.9 is also sent out through the input/output coupling transformer consisting of To prevent interference between the terminals 6 and 4, on the other hand, the f, none, and f signals can be simultaneously or (
Common input/output coupling element 57 even when added after i time
．． 2 or 5 act as a stub circuit, and each signal is sent out from the input/output terminals 6I to 6DA via each corresponding BPP').
本発明分波器においては、８ＢＰＦをコムライン型ＢＰ
Ｆを以て構成しでいるため共振素子の開放端と筐体壁と
の間隙及び共振周波数微細調整素子が各ＢＰＦ毎に同一
側に配設され、全体の形状が簡潔小型となるばかりでな
く、各ＢＰＦ毎の共振素子の軸長を電気長で共振波長の
はＩよ匈に選んで共振を図ると共に、股間結合を磁界結
合により行うように構成することにより各共振素子の開
放端と筐体壁間の間隙が比較的大で耐圧特性に優れ、周
囲温度の変化の影響を受けることなく安定良好な電気的
特性を有すると共に、ＢＰＦ ｆ８：構成する共振器を
誘電体共振器で形成した場合にも誘電率の影響をほとん
ど受けることなく、透磁率を空気の場合と同じ１ とし
て扱えるので設計製作が容易である。In the duplexer of the present invention, the 8BPF is replaced by a comline type BP.
F, the gap between the open end of the resonant element and the housing wall and the resonant frequency fine adjustment element are arranged on the same side for each BPF, and the overall shape is not only simple and compact, but also The axial length of the resonant element for each BPF is selected to be electrical length and the resonant wavelength is set to I to achieve resonance, and by configuring the groin coupling to be performed by magnetic field coupling, the open end of each resonant element and the housing wall are BPF f8: When the resonator is formed from a dielectric resonator, It is easy to design and manufacture because it is hardly affected by the dielectric constant and the magnetic permeability can be treated as 1, which is the same as that of air.
又、各ＢＰＦの股間結合が磁界結合により行われるため
段間結合調整素子３８．ないし３ＬＩルＩ）、３．、な
いし３コ（ｎ−Ｉ）％ ３Ｊ、なしゝし３３（ｎ−ｒ）
＼３ｑ、なしゝし３Ｙ、Ｉｎ−１）として可変挿入長
型の容量性ねじを用いることが出来、その取付用ねじ孔
を筐体壁に穿つことは極めて容易であるからコストを低
、威せしめることが出来る。Further, since the crotch coupling of each BPF is performed by magnetic field coupling, the interstage coupling adjustment element 38. to 3LI), 3. , to 3(n-I)% 3J, to 33(n-r)
Capacitive screws with variable insertion length can be used for \3q, 3Y, In-1), and it is extremely easy to drill the mounting screw holes in the housing wall, reducing cost and power. I can force it.
第７図は前記本発明分波器の等価回路図で、Ｒｌｌない
しＲ戊、ＲｌｌないしＲＱｎ、ＲＪＪないしＲ川、Ｒ９
，ないしＲ，戸は共振素子と筐体及び隔壁誹り成る共振
［Ｅ］ｆｆｌ各、 Ｃ／６／ 、 Ｃｒ、ノｔ（ｎ＋
ｒ） ％ Ｃコｏｌ Ｓ ”ｐ、ｎｔｎＡｒ）
Ｎ ＣＪＯ／ ％Ｃ１，ｎ（ｖｔｔｒ） ′Ｃｑａｔ
” ｑｊ７／ｉ＋＋） ｌま入出力結合素子、Ｍ
ｌｒ、＞’ｉ’−ゝ し Ｍ ／、（７Ｚ−１）、７Ｌ
′ Ｍン一 な しゝ し Ｍｉ（ｎ−ｒ）７
し ゝ Ｍ ３１２ないし＋１１３．Ｉｎ−を入ｎ
ｓ Ｍｑ１２ないしＭ １（ｎ−ｒ）７７ ハ股間の
磁界結合係数、Ｓ２．及びＳノｑはスタブ回路で、他の
符号は第３図及び第４図と同様である。FIG. 7 is an equivalent circuit diagram of the duplexer of the present invention.
, to R, the door has a resonance consisting of a resonant element, a casing, and a partition wall [E] ffl each, C/6/ , Cr, not (n+
r) % Col S ”p, ntnAr)
N CJO/ %C1,n(vttr) 'Cqat
” qj7/i++) l input/output coupling element, M
lr, >'i'-ゝ M/, (7Z-1), 7L
' M-n-1 Na Shi-shi Mi(n-r)7
ゝ M 312 to +113. Enter In-
s Mq12 to M1(n-r)77 C magnetic field coupling coefficient between legs, S2. and Snoq are stub circuits, and other symbols are the same as in FIGS. 3 and 4.
第７図に示すように共通入出力結合素子５７−と共振素
子２２．及び２１．から成る共通入出力結合素子５バに
入出力結合素子５バと共振素子２３７及び２４１から成
る共通入出力結合変成器の各結合は、共振用仮数におい
では容量結合で、この入出力結合容量Ｃ／６／及びＣ，
、、と共通入出力結合端子６７．９との接続点とアース
間に勾、皮長スクプロ路Ｓ／Ｊが共振回路と並列に接続
され、このスタブ回１絡が信号【こ対してほぼ無限大の
インピーダンス？呈する。As shown in FIG. 7, the common input/output coupling element 57- and the resonant element 22. and 21. Each coupling of the common input/output coupling element 5 bar consisting of the input/output coupling element 5 bar and the common input/output coupling transformer consisting of the resonant elements 237 and 241 is a capacitive coupling in the resonance mantissa, and this input/output coupling capacitance C /6/ and C,
,, between the connection point with the common input/output coupling terminal 67.9 and the ground, a long strip S/J is connected in parallel with the resonant circuit, and this stub circuit 1 is used as a signal Large impedance? present.
共通入出力結合素子５バと共振素子２Ｊ／及び２．、ｌ
よＱ成る共通入出力結合変成器側の等価回路も上記と全
く同様である。Common input/output coupling element 5B, resonance element 2J/and 2. ,l
The equivalent circuit on the side of the common input/output coupling transformer consisting of Q is exactly the same as above.
第３図及び第４図には共通入出力結合素子５７−及び心
、？棒状又は筒状導体を以て形成した場合を例示したが
、共振素子と逆極性のスト＋ノツプラインを以て形成し
てもよい。又、例えば中心周波数ｆ９のＢＰＦ、、：を
省いて３波の分波器を構成し、例えば中心周波数ｆＪ及
びｆｔＩのＢＰＦ３及びＢＰＦｇ を省いて２波の分波
器を構成することも可能である。２波の分派器を構成す
る場合、ＢＰＦＪ及びＢＰＦ、を省く代りに例えばＢＰ
Ｆ、とＢ ＰＦ４を省き、共通入出力結合素子５７、及
び５１φを共通入出力端子６７．９に接続するように構
成してもよい。3 and 4 show a common input/output coupling element 57- and a core, ? Although the case where the conductor is formed using a rod-shaped or cylindrical conductor is illustrated, it may be formed using a stop+knot line having a polarity opposite to that of the resonant element. It is also possible to configure a 3-wave duplexer by omitting, for example, BPF, . be. When configuring a two-wave splitter, instead of omitting BPFJ and BPF, for example, BP
F and B PF4 may be omitted and the common input/output coupling element 57 and 51φ may be connected to the common input/output terminal 67.9.
第８図は本発明の他の実施例を示す断面図（第９図のＢ
−８断面図ン、第９図は第８図のＡ−Ａ断面図で、ｉｏ
は導体より成る隔壁で、ＢＰＦ”、とＢＰＦ。FIG. 8 is a sectional view (B in FIG. 9) showing another embodiment of the present invention.
-8 cross-sectional view, and Figure 9 is a cross-sectional view taken along line A-A in Figure 8.
is a partition wall made of a conductor, BPF", and BPF.
間及びＢＰＦ、とＢＦ４間を電磁的に遮へいする。５，
７．５１１．５３１及び５Ｊ／は入出力結合素子で、適
宜直径の細線より成り、それぞれの長≧を、５ｒｔは電
気長で共振波要人ｌのほぼ匈に選び、共振素子２．。Electromagnetic shielding between BPF and BF4 is provided. 5,
7.511.531 and 5J/ are input/output coupling elements, which are made of thin wires with appropriate diameters, each length ≧, and 5rt is an electrical length, which is approximately the length of the resonant wave element l, and the resonant element 2. .
と適宜間隔を隔てで逆極性を以て配設すると共にその開
放端を共通入出力端子６７〜３に接続しである。素子５
１．５Ｊ、、５勾もまた同様に電気長で共振、皮要人ユ
、入ヨ、入、のほぼ凶に選び、共（辰素子２ユ７．２１
７．２４１と適宜間隔を隔てで逆極性を以て配設すると
共に開放端を共通入出力端子６７Ｎ４に接続しである。They are arranged with opposite polarity at appropriate intervals and their open ends are connected to the common input/output terminals 67-3. Element 5
1.5J,, 5-degree also resonates with electrical length, skin key person Yu, entering Yo, entering, almost evil, both (Tatsu Motoko 2 Yu 7.21)
7.241 and are arranged with opposite polarity at appropriate intervals, and the open ends are connected to the common input/output terminal 67N4.
この実施例においては入出力結合素子５１ないし５りも
また電気長で／／４波長の畏さの細線を以て形成し、共
振素子２，７ｔないし２４ｅ１と各逆極性を以て対向せ
しめである。他の構成及び符号は第３図及び第４図と同
様である。In this embodiment, the input/output coupling elements 51 to 5 are also formed of thin wires with an electrical length of //4 wavelength, and are opposed to the resonant elements 2, 7t to 24e1 with opposite polarities. Other structures and symbols are the same as those in FIGS. 3 and 4.
Ｂ ＰＦ’、の入出力端子６．にｆ、信号を加えると入
出力結合素子５，７を介して共通入出力端子６．〜９か
ら送出されるが、入出力結合素子５２２、”ｊ／、５４
７を形成する細線は凶波畏の端部短絡回路で、ｆ、信号
に対しでそれぞれほぼ無限大のインピーダンスを呈し、
これらが共通入出力端子６．〜９に並列接続されている
ためｆ、信号がＢＰＦ、ないしＢＰＦ＜に結合されるこ
とはない。同様に入出力端子６２ないし６３にｆ、ない
しｆ、信号を加えた場合にも各信号は他のＢＰＦに結合
することなく、共通入出力端子６７９□にのみ結合する
。逆に共通入出力端子６７Ｎケに各信号を加えた場合は
、各信号は各対応するＢＰＦにのみ結合し相互干渉を生
ずることはない。B PF', input/output terminal 6. When a signal f is added to the common input/output terminal 6. ~9, but the input/output coupling element 522, "j/, 54
The thin wire forming 7 is a dangerous end short circuit, and exhibits almost infinite impedance to f and the signal, respectively.
These are the common input/output terminals 6. Since f is connected in parallel with .about.9, no signal is coupled to BPF or BPF<. Similarly, when signals f and f are applied to the input/output terminals 62 and 63, each signal is not coupled to other BPFs but is coupled only to the common input/output terminal 679□. Conversely, when each signal is applied to the common input/output terminals 67N, each signal is coupled only to each corresponding BPF, and no mutual interference occurs.
尚、第８図には股間結合調整素子及び共振周波数微細調
整素子を示すのを省いであるが、実際には前実施例と同
様のものを設けること勿論である。Although the crotch coupling adjustment element and the resonant frequency fine adjustment element are not shown in FIG. 8, it goes without saying that the elements similar to those in the previous embodiment are actually provided.
第１０図は上記実施例の等価口路図で、Ｓｌ、ないしＳ
約及びＳ／ないしＳ４１まそれぞれ凶波長ヌタプ回路で
、他の符号１よ第７図と同様である。FIG. 10 is an equivalent path diagram of the above embodiment, showing Sl to S.
Approximately and S/ to S41 are respectively bad wavelength Nutapu circuits, and the other symbols 1 to 7 are the same as in FIG.
第１１図もまた本発明の他の実施例を示す断面図（第１
２図のＢ−Ｂ断面図）、第１２図（ま第１１図のＡ−Ａ
断面図で、本実施例（こお（＼て（ま入出力結合回路５
ｒｒ 、５Ｊｌ、５８．及び５４．を線、条文（ま板等
より成る電極を以て形成し、共振素子２ｏ 、２．；Ｉ
＋、２３゜及び２４／との間に結合容量を形成せしめる
と共イこ、素子５７．と２１．とより成る回路のインピ
ーダンス力くｆ１４Ｍ？’ｒに対してＢＰＦ、の特性イ
ンピーダンスを呈し、らないしｆ４信号に対しで杼めで
高し＼インピーダンスを呈するように調整し、同様（こ
素子５．７と２５．とより成る回路、素子”Ｊ／と２，
７とより成る口８各、素子５□、と６．とより成る回路
の各インピーダンスを各対応するｆ２、ｆＪ、ｆイ信号
ｆこ対してＢＰＦ２、ＢＰＦＪ。FIG. 11 is also a sectional view (first embodiment) showing another embodiment of the present invention.
(B-B sectional view in Figure 2), Figure 12 (or A-A in Figure 11)
The cross-sectional view shows the input/output coupling circuit 5 of this embodiment.
rr, 5Jl, 58. and 54. are formed using wires, articles (electrodes made of cutting boards, etc.), and the resonant elements 2o, 2.;I
+, 23° and 24/, and element 57. and 21. Is the impedance of the circuit consisting of f14M? It is adjusted so that it exhibits the characteristic impedance of BPF for 'r, and exhibits a high impedance for the f4 signal. J/ and 2,
7, an opening 8 each consisting of an element 5□, and 6. The respective impedances of the circuit consisting of the corresponding f2, fJ, and f signals are BPF2 and BPFJ.
ＢＰＦ−特性インピーダンスを呈し、イ也のイ言号に対
して高いインピーダンスを呈するよう（こ調整してアル
。又、この実施例におし＼て【ま入出力結合素子５、な
いし５Ｊループを以て形成し、共振周波数微細調整素子
を共通筐体１の側壁に設けた場合を例示しである。尚、
共振周波数微細調整素子ｌま４，７及び４．？、のみが
図示之れ、他は図面上ｆ；現れてｔ＼ない。又、段間結
合調整素子は前実施例同様図面に（ま示していない。This is adjusted so that it exhibits a BPF-characteristic impedance and exhibits a high impedance for the A word of A. Also, in this embodiment, the input/output coupling element 5 or 5J loop is This example shows a case in which the resonant frequency fine adjustment element is provided on the side wall of the common housing 1.
Resonant frequency fine adjustment elements 4, 7 and 4. ? , are shown; the others appear f; but not t\ in the drawing. Also, the interstage coupling adjustment element is not shown in the drawings as in the previous embodiment.
第１３図はこの実施例の要部等価回路図で、符号は第７
図と（同様である。FIG. 13 is an equivalent circuit diagram of the main part of this embodiment, and the reference numeral is 7th.
(Similar to the figure.
第７図、第１０図及び第１３図の各等価回路図力＼ら明
らかなように、本発明分波器におし＼で（ま共通入出力
端子６７〜７に接続される入出力結合回路を容量結合回
路に形成して分波を確実ならしめである。As is clear from the equivalent circuit diagrams in FIGS. 7, 10, and 13, the duplexer of the present invention is connected to the input/output couplings connected to the common input/output terminals 67 to 7. The circuit is formed into a capacitively coupled circuit to ensure demultiplexing.
以上何れの実施例においても入出力端子６７なＣ＼し６
４に接続される入出力結合素子？前記のように、結合容
量を形成する電極、細線又はループを以て形成する他、
棒状又は筒状導体或はストリ・ンプライン等を以て形成
してもよし１゜
又、以上何れの実施例においでも段間結合調整素子を容
量性ねじを以て形成する代りに、誘導性又は容量性絞り
或は誘導性短絡棒等を以て形成してもよ（、これらの中
、任意の素子を単独で設ける代りに、誘導性又は容量性
絞りと容量性ねじとを組合せて設けるか、誘導性短絡棒
と容量性ねじとを併せて設けるようにしてもよく、何れ
の場合にも各ＢＰｌｉ’を構成する共振素子の中心間隔
を適当に選ぶと共に、容量性ねじの挿入長、絞り幅、誘
導性短絡棒の本数、設置位置及び直径等を適当に選んで
段間磁界結合係数を適当ならしめることにより任意の伝
送特性を有する分波器を構成することが出来る。In any of the above embodiments, the input/output terminal 67
Input/output coupling element connected to 4? As mentioned above, in addition to forming an electrode, a thin wire or a loop to form a coupling capacitance,
It may be formed with a rod-shaped or cylindrical conductor, a striped line, etc. 1. In addition, in any of the above embodiments, instead of forming the interstage coupling adjustment element with a capacitive screw, it may be formed with an inductive or capacitive restrictor or with a capacitive screw. may be formed using an inductive shorting rod, etc. (Instead of providing any element alone, an inductive or capacitive restrictor and a capacitive screw may be provided in combination, or an inductive shorting rod and a capacitive screw may be provided.) A capacitive screw may also be provided, and in either case, the center spacing of the resonant elements constituting each BPli' is appropriately selected, and the insertion length of the capacitive screw, the aperture width, and the inductive shorting rod are carefully selected. A duplexer having arbitrary transmission characteristics can be constructed by appropriately selecting the number, installation position, diameter, etc., and making the interstage magnetic field coupling coefficient appropriate.
上記各実施例においでは、分波器を構成する各ＢＰＦに
おける共振素子を一列に配設しであるため全体が横長と
なって実装設計上不利な場合があるが、共振素子をコの
字型に配設することによりこのような欠点を除くことが
出来る。In each of the above embodiments, since the resonant elements in each BPF constituting the duplexer are arranged in a line, the whole becomes horizontally long, which may be disadvantageous in terms of mounting design. This drawback can be eliminated by arranging the
第１４図は共振素子をコの字型に配設した一例を示す断
面図（第１５図のＢ−８断面図）、第１５図は第１４図
のＡ−Ａ断面図で、１１ は導体より成る隔壁で、この
隔壁により各ＢＰＦ内をコの字型に仕切り、その中に共
振素子をコの字型に配設しである。１２もまた導体より
成る隔壁で、左右に隣接するＢＰＦ、の共振素子２Ｉｎ
とＢＰＩｉ”−の共振素子２．＋を間を電磁的ｌこ遮断
するための隔壁である。ＢＰＦ、及びＢＰＦ４を側も全
く同様の構成である。他の符号、構成作動等は前記各実
−施例と同様である。尚、・図には示していないが共振
周波数微細調整素子及び股間結合調整素子も前記各実施
例と同様のものを設けること勿論である。更にこの実施
例においても共通入出力結合素子５７２及び５Ｊい入出
力結合素子５゜ないし５や、股間結合調整素子等を前実
施例と同様各種の素子を用いることが出来る。Fig. 14 is a cross-sectional view showing an example of resonant elements arranged in a U-shape (B-8 cross-sectional view in Fig. 15), Fig. 15 is a cross-sectional view taken along A-A in Fig. 14, and 11 is a conductor. This partition wall partitions the inside of each BPF into a U-shape, and the resonant elements are arranged in a U-shape within the partition wall. 12 is a partition wall also made of a conductor, and the resonant element 2In of the BPF adjacent to the left and right
This is a partition wall for electromagnetically shielding between the resonant element 2.+ of - Same as in the embodiments.Although not shown in the figure, it goes without saying that the resonant frequency fine adjustment element and the crotch joint adjustment element are also similar to those in each of the above embodiments.Furthermore, in this embodiment as well. As with the previous embodiment, various elements can be used for the common input/output coupling element 572, the input/output coupling element 5J, the crotch coupling adjustment element, etc.
この実施例におけるＢＰＦの折返し部分１よ、第１６図
に要部断面図（第１７図のＢ−Ｂ断面図）を、第１７図
ｊこ第１６図のＡ−Ａ断面図を示すように、隔壁１１
を筐体１の端壁まで延長し、折返し部分の共振素子２ｒ
ｒＬと２．ｍや、の対向部分に結合孔１３を穿ち、この
結合孔１３の直径を適当に変えて段間磁界結合係数を変
化せしめるように構成してもよい。The folded part 1 of the BPF in this embodiment is shown in FIG. 16 as a sectional view of the main part (BB sectional view in FIG. 17), and as shown in FIG. , bulkhead 11
is extended to the end wall of the housing 1, and the resonant element 2r at the folded part is
rL and 2. It may be configured such that a coupling hole 13 is bored in the opposing portion of the coupling hole 13 and the diameter of the coupling hole 13 is appropriately changed to change the interstage magnetic field coupling coefficient.
以上何れの実施例においでも分波器を構成するＢＰＦの
共振素子の中、縦続接続関係にある２個又はその整数倍
の個数の共振素子を隔てた共振素子相互を間（妾結合す
ることにより減衰域に減衰極を生せしめて減衰特性を良
好ならしめ、分波器の特性を改善することが出来る。共
振素子を一列に配設した場合には、同軸線路又はストリ
ップラインと、これらの線路と共振素子間を結合する容
量結合素子又は磁界結合素子とを以て間接結合回路を形
成し、共振素子をコの字型に配設した場合には第１８図
に示すように、隔壁１１に間接結合孔１４を穿つか、隔
壁１１ を貫いて間接結合ループを設け、或は隔壁１１
を貫いて間接結合容量素子１５を設ける。このように
間接結合０路を設けると共に、共振回路より成る主回路
と間接結合回路との結合極性及び結合度を適当ならしめ
ることにより、主回路を伝送して下流側の間接結合点ｆ
二到る減衰域信号の位相及び振幅と、間接結合口ｊ路を
介して下流側の間接結合点に到る減衰域信号の位相及び
振幅の関係が、逆相で振幅が等しくなる周波数位置に減
衰極を生せしめることが出来る。In any of the above embodiments, among the resonant elements of the BPF constituting the duplexer, two or an integral multiple of the resonant elements in a cascade connection are separated from each other (by concubine coupling). It is possible to create an attenuation pole in the attenuation region to improve the attenuation characteristics and improve the characteristics of the duplexer.If the resonant elements are arranged in a row, the coaxial lines or strip lines and these lines An indirect coupling circuit is formed by a capacitive coupling element or a magnetic field coupling element that couples between the resonant elements, and when the resonant elements are arranged in a U-shape, indirect coupling is made to the partition wall 11 as shown in FIG. A hole 14 is drilled or an indirect coupling loop is provided through the septum 11 or the septum 11
An indirect coupling capacitance element 15 is provided through it. In this way, by providing an indirect coupling zero path and making the coupling polarity and degree of coupling between the main circuit consisting of a resonant circuit and the indirect coupling circuit appropriate, the main circuit is transmitted and the downstream indirect coupling point f
The relationship between the phase and amplitude of the two attenuated region signals and the phase and amplitude of the attenuated region signal that reaches the indirect coupling point on the downstream side via the indirect coupling port J is at a frequency position where the amplitudes are equal in opposite phases. It is possible to generate an attenuation pole.
第１９図は本発明分波器を用いて４波以上の分波器回路
を構成した一例を示すプロンク線図で、１６、ないし１
錦はそれぞれ本発明分波器で、１６．は＋７ないし＋７
信号、１６２はｆ、ないしｆ８信号、１６ヨは＋２ない
しｆ７カ信号、１６＜ｔはｆｙＪｆｉいし＋７を信号の
各分波器である。＋７．ないし１７＜７は分岐線路で、
１７７は電気長で、ｆ、ないしｆｌ信号の平均波長場、
のほぼｎ’７’２ （ｎ’は任意の整数）倍の長さを有
し、１７２はで。FIG. 19 is a Pronk diagram showing an example of a duplexer circuit having four or more waves using the duplexer of the present invention.
Each brocade is a duplexer of the present invention, 16. is +7 or +7
The signal 162 is the f to f8 signal, 16yo is the +2 to f7 signal, and 16<t is the demultiplexer for the fyJfi to +7 signal. +7. or 17<7 is a branch line,
177 is the electrical length, the average wavelength field of the f or fl signal,
It has a length of approximately n'7'2 (n' is any integer) times 172.
ないしｆ、信号の平均波要人２２のほぼｎ’７２倍、１
７？は＋２ないしｆ／２信号の平均波要人、３のほぼｎ
′／′；！倍、１７４はｆ／１ないし＋７６信号の平均
波要人ｑのほぼ１７２倍の長谷に形成しである。＋８は
分岐点で、例えば伶電線を介してアンテナ等に接続され
る。to f, approximately n'72 times the average wave of the signal 22, 1
7? is the average waveform of +2 or f/2 signal, approximately n of 3
′/′;! 174 times is approximately 172 times the average wave length q of the f/1 to +76 signal. +8 is a branch point, which is connected to an antenna or the like via a wire, for example.
分岐線路及び分波器の数を適宜増減すると共に分波器の
分波数を２ないし４の何れかに適宜選ぶことにより分波
数と自在に定めることが出来る。By appropriately increasing or decreasing the number of branch lines and branching filters and selecting the branching number of the branching filter from 2 to 4, it is possible to freely determine the branching number.
第１図及び第２図は従来の分波器の一例を示す断面図、
第３図、第４図、第８図、第９図、第１１図、第１２図
、第１４図、第１５図、第１８図及び第１９図は本発明
の一実施例を示す断面図、第７図、第１Ｏ図及び第１３
図はその等価回路図、第５図及び第６図（ま作動説明の
だめの図、第１６図及び第１７図は本発明の一実施例に
おける要部構成の一例を示す断面図で、ド筐体、２２．
２．．２１．ないし２２２０．２２．ないし２２□、２
Ｊ／ないし２ア及び２Ｚ／ないし２９４、共振素子、３
１．３１．３１．ないし３／、 （ｎ−ｔ＞ 、３Ｑ／
ないし３〕、。７−リ、３ｎ’−’いし３１．（ｎ−ｒ
）及び３ｚｌないし３イ、に〜２．：段間結合調整素子
、４７．４２．４，７ないし４／７Ｌ％’ Ａｗｔない
し４２い、４３．ないし４７，２及び４り、ないし４−
？ｙｔ’共振周波数微細調整素子、５．５ｚｉ及び５ｊ
４：共通入出力結合素子、５．ないし５２及び５１．な
いし５イ、：入出力結合素子、６及び６７〜３：共通入
出力端子、６７ないし６４：入出力端子、７及び１０な
いし１２：隔壁、１３及び１４：結合孔、１５：間接結
合素子、１６７ないし１６７：本発明分波器、１７．な
いし１７４：分岐線路、１．３：分岐点である。
第１図
第２図
第３図
第４図
第１］図
１３を
第１２図 第１３図
１
第１４図
第１５図1 and 2 are cross-sectional views showing an example of a conventional duplexer,
3, 4, 8, 9, 11, 12, 14, 15, 18, and 19 are cross-sectional views showing one embodiment of the present invention. , Fig. 7, Fig. 1O and Fig. 13
Figures 5 and 6 are equivalent circuit diagrams, and Figures 5 and 6 are diagrams for explaining the operation. body, 22.
2. ．． 21. to 2220.22. or 22□, 2
J/ to 2A and 2Z/ to 294, resonant element, 3
1.31.31. or 3/, (nt>, 3Q/
or 3],. 7-li, 3n'-'ish31. (n-r
) and 3zl to 3i, to 2. : Interstage coupling adjustment element, 47.42.4,7 to 4/7L%' Awt to 42, 43. to 47, 2 and 4-, to 4-
? yt' resonant frequency fine adjustment element, 5.5zi and 5j
4: common input/output coupling element, 5. to 52 and 51. to 5 A, : input/output coupling element, 6 and 67 to 3: common input/output terminal, 67 to 64: input/output terminal, 7 and 10 to 12: partition wall, 13 and 14: coupling hole, 15: indirect coupling element, 167 to 167: duplexer of the present invention, 17. to 174: Branch line, 1.3: Branch point. Figure 1 Figure 2 Figure 3 Figure 4 Figure 1] Figure 13 Figure 12 Figure 13 Figure 1 Figure 14 Figure 15
Claims (8)
性を保つと共に、 １、ｃに、（区・リ −−２０１０ｇ暇、３．＜ヤ、）
Ｃａ、、Ｃ計、）：共振素子相互の中心間隔に：ｌ
、 ２ 、３ 、 ・・・・・・ ｎｎ：ろ波器の
次数 ｄ：共振素子の直径 Ｗ：筐体（共振器の外部導体）の幅 ＬＯＩ＜、４にや５．：共振素子間のりアクタンス損失
ＭＫ、（Ｋヤ、）：共振素子間の磁界結合係数入。＝２
Ｗ【 ７−ｏ：遮断波長 入 ：伝送信号の波長 ε：共振器の内外導体間に介在する材質で定まる値（誘
電体の場合はその誘電率） で定まる中心間隔を隔てて配設された複数個の共振素子
と、前記複数個の共振素子の中、初段及び終段の共振素
子に各別に対向せしめた入出力結合素子とを備えると共
に、前記初段の共振素子に対向せしめた入出力結合素子
を共通の分岐点に直接接続して成る複数個のコムライン
型帯域通過ろ波器より成ることを特徴とする分波器。(1) It has an axial length that is approximately the same as the resonant wavelength in terms of electrical length, and maintains the same polarity.
Ca,, C meter): center distance between resonant elements: l
, 2 , 3 , ...... nn: Order of filter d: Diameter of resonant element W: Width of housing (outer conductor of resonator) LOI<, 4 or 5. :Actance loss MK between resonant elements, (Kya,): Enter magnetic field coupling coefficient between resonant elements. =2
W [7-o: Cutoff wavelength input: Transmission signal wavelength ε: Disposed with a center spacing determined by the value determined by the material interposed between the inner and outer conductors of the resonator (in the case of a dielectric, its permittivity) An input/output coupling element comprising a plurality of resonant elements, and an input/output coupling element facing each of the first-stage and final-stage resonant elements among the plurality of resonant elements, and facing the first-stage resonant element. A duplexer comprising a plurality of combline bandpass filters each having elements directly connected to a common branch point.
性を保つと共に、 。’＋＜、（Ｋ＋、）＝Ｑ、３ｄ・−二？血す５４．６
η Ｌ０ド、検子り −一２０１０ｇＭＫ、（に−・ンＣｄ
Ｈ，（ｙオ、）：共振素子相互の中心間隔に＝Ｉ 、
２ 、３ 、 ・・・・・・ ｎｎ：ろ波器の次
数 ｄ：共振素子の直径 Ｗ：筐体（共振器の外部導体ンの幅１ ＬＣＫ、いヤυ：共振素子開のりアクタンス損失Ｍ）’
；、＋に＋Ｑ ’共振素子間の磁界結合係数入。＝２ｗ
ｇ 入、： 週■祈、皮長 入 ：伝送信号の波長 ε；共振器の内外導体間に介在する材質で定まる値（誘
電体の場合はその誘電率ン で定まる中心間隔を隔てで配設された複数個の共振素子
と、前記複数個の共振素子の中、終段の共振素子に対向
せしめた入出力結合素子とを備えた２個のコムライン型
帯域通過ろ波器における前記複数個の共振素子の中、各
初段の共振素子に共通に対向せしめた入出力結合素子を
共通の分岐点に直接接続して成る１個又は複数個の単位
分波器より成ることを特徴とする分波器。(2) It has an axial length approximately equal to the resonant wavelength in electrical length, maintains the same polarity, and. '+<, (K+,)=Q, 3d・-2? blood 54.6
η L0 de, Kenshiri -12010gMK, (ni-nCd
H, (yo,): Center distance between resonant elements = I,
2, 3, ...... nn: Order of filter d: Diameter of resonant element W: Housing (width of external conductor of resonator 1 LCK, y υ: Resonant element open actance loss M )'
;, +Q' enters the magnetic field coupling coefficient between the resonant elements. =2w
G In, : Week ■ Prayer, Skin Long In : Wavelength ε of the transmission signal; value determined by the material interposed between the inner and outer conductors of the resonator (in the case of a dielectric, the center distance determined by the dielectric constant n) the plurality of resonant elements in two comb-line type bandpass filters comprising a plurality of resonant elements, and an input/output coupling element facing a final stage resonant element among the plurality of resonant elements; Among the resonant elements, a branch is characterized in that it consists of one or more unit demultiplexers formed by directly connecting input/output coupling elements commonly facing each first-stage resonant element to a common branch point. Wave equipment.
項又は第２項記載の分波器。(3) Claim 1 in which the resonant elements are arranged in a row
The duplexer according to item 1 or 2.
第１項又は第２項記載の分波器。(4) The duplexer according to claim 1 or 2, wherein the resonant elements are arranged in a U-shape.
、共振素子と逆極性を以て設けた棒状又は筒状導体より
成る特許請求の範囲第１項又は第２項記載の分波器。(5) The duplexer according to claim 1 or 2, wherein the input/output coupling element facing the first-stage resonant element comprises a rod-shaped or cylindrical conductor provided with a polarity opposite to that of the resonant element.
、共振素子と逆極性を以て設けたストリップラインより
成る特許請求の範囲第１項又は第２項記載の分波器。(6) The duplexer according to claim 1 or 2, wherein the input/output coupling element facing the first-stage resonant element comprises a strip line provided with a polarity opposite to that of the resonant element.
、共振素子と逆極性を以て設けた細線より成る特許請求
の範囲第１項記載の分波器。(7) The duplexer according to claim 1, wherein the input/output coupling element opposed to the first-stage resonant element comprises a thin wire provided with a polarity opposite to that of the resonant element.
、対向共振素子との間に結合容量？形成する電極より成
る特許請求の範囲第１項記載の分、波器。(8) Is there a coupling capacity between the input/output coupling element facing the first stage resonant element and the opposing resonant element? 2. A wave wave device according to claim 1, comprising electrodes formed therein.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP23207282A JPS59122201A (en) | 1982-12-28 | 1982-12-28 | Branching filter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP23207282A JPS59122201A (en) | 1982-12-28 | 1982-12-28 | Branching filter |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| JPS59122201A true JPS59122201A (en) | 1984-07-14 |
Family
ID=16933545
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP23207282A Pending JPS59122201A (en) | 1982-12-28 | 1982-12-28 | Branching filter |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS59122201A (en) |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS62235801A (en) * | 1986-04-05 | 1987-10-16 | Fuji Elelctrochem Co Ltd | Incorporated type dielectric multicoupler |
| US5151670A (en) * | 1991-04-10 | 1992-09-29 | Radio Frequency Systems, Inc. | Duplexing filter |
| US5892419A (en) * | 1995-09-26 | 1999-04-06 | Adc Solitra Oy | Integral resonators for a filter and a method for manufacturing thereof |
| US6593832B2 (en) | 2000-03-30 | 2003-07-15 | Allgon Ab | Coaxial cavity resonator, filter and use of resonator component in a filter |
Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS54103656A (en) * | 1978-02-01 | 1979-08-15 | Nec Corp | Signal compounding unit |
-
1982
- 1982-12-28 JP JP23207282A patent/JPS59122201A/en active Pending
Patent Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS54103656A (en) * | 1978-02-01 | 1979-08-15 | Nec Corp | Signal compounding unit |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS62235801A (en) * | 1986-04-05 | 1987-10-16 | Fuji Elelctrochem Co Ltd | Incorporated type dielectric multicoupler |
| US5151670A (en) * | 1991-04-10 | 1992-09-29 | Radio Frequency Systems, Inc. | Duplexing filter |
| US5892419A (en) * | 1995-09-26 | 1999-04-06 | Adc Solitra Oy | Integral resonators for a filter and a method for manufacturing thereof |
| US6593832B2 (en) | 2000-03-30 | 2003-07-15 | Allgon Ab | Coaxial cavity resonator, filter and use of resonator component in a filter |
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