JPH10164861A - Resonance inverter circuit - Google Patents
Resonance inverter circuitInfo
- Publication number
- JPH10164861A JPH10164861A JP8321434A JP32143496A JPH10164861A JP H10164861 A JPH10164861 A JP H10164861A JP 8321434 A JP8321434 A JP 8321434A JP 32143496 A JP32143496 A JP 32143496A JP H10164861 A JPH10164861 A JP H10164861A
- Authority
- JP
- Japan
- Prior art keywords
- inductor
- capacitor
- load
- switching
- transformer
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
Classifications
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Landscapes
- Circuit Arrangements For Discharge Lamps (AREA)
- Inverter Devices (AREA)
Abstract
Description
【０００１】[0001]
【発明の属する技術分野】この発明は直流電源の両端に
直列に接続され、交互にオンオフする第１，第２スイッ
チング素子が接続され、その一方のスイッチング素子の
両端間に直列共振回路が接続されると共に、その一方の
共振素子を１次又は２次側に並列接続されたトランスを
介して、熱陰極放電管のような負荷が接続される共振形
インバータ回路に関する。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a DC power supply, wherein first and second switching elements are connected in series and alternately turned on and off, and a series resonance circuit is connected between both ends of one of the switching elements. And a resonance type inverter circuit to which a load such as a hot cathode discharge tube is connected via a transformer having one of the resonance elements connected in parallel to the primary or secondary side.
【０００２】[0002]
【従来の技術】図４Ａに従来のインバータ回路を示す。
直流電源１１の両端は、コンデンサ１２，１３の直列回
路と、スイッチング素子１４，１５の直列回路の各両端
に接続され、コンデンサ１２，１３の接続点１６と、ス
イッチング素子１４，１５の接続点１７との間に、イン
ダクタ１８と、コンデンサ１９と、例えば蛍光灯（熱陰
極放電管）のような負荷２１との直列回路が接続され
る。スイッチング素子１４，１５にこれをそれぞれオン
オフ制御する駆動回路２２，２３が接続される。2. Description of the Related Art FIG. 4A shows a conventional inverter circuit.
Both ends of the DC power supply 11 are connected to both ends of the series circuit of the capacitors 12 and 13 and the series circuit of the switching elements 14 and 15, respectively. A connection point 16 of the capacitors 12 and 13 and a connection point 17 of the switching elements 14 and 15 are provided. A series circuit of an inductor 18, a capacitor 19, and a load 21 such as a fluorescent lamp (hot cathode discharge tube) is connected between them. Driving circuits 22 and 23 for turning on and off the switching elements 14 and 15 are connected to the switching elements 14 and 15, respectively.
【０００３】駆動回路２２，２３によりスイッチング素
子１４，１５はそれぞれ図４Ｂのａ，ｂに示すように、
交互に同一期間Ｔ／２ずつオン、オフ制御される。スイ
ッチング素子１４がオンになると、コンデンサ１２の電
荷がスイッチング素子１４を通じて更に負荷２１を通じ
て接続点１６へ電流として流れ、スイッチング素子１５
がオンとなった時はコンデンサ１３の電荷が接続点１６
から負荷２１を通じ、更にスイッチング素子１５を通じ
て電流として流れ、負荷２１に交互に逆方向に電流が流
れる。インダクタ１８とコンデンサ１９の共振周波数が
スイッチング素子１４，１５の各スイッチング周波数１
／Ｔの場合、接続点１２，１３間に発生する電圧、つま
りスイッチング回路の出力電圧は図４ＢＣの曲線２４と
なり、これら接続点１２，１３間に流れる電流、つまり
スイッチング回路の出力電流は曲線２５となる。つまり
スイッチング素子１４，１５は、スイッチング回路の電
流がゼロとなった時点（ゼロ点を切る時点）でオンオフ
の切替えが行われる。このため、スイッチング素子１
４，１５での電力損失は最小となる。As shown in FIGS. 4A and 4B, the switching elements 14 and 15 are driven by driving circuits 22 and 23, respectively.
On / off control is performed alternately by the same period T / 2. When the switching element 14 is turned on, the electric charge of the capacitor 12 flows as a current through the switching element 14 to the connection point 16 through the load 21, and the switching element 15
Is turned on, the charge of the capacitor 13 is
Flows through the load 21 and further through the switching element 15, and the current alternately flows through the load 21 in the opposite direction. The resonance frequency of the inductor 18 and the capacitor 19 is equal to the switching frequency 1 of the switching elements 14 and 15.
In the case of / T, the voltage generated between the connection points 12 and 13, that is, the output voltage of the switching circuit becomes a curve 24 in FIG. 4BC, and the current flowing between these connection points 12 and 13, that is, the output current of the switching circuit becomes a curve 25. Becomes That is, the switching elements 14 and 15 are switched on and off when the current of the switching circuit becomes zero (the point where the current crosses the zero point). Therefore, the switching element 1
The power loss at 4 and 15 is minimal.
【０００４】しかし、インダクタ１８、コンデンサ１９
の直列共振回路のリアクタンス特性は図５Ａに示すよう
に共振周波数ｆｒでリアクタンスｊｘはゼロとなるが、
例えば周波数ｆがｆｒより低くなると、リアクタンスｊ
ｘは負となり、共振回路を流れる電流は進み位相とな
り、図５ＢＣの曲線２５に示すようにスイッチング出力
回路の出力電流は、スイッチング出力回路の出力電圧
（曲線２４）よりも進み位相となる。このため、スイッ
チング素子１４，１５は、スイッチング出力回路に電流
が流れている状態でオン制御が行われ、スイッチング素
子１４，１５の損失が大きくなる。However, the inductor 18 and the capacitor 19
5A, the reactance jx becomes zero at the resonance frequency fr as shown in FIG. 5A.
For example, when the frequency f becomes lower than fr, the reactance j
x becomes negative, the current flowing through the resonance circuit has a leading phase, and the output current of the switching output circuit has a leading phase with respect to the output voltage (curve 24) of the switching output circuit as shown by a curve 25 in FIG. 5BC. For this reason, the switching elements 14 and 15 are turned on while the current is flowing through the switching output circuit, and the loss of the switching elements 14 and 15 increases.
【０００５】この問題を解決するには、スイッチング素
子１４，１５のスイッチング周波数１／Ｔを低くして、
共振周波数ｆｒと一致するようにスイッチング周波数１
／Ｔを制御する。又は図６Ｃに示すように、スイッチン
グ素子１４，１５の各オン期間ＴONを、スイッチング周
期Ｔの１／２よりも短かくして、いわゆるＰＷＭ制御し
て、スイッチング回路の出力電流のゼロ点でスイッチン
グ素子１４，１５をオンにするようにしている。In order to solve this problem, the switching frequency 1 / T of the switching elements 14 and 15 is reduced,
The switching frequency 1 is set to match the resonance frequency fr.
/ T is controlled. Alternatively, as shown in FIG. 6C, the on-period T ON of the switching elements 14 and 15 is set to be shorter than の of the switching period T, and so-called PWM control is performed, and the switching element is switched at the zero point of the output current of the switching circuit. 14 and 15 are turned on.
【０００６】[0006]
【発明が解決しようとする課題】以上のように従来にお
いては、共振周波数ｆｒの変動に対して、スイッチング
周波数、又はスイッチング期間を制御して、スイッチン
グ損失を低減しているため、その共振周波数ｆｒの変動
の検出と、これに対応したスイッチング周波数や期間を
制御するための構成が複雑となり、かつ、高価なものと
なった。As described above, conventionally, the switching frequency or the switching period is controlled in response to the fluctuation of the resonance frequency fr to reduce the switching loss. The structure for detecting the fluctuation of the voltage and controlling the switching frequency and the period corresponding to the fluctuation are complicated and expensive.
【０００７】[0007]
【課題を解決するための手段】請求項１の発明によれ
ば、直列共振回路の共振用インダクタの一端が第１，第
２スイッチング素子の接続点に接続される形式のインバ
ータ回路において、トランスの２次巻線の一端と負荷と
の間に、第２インダクタが直列に挿入されて、これによ
り負荷に流れるリアクタンス成分を打消し、負荷変動に
かかわらず、ゼロ点でのスイッチングが行われるように
する。According to the first aspect of the present invention, there is provided an inverter circuit in which one end of a resonance inductor of a series resonance circuit is connected to a connection point between a first switching element and a second switching element. A second inductor is inserted in series between one end of the secondary winding and the load, thereby canceling a reactance component flowing through the load, and performing switching at a zero point regardless of a load change. I do.
【０００８】請求項２の発明によれば、直列共振回路の
共振用コンデンサの一端が第１，第２スイッチング素子
の接続点に接続される形式のインバータ回路において、
トランスの２次巻線の一端と負荷との間に、第２コンデ
ンサが直列に挿入されて、これにより負荷に流れるリア
クタンス成分を打消し、負荷変動にかかわらず、ゼロ点
でのスイッチングが行われるようにする。According to the second aspect of the present invention, there is provided an inverter circuit in which one end of a resonance capacitor of a series resonance circuit is connected to a connection point between the first and second switching elements.
A second capacitor is inserted in series between one end of the secondary winding of the transformer and the load, thereby canceling the reactance component flowing through the load, and performing switching at the zero point regardless of the load fluctuation. To do.
【０００９】[0009]
【発明の実施の形態】図１Ａにこの発明の実施例を示
す。直流電源１１の両端にスイッチング素子１４，１５
の直列回路の両端が接続され、一方のスイッチング素子
１５の両端間に直流阻止コンデンサ３１を通じ、更にイ
ンダクタ１８を通じてトランス３２の１次巻線３３の両
端が接続され、トランス３２の２次巻線３４の一端と他
端よりわずか手前の点にコンデンサ１９の両端が接続さ
れ、この接続点３６と２次巻線３４の他端との間に、負
荷２１としての蛍光灯の一方のフィラメントの両端が接
続され、トランス３２の３次巻線３７の両端に負荷２１
としての蛍光灯の他方のフィラメントの両端が接続さ
れ、２次巻線３４の一端と３次巻線３７の一端の間にコ
イル３８の両端が接続される。コンデンサ１９の容量を
Ｃ2 とし、トランス３２の巻数比をａ＝ｎ2 ／ｎ1 とす
ると、Ｃ2 ′＝Ｃ2 ／ａ2 に対し、コンデンサ３１の容
量Ｃ1 は１０〜１００倍程度に選定されている。FIG. 1A shows an embodiment of the present invention. Switching elements 14 and 15 are provided at both ends of the DC power supply 11.
The two ends of a primary winding 33 of a transformer 32 are connected through a DC blocking capacitor 31 between both ends of one switching element 15, and further through an inductor 18. Both ends of the capacitor 19 are connected to a point slightly before the other end of the fluorescent lamp as the load 21 between the connection point 36 and the other end of the secondary winding 34. The load 21 is connected to both ends of the tertiary winding 37 of the transformer 32.
Both ends of the other filament of the fluorescent lamp are connected, and both ends of a coil 38 are connected between one end of the secondary winding 34 and one end of the tertiary winding 37. Assuming that the capacitance of the capacitor 19 is C 2 and the turns ratio of the transformer 32 is a = n 2 / n 1 , the capacitance C 1 of the capacitor 31 is about 10 to 100 times that of C 2 ′ = C 2 / a 2. Selected.
【００１０】図１Ａに示した回路の等価回路を図１Ｂに
示す。トランス３２はインダクタ１８（Ｌ1 ）と直列の
二つの漏洩インダクタＬ′，Ｌ′と、漏洩インダクタ
Ｌ′，Ｌ′の接続点に一端接続されたシャントの相互イ
ンダクタＭとで表わせ、相互インダクタＭのインダクタ
ンスが十分大であり、漏洩インダクタＬ′のインダクタ
ンスが十分小さいとし、またインダクタ３８のインダク
タンスＬ2 に対し、等価回路ではインダクタンスが
Ｌ2 ′＝ａ2 Ｌ2 となり、共振周波数ｆｒ は１／√
（Ｌ1 Ｃ2 ′）となる。所でスイッチング素子１５の両
端に発生する電圧をＥ、負荷２１の抵抗値をＲとする
と、電源１１から流れる全電流ｉは次式となる。FIG. 1B shows an equivalent circuit of the circuit shown in FIG. 1A. The transformer 32 is represented by two leakage inductors L ′ and L ′ in series with the inductor 18 (L 1 ) and a shunt mutual inductor M connected to a connection point between the leakage inductors L ′ and L ′. Is sufficiently large, the inductance of the leakage inductor L 'is sufficiently small, and the inductance L 2 ' = a 2 L 2 in the equivalent circuit with respect to the inductance L 2 of the inductor 38, and the resonance frequency fr Is 1 / √
(L 1 C 2 ′). Assuming that the voltage generated at both ends of the switching element 15 is E and the resistance value of the load 21 is R, the total current i flowing from the power supply 11 is expressed by the following equation.
【００１１】 ｉ＝（Ｅ／Ｌ1 ）（ＲＣ2 ′＋ｊωＬ1 Ｃ2 ′） …（１） 従って負荷２１に流れる電流ｉR は次式となる。 ｉR ＝Ｃ−Ｅω2 Ｌ1 Ｃ2 ′／（ＲＣ1 −ω2 Ｌ1 Ｃ2 ′）＋ｊωＬ1 ） …（２） １−ω2 Ｌ1 Ｃ2 ′＝０ つまり、共振周波数ｆｒ
では、 ｉR ＝−Ｅω2 Ｌ1 Ｃ2 ′／（ｊωＬ1 ）＝ｊＥωＣ2 ′ …（３） となり、負荷２１を流れる電流は負荷２１のインピーダ
ンスＲによらず一定となる。しかし、全電流ｉは式
（１）で与えられ、Ｒ＝０での立上りも予想され、ｉ＝
ｊＥωＣとｊR と同一となり、つまり電圧Ｅに対し電流
ｉが９０°遅れ、電流ゼロ点でのスイッチングができな
いことになる。I = (E / L 1 ) (RC 2 ′ + jωL 1 C 2 ′) (1) Accordingly, the current i R flowing through the load 21 is given by the following equation. i R = C-Eω 2 L 1 C 2 '/ (RC 1 -ω 2 L 1 C 2') + jωL 1) ... (2) 1-ω 2 L 1 C 2 '= 0 That is, the resonance frequency fr
, I R = −Eω 2 L 1 C 2 ′ / (jωL 1 ) = jEωC 2 ′ (3), and the current flowing through the load 21 is constant regardless of the impedance R of the load 21. However, the total current i is given by equation (1), a rise at R = 0 is also expected, and i =
It becomes the same as the j R jEωC, i.e. current i 90 ° delayed relative to the voltage E, would not be switching at zero current point.
【００１２】従って、負荷２１にリアクタンス成分ｊｘ
を直列に接続してスイッチング素子１４，１５を流れる
電流が、その１部が電圧と同位相になるようにされる。
つまり図１Ａではインダクタ３８が負荷２１と直列に接
続され、この直列回路がコンデンサ１９の両端に接続さ
れる。この場合でかつＲ＝０の時の全電流ｉは式（１）
より次式となる。Therefore, the reactance component jx is added to the load 21.
Are connected in series so that a part of the current flowing through the switching elements 14 and 15 has the same phase as the voltage.
That is, in FIG. 1A, the inductor 38 is connected in series with the load 21, and this series circuit is connected to both ends of the capacitor 19. In this case, when R = 0, the total current i is given by the following equation (1).
From the following equation:
【００１３】 ｉ＝ｊ（Ｅ／Ｌ1 ）（ωＬ2 ′Ｃ2 ′＋ωＬ1 Ｃ2 ′） …（４） この式（４）の電流がゼロになれば、インダクタ１８に
流れる電流と、インダクタンスＬ2 ′のインダクタ３８
に流れる電流との位相差は１８０°となり、打ち消しあ
うことになる。従って （Ｅ／Ｌ1 ）（ωＬ2 ′Ｃ2 ′＋ωＬ1 Ｃ2 ′）＝０ とおき、かつ １−ω2 Ｌ1 Ｃ2 ′＝０ （共振条
件）より、 ｊωＬ2 ′＝−１／ωＣ2 ′＝１／（ｊωＣ2 ′） …（５） となり、インダクタ３８のインダクタンスＬ2 はＣ2 ／
ａ4 又はＬ1 ／ａ2 とすればよい。この時、全電流ｉは
ωＬ1 ＝１／ωＣ2 ′ で ｉ＝（Ｅ／Ｌ）ＲＣ2 ′ となり、負荷２１に流れる電流ｉR は次式となり、負荷
Ｒの値に拘わらず一定となる。I = j (E / L 1 ) (ωL 2 ′ C 2 ′ + ωL 1 C 2 ′) (4) If the current of equation (4) becomes zero, the current flowing through the inductor 18 and the inductance L 2 'inductor 38
Has a phase difference of 180 ° with the current flowing therethrough, and is canceled out. Accordingly, (E / L 1 ) (ωL 2 ′ C 2 ′ + ωL 1 C 2 ′) = 0 and 1−ω 2 L 1 C 2 ′ = 0 (resonance condition), jωL 2 ′ = −1 / ωC 2 ′ = 1 / (jωC 2 ′) (5), and the inductance L 2 of the inductor 38 is C 2 /
a 4 or L 1 / a 2 may be used. At this time, the total current i is ωL 1 = 1 / ωC 2 ′ and i = (E / L) RC 2 ′, and the current i R flowing through the load 21 is given by the following equation, and is constant regardless of the value of the load R. .
【００１４】ｉR ＝Ｅ／（ｊωＬ1 ） このようにすれば負荷２１の変動にかかわらず、電流ゼ
ロ点でスイッチングを行うことができる。図２Ａに示す
ように、コンデンサ１９の両端にそれぞれコンデンサ４
１，４２の一端を接続し、コンデンサ４１，４２の各他
端を２次巻線３４の両端にそれぞれ接続し、その両接続
点と負荷２１としての蛍光灯の両端フィラメントの各一
端にコイル４３，４４の各両端を接続し、各フィラメン
トの他端と、コンデンサ１９とコンデンサ４１，４２の
各接続点との間にコイル４５，４６をそれぞれ接続す
る。コイル４３，４５、４４，４６は１つの磁気コア上
に巻き、負荷２１の電流に対し、コイル４３と４５を同
相、コイル４４，４６を同相、コイル４３，４４を差
動、コイル４５，４６を差動関係とし、コンデンサ４１
の両端間の電圧で一方のフィラメントにフィラメント電
流を流し、コンデンサ４２の両端間の電圧で他方のフィ
ラメントにフィラメント電流を流し、かつ、コンデンサ
１９に対し、コイル４３，４５の結合、コイル４４，４
６の結合が負荷２１に対して直列となり、つまり、図１
Ａのインダクタ３８と同様の作用をなさしめている。こ
の場合はトランス３２の２次巻線３４にタップを設ける
必要がない。この場合、コイル４３〜４６の各インダク
タンスを同一値Ｌとすれば、図１Ａ中のインダクタ３８
のＬ2 の１／４でよい。I R = E / (jωL 1 ) In this way, the switching can be performed at the zero current point regardless of the fluctuation of the load 21. As shown in FIG.
1 and 42 are connected to each other, the other ends of the capacitors 41 and 42 are connected to both ends of the secondary winding 34, respectively. , 44 are connected to each other, and coils 45, 46 are connected between the other end of each filament and each connection point of the capacitor 19 and the capacitors 41, 42, respectively. The coils 43, 45, 44, and 46 are wound on one magnetic core, and the coils 43 and 45 are in-phase, the coils 44 and 46 are in-phase, the coils 43 and 44 are differential, and the coils 45 and 46 are applied to the current of the load 21. Is a differential relationship, and the capacitor 41
And a filament current flows through the other filament at a voltage between both ends of the capacitor 42, and a coupling between the coils 43 and 45 and the coils 44 and 4 with respect to the capacitor 19.
6 are in series with the load 21;
The same operation as that of the inductor 38 of FIG. In this case, it is not necessary to provide a tap on the secondary winding 34 of the transformer 32. In this case, assuming that the respective inductances of the coils 43 to 46 have the same value L, the inductor 38 in FIG.
Ｌ of L 2 may be used.
【００１５】図２Ｂに示すように、図１Ａ中のコンデン
サ１９を、トランス３２の２次巻線３４ではなく１次巻
線３３の両端に設けてもよい。更に３Ａに示すように共
振用コンデンサ１９をトランス３２の１次巻線３３を介
してスイッチング素子１５の両端に接続し、トランス３
２の２次巻線３４と並列にインダクタ１８を接続し、イ
ンダクタ１８及び２次巻線３４の一端の接続点をコンデ
ンサ５１を介して３次巻線３７の一端に接続し、つま
り、図１Ａ中のコンデンサ３１を省略し、インダクタ１
８とコンデンサ１９とを入れかえ、かつ、インダクタ３
８とコンデンサ５１とを入れかえた構成としてもよい。
この場合、コンデンサ５１の容量は、コンデンサ１９の
容量のａ2 倍とすればよい。この場合も図３Ｂに示すよ
うに、インダクタ１８をトランス３２の１次巻線３３側
に変更してもよい。またこの実施例に示すように、トラ
ンス３２に帰還コイル５２，５３をそれぞれ設け、帰還
コイル５２，５３の誘起電圧でスイッチング素子１４，
１５をオンオフ制御するように、つまり自動発振形イン
バータ回路とした場合であり、前記の他の実施例も、こ
のように自動発振形インバータ回路として構成すること
もできる。As shown in FIG. 2B, the capacitor 19 in FIG. 1A may be provided at both ends of the primary winding 33 instead of the secondary winding 34 of the transformer 32. Further, as shown in FIG. 3A, the resonance capacitor 19 is connected to both ends of the switching element 15 via the primary winding 33 of the transformer 32, and
2 is connected in parallel with the secondary winding 34, and the connection point between the inductor 18 and one end of the secondary winding 34 is connected to one end of the tertiary winding 37 via the capacitor 51, that is, FIG. The capacitor 31 inside is omitted and the inductor 1
8 and the capacitor 19 are replaced, and the inductor 3
8 and the capacitor 51 may be replaced.
In this case, the capacity of the capacitor 51 may be set to a 2 times the capacity of the capacitor 19. Also in this case, as shown in FIG. 3B, the inductor 18 may be changed to the primary winding 33 of the transformer 32. As shown in this embodiment, the transformer 32 is provided with feedback coils 52 and 53, respectively, and the switching elements 14 and
This is a case in which 15 is turned on / off, that is, an automatic oscillation type inverter circuit. The other embodiments described above can also be configured as an automatic oscillation type inverter circuit.
【００１６】[0016]
【発明の効果】以上述べたように、この発明によれば、
トランスの２次巻線と負荷との間に直列にインダクタ又
はコンデンサを接続するという頗る簡単な構成により、
放電管のように、負荷インピーダンスが大幅に変化する
負荷に対しても、常に、ゼロ電流点でスイッチング素子
に対するスイッチングが行われ、スイッチング損失が少
なく、効率がよい、しかも安価に構成することができ
る。As described above, according to the present invention,
With a very simple configuration of connecting an inductor or a capacitor in series between the secondary winding of the transformer and the load,
Even for a load whose load impedance changes greatly, such as a discharge tube, switching to the switching element is always performed at the zero current point, so that the switching loss is small, the efficiency is high, and the cost can be reduced. .
【図１】Ａは請求項１の発明の実施例を示す回路図、Ｂ
はその等価回路図である。FIG. 1A is a circuit diagram showing an embodiment of the invention of claim 1; FIG.
Is an equivalent circuit diagram thereof.
【図２】請求項１の発明の他の実施例を示す回路図。FIG. 2 is a circuit diagram showing another embodiment of the present invention.
【図３】請求項２の発明の実施例を示す回路図。FIG. 3 is a circuit diagram showing an embodiment of the invention according to claim 2;
【図４】Ａは従来の共振形インバータ回路を示す図、Ｂ
はその動作波形図である。FIG. 4A is a diagram showing a conventional resonant inverter circuit, and FIG.
FIG. 4 is an operation waveform diagram thereof.
【図５】Ａは共振回路のリアクタンスの周波数特性図、
Ｂは共振周波数がスイッチング周波数より高い方へずれ
た場合の動作波形図、Ｃはその改善動作波形図である。FIG. 5A is a frequency characteristic diagram of the reactance of the resonance circuit,
B is an operation waveform diagram when the resonance frequency is shifted to a higher frequency than the switching frequency, and C is an improved operation waveform diagram.
Claims (2)
フされる第１，第２スイッチング素子が直流電源の両端
間に接続され、一方のスイッチング素子の両端間に共振
用インダクタを介してトランスの１次巻線が接続され、
上記トランスの１次巻線及び２次巻線の一方と並列に共
振用コンデンサが接続され、上記２次巻線の両端間に負
荷が接続される共振形インバータ回路において、 上記２次巻線の一端と上記負荷との間に第２インダクタ
が直列に挿入されていることを特徴とする共振形インバ
ータ回路。1. A first and a second switching element connected in series and alternately turned on and off are connected between both ends of a DC power supply, and a transformer is connected between both ends of one switching element via a resonance inductor. Primary winding is connected,
In a resonance type inverter circuit in which a resonance capacitor is connected in parallel with one of a primary winding and a secondary winding of the transformer and a load is connected between both ends of the secondary winding, A resonance type inverter circuit, wherein a second inductor is inserted in series between one end and the load.
フされる第１，第２スイッチング素子が直流電源の両端
間に接続され、一方のスイッチング素子の両端間に共振
用コンデンサを介してトランスの１次巻線が接続され、
上記トランスの１次巻線及び２次巻線の一方と並列に共
振用インダクタが接続され、上記２次巻線の両端間に負
荷が接続される共振形インバータ回路において、 上記２次巻線の一端と上記負荷との間に第２コンデンサ
が直列に挿入されていることを特徴とする共振形インバ
ータ回路。2. A first and a second switching element connected in series and alternately turned on and off are connected between both ends of a DC power supply, and a transformer is connected between both ends of one of the switching elements via a resonance capacitor. Primary winding is connected,
In a resonance type inverter circuit in which a resonance inductor is connected in parallel with one of a primary winding and a secondary winding of the transformer, and a load is connected between both ends of the secondary winding, A resonance type inverter circuit, wherein a second capacitor is inserted in series between one end and the load.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP8321434A JPH10164861A (en) | 1996-12-02 | 1996-12-02 | Resonance inverter circuit |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP8321434A JPH10164861A (en) | 1996-12-02 | 1996-12-02 | Resonance inverter circuit |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| JPH10164861A true JPH10164861A (en) | 1998-06-19 |
Family
ID=18132517
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP8321434A Pending JPH10164861A (en) | 1996-12-02 | 1996-12-02 | Resonance inverter circuit |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPH10164861A (en) |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2003030340A3 (en) * | 2001-09-28 | 2004-01-15 | Koninkl Philips Electronics Nv | Adaptable inverter |
| JP2007174881A (en) * | 2005-12-22 | 2007-07-05 | Samsung Electronics Co Ltd | Inverter circuit, backlight device, and liquid crystal display device made thereby |
| US7746337B2 (en) | 2005-11-17 | 2010-06-29 | Samsung Electronics Co., Ltd. | Inverter circuit |
| JPWO2013061800A1 (en) * | 2011-10-25 | 2015-04-02 | 株式会社村田製作所 | Inverter device |
-
1996
- 1996-12-02 JP JP8321434A patent/JPH10164861A/en active Pending
Cited By (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2003030340A3 (en) * | 2001-09-28 | 2004-01-15 | Koninkl Philips Electronics Nv | Adaptable inverter |
| US7746337B2 (en) | 2005-11-17 | 2010-06-29 | Samsung Electronics Co., Ltd. | Inverter circuit |
| JP2007174881A (en) * | 2005-12-22 | 2007-07-05 | Samsung Electronics Co Ltd | Inverter circuit, backlight device, and liquid crystal display device made thereby |
| KR101178833B1 (en) | 2005-12-22 | 2012-09-03 | 삼성전자주식회사 | Inverter circuit, backlight device, and liquid crystal display device using the same |
| JPWO2013061800A1 (en) * | 2011-10-25 | 2015-04-02 | 株式会社村田製作所 | Inverter device |
| US9484841B2 (en) | 2011-10-25 | 2016-11-01 | Murata Manufacturing Co., Ltd. | Inverter device |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| US4257087A (en) | DC-to-DC switching converter with zero input and output current ripple and integrated magnetics circuits | |
| EP2056438A2 (en) | Switching power supply | |
| JP2003520407A (en) | Power feedback power factor correction scheme for multiple lamp operation. | |
| EP1071199A3 (en) | Power supply | |
| JP3404384B2 (en) | Piezoelectric transformer inverter | |
| US6018221A (en) | Lighting circuit and lighting device | |
| EP0855132B1 (en) | Circuit arrangement | |
| US4609850A (en) | Current driven gain controlled electronic ballast system | |
| JPH10164861A (en) | Resonance inverter circuit | |
| US5309350A (en) | Push-pull inverter | |
| JP5176767B2 (en) | Switching power supply | |
| KR20170104434A (en) | Resonance-type dc-dc converter | |
| JP7409344B2 (en) | Contactless power transmission device and its adjustment method | |
| JP3610842B2 (en) | Power supply device | |
| JPH0833353A (en) | Push-pull inverter | |
| WO2023007839A1 (en) | Output stabilizing circuit and dc/dc converter circuit | |
| JP3656449B2 (en) | Power supply | |
| JP3259337B2 (en) | Power converter | |
| JP2605327Y2 (en) | Cold cathode tube lighting device | |
| KR20040052939A (en) | Adaptive High Frequency Power Supply Using Multi-Resonance | |
| JPH0315434B2 (en) | ||
| KR20220122915A (en) | Three phase and single phase compatible charger | |
| JPH0538151A (en) | Resonance power circuit | |
| JPH04340364A (en) | Switching regulator | |
| JPH10149887A (en) | Fluorescent lamp lighting circuit |