JPH0435550A - Interference wave eliminating device - Google Patents

Abstract

PURPOSE:To effectively eliminate both of a wide-band interference wave included in a reception signal in an arbitrary d/U and the multipath distortion by providing a diversity switch which takes a first discrimination signal and the output signal of a delay element as the input and selects and outputs of one of them. CONSTITUTION:This device consists of matching filters 1 and 2, discrimination feedback equalizers 3 and 4, a convoluter 5, a diversity switch 6, a subtractor 7, an AGC amplifier 8, multipliers 9 and 10, correlators 11 and 12, subtractors 13 and 14, and a delay element 15 having a delay times gamma. A desired signal replica is substracted from a reception signal without anti-phase synthesis of interference waves to extract an interference component, and this interference component is controlled and is subtracted from the reception signal to eliminate the interference wave. Consequently, the desired signal subjected to the multipath distortion is not affected by interference wave elimination. Thus, both of the wide-band interference wave included in the reception signal in an arbitrary D/U and the multipath distortion are effectively eliminated.

Description

【発明の詳細な説明】 （産業上の利用分野） 本発明はダイバーシティ方式を用いる干渉波除去装置に
関し、特にマルチパスフェージング回線において強い干
渉波が存在した場合にフェージングによる波形歪の適応
等化および干渉波の除去を行なう干渉波除去装置に関す
る。DETAILED DESCRIPTION OF THE INVENTION (Industrial Application Field) The present invention relates to an interference wave removal device using a diversity method, and in particular to adaptive equalization of waveform distortion due to fading and The present invention relates to an interference wave removal device that removes interference waves.

（従来の技術） 従来、ＰＳＫやＱＡＭを用いたディジタルマイクロ波回
線に対してＦＭ回線による干渉や、隣接チャンネルから
の干渉あるいは妨害波などが問題となることがある。特
にディジタル伝送が高速の場合、ＦＭ干渉波は狭帯域干
渉波と見なされるが、それ以外の干渉波は広い帯域の場
合がある。また、強度のマルチパスフェージング回線に
おいてはダイバーシティ方式や適応等化技術が不可欠で
あり、見通し外通信のように伝搬距離が大きな回線では
整合フィルタ（ＭＰ）と判定帰還形等化器（ＤＦＥ）と
を用いた受信機が必要となる。マルチパスフェージング
環境下での広帯域干渉波の除去を行なう従来の干渉波除
去装置の一例を第８図に示す。(Prior Art) Conventionally, digital microwave lines using PSK or QAM have sometimes had problems such as interference by FM lines, interference from adjacent channels, or interference waves. Particularly when digital transmission is high-speed, FM interference waves are considered narrowband interference waves, but other interference waves may have a wide band. In addition, diversity methods and adaptive equalization techniques are essential for strong multipath fading lines, and matched filters (MPs) and decision feedback equalizers (DFEs) are required for lines with long propagation distances such as non-line-of-sight communications. A receiver using this is required. FIG. 8 shows an example of a conventional interference wave removal device that removes broadband interference waves under a multipath fading environment.

第８図において、８０１と８０２は乗算器、８０３は加
算器、８０４は減算器、８０５はへ〇Ｃ増幅器、８０６
と８０７は相関器、８０８と８０９はＡＧＣ増幅器、８
１０は切換え器、８１１は整合フィルタ、８１２は判定
帰還形等化器である。In FIG. 8, 801 and 802 are multipliers, 803 is an adder, 804 is a subtracter, 805 is a C amplifier, and 806
and 807 are correlators, 808 and 809 are AGC amplifiers, 8
10 is a switch, 811 is a matched filter, and 812 is a decision feedback equalizer.

この従来の干渉波除去装置はダイバーシティ受信方式を
用いており、２重ダイバーシティ合成後にその合成信号
を適応整合フィルタ（ＭＦ）８１１と判定帰還型等止器
（ＤＦＥ）８１２とを通過させて受信信号に含まれる干
渉波を除去する。ダイバーシティ合成は加算器８０３に
より行われ、その合成方式は最大比合成である。各ダイ
バーシティ入力すなわち入力１と入力２とにそれぞれ入
力する受＠信号８２１．８２２は、ＡＧＣ増幅器８０８
と８０９によりフラットフェージングによるレベル変動
を除かれ、さらに加算器８０３において最大比合成され
るように乗算器８０１と８０２により複素タップ係数８
２３，８２４がそれぞれ乗じられる。これらのタップ係
数は相関器８０６および８０７で生成される信号であり
、それぞれダイバーシティ合成後のＡＧＣ増幅器８０５
の出力と、ＡＧＣ増幅器８０８，８０９の出力との間の
相関値である。受信信号中に干渉波が存在しない時は、
切換え器８１０はＡ　Ｇ　Ｃｊ１幅器８０５の出力を選
択して出力し、ＭＦ８１１に受信信号を供給し　ＭＦ８
１１によりＳＮ比が最大化され、ＤＦＥ８１２によりマ
ルチパスフェージングによる波形歪が除去される。This conventional interference wave canceling device uses a diversity reception method, and after double diversity combining, the combined signal is passed through an adaptive matched filter (MF) 811 and a decision feedback equalizer (DFE) 812 to generate a received signal. Removes interference waves contained in. Diversity combining is performed by adder 803, and its combining method is maximum ratio combining. The received signals 821 and 822 input to each diversity input, that is, input 1 and input 2, are sent to the AGC amplifier 808.
and 809 remove level fluctuations due to flat fading, and multipliers 801 and 802 add complex tap coefficients 8 to
They are multiplied by 23 and 824, respectively. These tap coefficients are signals generated by correlators 806 and 807, and are respectively generated by AGC amplifier 805 after diversity combining.
This is a correlation value between the output of the AGC amplifier 808 and the output of the AGC amplifier 808, 809. When there is no interference wave in the received signal,
The switch 810 selects and outputs the output of the A G Cj1 width switch 805, and supplies the received signal to the MF811.
11 maximizes the SN ratio, and DFE 812 removes waveform distortion due to multipath fading.

第８図の従来の干渉波除去装置において、受信信号中に
広帯域でＤ／Ｕ比（干渉波と希望波の比）がマイナスと
なるような強力な干渉波が存在する場合、切換え器８１
０は減算器８０４の出力を選択して出力する。この減算
器８０４は、乗算器８０１の出力から乗算器８０２の出
力を減じており、加算器８０３が位相について同相合成
を行うのに対し、減算器８０４は逆相合成を行うことで
１渉波の除去を行う。In the conventional interference wave canceling device shown in FIG.
0 selects and outputs the output of the subtracter 804. This subtracter 804 subtracts the output of the multiplier 802 from the output of the multiplier 801, and while the adder 803 performs in-phase synthesis of the phase, the subtracter 804 performs anti-phase synthesis. Perform the removal of.

第９図にその干渉波除去の動作を示す、（ａ）と（ｄ）
はそれぞれダイバーシティルートエ２の入力１，２を示
している。ここで、各ルートの希望波をそれぞれＳｉ、
８２とし、干渉波をＪｌ。Figure 9 shows the interference wave removal operation (a) and (d).
indicate inputs 1 and 2 of diversity route 2, respectively. Here, the desired waves of each route are Si,
82, and the interference wave is Jl.

Ｊ２とする。Ｄ／Ｕがマイナスとなるくらい干渉波が大
きい時には干渉波どうしが同相合成されるように制御さ
れ、（ｂ）と（ｅ）に示すように、乗算器８０１と８０
２の出力において干渉波Ｊ１とＪ２とが振幅および位相
が等しくなる。この場合、（Ｃ）に示す加算器８０３の
出力は、干渉波どうしの同相合成を示している。一方、
（ｆ）に示すように減算器８０４では干渉波どうしが逆
相合成され、干渉波が除去されて希望信号波のみ抽出さ
れている。しかし、希望波Ｓ１と８２については、最大
比合成のみならず同相合成すら行なわれないことになる
。特に、希望波Ｓと干渉波Ｊとの位相関係により、希望
信号波が消えることがある。入カニと２が（ｇ）と（Ｊ
）に示すようにＳとＪとの振幅位相関係が同じ場合、乗
算器８０１と８０２の出力は（ｈ）と（ｋ）に示すよう
に一致する。この時、加算器８０３の出力は（ｉ）に示
すようにＳもＪも同相合成で、減算器８０４の出力は（
ｊ　）に示すようにＳＬ、Ｊも逆相合成となる。すなわ
ち干渉波は除去されているが、希望信号波も消失するこ
とになる。Let's call it J2. When the interference waves are large enough to make D/U negative, the interference waves are controlled to be combined in phase, and as shown in (b) and (e), multipliers 801 and 80
At the second output, the interference waves J1 and J2 have the same amplitude and phase. In this case, the output of adder 803 shown in (C) represents in-phase combination of interference waves. on the other hand,
As shown in (f), in the subtracter 804, the interference waves are combined in reverse phase, the interference waves are removed, and only the desired signal wave is extracted. However, for the desired waves S1 and 82, not only maximum ratio combining but also in-phase combining is not performed. In particular, the desired signal wave may disappear due to the phase relationship between the desired signal S and the interference wave J. Irikani and 2 are (g) and (J
), when the amplitude phase relationship between S and J is the same, the outputs of multipliers 801 and 802 match as shown in (h) and (k). At this time, the output of the adder 803 is the in-phase combination of both S and J as shown in (i), and the output of the subtracter 804 is (
As shown in j), SL and J are also synthesized in reverse phase. In other words, although the interference wave is removed, the desired signal wave also disappears.

また、この従来の干渉波除去装置は、Ｄ／Ｕがマイナス
の領域でしか干渉波を除去できず、Ｄ／Ｕがプラスにな
ると、希望信号波に制御がかかつてしまって干渉波につ
いて逆相合成できない。In addition, this conventional interference wave removal device can only remove interference waves in the region where D/U is negative, and when D/U becomes positive, the desired signal wave is over-controlled, and the interference wave is out of phase. Cannot be synthesized.

（発明が解決しようとする課題） 上述した従来の干渉波除去装置では、受信信号に含まれ
る干渉波を除去しようとすると、希望波についてダイバ
ーシティの最大比合成または同相合成が行なわれないか
ら、マルチパスフェージング回線での適応等化による最
適受信と干渉波除去とが両立せず、場合によっては希望
信号を消失させてしまう場合がある。また、干渉波を除
去できるのはＤ／Ｕがマイナスの領域に限られると言う
欠点がある。(Problem to be Solved by the Invention) In the above-mentioned conventional interference wave canceling device, when trying to cancel the interference waves included in the received signal, maximum ratio diversity combining or in-phase combining is not performed for the desired signal, so multi-purpose interference wave canceling equipment is used. Optimal reception by adaptive equalization on a path fading line and interference wave removal are not compatible, and in some cases, the desired signal may be lost. Another disadvantage is that interference waves can only be removed in areas where D/U is negative.

そこで本発明の目的は、任意のＤ／Ｕにおいて受信信号
に含まれる広帯域干渉波とマルチパス歪の両方を効果的
に除去することができる干渉波除去装置を揚供すること
にある。SUMMARY OF THE INVENTION Therefore, an object of the present invention is to provide an interference wave removal device that can effectively remove both wideband interference waves and multipath distortion contained in a received signal in any D/U.

（課題を解決するための手段） 本発明に係る第１の干渉波除去装置は、２つのルートを
設定してそれぞれのルートの受信出力を切換える切換え
ダイバーシティ方式の干渉波検出装置であって、時間τ
の遅延が与えられて送イハされた希望信号および第１の
干渉波でなる第１の受信信号と第１の推定干渉波との差
である第１の差信号を生成する第１の減算器と、遅延が
与えられることなく送信された希望信号および第２の干
渉波でなる第２の受信信号と第２の推定干渉波との差で
ある第２の差信号を生成する第２の減算器と、前記第１
の差信号と第１の判定信号とから第１のルートの伝送系
のインパルス応答を推定して推定インパルス応答を得る
と共に該推定インパルス応答の時間反転で複素共役な＆
ｉ５答と前記第１の差信号とを畳込んだ第１の整合信号
を得る第１の整合フィルタと、前記第２の差信号と第２
の判定信号とから推定する第２のルートの伝送系のイン
パルス応答の時間反転で複素共役な応答と前記第２の差
信号とを畳込んだ第２の整合信号を得る第２の整合フィ
ルタと、前記第１の整合信号を適応等化して前記第１の
判定信号を得る第１の判定帰還形等化器と、前記第２の
整合信号を適応等化して前記第２の判定信号を得る第２
の判定帰還形等化器と、前記推定インパルス応答と前記
第２の判定信号とを畳込んで推定希望信号を得る畳込み
器と、前記第１の受信信号と前記推定希望信号との差を
取って干渉波成分を抽出する第３の減算器と　前記干渉
波成分の振幅を１に正規化して正規化干渉波成分を得る
ＡＧＣ増幅器と、前記第１の受信信号と前記正規化干渉
波成分との相関を取って第１の相関値を得る第１の相関
器と、前記第２の受信信号と前記正規化干渉波成分との
相関を取って第２の相関値を得る第２の相関器と、前記
正規化干渉波成分に前記第１の相関値を乗じて前記第１
の推定干渉波を得る第１の乗算器ど、前記正規化干渉波
成分に前記第２の相関値を乗じて前記第２の推定干渉波
を得る第２の乗算器と、前記ｗＳ２の判定信号に時間τ
の遅延を与える遅延素子と、前記第１の判定信号と前記
遅延素子の出力信号とを入力していずれか一方の信号を
選択して出力するダイバーシティルート切換え器とから
なることを特徴とする特 本発明に偽る第２の干渉波除去装置は、２つのルートを
設定１．てそれぞれのルーｌ、の受信出力を切換える切
換えダイバーシティ方式の干渉波除去装置であって、時
間τの遅延が与えられて送信された希望信号および第１
の干渉波でなる第１の受信信号と第１の推定干渉波との
差である第１の差信号を生成する第１の減算器と、遅延
が与えられることなく送信された希望信号および第２の
干渉波でなる第２の受信信号と第２の推定干渉波との差
である第２の差信号を生成する第２の減算器と、前記第
１の差信号と第１の基準信号とから第１のルートの伝送
系のインパルス応答を推定し２て推定インパルス応答を
得ると共に該推定インパルス応答の時間反転で複素共役
な応答と前記第１の差信号とを畳込んだ第１の整合信号
を得る第１の整合フィルタと、前記第２の差信号と第２
の基準信号とから推定する第２のルートの伝送系のイン
パルス応答の時間反転で複素共役な応答と前記第２の差
信号とを畳込んだ第２の整合信号を得る第２の整合フィ
ルタと、前記第１の基準信号を用いて前記第１の整合信
号を適応等化して第１の判定信号と判定結果の第１の誤
差信号とを得る第１の判定帰還形振化器と、前記第２の
基準信号を用いて前記＄２の整合信号を適応等化して第
２の判定信号と判定結果の第２の誤差信号とを得る第２
の判定帰還形振化器と、前記推定インパルス応答と前記
第２の基準信号とを畳込んで推定希望信号を得る畳込み
器と、前記第１の受信信号と前記播定希ＩＪ信号の差を
取って、干渉波成分を抽出する第３の減算器と、仮定し
た送信シンボル列を表すトレーニング信号を発生するト
レーニング信号発生器と、前記トレーニング信号に時間
υの遅延を与える第１の遅延素子ど、前記第１の誤差信
号に応じて前記第１の判定信号と前記第１の遅延素子の
出力信号のいずれか一方を選択して前記第１の基準信号
として出力する第１の切換え器と５前記第２の誤差信号
に応じて前記第２の判定信号と前記トレーニング信号の
いずれか一方を選択して前記第２の基準信号として出力
する第２の切換え器と、前記干渉波成分の振幅を１に正
規化して正規化Ｆ渉波成分を得るＡＧＣ増幅器と、前記
第１の受信信号と前記正規化干渉波成分との相関を取っ
て第１の相関値を得る第１の相関器と、前記第２の受信
信号と前記正規化干渉波成分との相関を取って第２の相
関値を得る第２の相関器と、前記正規化干渉波成分に前
記第１の相関値を乗じて前記第１の推定干渉波を得る第
１の乗算器と、前記正規化干渉波成分に前記第２の相関
値を乗じて前記第２の推定干渉波を得る第２の乗算器と
、前記第２の判定信号に時間τの遅延を与える第２の遅
延素子ど、前記第１の判定信号と前記第２の遅延素子の
出力信号とを入力していずれが一方の信号を選択して出
力するダイバージティル・−ト切換え器とからなること
を特徴とする。(Means for Solving the Problems) A first interference wave removal device according to the present invention is a switching diversity type interference wave detection device that sets two routes and switches the reception output of each route, and τ
a first subtracter that generates a first difference signal that is the difference between a first received signal consisting of the desired signal and the first interference wave and the first estimated interference wave, which are transmitted with a delay of and a second subtraction to generate a second difference signal that is the difference between the second estimated interference wave and a second received signal consisting of the desired signal and the second interference wave transmitted without any delay being applied. and the first
The impulse response of the transmission system of the first route is estimated from the difference signal and the first determination signal to obtain an estimated impulse response, and the complex conjugate &
a first matched filter that obtains a first matched signal that is a convolution of the i5 answer and the first difference signal;
a second matched filter that obtains a second matched signal by convolving the second difference signal with a time-reversed, complex conjugate response of the impulse response of the second route transmission system estimated from the decision signal; , a first decision feedback equalizer that adaptively equalizes the first matching signal to obtain the first decision signal; and a first decision feedback equalizer that adaptively equalizes the second matching signal to obtain the second decision signal. Second
a decision feedback equalizer, a convolver that convolves the estimated impulse response and the second decision signal to obtain an estimated desired signal, and a convolver that calculates the difference between the first received signal and the estimated desired signal. an AGC amplifier that normalizes the amplitude of the interference wave component to 1 to obtain a normalized interference wave component; and an AGC amplifier that normalizes the amplitude of the interference wave component to 1 to obtain a normalized interference wave component; a first correlator that obtains a first correlation value by taking a correlation between the second received signal and the normalized interference wave component; and a second correlator that obtains a second correlation value by taking a correlation between the second received signal and the normalized interference wave component. and the normalized interference wave component is multiplied by the first correlation value to obtain the first correlation value.
a first multiplier for obtaining an estimated interference wave, a second multiplier for obtaining the second estimated interference wave by multiplying the normalized interference wave component by the second correlation value, and a determination signal of the wS2. time τ
and a diversity route switch that inputs the first determination signal and the output signal of the delay element and selects and outputs one of the signals. The second interference wave removal device which is based on the present invention sets two routes: 1. A switching diversity type interference wave canceling device that switches the received output of each rule L, and the interference wave canceling device is a switching diversity type interference wave canceling device that switches the received output of each rule L,
a first subtractor that generates a first difference signal that is the difference between a first received signal consisting of an interference wave and a first estimated interference wave; a second subtracter that generates a second difference signal that is the difference between a second received signal consisting of two interference waves and a second estimated interference wave, and the first difference signal and the first reference signal. estimate the impulse response of the transmission system of the first route from a first matched filter that obtains a matched signal; a first matched filter that obtains a matched signal;
a second matched filter that obtains a second matched signal by convolving the second difference signal with a time-reversed complex conjugate response of the impulse response of the second route transmission system estimated from the reference signal; , a first decision feedback type oscillator that adaptively equalizes the first matching signal using the first reference signal to obtain a first decision signal and a first error signal of the decision result; A second method for adaptively equalizing the matching signal of $2 using a second reference signal to obtain a second judgment signal and a second error signal of the judgment result.
a decision feedback type oscillator, a convolver that obtains an estimated desired signal by convolving the estimated impulse response and the second reference signal, and a difference between the first received signal and the random IJ signal. a third subtractor that extracts interference wave components by extracting interference wave components; a training signal generator that generates a training signal representing an assumed transmission symbol sequence; and a first delay element that delays the training signal by a time υ. a first switch that selects either the first determination signal or the output signal of the first delay element according to the first error signal and outputs the selected signal as the first reference signal; 5 a second switch that selects either the second determination signal or the training signal according to the second error signal and outputs it as the second reference signal; and an amplitude of the interference wave component. an AGC amplifier that normalizes F to 1 to obtain a normalized interference wave component, and a first correlator that obtains a first correlation value by correlating the first received signal and the normalized interference wave component. , a second correlator that obtains a second correlation value by correlating the second received signal and the normalized interference wave component; a first multiplier for obtaining the first estimated interference wave; a second multiplier for obtaining the second estimated interference wave by multiplying the normalized interference wave component by the second correlation value; A second delay element that delays the second determination signal by a time τ inputs the first determination signal and the output signal of the second delay element, and selects and outputs one of the signals. It is characterized by comprising a divergent tilt switch.

本発明に係る第３の干渉波除去装置は、２つのルートを
設定してそれぞれのルートの受信出力を切換える切換え
ダイバーシティ方式の干渉波除去装置て゛あっで、時間
τの遅延が与えられて送信された希望信号および第１の
干渉波でなる第１の受信信号と第１の推定干渉波どの差
である第１の差信Ｊｉ＋を生成する第１の減算器と、遅
延が与えられることなく送信された希望信号および第２
の干渉波でなる第２の受信信号と第２の推定干渉波との
差である第２の差信号を生成する第２の減算器と、前記
第１の差信号と第１の判定信号とから第１のルートの伝
送系のインパルス応答を推定して推定インパルス応答を
得ると共に該推定インパルス応答の時間反転で複素共役
な応答と前記第１の差信号とを畳込Ｘ７だ第１の整合信
号を得る第１の整合フィルタど、前記第２の差信号と第
２の判定信号とから推定する第２のルートの伝送系のイ
ンパルス応答の時間反転で複素共役な応答と前記第２の
差信号とを管込んだ第２の整合信号を得る第２の整合フ
ィルタと、前記第１の整合信号を適応等化して前記第１
の判定信号と判定結果の第１の誤差信号とを得る第１の
判定帰還形振化器と、前記第２の整合信号を適応等化し
て前記第２の判定信号と判定結果の第２の誤差信号とを
得る第２の判定帰還形振化器ど、前記推定インパルス応
答と前記第２の判定信号とを畳込んで推定希望信号を得
る畳込み器と、前記第１の受信信号と前記推定希望信号
との差を取って干渉波成分を抽出する第３の減算器と、
前記第１の誤差信号と前記干渉波成分との相関を取って
第１の相関値を得る第１の相関器と、前記第２り誤差信
号と前記干渉波成分との相関を取って第２の相関値を得
る第２の相関器と、前記干渉波成分に前記第１の相関値
を乗じて前記第１の推定干渉波を得る第１の乗算器と、
前記干渉波成分に前記第２の相関値を乗じて前記第２の
推定干渉波を得る第２の乗算器と、前記第２の判定信号
に時間τの遅延を与える遅延素子と、前記第１の判定信
号と前記遅延素子の出力信号とを入力していずれか一方
の信号を選択して出力するダイバーシティルート切換え
器とからなることを特徴とする。The third interference wave canceling device according to the present invention is a switching diversity type interference wave canceling device that sets two routes and switches the reception output of each route, and transmits with a delay of time τ. a first subtracter that generates a first difference signal Ji+, which is the difference between a first received signal consisting of a desired signal and a first interference wave, and a first estimated interference wave; desired signal and the second
a second subtracter that generates a second difference signal that is a difference between a second received signal consisting of an interference wave and a second estimated interference wave; to obtain an estimated impulse response by estimating the impulse response of the transmission system of the first route, and convolving the time-reversed complex conjugate response of the estimated impulse response with the first difference signal. A first matched filter for obtaining a signal, etc., calculates the difference between the time-reversed and complex conjugate response of the impulse response of the transmission system of the second route estimated from the second difference signal and the second determination signal, and the second difference. a second matched filter that adaptively equalizes the first matched signal and obtains a second matched signal including the first matched signal;
a first decision feedback type vibration generator that obtains a decision signal and a first error signal of the decision result, and adaptively equalizes the second matching signal to obtain the second decision signal and a second error signal of the decision result. a second decision feedback type oscillator for obtaining an error signal; a convolver for obtaining an estimated desired signal by convolving the estimated impulse response and the second decision signal; a third subtractor that extracts an interference wave component by taking the difference from the estimated desired signal;
a first correlator that correlates the first error signal and the interference wave component to obtain a first correlation value; and a second correlator that correlates the second error signal and the interference wave component to obtain a first correlation value. a second correlator that obtains a correlation value; a first multiplier that multiplies the interference wave component by the first correlation value to obtain the first estimated interference wave;
a second multiplier that multiplies the interference wave component by the second correlation value to obtain the second estimated interference wave; a delay element that delays the second determination signal by a time τ; and a diversity route switching device which inputs the determination signal of and the output signal of the delay element, selects one of the signals, and outputs the selected signal.

本発明に係る第４の干渉波除去装置は、２つのルートを
設定してそれぞれのルートの受信出力を切換える切換え
ダイバーシティ方式の干渉波除去装置であって、時間τ
の遅延が与えられて３！！信された希望信号および第１
の干渉波でなる第１の受信信号と第１の推定干渉波との
差である第１の差信号を生成する第１の減算器と、遅延
が与えられることなく送信された希望信号および第２の
干渉波でなる第２の受信信号と第２の推定干渉波との差
である第２の差信号を生成する第２の減算器と、前記第
１の差信号と第１の基準信号とから第１のルートの伝送
系のインパルス応答を推定して推定インパルス応答を得
ると共に該推定インパルス応答の時間反転で複素共役な
応答と前記第１の差信号とを畳込んだ第１の整合信号を
得る第１の整合フィルタと、前記第２の差信号と第２の
基準信号とから推定する第２のルートの伝送系のインパ
ルス応答の時間反転で複素共役な応答と前記第２の差信
号とを畳込んだ第２の整合信号を得る第２の整合フィル
タと、前記第１の基準信号を用いて前記第１の整合信号
を適応等化して第１の判定信号と判定結果の第１の誤差
信号とを得る第１の判定帰還形等化器と、前記第２の基
準信号を用いて前記第２の整合信号を適応等化して第２
の判定信号と判市結果の第２の誤差信号とを得る第２の
判定帰還形等化器と、前記推定インパルス応答と前記第
２の基準信号とを畳込んで推定希望信号を得る畳込み器
と、前記第１の受信信号と前記推定希望信号の差を取っ
て干渉波成分を抽出する第３の減算器と、仮定した送信
シンボル列を表すトレーニング信号を発生するトレーニ
ング信号発生器と、前記トレーニング信号に時間τの遅
延を与える第１の遅延素子と、前記第１の誤差信号に応
じて前記第１の判定信号と前記第１の遅延素子の出力信
号のいずれか一方を選択して前記第１の基準信号として
出力する第１の切換え器と、前記第２の誤差信号に応じ
て前記第２の判定信号と前記トレーニング信号のいずれ
か一方を選択して前記第２の基準信号として出力する第
２の切換え器と、前記第１の誤差信号と前記干渉波成分
との相関を取って第１の相関値を得る第１の相関値と、
前記第２の誤差信号と前記干渉波成分との相関を取って
第２の相関値を得る第２の相関値と、前記干渉波成分に
前記第１の相関値を乗じて前記第１の推定干渉波を得る
第１の乗算器と、前記干渉波成分に前記第２の相関値を
乗じて前記第２の推定干渉波を得る第２の乗算器と、前
記第２の判定信号に時間τの遅延を与える第２の遅延素
子と、前記第１の判定信号と前記第２の遅延素子の出力
信号とを入力していずれか一方の信号を選択して出力す
るダイバーシティルート切換え器とからなることを特徴
とする。A fourth interference wave canceling device according to the present invention is a switching diversity type interference wave canceling device that sets two routes and switches the reception output of each route, and has a time τ
Given the delay of 3! ! The received desired signal and the first
a first subtractor that generates a first difference signal that is the difference between a first received signal consisting of an interference wave and a first estimated interference wave; a second subtracter that generates a second difference signal that is the difference between a second received signal consisting of two interference waves and a second estimated interference wave, and the first difference signal and the first reference signal. and a first matching in which an estimated impulse response is obtained by estimating the impulse response of the transmission system of the first route from a first matched filter for obtaining a signal; a time-reversed complex conjugate response of an impulse response of a second route transmission system estimated from the second difference signal and the second reference signal; and the second difference. a second matched filter that obtains a second matched signal by convolving the first reference signal with the first reference signal; a first decision feedback equalizer that obtains an error signal of 1; and a second decision feedback equalizer that adaptively equalizes the second matching signal using the second reference signal;
a second decision feedback equalizer for obtaining a decision signal and a second error signal of the judgment result; and convolution for obtaining an estimated desired signal by convolving the estimated impulse response and the second reference signal. a third subtractor that extracts an interference wave component by taking the difference between the first received signal and the estimated desired signal; a training signal generator that generates a training signal representing an assumed transmission symbol sequence; a first delay element that delays the training signal by a time τ; and one of the first determination signal and the output signal of the first delay element is selected according to the first error signal. a first switch that outputs the first reference signal; and a first switch that selects either the second determination signal or the training signal as the second reference signal according to the second error signal. a second switching device for outputting, a first correlation value that obtains a first correlation value by correlating the first error signal and the interference wave component;
a second correlation value that obtains a second correlation value by correlating the second error signal and the interference wave component; and the first estimation by multiplying the interference wave component by the first correlation value. a first multiplier that obtains an interference wave; a second multiplier that multiplies the interference wave component by the second correlation value to obtain the second estimated interference wave; and a second multiplier that obtains the second estimated interference wave; a second delay element that provides a delay of It is characterized by

本発明に係る第５の干渉波除去装置は、２つのルートを
設定してそれぞれのルートの受信出力を切換える切換え
ダイバーシティ方式の干渉波検出装置であって、時間τ
の遅延が与えられて送信された希望信号および第１の干
渉波でなる第１の受信信号と第１の推定干渉波との差で
ある第１の差信号を生成する第１の減算器と、遅延か与
えられることなく送信された希望信号および第２の干渉
波でなる第２の受信信号と第２の推定干渉波との差であ
る第２の差信号を生成する第２の減算器と、前記第１の
差信号と第１の判定信号とから第１のルートの伝送系の
インパルス応答を推定して推定インパルス応答を得ると
共に該推定インパルス応答の時間反転で複索共役は応答
と前記第１の差信号とを畳込んだ第１の整合信号を得る
第１の整合フィルタと、前記第２の差信号と第２の判定
信号とから推定する第２のルートの伝送系のインパルス
応答の時間反転で複素共役な応答と前記第２の差信号と
を畳込んだ第２の整合信号を得る第２の整合フィルタと
、前記第１の整合信号を適応等化して前記第１の判定信
号を得る第１の判定帰還形等化器と、前記第２の整合信
号を適応等化して前記第２の判定信号を得る第２の判定
帰還形等化器と、前記推定インパルス応答と前記第２の
判定信号とを畳込んで推定希望信号を得る畳込み器と、
前記第１の受信信号と前記推定希望信号との差を取って
干渉波成分を抽出する第３の減算器と、前記第１の整合
フィルタに入力する前記第１の差信号の電力を検出する
第１の電力検出器と、前記第２の整合フィルタに入力す
る前記第２の差信号の電力を検出する第２の電力検出器
と、前記第１の電力検出器が検出する電力を最小とする
第１のタップ係数を得る第１のタップ係数制御器と、前
記第２の電力検出器が検出する電力を最小とする第２の
タップ係数を得る第２のタップ係数制御器と、前記干渉
波成分に前記第１のタップ係数を乗じて前記第１の推定
干渉波を得る第１の乗算器と、前記干渉波成分に前記第
２のタップ係数を乗じて前記第２の推定干渉波を得る第
２の乗算器と、前記第２の判定信号に時間での遅延を与
える遅延素子と、前記第１の判定信号と前記遅延素子の
出力信号とを入力していずれか一方の信号を選択して出
力するダイバーシティルート切換え器とからなることを
特徴とする。A fifth interference wave removal device according to the present invention is a switching diversity type interference wave detection device that sets two routes and switches the reception output of each route, and has a time τ
a first subtracter that generates a first difference signal that is the difference between the first estimated interference wave and a first received signal consisting of the desired signal and the first interference wave transmitted with a delay of , a second subtractor that generates a second difference signal that is the difference between the second estimated interference wave and a second received signal consisting of the desired signal and the second interference wave transmitted without being delayed; Then, an estimated impulse response is obtained by estimating the impulse response of the transmission system of the first route from the first difference signal and the first determination signal, and by time reversing the estimated impulse response, the complex conjugate is a response. a first matched filter that obtains a first matched signal convoluted with the first difference signal; and a second route transmission system impulse estimated from the second difference signal and the second determination signal. a second matched filter that obtains a second matched signal by convolving the second difference signal with a complex conjugate response by time reversal of the response; and a second matched filter that adaptively equalizes the first matched signal to obtain the first matched signal. a first decision feedback equalizer that obtains a decision signal; a second decision feedback equalizer that adaptively equalizes the second matching signal to obtain the second decision signal; and an estimated impulse response. a convolver that obtains an estimated desired signal by convolving the second determination signal;
a third subtractor that extracts an interference wave component by taking the difference between the first received signal and the estimated desired signal; and detecting the power of the first difference signal input to the first matched filter. a first power detector; a second power detector that detects the power of the second difference signal input to the second matched filter; and a second power detector that minimizes the power detected by the first power detector. a first tap coefficient controller that obtains a first tap coefficient that minimizes the power detected by the second power detector; a second tap coefficient controller that obtains a second tap coefficient that minimizes the power detected by the second power detector; a first multiplier that multiplies the wave component by the first tap coefficient to obtain the first estimated interference wave; and a first multiplier that multiplies the interference wave component by the second tap coefficient to obtain the second estimated interference wave. a second multiplier that provides a time delay to the second determination signal, a delay element that provides a time delay to the second determination signal, and the first determination signal and the output signal of the delay element that are input to select one of the signals. and a diversity route switcher that outputs the same signal.

本発明に係る第６の干渉波除去装置は、２つのルートを
設定してそれぞれのルートの受信出力を切換える切換え
ダイバーシティ方式の干渉波検出装置であって、時間τ
の遅延が与えられて送信された希望信号および第１の干
渉波でなる第１の受信信号と第１の推定干渉波との差で
ある第１の差信号を生成する第１の減算器と、遅延が与
えられることなく送信された希望信号および第２の干渉
波でなる第２の受信信号と第２の推定干渉波との差であ
る第２の差信号を生成する第２の減算器と、前記第１の
差信号と第１の基準信号とから第１のルートの伝送系の
インパルス応答を推定して推定インパルス応答を得ると
共に該推定インパルス応答の時間反転で複素共役な応答
と前記第１の差信号とを畳込んだ第１の整合信号を得る
第１の整合フィルタと、前記第２の差信号と第２の基準
信号とから推定する第２のルートの伝送系のインパルス
応答の時間反転で複素共役な応答と前記第２の差信号と
を畳込んだ第２の整合信号を得る第２の整合フィルタと
、前記第１の基準信号を用いて前記第１の整合信号を適
応等化して第１の判定信号と判定結果の第１の誤差信号
とを得る第１の判定帰還形等化器と、前記第２の基準信
号を用いて前記第２の整合信号を適応等化して第２の判
定信号と判定結果の第２の誤差信号とを得る第２の判定
帰還形等化器と、前記推定インパルス応答と前記第２の
基準信号とを畳込んで推定希望信号を得る畳込み器と、
前記第１の受信信号と前記推定希望信号との差を取って
干渉波成分を抽出する第３の減算器と、仮定した送信シ
ンボル列を表すトレーニング信号を発生するトレーニン
グ信号発生器と、前記トレーニング信号に時間τの遅延
を与える第１の遅延素子と、前記第１の誤差信号に応じ
て前記第１の判定信号と前記第１の遅延素子の出力信号
のいずれか一方を選択して前記第１の基準信号として出
力する第１の切換え器と、前記第２の誤差信号に応じて
前記第２の判定信号と前記トレーニング信号のいずれか
一方を選択して前記第２の基準信号として出力する第２
の切換え器と、前記第１の整合フィルタに入力する前記
第１の差信号の電力を検出する第１の電力検出器と、前
記第２の整合フィルタに入力する前記第２の差信号の電
力を検出する第２の電力検圧器と、前記第１の電力検出
器が検出する電力を最小とする第１のタップ係数を得る
第１のタップ係数制御器と、前記第２の電力検出器が検
出する電力を最小とする第２のタップ係数を得る第２の
タップ係数制御器と、前記干渉波成分に前記第１のタッ
プ係数を乗じて前記第１の推定干渉波を得る第１の乗算
器と、前記干渉波成分に前記第２のタップ係数を乗じて
前記第２の推定干渉波を得る第２の乗算器と、前記第２
の判定信号に時間τの遅延を与える第２の遅延素子と、
前記第１の判定信号と前記第２の遅延素子の出力信号と
を入力していずれか一方の信号を選択して出力するダイ
バーシティルート切換え器とからなることを特徴とする
（実施例） 次に、本発明について図面を参照して説明する。A sixth interference wave removal device according to the present invention is a switching diversity type interference wave detection device that sets two routes and switches the reception output of each route, and has a time τ
a first subtracter that generates a first difference signal that is the difference between the first estimated interference wave and a first received signal consisting of the desired signal and the first interference wave transmitted with a delay of , a second subtractor that generates a second difference signal that is the difference between the second estimated interference wave and a second received signal consisting of the desired signal and the second interference wave transmitted without being given a delay. Then, the impulse response of the transmission system of the first route is estimated from the first difference signal and the first reference signal to obtain an estimated impulse response, and a time-reversed complex conjugate response of the estimated impulse response and the above-mentioned a first matched filter that obtains a first matched signal convolved with the first difference signal; and an impulse response of the transmission system of the second route estimated from the second difference signal and the second reference signal. a second matched filter that obtains a second matched signal by convolving the time-reversed complex conjugate response of the second difference signal with the second difference signal; a first decision feedback equalizer that performs adaptive equalization to obtain a first decision signal and a first error signal of the decision result; and a first decision feedback equalizer that adaptively equalizes the second matching signal using the second reference signal. a second decision feedback equalizer that obtains a second decision signal and a second error signal of the decision result; and a second decision feedback equalizer that convolves the estimated impulse response and the second reference signal to obtain an estimated desired signal. A convolver that obtains
a third subtractor that extracts an interference wave component by taking the difference between the first received signal and the estimated desired signal; a training signal generator that generates a training signal representing an assumed transmission symbol sequence; a first delay element that delays the signal by a time τ; and a first delay element that selects one of the first determination signal and the output signal of the first delay element according to the first error signal. a first switch that outputs the first reference signal as the second reference signal; and a first switch that selects either the second determination signal or the training signal according to the second error signal and outputs the selected signal as the second reference signal. Second
a switch, a first power detector that detects the power of the first difference signal input to the first matched filter, and a power of the second difference signal input to the second matched filter. a second power voltage detector that detects the power detected by the first power detector; a first tap coefficient controller that obtains a first tap coefficient that minimizes the power detected by the first power detector; a second tap coefficient controller that obtains a second tap coefficient that minimizes detected power; and a first multiplier that multiplies the interference wave component by the first tap coefficient to obtain the first estimated interference wave. a second multiplier that obtains the second estimated interference wave by multiplying the interference wave component by the second tap coefficient;
a second delay element that provides a delay of time τ to the determination signal;
(Embodiment) The device is characterized by comprising a diversity route switch that inputs the first determination signal and the output signal of the second delay element and selects and outputs one of the signals (embodiment). , the present invention will be explained with reference to the drawings.

第１ｒＭは本発明に係る第１の干渉波除去装置の一実ｍ
鍔の構成を示すブロック図である。第２図は本発明に係
る第２の干渉波除去装置の一実施例の構成を示すブロッ
ク図である。第３図は本発明に係る第３の干渉波除去装
置の一実施例の構成を示すブロック図である。第４図は
本発明に係る第４の干渉波除去装置の一実施例の構成を
示すブロック図である。第５図は本発明に係る第５の干
渉波除去装置の一実施例の構成を示すブロック図である
。第６図は本発明に係る第６の干渉波除去装置の一実施
例の構成を示すブロック図である。The first rM is a part of the first interference wave removal device according to the present invention m
FIG. 3 is a block diagram showing the configuration of the tsuba. FIG. 2 is a block diagram showing the configuration of an embodiment of the second interference wave removal device according to the present invention. FIG. 3 is a block diagram showing the configuration of an embodiment of a third interference wave removal device according to the present invention. FIG. 4 is a block diagram showing the configuration of an embodiment of the fourth interference wave removal device according to the present invention. FIG. 5 is a block diagram showing the configuration of an embodiment of the fifth interference wave removal device according to the present invention. FIG. 6 is a block diagram showing the configuration of an embodiment of the sixth interference wave removal device according to the present invention.

第１図において、１と２は整合フィルタ（ＨＦ）、３と
４は判定帰還形等化器（ＤＦＥ＞　、５は畳込み器、６
はダイバーシティルート切換え器、７は減算器、８はＡ
ＧＯ増幅器、９と１０は乗算器、１１と１２は相関器、
１３と１４は減算器、１５はτの遅延時間を有する遅延
素子である。In Figure 1, 1 and 2 are matched filters (HF), 3 and 4 are decision feedback equalizers (DFE>, 5 is a convolution device, and 6 is a
is a diversity route switcher, 7 is a subtracter, 8 is A
GO amplifier, 9 and 10 are multipliers, 11 and 12 are correlators,
13 and 14 are subtracters, and 15 is a delay element having a delay time of τ.

第２図において、２０１と２０２は整合フィルタ（ＭＦ
）、２０３と２０４は判定帰還形等化器（ＤＦＥ）、２
０５は畳込み器、２０６はダイバーシティルート切換え
器、２０７は減算器、２０８はＡＧＣ増幅器、２０９と
２１０は乗算器、２１１と２１２は相関器、２１３と２
１４は減算器、２１５はτの遅延時間を有する遅延素子
、２１６はトレーニング信号発生器、２１７はτの遅延
時間を有する遅延素子、２１８と２１９は切換え器、２
２０と２２１は制御器である。In FIG. 2, 201 and 202 are matched filters (MF
), 203 and 204 are decision feedback equalizers (DFE), 2
05 is a convolver, 206 is a diversity route switcher, 207 is a subtracter, 208 is an AGC amplifier, 209 and 210 are multipliers, 211 and 212 are correlators, 213 and 2
14 is a subtracter; 215 is a delay element having a delay time of τ; 216 is a training signal generator; 217 is a delay element having a delay time of τ; 218 and 219 are switchers;
20 and 221 are controllers.

第３図において、３０１と３０２は整合フィルタ（ＭＦ
）、３０３と３０４は判定帰還形等化器（ＤＦＥ）、３
０５は畳込み器、３０６はダイバーシティルート切換え
器、３０７は減算器、３０８はτの遅延時間を有する遅
延素子、３０９と３１０は乗算器、３１１と３１２は相
関器、３１３と３１４は減算器である。In FIG. 3, 301 and 302 are matched filters (MF
), 303 and 304 are decision feedback equalizers (DFE), 3
05 is a convolution device, 306 is a diversity route switcher, 307 is a subtracter, 308 is a delay element having a delay time of τ, 309 and 310 are multipliers, 311 and 312 are correlators, and 313 and 314 are subtracters. be.

第４図において、４０１と４０２は整合フィルタ（ＭＦ
）、４０３と４０４は判定帰還形等化器（ＤＦＥ）、４
０５は畳込み器、４０６はダイバーシティルート切換え
器、４０７は減算器、４０８はτの遅延時間を有する遅
延素子、４０９と４１０は乗算器、４１１と４１２は相
関器、４１３と４１４は減算器、４１５はトレーニング
信号発生器、４１６と４１７は切換え器、４１８と４１
９は制御器、４２０はτの遅延時間を有する遅延素子で
ある。In FIG. 4, 401 and 402 are matched filters (MF
), 403 and 404 are decision feedback equalizers (DFE), 4
05 is a convolution device, 406 is a diversity route switcher, 407 is a subtracter, 408 is a delay element having a delay time of τ, 409 and 410 are multipliers, 411 and 412 are correlators, 413 and 414 are subtracters, 415 is a training signal generator, 416 and 417 are switchers, 418 and 41
9 is a controller, and 420 is a delay element having a delay time of τ.

第５図において、５０１と５０２は整合フィルタ（ＭＰ
）、５０３と５０４は判定帰還形等化器＜ＤＦＥ）、５
０５は畳込み器、５０６はダイバーシティルート切換え
器、５０７は減算器、５０８はτの遅延時間を有する遅
延素子、５０９と５１０は乗算器、５１１と５１２はタ
ップ係数制御器、５１３と５１４は減算器、５１５と５
１６は電力検出器である。In FIG. 5, 501 and 502 are matched filters (MP
), 503 and 504 are decision feedback equalizers <DFE), 5
05 is a convolution device, 506 is a diversity route switcher, 507 is a subtracter, 508 is a delay element having a delay time of τ, 509 and 510 are multipliers, 511 and 512 are tap coefficient controllers, and 513 and 514 are subtractors. vessel, 515 and 5
16 is a power detector.

第６図において、６０１と６０２は整合フィルタ（ＭＰ
）、６０３と６０４は判定帰還形等化器（ＤＰＥ）、６
０５は畳込み器、６０６はダイバーシティルート切換え
器、６０７は減算器、６０８はτの遅延時間を有する遅
延素子、６０９と６１０は乗算器、６１１と６１２はタ
ップ係数制御器、６１３と６１４は減算器、６１５と６
１６は電力検出器、６１７はトレーニング信号発生器、
６１８はτの遅延時間を有する遅延素子、６１９と６２
０は切換え器、６２１と６２２は制御器である。In FIG. 6, 601 and 602 are matched filters (MP
), 603 and 604 are decision feedback equalizers (DPE), 6
05 is a convolution device, 606 is a diversity route switcher, 607 is a subtracter, 608 is a delay element having a delay time of τ, 609 and 610 are multipliers, 611 and 612 are tap coefficient controllers, 613 and 614 are subtractors vessel, 615 and 6
16 is a power detector, 617 is a training signal generator,
618 is a delay element having a delay time of τ, 619 and 62
0 is a switch, and 621 and 622 are controllers.

本発明は２重ダイバーシティ方式を用いており、送信側
において、２重ダイバーシティのうち第１のルートのシ
ンボル列を第２のルートに対してτだけ遅延させて送信
する０本発明に係る干渉波除去装置は受信側となる。The present invention uses a double diversity system, and on the transmitting side, the symbol sequence of the first route of the double diversity is delayed by τ with respect to the second route and transmitted. The removal device becomes the receiving side.

第１図の実施例において、第１のダイバーシティルート
の送信シンボル列をａ、（ｎ＝−ω・・・十ω）、ＭＦ
ｌに入力されるまでの伝送系のインパルス応答の離散値
をり、とすると、受信信号１０３の離散値ｒ、は、 で示される。ここで、Ｊｌはルート１の干渉波を示す、
干渉波については任意のレベルを有する広帯域干渉とす
る。また、その発生源は１つで、この干渉波をＪとし、
ルート１の干渉波をＪ１＝Ａ１ｅｘｐ　　（Ｊφ１　）
　−Ｊ　　　　　　−（２）でモデル化する。ここで、
Ａｌｅｘｐ（Ｊφ１）はＪに対するルート１の伝達間数
である。同様に、ルート２に対しても干渉波を Ｊ２＝Ａ２１３ＸＤ　　（Ｊφ２　）　−Ｊ　　　　　
　−（３）とおく。In the embodiment of FIG. 1, the transmission symbol sequence of the first diversity route is a, (n=-ω...10ω), MF
If the discrete value of the impulse response of the transmission system until it is input to l is , then the discrete value r of the received signal 103 is expressed as follows. Here, Jl indicates the interference wave of route 1,
The interference wave is broadband interference having an arbitrary level. Also, there is only one source, and this interference wave is J,
Route 1 interference wave is J1=A1exp (Jφ1)
-J-(2). here,
Alexp(Jφ1) is the number of transmissions of route 1 for J. Similarly, for route 2, the interference wave is J2=A213XD (Jφ2) −J
- (3).

△ ＭＦＩは判定信号ａ、１０７と（１）式で示される受信
信号１０３との相関を取ることにより、伝送系のインパ
ルス応答を推定する０次式はその相関過程を示す。ΔMFI takes the correlation between the decision signal a, 107 and the received signal 103 shown by equation (1), and the zero-order equation for estimating the impulse response of the transmission system shows the correlation process.

△ Ｅａｒ、・ａ、′〕 ｋ−一ω ・・・（４） ＭＦＩは、この推定インパルス応答の時間反転で複素共
役な応答ｈ−，。と受信信号１０３とを畳込む操作を行
なう。ΔEar,·a,′] k−1ω (4) MFI is a time-reversed, complex conjugate response h−, of this estimated impulse response. An operation of convolving the received signal 103 and the received signal 103 is performed.

ダイバーシティルート２についても、上に述べた動作が
ＭＦ２により行なわれる。ルート２の送信シンボルはル
ート１よりτだけ先行しているから、ＤＦＢ４が出力す
る判定信号１０８は、ルート１の判定信号１０７よりτ
だけ進んでいる。Regarding diversity route 2 as well, the above-mentioned operation is performed by MF2. Since the transmission symbol of route 2 is ahead of route 1 by τ, the decision signal 108 outputted by DFB4 is τ more than the decision signal 107 of route 1.
Only progress has been made.

一方、畳込み器５は、ＭＰＩの推定したルート１のイン
パルス応答り、１０９と、ルート１よりτだけ進んでい
るルート２のＤＦＢ４の出力の判定信号ａ、ｌＯＲとを
畳込む。この畳込みには処理時間が必要であり、送信側
におけるルート１とルート２との遅延時間差τをこの処
理時間に設定する。この場合、畳込み器５は、ルート１
の希望信号Ｓ１を遅延を生ぜずに推定することになる。On the other hand, the convolver 5 convolves the impulse response 109 of the route 1 estimated by MPI with the determination signal a, lOR of the output of the DFB 4 of the route 2 which is ahead of the route 1 by τ. This convolution requires processing time, and the delay time difference τ between routes 1 and 2 on the transmitting side is set to this processing time. In this case, the convolver 5 uses the root 1
This means that the desired signal S1 of is estimated without any delay.

すなわち、減算器７において、畳込み器５の出力の希望
信号レプリカ（再生波形）をルート１の入力信号１０１
から減じることにより、ルート１の干渉波Ｊ１を遅延を
生じることなく抽出することができる。That is, in the subtracter 7, the desired signal replica (reproduced waveform) of the output of the convolver 5 is converted into the input signal 101 of the route 1.
By subtracting from , the interference wave J1 of route 1 can be extracted without causing any delay.

抽出された干渉波成分Ｊ１は、ＡＧＣ増幅器８によりそ
の振幅が１に正規化され、１・ｅｘｐ（ｊφ１）となる
、相関器１１と１２はそれぞれこの正規化干渉波成分１
１０とルート１とルート２の入力信号１０１，１０２と
の相関を取る。この相関操作はＡＧＣｊｌｌｌ器８の出
方の複素共役と各ダイバーシティ入力との積の平均を取
ることにより行われる。上記相関値をそれぞれＷｌ、Ｗ
２とすれば、下記のように示せる。The amplitude of the extracted interference wave component J1 is normalized to 1 by the AGC amplifier 8, and becomes 1·exp(jφ1).
10 and the input signals 101 and 102 of routes 1 and 2 are correlated. This correlation operation is performed by averaging the products of the complex conjugate of the output of the AGCjll unit 8 and each diversity input. The above correlation values are Wl and W, respectively.
2, it can be shown as follows.

Ｗ１＝Ｅ　ＥｅＸＤ　　（−Ｊφ１） （Ｓ１＋Ｊ１）］＝Ａ１・Ｊ　　　　・・・（５）Ｗ２
＝Ｅ　［ｅｘｐ　　（−Ｊφ１） （３２＋Ｊ２）］＝Ａ２−ｅｘｐ （ｊ（φ２−１）Ｊ　　　　　　　　　、、・（６）乗
算器９と１０は、正規化された干渉波成分１・ｅｘｐ（
ｊφ１）１１０に（５）、（６）式の複素係数Ｗ１およ
びＷ２を乗じる。すなわち乗算器９と１０の出力はそれ
ぞれ（２）、（３）式で示されるＪｌと５２となる。こ
のＪｌと５２の推定値Ｊ１と５２をそれぞれルート１と
ルーに２の入力信号１０１，１０２から減算器１３と１
４で減することにより、広帯域干渉波を除去できる。W1=E EeXD (-Jφ1) (S1+J1)]=A1・J...(5) W2
=E [exp (-Jφ1) (32+J2)]=A2-exp (j(φ2-1)J ,, (6) Multipliers 9 and 10 calculate the normalized interference wave component 1・exp(
jφ1) 110 is multiplied by the complex coefficients W1 and W2 of equations (5) and (6). That is, the outputs of multipliers 9 and 10 are Jl and 52, respectively, shown by equations (2) and (3). The estimated values J1 and 52 of Jl and 52 are subtracted from the input signals 101 and 102 of routes 1 and 2, respectively, by subtractors 13 and 1.
By reducing by 4, broadband interference waves can be removed.

以後の動作において干渉波が変動しても、適応的に干渉
波が除去される。一方、マルチパスフェージングによる
波形歪については、干渉波除去とは独立にＭＦとＤＦＢ
でなるＭ／Ｄ　ＦＥ受信機により除去される。ＤＦＢ４
の出力はＤＦＢ３の出力よりτだけ進んでいる。そこで
、ＤＦＢ４の出力をτの遅延時間を有する遅延素子１５
により遅らせ、ダイバーシティ切換え器６により、ルー
ト１とルート２の間で切換えダイバーシティを行う。Even if the interference waves fluctuate in subsequent operations, the interference waves are adaptively removed. On the other hand, regarding waveform distortion due to multipath fading, MF and DFB are independent of interference wave removal.
is removed by the M/D FE receiver. DFB4
The output of DFB3 is ahead of the output of DFB3 by τ. Therefore, the output of the DFB4 is transferred to the delay element 15 having a delay time of τ.
, and the diversity switch 6 performs switching diversity between route 1 and route 2.

以上の動作を第７図に示すベクトル図とスペクトラムを
用いて説明する。伝搬路でマルチパス歪を受けた希望信
号スペクトラムに広帯域干渉波が存在する様子を第７図
（ａ）と（ｂ）のスペクトラム欄に示す、また、そのベ
クトル関係をベクトル図の欄に示す、マルチパス歪のた
めに、希望信号スペクトラムにノツチあるいは歪が生じ
ている。The above operation will be explained using the vector diagram and spectrum shown in FIG. The presence of broadband interference waves in the spectrum of the desired signal subjected to multipath distortion in the propagation path is shown in the spectrum column of FIGS. 7(a) and (b), and the vector relationship is shown in the vector diagram column. Multipath distortion causes notches or distortions in the desired signal spectrum.

畳込み器５は、ルート１の希望信号Ｓ１のレプリ力を遅
延を生じないで推定するから、その出力信号は第７図（
ａ）の８１ベクトルに一致する。すなわち、減算器７の
出力は（ｄ）に示すようにルート１の干渉波Ｊ１を正し
く推定していることになる。これを振幅について正規化
し、各ダイバーシティルート入力と相関を取り、それら
の相関値を前記正規化干渉波成分に乗じたものが、乗算
器９と１０の出力である。これらは（ｅ）と（ｆ）に示
すように、各ルートにおける干渉波の推定値となってい
る。これらの推定干渉波Ｊ１とＪ２をそれぞれ（ａ）と
（ｂ）の入力から減じることにより（ｇ）と（ｈ）に示
すようにマルチパス歪を受けた希望信号成分のみを抽出
することができ、Ｍ　Ｆ／Ｄ　Ｆ　Ｅ受信機により、適
応等化される。Since the convolution device 5 estimates the repliability of the desired signal S1 of route 1 without causing any delay, its output signal is as shown in FIG.
It matches the 81 vector in a). That is, the output of the subtractor 7 correctly estimates the interference wave J1 of the route 1, as shown in (d). This is normalized in terms of amplitude, correlated with each diversity route input, and the normalized interference wave component is multiplied by these correlation values to provide the outputs of multipliers 9 and 10. These are estimated values of interference waves in each route, as shown in (e) and (f). By subtracting these estimated interference waves J1 and J2 from the inputs in (a) and (b), respectively, it is possible to extract only the desired signal components that have undergone multipath distortion, as shown in (g) and (h). , M F/D F E is adaptively equalized by the receiver.

上記の動作において、干渉波除去により希望信号を損な
うことは無い、また、本実施例はＤ／ｌＪが任意の値で
あって動作する。さらに、複数の干渉波が存在しても除
去が可能である。In the above operation, the interference wave removal does not damage the desired signal, and this embodiment operates with D/lJ at any value. Furthermore, even if a plurality of interference waves exist, they can be removed.

ところでＭＰ／ＤＦＥ受信機を立ち上げる時、すでにＤ
／Ｕがマイナスとなるくら強い干渉波が存在している場
合、Ｍ　Ｆ／Ｄ　Ｆ　Ｅ受信機は正しい判定信号を出力
できない９判定信号が誤まっていると、ＭＰは正しいイ
ンパルス応答推定を行えない、従って、希望信号レプリ
カはもはや正しいものではなくなる。この場合、このま
ま放置しておくと永久に立ち上げることができなくなっ
てしまう。By the way, when I start up the MP/DFE receiver, it is already D.
If there is an interference wave strong enough for /U to be negative, the MF/D F E receiver cannot output the correct judgment signal.9If the judgment signal is incorrect, the MP cannot estimate the impulse response correctly. Therefore, the desired signal replica is no longer the correct one. In this case, if you leave it as is, you will be unable to start it up forever.

そこで、この初期引き込みを解決するものが第２図に示
した実施例である。Therefore, the embodiment shown in FIG. 2 solves this initial pull-in problem.

第２図において、２０１．２０２．２０３．２０４．２
０５．２０６．２０７．２０８．２０９．２１０．２１
１．２１２．２１３．２１４および２１５はそれぞれ第
１図の１．２．３．４．５．６．７．８．９．１０．１
１．１２．１３．１４、および１５に対応しており、こ
れら第２図の構成要素は第１図の構成要素と同じ動作を
行なう、干渉波が除去されるまでの間、送信シンボル系
列と同じトレーニング信号をトレーニング信号発生器２
１６に出力させる。この際、発生させるタイミングは、
送信側においてダイバーシティルート１よりτだけ進ん
だダイバーシティルート２のタイミングに合わせる。こ
のトレーニング信号発生器２１６の出力をルート２用の
トレーニング信号として切換え器２１９に供給する。一
方、ルート１のために、トレーニング信号発生器２１６
から出力されるトレーニング信号をτの遅延時間を有す
る遅延素子２１７に供給する。遅延素子２１７の出力は
切換え器２１８に入力される。切換え器２１８と２１９
はトレーニング信号を選択し、それぞれのルートのＭＰ
とＤＦＥに供給する。なおルート２の切換え器２１９は
、その出力を畳込み器２０５にも供給する。ＭＰおよび
ＤＦＥは、供給されたトレーニング信号を基準信号とし
て適応制御に用いる。すなわち、ＭＰ２０１と２０２は
トレーニング系列ａ、を用いて（１）式で示された受信
信号２５３，２５４と相関を取ることにより伝送系のイ
ンパルス応答を推定する。この際、干渉波と判定信号と
の相関値が零となるから、干渉波がまだ除去されていな
くても推定インパルス応答は正しい値となる。また、畳
込み器２０５はルート２の送信シンボルにタイミングが
合ったトレーニング系列を用いるから、その出力は遅延
が生じていない正しい希望信号レプリカとなる。希望信
号レプリカが止しい値となれば、乗算器２０９と２１０
の出力に干渉波推定値Ｊ１とＪ２が得られ、干渉波の除
去が可能となる。干渉波が除去され、Ｍ　Ｐ／Ｄ　Ｆ　
Ｅ受信機が回線のマルチパス歪を除去し、希望信号が正
しく判定されるようになると、ＤＦＥ２０３とＤＦＥ２
０４に含まれる判定器の誤差信号εが小さくなっていく
、制御器２２０と２２１は判定器の誤差信号εを入力と
してその自乗平均値ξを監視しており、これが予め設定
されたしきい値以下となった場合、干渉が正しく除去さ
れたと判断して切換え器２１８と２１９をそれぞれ制御
し、ＤＦＥ２０３とＤＦＥ２０４がらの判定信号を選択
して出力させる。それ以後、ＭＰ２０１とＤＦＥ２０３
はルート１の判定信号を、ＭＰ２０２とＤＦＥ２０４と
畳込み器２０５はルート２の判定信号を供給され、第１
図の実施例で説明したのと同じ干渉波除去操作を続ける
。In Figure 2, 201.202.203.204.2
05.206.207.208.209.210.21
1.212.213.214 and 215 are respectively 1.2.3.4.5.6.7.8.9.10.1 in FIG.
1.12.13.14, and 15, these components in FIG. 2 perform the same operations as the components in FIG. The same training signal is sent to training signal generator 2.
16 to output. In this case, the timing to generate
On the transmitting side, the timing is adjusted to the timing of diversity route 2, which is ahead of diversity route 1 by τ. The output of this training signal generator 216 is supplied to the switch 219 as a training signal for route 2. Meanwhile, for route 1, the training signal generator 216
A training signal outputted from the input signal is supplied to a delay element 217 having a delay time of τ. The output of delay element 217 is input to switch 218. Switchers 218 and 219
selects the training signals and calculates the MP of each route.
and supplied to the DFE. Note that the switch 219 of route 2 also supplies its output to the convolver 205. The MP and DFE use the supplied training signal as a reference signal for adaptive control. That is, the MPs 201 and 202 estimate the impulse response of the transmission system by correlating with the received signals 253 and 254 shown in equation (1) using the training sequence a. At this time, since the correlation value between the interference wave and the determination signal becomes zero, the estimated impulse response has a correct value even if the interference wave has not been removed yet. Furthermore, since the convolution device 205 uses a training sequence whose timing matches the transmission symbol of route 2, its output becomes a correct replica of the desired signal without any delay. If the desired signal replica reaches a certain value, the multipliers 209 and 210
The interference wave estimation values J1 and J2 are obtained as the outputs, and the interference wave can be removed. Interfering waves are removed and M P/D F
When the E receiver removes the multipath distortion of the line and the desired signal is correctly determined, the DFE203 and DFE2
The error signal ε of the determiner included in 04 becomes smaller. Controllers 220 and 221 monitor the root mean square value ξ of the error signal ε of the determiner as input, and this becomes the preset threshold value. If the following happens, it is determined that the interference has been correctly removed, and the switching devices 218 and 219 are controlled respectively, and the determination signals from the DFE 203 and the DFE 204 are selected and output. After that, MP201 and DFE203
is supplied with the decision signal of route 1, and MP202, DFE204, and convolver 205 are supplied with the decision signal of route 2.
Continue the same interference wave removal operation as described in the illustrated embodiment.

なお、送信側に対するトレーニング信号の挿入方法には
２通りあり、１つは送信信号系列に周期的にバースト状
で挿入する方法、他方は受信側からの制御信号により挿
入または解除という方法がある。Note that there are two methods for inserting a training signal on the transmitting side; one is a method in which the training signal is periodically inserted into the transmitting signal sequence in a burst form, and the other is a method in which the training signal is inserted or canceled by a control signal from the receiving side.

以上の第２図の実施例により、初期引き込みを解決した
広帯域干渉波除去が可能となる。The embodiment shown in FIG. 2 described above makes it possible to eliminate broadband interference waves that solve the initial pull-in problem.

次に、第３図の実施例について説明する。送信側では、
第１図の実施例と同様に、２重ダイバーシティのうち第
１のルートのシンボル列を第２のルートに対してτだけ
遅延させて送信する。Next, the embodiment shown in FIG. 3 will be described. On the sending side,
Similar to the embodiment shown in FIG. 1, the symbol sequence of the first route in the double diversity is transmitted with a delay of τ with respect to the second route.

第３図において、３０１．３０２．３０３．３０４．３
０５．３０６．３０７．３０８．３１３および３１４は
それぞれ第１図の１．２．３．４．５．６．７．１５．
１３および１４に対応しており、同し動作を行なう。In Figure 3, 301.302.303.304.3
05.306.307.308.313 and 314 are respectively 1.2.3.4.5.6.7.15.
13 and 14, and perform the same operations.

減算器３０７で抽出された干渉波成分Ｊ１は乗算器３０
９と３１０において、相関器３１１と３１２からのタッ
プ係数Ｗｌ、Ｗ２を乗じられて減算器３１３と３１４に
供給され、各ダイバーシティルートの入力１と入力２に
おける減算に用いられる。乗算器３０９の出力は Ｊ１＝＝Ｗ１−Ｊ１＝Ｗ１・Ｊ−Ａｌｅｘｐ　　（Ｊφ
１）・・・（７） 乗算器３１０の出力は Ｊ２＝Ｗ２−Ｊ１＝Ｗ２−Ｊ−ＡｌｅＸＩ）（ｊφ１）
・・・（８） で示される。The interference wave component J1 extracted by the subtracter 307 is sent to the multiplier 30
9 and 310, the signals are multiplied by the tap coefficients Wl and W2 from correlators 311 and 312 and supplied to subtracters 313 and 314, which are used for subtraction at input 1 and input 2 of each diversity route. The output of the multiplier 309 is J1==W1-J1=W1・J-Alexp (Jφ
1)...(7) The output of the multiplier 310 is J2=W2-J1=W2-J-AleXI)(jφ1)
...(8) It is shown as follows.

ルート１において、減算器３１３の出力は（Ｓ１＋Ｊ１
−Ｊｌ）となる。ＤＦＥ３０３内の判定器には、減算器
３１３の出力にＭＦ３０１およびＤＦＥ３０３の伝達間
数Ｈ１が乗じられたものが入力される。すなわちＤＦＥ
３０３における判定器の誤差信号ε３４１には、干渉波
Ｊ１による誤差成分が含まれる。特に、マルチパスフェ
ージングによる符号量干渉（ＩＳＩ）も同時に存在する
場合、判定器の誤差信号ε３４１はＩＳＩによる誤差成
分と干渉波Ｊ１による誤差成分の両方を含む、ところで
ＤＦＥの制御には誤差信号εが用いられるが、誤差信号
ε中の干渉波成分はＩＳＩによる成分とは独立であるか
ら、ＤＦＥのタップ修正には影響を与えない。すなわち
、ＩＳＩがＭ　Ｆ／Ｄ　Ｆ　Ｅ受信機により除去された
とすれば、誤差信号εは次のように近似される。In route 1, the output of the subtracter 313 is (S1+J1
-Jl). The output of the subtracter 313 multiplied by the transmission interval number H1 of the MF 301 and the DFE 303 is input to the determiner in the DFE 303 . That is, DFE
The error signal ε341 of the determiner in 303 includes an error component due to the interference wave J1. In particular, when code amount interference (ISI) due to multipath fading also exists at the same time, the error signal ε341 of the determiner includes both an error component due to ISI and an error component due to interference wave J1. is used, but since the interference wave component in the error signal ε is independent of the component due to ISI, it does not affect the tap correction of the DFE. That is, if ISI is removed by the M F/D F E receiver, the error signal ε is approximated as follows.

ε＝Ｈ１・　（Ｊｔ−Ｊｌ）　　　　　　　　・・・（
９）この誤差信号εの自乗平均値である評価間数ξは、
干渉波Ｊ１に対する伝搬路の伝達関数の変動の速さが、
希望信号速度に比べ遅いときにはξ＝Ｅ［ε・ε”］＝
ＨＩＨ１゜ （Ｊｌ−Ｊｌ）・（Ｊｌ−Ｊｌ）” のように平均値表示Ｅを省略して示せる。ε=H1・(Jt−Jl) ・・・(
9) The evaluation interval number ξ, which is the root mean square value of this error signal ε, is
The speed of fluctuation of the transfer function of the propagation path for the interference wave J1 is
When the signal speed is slower than the desired signal speed, ξ=E[ε・ε”]=
HIH1°(Jl-Jl)・(Jl-Jl)'' The average value display E can be omitted.

ξは乗算器３０９のタップ係数Ｗ１の関数であり、ξが
最小となるＷｌは より与えられ、＜２）、（７）式を用いてＷ１°ｐｔ＝
１　　　　　　　　　　　　　　　・・・（１１）とな
る。ξ is a function of the tap coefficient W1 of the multiplier 309, and Wl that minimizes ξ is given by <2), and using equation (7), W1°pt=
1...(11).

ところで、このＷｌの理想値に適応的に追随するには、
評価間数ξに対して勾配法を用いる。あるＷｌの値にお
けるξ面の勾配は、平均値表示Ｅを省略して次のように
示される。By the way, in order to adaptively follow this ideal value of Wl,
The gradient method is used for the evaluation interval number ξ. The slope of the ξ plane at a certain value of Wl is shown as follows, omitting the average value E.

θＷ１　　　　　θε°　　　　θＷ１＝−ε　・　Ｊ
ｌ”　　・Ｈｌ”　　　　　　・・・（１２）すなわち
、タップ係数ｗ１は次式でタップ修正すれば（１１）式
の理想値に収束する。θW1 θε° θW1=-ε・J
l''·Hl'' (12) That is, the tap coefficient w1 converges to the ideal value of the equation (11) if the tap is corrected using the following equation.

Ｗｌ”＝Ｗ１”−１−μ・ε・Ｊｌ＠　　・・・口３）
ここでμは修正係数である。Wl"=W1"-1-μ・ε・[email protected] 3)
Here μ is a correction coefficient.

上記タップ修正掃作は、第３図において相関器３１１で
行われる。相関器３１１は、減算器３０７からの信号Ｊ
ｌ　（３４０）の複素共役とＤＦＥ３０３からの誤差信
号ε３４１との積の平均を取ることにより、（１３）式
で示されるタップ修正を実現する。The tap correction sweep described above is performed by correlator 311 in FIG. Correlator 311 receives signal J from subtractor 307
By taking the average of the products of the complex conjugate of l (340) and the error signal ε341 from the DFE 303, the tap correction shown in equation (13) is realized.

以上の操作により、乗算器３０９の出力には、入力信号
３３１中の干渉波Ｊ１の推定値が得られる。この推定干
渉波Ｊ１を減算器３１３を用いて入力信号Ｓ１＋Ｊ１　
（３３１）から減じることにより干渉波Ｊ１を除去でき
る。Through the above operations, the estimated value of the interference wave J1 in the input signal 331 is obtained as the output of the multiplier 309. This estimated interference wave J1 is converted into an input signal S1+J1 using a subtracter 313.
The interference wave J1 can be removed by subtracting it from (331).

ルート２においても、同様な動作が相関器３１２．、Ｄ
ＦＥ３０４．乗算器３１０と減算器３１４により行われ
る。なおルート２でのタップ係数Ｗ２の理想値は Ｗ２＝　（Ａ２／Ａｔ　）　−＋３Ｘｔｌ（ｊ（φ２−
φ１））　　　　　　　・・・（１４）となっている６
以上に述べた動作によりルート１およびルート２の干渉
波は除去される。In route 2, a similar operation occurs in correlator 312 . ,D
FE304. This is performed by a multiplier 310 and a subtracter 314. The ideal value of tap coefficient W2 in route 2 is W2= (A2/At) -+3Xtl(j(φ2-
φ1)) ...(14) 6
Through the operations described above, interference waves on routes 1 and 2 are removed.

以後の動作において干渉波が変動しても、適応的に干渉
波が除去される。一方、マルチパルスフェージングによ
る波形歪については、干渉波除去とは独立にＭＰ／ＤＦ
Ｅ受信機により除去される。Even if the interference waves fluctuate in subsequent operations, the interference waves are adaptively removed. On the other hand, regarding waveform distortion due to multipulse fading, MP/DF
E is removed by the receiver.

Ｄ　Ｆ　Ｅ　３０４の出力はＤＦＥ３０３の出力よりτ
だけ進んでいる。そこで、ＤＦＥ３０４の出力をτの遅
延時間を有する遅延素子３０８により遅らせ、ダイバー
シティ切換え器３０６によりルート１とルート２の間で
切換えダイバーシティを行う。The output of DFE304 is τ from the output of DFE303.
Only progress has been made. Therefore, the output of the DFE 304 is delayed by a delay element 308 having a delay time of τ, and the diversity switch 306 performs switching diversity between routes 1 and 2.

ところでＭＰ／ＤＦＥ受信機を立ち上げる時、すでにＤ
／Ｕがマイナスとなるくらい強い干渉波が存在している
場合、Ｍ　Ｐ／Ｄ　Ｆ　Ｅ受信機は正しい判定信号を出
力できない。判定信号が誤まってイルト、ＭＰは正しい
インパルス応答推定を行えない、従って、希望信号レプ
リカはもはや正しいものではなくなる。この場合、この
まま放置しておくと永久に立ち上がることができなくな
ってしまう。By the way, when I start up the MP/DFE receiver, it is already D.
If there is an interference wave so strong that /U is negative, the MP/DFE receiver cannot output a correct determination signal. If the decision signal is incorrect, the MP cannot make a correct impulse response estimation, and therefore the desired signal replica is no longer correct. In this case, if you leave it as it is, you will be unable to stand up forever.

そこで、この初期引き込みを解決するものが第４図に示
した実施例である。Therefore, the embodiment shown in FIG. 4 solves this initial pull-in problem.

第４図において、４０１．４０２．４０３．４０４．４
０５．４０６．４０７．４０８．４０９．４１０．４１
１．４１２．４１３および４１４はそれぞれ第３図の３
０１．３０２．３０３．３０４．３０５．３０６．３０
７．３０８．３０９．３１０．３１１．３１２．３１３
および３１４に対応しており、これら第４図の構成要素
の動作は第３図の構成要素と同じである。In Figure 4, 401.402.403.404.4
05.406.407.408.409.410.41
1.412.413 and 414 are 3 in Fig. 3, respectively.
01.302.303.304.305.306.30
7.308.309.310.311.312.313
and 314, and the operations of these components in FIG. 4 are the same as those in FIG. 3.

また、第４図において、４１５．４２０，４１６．４１
７．４１８および４１９はそれぞれ第２図の２１６．２
１７．２１８．２１９．２２０、および２２１に対応し
ており、これら第４の構成要素の動作は第２図の構成要
素と同じである。Also, in Figure 4, 415.420, 416.41
7.418 and 419 are respectively 216.2 in Fig. 2
17, 218, 219, 220, and 221, and the operation of these fourth components is the same as that of the components in FIG.

第２図の実施例で述べたのと同様に干渉波が除去される
まで、トレーニング信号発生器４１５から出力されるト
レーニング信号を用いることで、第３図に示す干渉波除
去装置の初期引き込みを解決できる。その後はトレーニ
ング信号から各ルートの判定信号に切換えて制御を行い
、適応的に干渉除去操作を続ける。なお、送信側に対す
るトレーニング信号の挿入方法には２通りあり、１つは
送信信号系列に周期的にバースト状で挿入する方法、他
方は受信側からの制御信号により挿入または解除という
方法がある。The initial pull-in of the interference wave canceling device shown in FIG. 3 is performed by using the training signal output from the training signal generator 415 until the interference wave is removed in the same manner as described in the embodiment of FIG. Solvable. Thereafter, control is performed by switching from the training signal to the determination signal for each route, and adaptive interference removal operation is continued. Note that there are two methods for inserting a training signal on the transmitting side; one is a method in which the training signal is periodically inserted into the transmitting signal sequence in a burst form, and the other is a method in which the training signal is inserted or canceled by a control signal from the receiving side.

次に、第５図に示す実施例について説明する。Next, the embodiment shown in FIG. 5 will be described.

送信側では、第１図の実施例と同様に、２重ダイバーシ
ティのうち第１のルートのシンボル列を第２のルートに
対してτだけ遅延させて送信する。On the transmitting side, as in the embodiment shown in FIG. 1, the symbol string of the first route in the double diversity is transmitted with a delay of τ with respect to the second route.

第５図において、５０１．５０２．５０３．５０４．５
０５．５０６．５０７．５０８．５１３および５１４は
それぞれ第１図の１．２．３．４．５．６．７．１５．
１３および１４に対応しており、同じ動作を行なう。In Figure 5, 501.502.503.504.5
05.506.507.508.513 and 514 are respectively 1.2.3.4.5.6.7.15.
13 and 14, and perform the same operations.

減菫器５０７で抽出された干渉波成分Ｊ１は、乗算器５
０９と５１０において、制御器５１１と５１２からのタ
ップ係数Ｗｌ、Ｗ２を乗じられて減算器５１３と５１４
に供給され、各ダイバーシティルートの入力１と入力２
における減算に用いられる０乗算器５０９の出力は Ｊ１＝Ｗ１・Ｊ１＝Ｗ１−Ｊ−Ａｌｅｘｐ　　（ｊφ１
）・・・（１５） 乗算器５１０の出力は Ｊ２＝Ｗ２−Ｊ１＝Ｗ２−Ｊ−Ａｌｅｘｐ　　（ｊ　φ
１）・・・（１６） で示される。The interference wave component J1 extracted by the violet reducer 507 is transmitted to the multiplier 5.
09 and 510, the subtractors 513 and 514 are multiplied by the tap coefficients Wl and W2 from the controllers 511 and 512.
input 1 and input 2 of each diversity route.
The output of the 0 multiplier 509 used for subtraction in is J1=W1・J1=W1−J−Alexp (jφ1
)...(15) The output of the multiplier 510 is J2=W2-J1=W2-J-Alexp (j φ
1)...(16) It is shown as follows.

ルート１において、減算器５１３の出力は（３１＋Ｊ１
−Ｊｌ＞となる、この減算器５１３の出力信号は、ＭＦ
５０１の入力となっており、電力検出器５１５はその電
力Ｐを検出する。電力Ｐは次のように示される。In route 1, the output of subtractor 513 is (31+J1
-Jl>, the output signal of this subtracter 513 is MF
501, and a power detector 515 detects the power P. Power P is shown as follows.

Ｐ＝　（Ｓ１＋Ｊ１−Ｊｌ） （Ｓｌ十Ｊｌ−Ｊｌ） ＝ＳＩＳ１°　＋（ＪＩＪＩｏ−ＪＩＪＩ。P= (S1+J1-Jl) (Sl 10 Jl-Jl) =SIS1° +(JIJIo-JIJI.

−Ｊ　Ｉ　Ｊ　１°　＋Ｊ　Ｉ　Ｊ　１°　）　＋Δ　
　　・・・（１１）ここで、ΔはＳｌとＪｌとの積の成
分で、干渉波Ｊ１が５１により除去されれば、零となる
。Ｐは乗算器５０９のタップ係数Ｗ１の関数であり、Ｐ
が最小となるＷｌは より与えられ、（２）、（１５）式を用いてＷ１°？ｔ
＝１　　　　　　　　　　　　　　・・・（１９）とな
る。−J I J 1° + J I J 1° ) +Δ
(11) Here, Δ is a component of the product of Sl and Jl, and becomes zero if the interference wave J1 is removed by 51. P is a function of the tap coefficient W1 of the multiplier 509, and P
Wl for which is the minimum is given by W1°? using equations (2) and (15). t
=1...(19).

（１９）式のタップ係数を乗算器５０９で減算器５０７
の出力Ｊ１に乗することにより、入力信号５３１中の干
渉波Ｊ１を推定することが出来る。The tap coefficient of equation (19) is subtracted by the multiplier 509 and the subtracter 507
By multiplying by the output J1 of , the interference wave J1 in the input signal 531 can be estimated.

この乗算器５０９の出力の推定干渉波Ｊ１を減算器５１
３で入力信号Ｓ１＋Ｊ１　（５３１）から減じることに
より干渉波Ｊ１を除去できる。そこでタップ係数制御器
５１１は、乗算器５０９にタップ係数Ｗ１を乗じてＰが
最小となるようにフィードバック制御を行なう。The estimated interference wave J1 output from the multiplier 509 is subtracted by the subtracter 51.
3 from the input signal S1+J1 (531), the interference wave J1 can be removed. Therefore, the tap coefficient controller 511 performs feedback control so that the multiplier 509 is multiplied by the tap coefficient W1 to minimize P.

以−１の操作により干渉波Ｊ１は除去される。この時、
（１７）式の電力は最小値を示しＳＳｏの希望波成分の
みとなる。The interference wave J1 is removed by the above-1 operation. At this time,
The power in equation (17) has a minimum value and is only the desired wave component of SSo.

ルート２においても、同様な動作が電力検出器５１６、
タップ係数制御器５１２、乗算器５１０減算器５１４に
より行なわれる。なお、ルート２でのタップ係数Ｗ２の
理想値は Ｗ２＝　（Ａ２／Ａｌ　）　−ｅＸＩ）　　（Ｊ　（φ
２−φ１））・・・（１４） となっている。以上に述べた動作によりルート１および
ルート２の干渉波は除去される。In route 2, similar operation is performed by the power detector 516,
This is performed by a tap coefficient controller 512, a multiplier 510, and a subtracter 514. Note that the ideal value of the tap coefficient W2 in route 2 is W2= (A2/Al ) −eXI) (J (φ
2-φ1))...(14) Through the operations described above, interference waves on routes 1 and 2 are removed.

以後の動作において干渉波が変動しても、適応的に干渉
波が除去される。一方、マルチパスフェージングによる
波形歪については、干渉除去とは独立にＭＦ／ＤＦＥ受
信機により除去される。ＤＦＥ５０４の出力はＤＦＥ５
０３の出力よりτだけ進んでいる。そこで、ＤＦＥ５０
４の出力をτの遅延時間を有する遅延素子５０８により
遅らせ、ダイバーシティルート切換え器５０６によりル
ート１とルート２の間で切換えダイバーシティを行う。Even if the interference waves fluctuate in subsequent operations, the interference waves are adaptively removed. On the other hand, waveform distortion due to multipath fading is removed by the MF/DFE receiver independently of interference removal. The output of DFE504 is DFE5
It is ahead of the output of 03 by τ. Therefore, DFE50
4 is delayed by a delay element 508 having a delay time of τ, and a diversity route switch 506 performs switching diversity between routes 1 and 2.

ところでＭＦ／ＤＦＥ受信機を立ち上げる時、すでにＤ
／Ｕがマイナスとなるくらい強い干渉波が存在している
場合、ＭＰ／ＤＦＥ受信機は正しい判定信号を出力でき
ない４判定信号が誤っていると、ＭＦは正しいインパル
ス応答推定を行えない、従って、希望信号レプリカはも
はや正しいものではなくなる。この場合、このまま放置
しておくと永久に立ち上がることができなくなってしま
う。By the way, when starting up the MF/DFE receiver, it is already D.
If there is an interference wave so strong that /U is negative, the MP/DFE receiver cannot output the correct judgment signal.4If the judgment signal is incorrect, the MF cannot estimate the impulse response correctly.Therefore, The desired signal replica is no longer the correct one. In this case, if you leave it as it is, you will be unable to stand up forever.

そこで、この初期引き込みを解決するものが第６図に示
した実施例である。Therefore, the embodiment shown in FIG. 6 solves this initial pull-in problem.

第６図において、６０１．６０２．６０３．６０４．６
０５．６０６．６０７．６０８．６０９．６１０．６１
１．６１２．６１３．６１４．６１５および６０６それ
ぞれ第５図の５０１．５０２．５０３．５０４．５０５
．５０６．５０７．５０８．５０９．５１０．５１１．
５１２．５１３．５１４．５１５および５１６に対応し
ており、これら第６の構成要素の動作は第５図の構成要
素と同じである。In Figure 6, 601.602.603.604.6
05.606.607.608.609.610.61
1.612.613.614.615 and 606 respectively 501.502.503.504.505 in Figure 5
．． 506.507.508.509.510.511.
512, 513, 514, 515 and 516, and the operations of these sixth components are the same as those of FIG.

また、第６図の６１７．６１８．６１９．６２０．６２
１および６２２はそれぞれ第２図の２１６．２１７．２
１８．２１９．２２０、および２２１に対応しており、
これら第６図の構成要素の動作は第２図の構成要素と同
じである。Also, 617.618.619.620.62 in Figure 6
1 and 622 are respectively 216.217.2 in Fig. 2
18.219.220 and 221,
The operations of these components in FIG. 6 are the same as those in FIG. 2.

第２図の実施例で述べたのと同様に干渉波が除去される
まで、トレーニング信号発生器６１７からｕｉ力される
トレーニング信号を用いることで、第５図に示す干渉波
除去装置の初期引き込みを解決できる。その後はトレー
ニング信号から各ルートの判定信号に切換えて制御を行
い、適応的に干渉波除去操作を続ける。なお、送信側に
対するトレーニング信号の挿入方法には２通りあり、１
つは送信信号系列に周期的にバースト状で挿入する方法
、他方は受信側からの制御信号により挿入または解除と
いう方法がある。In the same way as described in the embodiment of FIG. 2, the initial pull-in of the interference wave canceling device shown in FIG. can be solved. Thereafter, control is performed by switching from the training signal to the determination signal for each route, and the interference wave removal operation is continued adaptively. There are two ways to insert training signals to the transmitter side.
One method is to periodically insert the signal into the transmission signal sequence in burst form, and the other method is to insert or cancel the signal using a control signal from the receiving side.

（発明の効果） 本発明は、以上に説明したように、干渉波どうしの逆相
合成を行なわず、希望信号レプリカを受色信号か４減ｊ
Ｚることにより干渉成分を抽出し、この■渉成分を制御
＃の後に、受信信号から減じることにより干渉波の除去
を行なうから、マルチ歪を受けた希望信号に干渉波除去
による影響を与えることなく、干渉波が複数存在してい
ても、またＤ／Ｕが任意の値であっても広帯域干渉波と
マルチパス歪の両方を効果的に除去できるという効果が
ある。(Effects of the Invention) As explained above, the present invention does not perform reverse phase synthesis of interference waves, and instead converts a desired signal replica to a colored signal by 4
The interference component is extracted by Z, and the interference wave is removed by subtracting this interference component from the received signal after control #, so the interference wave removal will not affect the desired signal that has undergone multi-distortion. Even if a plurality of interference waves exist or D/U has an arbitrary value, both broadband interference waves and multipath distortion can be effectively removed.

【図面の簡単な説明】[Brief explanation of the drawing]

第１図は本発明に係る第１の干渉波除去装置の一実施例
の構成を示すブロック図、第２図は本発明に係る第２の
干渉波検出装置の一実施例の構成を示すブロック図、第
３図は本発明に係る第３の１渉波除去装置の一実施例の
構成を示すブロック図、第４図は本発明に係る第４の干
渉波除去装置の一実施例の構成を示すブロック図、第５
図は本発明に係る第５の干渉波除去装置の一実施例の構
成を示すブロック図、第６図は本発明に係る第６の干渉
波除去装置の一実施例の構成を示すブロック図、第７図
は本発明の干渉波除去装置の動作を説明する図、第８図
は従来の干渉波除去装置の構成を示すブロック図、第９
図は第８図に示す従来の干渉波除去装置の動作を説明す
る図である。 １．２，２０１，２０２，３０１，３０２゜４０１．４
０２，５０１，５０２，６０１，６０２゜８１１・・・
整合フィルタ（ＭＦ）、３，４，２０３゜２０４、．３
０３，３０４，４０３，４０４，５０３゜５０４．６０
３，６０４．８１２・・・判定帰還形等化器（ＤＦＥ）
、５，２０５，３０５，４０５゜５０５．６０５・・・
畳込み器、６，２０６，３０６゜４０６．５０６，６０
６．・・・ダイバーシティルート切換え器、７．１３．
１４，２０７，２１３゜２１４．３０７，３１３，３１
４，４０７，４１３゜４１４．５０７，５１３，５１４
，６０７，６１３．６１４，８０４・・・減算器、８，
２０８，８０５゜８０８．８０９・・・ＡＧＣ＃！１幅
器、９．１０，２０９゜２１０．３０９，３１０，４０
９，４１０，５０９゜５１０．６０９，６１０，８０１
．８０２・・・乗算器、１１，１２，２１１，２１２，
３１１，３１２゜４１１．４１２，８０６，８０７・・
・相関器、１５゜２１　５、　２１７．　３０８，４０
８．　４２０，５０８゜６０８．６１８．・・・遅延素
子、２１６，４１５゜６１７・・・トレーニング信号発
生器、２１８，２１９４１６．４１７，６１９，６２０
．８１０・・・切換え器、２２０，２２１，４１８，４
１９，６２１゜６２２・・・制御器、５１１，５１２，
６１１，６１２・・・タップ係数制御器、５１５，５１
６，６１５゜６１６・・・電力検出器、８０３・・・加
算器。 代理人　弁理士　本　庄　伸　介 第７図 （ａ）　入力１ （ｂ）＊算ａｓｏｔ出ヵ （ｄ）入力２ （ｅ）乗算器ｇｏｚ出力 （イ）減算Ｍ［Ｉｏ４出ヵ （９）入力１ （ｈ）乗算器８０１出力 （ｊ）入力２ （ｋ）乗算１１８ｏｚ出力 （１）減算器８０４出力 第９図FIG. 1 is a block diagram showing the configuration of an embodiment of a first interference wave removal device according to the present invention, and FIG. 2 is a block diagram showing the configuration of an embodiment of the second interference wave detection device according to the present invention. 3 is a block diagram showing the configuration of an embodiment of the third interference wave removal device according to the present invention, and FIG. 4 is a block diagram showing the configuration of an embodiment of the fourth interference wave cancellation device according to the present invention. Block diagram showing 5th
FIG. 6 is a block diagram showing the configuration of an embodiment of the fifth interference wave removal device according to the present invention; FIG. 6 is a block diagram showing the configuration of an embodiment of the sixth interference wave removal device according to the invention FIG. 7 is a diagram explaining the operation of the interference wave removal device of the present invention, FIG. 8 is a block diagram showing the configuration of a conventional interference wave removal device, and FIG.
This figure is a diagram explaining the operation of the conventional interference wave removal device shown in FIG. 8. 1.2,201,202,301,302゜401.4
02,501,502,601,602°811...
Matched filter (MF), 3, 4, 203° 204, . 3
03,304,403,404,503゜504.60
3,604.812...Decision feedback equalizer (DFE)
, 5,205,305,405°505.605...
Convolver, 6,206,306°406.506,60
6. ...Diversity route switch, 7.13.
14,207,213゜214.307,313,31
4,407,413゜414.507,513,514
,607,613.614,804...Subtractor, 8,
208,805°808.809...AGC#! 1 width instrument, 9.10,209°210.309,310,40
9,410,509゜510.609,610,801
．． 802... Multiplier, 11, 12, 211, 212,
311,312゜411.412,806,807...
・Correlator, 15°21 5, 217. 308,40
8. 420,508°608.618. ...Delay element, 216,415°617...Training signal generator, 218,219416.417,619,620
．． 810...Switcher, 220, 221, 418, 4
19,621°622...Controller, 511,512,
611, 612...Tap coefficient controller, 515, 51
6,615°616...Power detector, 803...Adder. Agent Patent Attorney Shinsuke Honjo Figure 7 (a) Input 1 (b) * Calculation asot output (d) Input 2 (e) Multiplier goz output (a) Subtraction M [Io4 output (9) Input 1 (h) Multiplier 801 output (j) Input 2 (k) Multiplication 118oz output (1) Subtractor 804 output Fig. 9

Claims (6)

【特許請求の範囲】[Claims] （１）２つのルートを設定してそれぞれのルートの受信
出力を切換える切換えダイバーシティ方式の干渉波検出
装置において、時間τの遅延が与えられて送信された希
望信号および第１の干渉波でなる第１の受信信号と第１
の推定干渉波との差である第１の差信号を生成する第１
の減算器と、遅延が与えられることなく送信された希望
信号および第２の干渉波でなる第２の受信信号と第２の
推定干渉波との差である第２の差信号を生成する第２の
減算器と、前記第１の差信号と第１の判定信号とから第
１のルートの伝送系のインパルス応答を推定して推定イ
ンパルス応答を得ると共に該推定インパルス応答の時間
反転で複素共役な応答と前記第１の差信号とを畳込んだ
第１の整合信号を得る第１の整合フィルタと、前記第２
の差信号と第２の判定信号とから推定する第２のルート
の伝送系のインパルス応答の時間反転で複素共役な応答
と前記第２の差信号とを畳込んだ第２の整合信号を得る
第２の整合フィルタと、前記第１の整合信号を適応等化
して前記第１の判定信号を得る第１の判定帰還形等化器
と、前記第２の整合信号を適応等化して前記第２の判定
信号を得る第２の判定帰還形等化器と、前記推定インパ
ルス応答と前記第２の判定信号とを畳込んで推定希望と
信号を得る畳込み器と、前記第１の受信信号と前記推定
希望信号との差を取って干渉波成分を抽出する第３の減
算器と、前記干渉波成分の振幅を１に正規化して正規化
干渉波成分を得るＡＧＣ増幅器と、前記第１の受信信号
と前記正規化干渉波成分との相関を取って第１の相関値
を得る第１の相関器と、前記第２の受信信号と前記正規
化干渉波成分との相関を取つて第２の相関値を得る第２
の相関器と、前記正規化干渉波成分に前記第１の相関値
を乗じて前記第１の推定干渉波を得る第１の乗算器と、
前記正規化干渉波成分に前記第２の相関値を乗じて前記
第２の推定干渉波を得る第２の乗算器と、前記第２の判
定信号に時間τの遅延を与える遅延素子と、前記第１の
判定信号と前記遅延素子の出力信号とを入力していずれ
か一方の信号を選択して出力するダイバーシティルート
切換え器とからなることを特徴とする干渉波除去装置。(1) In a switching diversity interference wave detection device that sets two routes and switches the reception output of each route, a first interference wave consisting of the desired signal and the first interference wave transmitted with a delay of time τ is used. 1 received signal and the first
a first difference signal that is the difference between the estimated interference wave of
a subtracter for generating a second difference signal, which is the difference between the second estimated interference wave and a second received signal consisting of the desired signal and the second interference wave transmitted without being delayed. 2, the impulse response of the transmission system of the first route is estimated from the first difference signal and the first determination signal to obtain an estimated impulse response, and the complex conjugate is obtained by time reversal of the estimated impulse response. a first matched filter that obtains a first matched signal that is a convolution of the response and the first difference signal;
A second matching signal is obtained by convolving the second difference signal with a time-reversed complex conjugate response of the impulse response of the transmission system of the second route estimated from the difference signal and the second determination signal. a second matched filter; a first decision feedback equalizer that adaptively equalizes the first matched signal to obtain the first decision signal; and a first decision feedback equalizer that adaptively equalizes the second matched signal to obtain the first decision signal; a second decision feedback equalizer that obtains a second decision signal; a convolver that obtains an estimated desired signal by convolving the estimated impulse response and the second decision signal; and a second decision feedback equalizer that obtains an estimated desired signal. and the estimated desired signal to extract an interference wave component; an AGC amplifier that normalizes the amplitude of the interference wave component to 1 to obtain a normalized interference wave component; a first correlator that correlates the received signal with the normalized interference wave component to obtain a first correlation value; and a first correlator that correlates the second received signal with the normalized interference wave component. The second to obtain the correlation value of 2
a first multiplier that multiplies the normalized interference wave component by the first correlation value to obtain the first estimated interference wave;
a second multiplier that obtains the second estimated interference wave by multiplying the normalized interference wave component by the second correlation value; a delay element that delays the second determination signal by a time τ; An interference wave removal device comprising a diversity route switch that receives a first determination signal and an output signal of the delay element, selects one of the signals, and outputs the selected signal. （２）２つのルートを設定してそれぞれのルートの受信
出力を切換える切換えダイバーシティ方式の干渉波除去
装置において、時間τの遅延が与えられて送信された希
望信号および第１の干渉波でなる第１の受信信号と第１
の推定干渉波との差である第１の差信号を生成する第１
の減算器と、遅延が与えられることなく送信された希望
信号および第２の干渉波でなる第２の受信信号と第２の
推定干渉波との差である第２の差信号を生成する第２の
減算器と、前記第１の差信号と第１の基準信号とから第
１のルートの伝送系のインパルス応答を推定して推定イ
ンパルス応答を得ると共に該推定インパルス応答の時間
反転で複素共役な応答と前記第１の差信号とを畳込んだ
第１の整合信号を得る第１の整合フィルタと、前記第２
の差信号と第２の基準信号とから推定する第２のルート
の伝送系のインパルス応答の時間反転で複素共役な応答
と前記第２の差信号とを畳込んだ第２の整合信号を得る
第２の整合フィルタと、前記第１の基準信号を用いて前
記第１の整合信号を適応等化して第１の判定信号と判定
結果の第１の誤差信号とを得る第１の判定帰還形等化器
と、前記第２の基準信号を用いて前記第２の整合信号を
適応等化して第２の判定信号と判定結果の第２の誤差信
号とを得る第２の判定帰還形等化器と、前記推定インパ
ルス応答と前記第２の基準信号とを畳込んで推定希望信
号を得る畳込み器と、前記第１の受信信号と前記推定希
望信号の差を取って干渉波成分を抽出する第３の減算器
と、仮定した送信シンボル列を表すトレーニング信号を
発生するトレーニング信号発生器と、前記トレーニング
信号に時間τの遅延を与える第１の遅延素子と、前記第
１の誤差信号に応じて前記第１の判定信号と前記第１の
遅延素子の出力信号のいずれか一方を選択して前記第１
の基準信号として出力する第１の切換え器と、前記第２
の誤差信号に応じて前記第２の判定信号と前記トレーニ
ング信号のいずれか一方を選択して前記第１の基準信号
として出力する第１の切換え器と、前記第２の誤差信号
に応じて前記第２の判定信号と前記トレーニング信号の
いずれか一方を選択して前記第２の基準信号として出力
する第２の切換え器と、前記干渉波成分の振幅を１に正
規化して正規化干渉波成分を得るＡＧＣ増幅器と、前記
第１の受信信号と前記正規化干渉波成分との相関を取っ
て第１の相関値を得る第１の相関器と、前記第２の受信
信号と前記正規化干渉波成分との相関を取って第２の相
関値を得る第２の相関器と、前記正規化干渉波成分に前
記第１の相関値を乗じて前記第１の推定干渉波を得る第
１の乗算器と、前記正規化干渉波成分に前記第２の相関
値を乗じて前記第２の推定干渉波を得る第２の乗算器と
、前記第２の判定信号に時間τの遅延を与える第２の遅
延素子と、前記第１の判定信号と前記第２の遅延素子の
出力信号とを入力していずれか一方の信号を選択して出
力するダイバーシティルート切換え器とからなることを
特徴とする干渉波除去装置。(2) In a switching diversity type interference wave canceling device that sets two routes and switches the reception output of each route, a first interference wave consisting of the desired signal and the first interference wave transmitted with a delay of time τ is used. 1 received signal and the first
a first difference signal that is the difference between the estimated interference wave of
a subtracter for generating a second difference signal, which is the difference between the second estimated interference wave and a second received signal consisting of the desired signal and the second interference wave transmitted without being delayed. 2, the impulse response of the transmission system of the first route is estimated from the first difference signal and the first reference signal to obtain an estimated impulse response, and the complex conjugate is obtained by time reversal of the estimated impulse response. a first matched filter that obtains a first matched signal that is a convolution of the response and the first difference signal;
A second matching signal is obtained by convolving the second difference signal with a time-reversed complex conjugate response of the impulse response of the transmission system of the second route estimated from the difference signal and the second reference signal. a second matched filter; and a first decision feedback type that adaptively equalizes the first matched signal using the first reference signal to obtain a first decision signal and a first error signal of the decision result. an equalizer, and a second decision feedback type equalization that adaptively equalizes the second matching signal using the second reference signal to obtain a second decision signal and a second error signal of the decision result. a convolver for convolving the estimated impulse response and the second reference signal to obtain an estimated desired signal; and extracting an interference wave component by taking the difference between the first received signal and the estimated desired signal. a third subtractor that generates a training signal representing an assumed transmission symbol sequence; a first delay element that delays the training signal by a time τ; Accordingly, one of the first determination signal and the output signal of the first delay element is selected and the first
a first switch that outputs the reference signal as a reference signal;
a first switch that selects either the second determination signal or the training signal and outputs it as the first reference signal according to the error signal; a second switch that selects one of the second determination signal and the training signal and outputs it as the second reference signal; and a normalized interference wave component that normalizes the amplitude of the interference wave component to 1. a first correlator that obtains a first correlation value by correlating the first received signal and the normalized interference wave component; and a first correlator that obtains a first correlation value by correlating the first received signal and the normalized interference wave component; a second correlator that obtains a second correlation value by correlating with the wave component; and a first correlator that obtains the first estimated interference wave by multiplying the normalized interference wave component by the first correlation value. a multiplier; a second multiplier that multiplies the normalized interference wave component by the second correlation value to obtain the second estimated interference wave; and a second multiplier that delays the second determination signal by a time τ. 2 delay elements, and a diversity route switch that inputs the first determination signal and the output signal of the second delay element and selects and outputs one of the signals. Interference wave removal device. （３）２つのルートを設定してそれぞれのルートの受信
出力を切換える切換えダイバーシティ方式の干渉波除去
装置において、時間τの遅延が与えられて送信された希
望信号および第１の干渉波でなる第１の受信信号と第１
の推定干渉波との差である第１の差信号を生成する第１
の減算器と、遅延が与えられることなく送信された希望
信号および第２の干渉波でなる第２の受信信号と第２の
推定干渉波との差である第２の差信号を生成する第２の
減算器と、前記第１の差信号と第１の判定信号とから第
１のルートの伝送系のインパルス応答を推定して推定イ
ンパルス応答を得ると共に該推定インパルス応答の時間
反転で複素共役な応答と前記第１の差信号とを畳込んだ
第１の整合信号を得る第１の整合フィルタと、前記第２
の差信号と第２の判定信号とから推定する第２のルート
の伝送系のインパルス応答の時間反転で複素共役な応答
と前記第２の差信号とを畳込んだ第２の整合信号を得る
第２の整合フィルタと、前記第１の整合信号を適応等化
して前記第１の判定信号と判定結果の第１の誤差信号と
を得る第１の判定帰還形等化器と、前記第２の整合信号
を適応等化して前記第２の判定信号と判定結果の第２の
誤差信号とを得る第２の判定帰還形等化器と、前記推定
インパルス応答と前記第２の判定信号とを畳込んで推定
希望信号を得る畳込み器と、前記第１の受信信号と前記
推定希望信号との差を取つて干渉波成分を抽出する第３
の減算器と、前記第１の誤差信号と前記干渉波成分との
相関を取つて第１の相関値を得る第１の相関器と、前記
第２の誤差信号と前記干渉波成分との相関を取つて第２
の相関値を得る第２の相関器と、前記干渉波成分に前記
第１の相関値を乗じて前記第１の推定干渉波を得る第１
の乗算器と、前記干渉波成分に前記第２の相関値を乗じ
て前記第２の推定干渉波を得る第２の乗算器と、前記第
２の判定信号に時間τの遅延を与える遅延素子と、前記
第１の判定信号と前記遅延素子の出力信号とを入力して
いずれか一方の信号を選択して出力するダイバーシティ
ルート切換え器とからなることを特徴とする干渉波除去
装置。(3) In a switching diversity type interference wave canceling device that sets two routes and switches the reception output of each route, a first interference wave consisting of the desired signal and the first interference wave transmitted with a delay of time τ is used. 1 received signal and the first
a first difference signal that is the difference between the estimated interference wave of
a subtracter for generating a second difference signal, which is the difference between the second estimated interference wave and a second received signal consisting of the desired signal and the second interference wave transmitted without being delayed. 2, the impulse response of the transmission system of the first route is estimated from the first difference signal and the first determination signal to obtain an estimated impulse response, and the complex conjugate is obtained by time reversal of the estimated impulse response. a first matched filter that obtains a first matched signal that is a convolution of the response and the first difference signal;
A second matching signal is obtained by convolving the second difference signal with a time-reversed complex conjugate response of the impulse response of the transmission system of the second route estimated from the difference signal and the second determination signal. a second matched filter; a first decision feedback equalizer that adaptively equalizes the first matched signal to obtain the first decision signal and a first error signal of the decision result; a second decision feedback equalizer that adaptively equalizes the matching signal of the matching signal to obtain the second decision signal and a second error signal of the decision result; and the estimated impulse response and the second decision signal. a convolver that obtains an estimated desired signal by convolution; and a third convolver that extracts an interference wave component by taking the difference between the first received signal and the estimated desired signal.
a subtracter, a first correlator that obtains a first correlation value by correlating the first error signal and the interference wave component, and a correlation between the second error signal and the interference wave component. Take the second
a second correlator that obtains a correlation value; and a first correlator that multiplies the interference wave component by the first correlation value to obtain the first estimated interference wave.
a second multiplier that multiplies the interference wave component by the second correlation value to obtain the second estimated interference wave, and a delay element that delays the second determination signal by a time τ. and a diversity route switch which inputs the first determination signal and the output signal of the delay element and selects and outputs one of the signals. （４）２つのルートを設定してそれぞれのルートの受信
出力を切換える切換えダイバーシティ方式の干渉波検出
装置において、時間τの遅延が与えられて送信された希
望信号および第１の干渉波でなる第１の受信信号と第１
の推定干渉波との差である第１の差信号を生成する第１
の減算器と、遅延が与えられることなく送信された希望
信号および第２の干渉波でなる第２の受信信号と第２の
推定干渉波との差である第２の差信号を生成する第２の
減算器と、前記第１の差信号と第１の基準信号とから第
１のルートの伝送系のインパルス応答を推定して推定イ
ンパルス応答を得ると共に該推定インパルス応答の時間
反転で複素共役は応答と前記第１の差信号とを畳込んだ
第１の整合信号を得る第１の整合フィルタと、前記第２
の差信号と第２の基準信号とから推定する第２のルート
の伝送系のインパルス応答の時間反転で複素共役な応答
と前記第２の差信号とを畳込んだ第２の整合信号を得る
第２の整合フィルタと、前記第１の基準信号を用いて前
記第１の整合信号を適応等化して第１の判定信号と判定
結果の第１の誤差信号とを得る第１の判定帰還形等化器
と、前記第２の基準信号を用いて前記第２の整合信号を
適応等化して第２の判定信号と判定結果の第２の誤差信
号とを得る第２の判定帰還形等化器と、前記推定インパ
ルス応答と前記第２の基準信号とを畳込んで推定希望信
号を得る畳込み器と、前記第１の受信信号と前記推定希
望信号との差を取って干渉波成分を抽出する第３の減算
器と、仮定した送信シンボル列を表すトレーニング信号
を発生するトレーニング信号発生器と、前記トレーニン
グ信号に時間τの遅延を与える第１の遅延素子と、前記
第１の誤差信号に応じて前記第１の判定信号と前記第１
の遅延素子の出力信号のいずれか一方を選択して前記第
１の基準信号として出力する第１の切換え器と、前記第
２の誤差信号に応じて前記第２の判定信号と前記トレー
ニング信号のいずれか一方を選択して前記第２の基準信
号として出力する第２の切換え器と、前記第１の誤差信
号と前記干渉波成分との相関を取って第１の相関値を得
る第１の相関器と、前記第２の誤差信号と前記干渉波成
分との相関を取って第２の相関値を得る第２の相関器と
、前記干渉波成分に前記第１の相関値を乗じて前記第１
の推定干渉波を得る第１の乗算器と、前記干渉波成分に
前記第２の相関値を乗じて前記第２の推定干渉波を得る
第２の乗算器と、前記第２の判定信号に時間τの遅延を
与える第２の遅延素子と、前記第１の判定信号と前記第
２の遅延素子の出力信号とを入力していずれか一方の信
号を選択して出力するダイバーシティルート切換え器と
からなることを特徴とする干渉波除去装置。(4) In a switching diversity type interference wave detection device that sets two routes and switches the reception output of each route, a first interference wave consisting of the desired signal and the first interference wave transmitted with a delay of time τ is used. 1 received signal and the first
a first difference signal that is the difference between the estimated interference wave of
a subtracter for generating a second difference signal, which is the difference between the second estimated interference wave and a second received signal consisting of the desired signal and the second interference wave transmitted without being delayed. 2, the impulse response of the transmission system of the first route is estimated from the first difference signal and the first reference signal to obtain an estimated impulse response, and the complex conjugate is obtained by time reversal of the estimated impulse response. a first matched filter that obtains a first matched signal that is a convolution of the response and the first difference signal;
A second matching signal is obtained by convolving the second difference signal with a time-reversed complex conjugate response of the impulse response of the transmission system of the second route estimated from the difference signal and the second reference signal. a second matched filter; and a first decision feedback type that adaptively equalizes the first matched signal using the first reference signal to obtain a first decision signal and a first error signal of the decision result. an equalizer, and a second decision feedback type equalization that adaptively equalizes the second matching signal using the second reference signal to obtain a second decision signal and a second error signal of the decision result. a convolver that obtains an estimated desired signal by convolving the estimated impulse response and the second reference signal, and a convolver that obtains an estimated desired signal by taking the difference between the first received signal and the estimated desired signal to obtain an interference wave component. a third subtractor for extracting, a training signal generator for generating a training signal representing an assumed transmission symbol sequence, a first delay element for providing a delay of time τ to the training signal, and the first error signal. The first determination signal and the first
a first switch that selects one of the output signals of the delay element and outputs it as the first reference signal; and a first switch that selects one of the output signals of the delay element and outputs it as the first reference signal; a second switch that selects one of the signals and outputs it as the second reference signal; and a first switch that correlates the first error signal and the interference wave component to obtain a first correlation value. a second correlator that obtains a second correlation value by correlating the second error signal and the interference wave component; 1st
a first multiplier for obtaining an estimated interference wave; a second multiplier for obtaining the second estimated interference wave by multiplying the interference wave component by the second correlation value; a second delay element that provides a delay of time τ; and a diversity route switch that receives the first determination signal and the output signal of the second delay element and selects and outputs one of the signals. An interference wave removal device characterized by comprising: （５）２つのルートを設定してそれぞれのルートの受信
出力を切換える切換えダイバーシティ方式の干渉波検出
装置において、時間τの遅延が与えられて送信された希
望信号および第１の干渉波でなる第１の受信信号と第１
の推定干渉波との差である第１の差信号を生成する第１
の減算器と、遅延が与えられることなく送信された希望
信号および第２の干渉波でなる第２の受信信号と第２の
推定干渉波との差である第２の差信号を生成する第２の
減算器と、前記第１の差信号と第１の判定信号とから第
１のルートの伝送系のインパルス応答を推定して推定イ
ンパルス応答を得ると共に該推定インパルス応答の時間
反転で複素共役は応答と前記第１の差信号とを畳込んだ
第１の整合信号を得る第１の整合フィルタと、前記第２
の差信号と第２の判定信号とから推定する第２のルート
の伝送系のインパルス応答の時間反転で複素共役な応答
と前記第２の差信号とを畳込んだ第２の整合信号を得る
第２の整合フィルタと、前記第１の整合信号を適応等化
して前記第１の判定信号を得る第１の判定帰還形等化器
と、前記第２の整合信号を適応等化して前記第２の判定
信号を得る第２の判定帰還形等化器と、前記推定インパ
ルス応答と前記第２の判定信号とを畳込んで推定希望信
号を得る畳込み器と、前記第１の受信信号と前記推定希
望信号との差を取つて干渉波成分を抽出する第３の減算
器と、前記第１の整合フィルタに入力する前記第１の差
信号の電力を検出する第１の電力検出器と、前記第２の
整合フィルタに入力する前記第２の差信号の電力を検出
する第２の電力検出器と、前記第１の電力検出器が検出
する電力を最小とする第１のタップ係数を得る第１のタ
ップ係数制御器と、前記第２の電力検出器が検出する電
力を最小とする第２のタップ係数を得る第２のタップ係
数制御器と、前記干渉波成分に前記第１のタップ係数を
乗じて前記第１の推定干渉波を得る第１の乗算器と、前
記干渉波成分に前記第２のタップ係数を乗じて前記第２
の推定干渉波を得る第２の乗算器と、前記第２の判定信
号に時間τの遅延を与える遅延素子と、前記第１の判定
信号と前記遅延素子の出力信号とを入力していずれか一
方の信号を選択して出力するダイバーシティルート切換
え器とからなることを特徴とする干渉波除去装置。(5) In a switching diversity type interference wave detection device that sets two routes and switches the reception output of each route, a first interference wave consisting of the desired signal and the first interference wave transmitted with a delay of time τ is used. 1 received signal and the first
a first difference signal that is the difference between the estimated interference wave of
a subtracter for generating a second difference signal, which is the difference between the second estimated interference wave and a second received signal consisting of the desired signal and the second interference wave transmitted without being delayed. 2, the impulse response of the transmission system of the first route is estimated from the first difference signal and the first determination signal to obtain an estimated impulse response, and the complex conjugate is obtained by time reversal of the estimated impulse response. a first matched filter that obtains a first matched signal that is a convolution of the response and the first difference signal;
A second matching signal is obtained by convolving the second difference signal with a time-reversed complex conjugate response of the impulse response of the transmission system of the second route estimated from the difference signal and the second determination signal. a second matched filter; a first decision feedback equalizer that adaptively equalizes the first matched signal to obtain the first decision signal; and a first decision feedback equalizer that adaptively equalizes the second matched signal to obtain the first decision signal; a second decision feedback equalizer that obtains the second decision signal; a convolver that obtains the estimated desired signal by convolving the estimated impulse response and the second decision signal; and a second decision feedback equalizer that obtains the second decision signal; a third subtractor that extracts an interference wave component by taking the difference from the estimated desired signal; and a first power detector that detects the power of the first difference signal input to the first matched filter. , a second power detector that detects the power of the second difference signal input to the second matched filter, and a first tap coefficient that minimizes the power detected by the first power detector. a second tap coefficient controller that obtains a second tap coefficient that minimizes the power detected by the second power detector; a first multiplier that multiplies the interference wave component by a tap coefficient to obtain the first estimated interference wave; and a first multiplier that multiplies the interference wave component by the second tap coefficient to obtain the second estimated interference wave.
a second multiplier that obtains an estimated interference wave; a delay element that delays the second determination signal by a time τ; An interference wave removal device comprising a diversity route switch that selects and outputs one signal. （６）２つのルートを設定してそれぞれのルートの受信
出力を切換える切換えダイバーシティ方式の干渉波検出
装置において、時間τの遅延が与えられて送信された希
望信号および第１の干渉波でなる第１の受信信号と第１
の推定干渉波との差である第１の差信号を生成する第１
の減算器と、遅延が与えられることなく送信された希望
信号および第２の干渉波でなる第２の受信信号と第２の
推定干渉波との差である第２の差信号を生成する第２の
減算器と、前記第１の差信号と第１の基準信号とから第
１のルートの伝送系のインパルス応答を推定して推定イ
ンパルス応答を得ると共に該推定インパルス応答の時間
反転で複素共役な応答と前記第１の差信号とを畳込んだ
第１の整合信号を得る第１の整合フィルタと、前記第２
の差信号と第２の基準信号とから推定する第２のルート
の伝送系のインパルス応答の時間反転で複素共役な応答
と前記第２の差信号とを畳込んだ第２の整合信号を得る
第２の整合フィルタと、前記第１の基準信号を用いて前
記第１の整合信号を適応等化して第１の判定信号と判定
結果の第１の誤差信号とを得る第１の判定帰還形等化器
と、前記第２の基準信号を用いて前記第２の整合信号を
適応等化して第２の判定信号と判定結果の第２の誤差信
号とを得る第２の判定帰還形等化器と、前記推定インパ
ルス応答と前記第２の基準信号とを畳込んで推定希望信
号を得る畳込み器と、前記第１の受信信号と前記推定希
望信号との差を取って干渉波成分を抽出する第３の減算
器と、仮定した送信シンボル列を表すトレーニング信号
を発生するトレーニング信号発生器と、前記トレーニン
グ信号に時間τの遅延を与える第１の遅延素子と、前記
第１の誤差信号に応じて前記第１の判定信号と前記第１
の遅延素子の出力信号のいずれか一方を選択して前記第
１の基準信号として出力する第１の切換え器と、前記第
２の誤差信号に応じて前記第２の判定信号と前記トレー
ニング信号のいずれか一方を選択して前記第２の基準信
号として出力する第２の切換え器と、前記第１の整合フ
ィルタに入力する前記第１の差信号の電力を検出する第
１の電力検出器と、前記第２の整合フィルタに入力する
前記第２の差信号の電力を検出する第２の電力検出器と
、前記第１の電力検出器が検出する電力を最小とする第
１のタップ係数を得る第１のタップ係数制御器と、前記
第２の電力検出器が検出する電力を最小とする第２のタ
ップ係数を得る第２のタップ係数制御器と、前記干渉波
成分に前記第１のタップ係数を乗じて前記第１の推定干
渉波を得る第１の乗算器と、前記干渉波成分に前記第２
のタップ係数を乗じて前記第２の推定干渉波を得る第２
の乗算器と、前記第２の判定信号に時間τの遅延を与え
る第２の遅延素子と、前記第１の判定信号と前記第２の
遅延素子の出力信号とを入力していずれか一方の信号を
選択して出力するダイバーシティルート切換え器とから
なることを特徴とする干渉波除去装置。(6) In a switching diversity type interference wave detection device that sets two routes and switches the reception output of each route, a first interference wave consisting of the desired signal and the first interference wave transmitted with a delay of time τ is used. 1 received signal and the first
a first difference signal that is the difference between the estimated interference wave of
a subtracter for generating a second difference signal, which is the difference between the second estimated interference wave and a second received signal consisting of the desired signal and the second interference wave transmitted without being delayed. 2, the impulse response of the transmission system of the first route is estimated from the first difference signal and the first reference signal to obtain an estimated impulse response, and the complex conjugate is obtained by time reversal of the estimated impulse response. a first matched filter that obtains a first matched signal that is a convolution of the response and the first difference signal;
A second matching signal is obtained by convolving the second difference signal with a time-reversed complex conjugate response of the impulse response of the transmission system of the second route estimated from the difference signal and the second reference signal. a second matched filter; and a first decision feedback type that adaptively equalizes the first matched signal using the first reference signal to obtain a first decision signal and a first error signal of the decision result. an equalizer, and a second decision feedback type equalization that adaptively equalizes the second matching signal using the second reference signal to obtain a second decision signal and a second error signal of the decision result. a convolver that obtains an estimated desired signal by convolving the estimated impulse response and the second reference signal, and a convolver that obtains an estimated desired signal by taking the difference between the first received signal and the estimated desired signal to obtain an interference wave component. a third subtractor for extracting, a training signal generator for generating a training signal representing an assumed transmission symbol sequence, a first delay element for providing a delay of time τ to the training signal, and the first error signal. The first determination signal and the first
a first switch that selects one of the output signals of the delay element and outputs it as the first reference signal; and a first switch that selects one of the output signals of the delay element and outputs it as the first reference signal; a second switch that selects one of the signals and outputs it as the second reference signal; and a first power detector that detects the power of the first difference signal input to the first matched filter. , a second power detector that detects the power of the second difference signal input to the second matched filter, and a first tap coefficient that minimizes the power detected by the first power detector. a second tap coefficient controller that obtains a second tap coefficient that minimizes the power detected by the second power detector; a first multiplier that obtains the first estimated interference wave by multiplying the interference wave component by a tap coefficient;
The second estimated interference wave is obtained by multiplying by the tap coefficient of
a multiplier, a second delay element that gives a delay of time τ to the second determination signal, and a multiplier that inputs the first determination signal and the output signal of the second delay element and outputs one of the signals. An interference wave removal device comprising a diversity route switch that selects and outputs a signal.