JPH0435547A - Interference wave eliminating device - Google Patents
Interference wave eliminating deviceInfo
- Publication number
- JPH0435547A JPH0435547A JP2142239A JP14223990A JPH0435547A JP H0435547 A JPH0435547 A JP H0435547A JP 2142239 A JP2142239 A JP 2142239A JP 14223990 A JP14223990 A JP 14223990A JP H0435547 A JPH0435547 A JP H0435547A
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- signal
- interference wave
- interference
- diversity
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- 230000015572 biosynthetic process Effects 0.000 abstract description 7
- 238000003786 synthesis reaction Methods 0.000 abstract description 7
- 230000000694 effects Effects 0.000 abstract description 6
- 230000003044 adaptive effect Effects 0.000 description 9
- 238000005562 fading Methods 0.000 description 8
- 238000010586 diagram Methods 0.000 description 7
- 238000000034 method Methods 0.000 description 4
- 238000012935 Averaging Methods 0.000 description 1
- 230000005540 biological transmission Effects 0.000 description 1
- 230000003111 delayed effect Effects 0.000 description 1
- 230000008034 disappearance Effects 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 239000000284 extract Substances 0.000 description 1
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Abstract
Description
【発明の詳細な説明】
(産業上の利用分野)
本発明は干渉波除去装置に関し、特にダイバーシティ方
式を必要とするマルチパスフェージング回線においてD
/U (希望波対干渉波比)がマイナスとなるような強
い干渉波が存在する場合の広帯域干渉波の除去およびフ
ェージングによる波形歪の適応等化を行なう干渉波除去
装置に関する。DETAILED DESCRIPTION OF THE INVENTION (Field of Industrial Application) The present invention relates to an interference wave canceling device, and in particular to a multipath fading line that requires a diversity method.
The present invention relates to an interference wave removal device that performs broadband interference wave removal and adaptive equalization of waveform distortion due to fading when there is a strong interference wave whose /U (desired wave to interference wave ratio) is negative.
(従来の技術)
従来、PSKJ??QAMを用いたディジタルマイクロ
波回線に対してFM回線による干渉や、隣接チャンネル
からの干渉または妨害波などが問題となることがある。(Conventional technology) Conventionally, PSKJ? ? Interference by FM lines, interference or jamming waves from adjacent channels, etc. may pose problems for digital microwave lines using QAM.
特に、ディジタル伝送が高速の場合、FM干渉波は狭帯
域干渉波と見なされるが、それ以外の干渉波は広帯域の
場合がある。また、強度のマルチパスフェージング回線
においてはダイバーシティ方式や適応等化技術が不可欠
であり、見通し外通信のように伝搬距離が大きな回線で
は整合フィルタ(MP)と判定帰還形等化器(DFE)
とを用いた受信機が必要となる。マルチパスフェージン
グ環境下での広帯域干渉波の除去を行なう従来の干渉波
除去装置の一例を第3図に示す。In particular, when digital transmission is high-speed, FM interference waves are considered narrowband interference waves, but other interference waves may be broadband interference waves. In addition, diversity methods and adaptive equalization techniques are essential for strong multipath fading lines, and matched filters (MPs) and decision feedback equalizers (DFEs) are used for lines with long propagation distances such as non-line-of-sight communications.
A receiver using this is required. FIG. 3 shows an example of a conventional interference wave removal device that removes broadband interference waves in a multipath fading environment.
第3図において、301と302は乗算器、303は加
算器、304は減算器、305と308と309はAG
C#!器、306と307は相関器、310は切換え器
、311は適応等化器である。この従来の干渉波除去装
置は、2つのルートのそれぞれの受信信号を2重ダイバ
ーシティ合成し、該合成信号を適応等化器(EQL)を
用いる適応受信機に通して等化を行なっている。In FIG. 3, 301 and 302 are multipliers, 303 is an adder, 304 is a subtracter, and 305, 308, and 309 are AG
C#! 306 and 307 are correlators, 310 is a switch, and 311 is an adaptive equalizer. This conventional interference wave removal device performs double diversity combining of received signals from two routes, and equalizes the combined signal by passing it through an adaptive receiver using an adaptive equalizer (EQL).
ダイバーシティ合成は加算器303で行われ、その合成
方式は最大比合成である。入力1と入力2の各ダイバー
シティ入力は、それぞれAGCtI!幅器308と30
9でフラットフェージングによるレベル変動を除かれ、
加算器303で最大比合成されるように乗算器301と
302においてそれぞれ複素タップ係数が乗じられる。Diversity combining is performed by adder 303, and its combining method is maximum ratio combining. Each diversity input of input 1 and input 2 is AGCtI! Width gauges 308 and 30
9 removes level fluctuations due to flat fading,
Multipliers 301 and 302 respectively multiply the signals by complex tap coefficients so that adder 303 performs maximum ratio combining.
これらのタップ係数は、相関器306と307によるダ
イバーシティ合成後のAGC増幅器305の出力と、A
GC@@器308器上0809の出力との間の相関値で
ある。干渉波が存在しない時は切換え器310はAGC
増幅器305の出力を選択して出力し、適応等化器(E
QL)311に受信信号を供給する。この適応等化器3
11でマルチパスフェージングによる波形歪が除去され
る。These tap coefficients are the output of AGC amplifier 305 after diversity synthesis by correlators 306 and 307, and A
This is the correlation value between the output of the GC @@ device 308 and the output of the device 0809. When there is no interference wave, the switch 310 switches to AGC.
The output of the amplifier 305 is selected and output, and the adaptive equalizer (E
QL) 311 with the received signal. This adaptive equalizer 3
11, waveform distortion due to multipath fading is removed.
第3図の従来の干渉波除去装置において受信信号中に広
帯域でD/U比(干渉波と希望波の比)fマイナスとな
るような強力な干渉波が存在する場合、切換え器310
は減算器304の出力を選択して出力する。この減算器
304は乗算器301の出力から乗算器302の出力を
減じており、加算器303が位相について同相合成を行
うのに対し、減算器304は逆相合成を行うことで干渉
波の除去を行う。In the conventional interference wave removal device shown in FIG. 3, if there is a strong interference wave in the received signal with a wide band D/U ratio (ratio of interference wave to desired wave) f minus, the switching device 310
selects and outputs the output of the subtracter 304. The subtracter 304 subtracts the output of the multiplier 302 from the output of the multiplier 301, and while the adder 303 performs in-phase synthesis, the subtracter 304 performs anti-phase synthesis to remove interference waves. I do.
第4図にその干渉波除去の動作を示す。(a>と(d)
はそれぞれダイバーシティルート1.2の入力1.2を
示している。ここで、各ルートの希望波を31.S2と
し、干渉波をJl、J2とする。D/Uがマイナスとな
るくらい干渉波が大きい時には、干渉波どうしが同相合
成されるように制御され、(b)と(e)に示すように
、乗算器301と302の出力において干渉波J1とJ
2の振幅および位相が等しくなる。この場合、(c)に
示す加算器303の出力は、干渉波どうしの同相合成を
示している。一方、(f)に示すように減算器304で
は干渉波どうしが逆相合成され、干渉波は除去されて、
希望信号波のみが抽出されている。しかしSlと82に
ついては、最大比合成のみならず同相合成すら行なわれ
ないことになる。特に、希望波Sと干渉波Jとの位相関
係により、希望信号波が消えることがある。入力1と入
力2が(g)と(J)に示すようにSとJとの振幅位相
関係が同じ場合、乗算器301と302の出力は(h)
と(k>に示すように一致する。この時<i>に示す加
算器303の出力はS#JJも同相合成となり(1)に
示す減算器304の出力はSもJも逆相合成となる。す
なわち干渉波は除去されているが、希望信号波も消滅す
ることになる。FIG. 4 shows the interference wave removal operation. (a> and (d)
respectively indicate input 1.2 of diversity route 1.2. Here, the desired wave for each route is 31. S2, and the interference waves are Jl and J2. When the interference waves are large enough to make D/U negative, the interference waves are controlled to be combined in phase, and as shown in (b) and (e), the interference waves J1 are generated at the outputs of the multipliers 301 and 302. and J
2 have the same amplitude and phase. In this case, the output of the adder 303 shown in (c) represents in-phase combination of interference waves. On the other hand, as shown in (f), in the subtracter 304, the interference waves are combined in reverse phase, and the interference waves are removed.
Only the desired signal wave is extracted. However, for Sl and 82, not only maximum ratio combining but also in-phase combining will not be performed. In particular, the desired signal wave may disappear due to the phase relationship between the desired signal S and the interference wave J. When input 1 and input 2 have the same amplitude and phase relationship with S and J as shown in (g) and (J), the outputs of multipliers 301 and 302 are (h)
and (k>).At this time, the output of the adder 303 shown in <i> is also an in-phase combination of S#JJ, and the output of the subtracter 304 shown in (1) is an anti-phase combination of both S and J. In other words, although the interference wave is removed, the desired signal wave also disappears.
(発明が解決しようとする課題)
上述した従来の干渉波除去装置は、干渉波を除去しよう
とすると希望波についてダイバーシティの最大比合成ま
たは同相合成が行なわれないから、ダイバーシティ効果
が得られず、マルチパスフェージング回線での適応等化
による最適受信と干渉波除去とが両立せず、場合によっ
ては希望信号を消失させてしまうと言う欠点がある。(Problems to be Solved by the Invention) In the conventional interference wave canceling device described above, when attempting to remove interference waves, maximum ratio combining or in-phase combining of diversity is not performed for desired waves, so no diversity effect can be obtained. Optimal reception by adaptive equalization on a multipath fading line and interference wave removal are not compatible, and there is a drawback that the desired signal may be lost in some cases.
そこで本発明の目的は、干渉波除去に伴う希望波の消滅
を防ぎかつダイバーシティ効果を損なわずに、強い広帯
域干渉波を除去し、さらにマルチパス歪を効果的に除去
することができる干渉波除去装置を提供することにある
。Therefore, an object of the present invention is to provide interference wave cancellation that can prevent the disappearance of desired waves due to interference wave cancellation, eliminate strong broadband interference waves, and effectively eliminate multipath distortion without impairing the diversity effect. The goal is to provide equipment.
(課題を解決するための手段)
本発明に係る干渉波除去装置は、
2つのルートを設定してそれぞれのルートの受信出力を
合成する合成ダイバーシティ方式の干渉波除去装置であ
って、第1の希望信号と第1の干渉波でなる第1の受信
信号と、第2の希望信号と第2の干渉波でなる第2の受
信信号とを前記第1の干渉波と前記第2の干渉波とが同
相となるように合成する第1の加算器と、該第1の加算
器の出力信号を正規化して正規化信号を得るAGC#!
I@器と、前記第1の受信信号と前記正規化信号との相
関を取って第1の相関値を得る第1の相関器と、前記第
2の受信信号と前記正規化信号との相関を取って第2の
相関値を得る第2の相関器と、前記正規化信号に前記第
1の相関値を乗ずる第1の乗算器と、前記正規化信号に
前記第2の相関値を乗ずる第2の乗算器と、前記第1の
受信信号と前記第1の乗算器の出力信号との差を取って
第1の差信号を得る第1の減算器と、前記第2の受信信
号と前記第2の乗算器の出力信号との差を取って第2の
差信号を得る第2の減算器と、前記第1の差信号のS/
N比を向上させる第1の整合フィルタと、前記第2の差
信号のS/N比を向上させる第2の整合フィルタと、前
記第1の整合フィルタの出力信号と前記第2の整合フィ
ルタの出力信号とを合成する第2の加算器と、該第2の
加算器の出力信号の等化を行なう判定帰還型等化器とか
らなることを特徴とする。(Means for Solving the Problems) An interference wave canceling device according to the present invention is a combining diversity type interference wave canceling device that sets two routes and combines the received outputs of the respective routes. A first received signal consisting of a desired signal and a first interference wave, and a second received signal consisting of a second desired signal and a second interference wave, are combined with the first interference wave and the second interference wave. A first adder that combines AGC#! so that they are in phase, and normalizes the output signal of the first adder to obtain a normalized signal.
a first correlator that obtains a first correlation value by correlating the first received signal and the normalized signal; and a correlation between the second received signal and the normalized signal. a second correlator that obtains a second correlation value by multiplying the normalized signal by the first correlation value; and a first multiplier that multiplies the normalized signal by the second correlation value. a second multiplier; a first subtracter that obtains a first difference signal by taking the difference between the first received signal and the output signal of the first multiplier; and a first subtracter that obtains a first difference signal; a second subtracter that obtains a second difference signal by taking the difference from the output signal of the second multiplier; and a S/S/ of the first difference signal.
a first matched filter that improves the S/N ratio, a second matched filter that improves the S/N ratio of the second difference signal, and an output signal of the first matched filter and the second matched filter. It is characterized by comprising a second adder that combines the output signals with the output signal, and a decision feedback type equalizer that equalizes the output signal of the second adder.
(実施例) 次に、本発明について図面を参照して説明する。(Example) Next, the present invention will be explained with reference to the drawings.
第1図は本発明の干渉波除去装置の一実施例の構成を示
すブロック図である。第2図は本発明の干渉波除去動作
を説明する図である。FIG. 1 is a block diagram showing the configuration of an embodiment of the interference wave removal device of the present invention. FIG. 2 is a diagram illustrating the interference wave removal operation of the present invention.
第1図において、1と2と8はAGC増幅器、3と4と
9と10は乗算器、5と6と11と12は相関器、7と
17は加算器、13と14は減算器、15と16は整合
フィルタ(MF118は判定帰還型等化器(DFE)で
ある。In FIG. 1, 1, 2, and 8 are AGC amplifiers, 3, 4, 9, and 10 are multipliers, 5, 6, 11, and 12 are correlators, 7 and 17 are adders, 13 and 14 are subtracters, 15 and 16 are matched filters (MF 118 is a decision feedback equalizer (DFE)).
第1図において、入力1と入力2の各ダイバーシティ入
力はそれぞれAGC増幅器1と2により振幅が1に正規
化され、加算器7で同相合成されるように乗算器3と4
においてそれぞれ複素タッグ係数が乗じられる。これら
のタッグ係数は、相関器5と6によるダイバーシティ合
成後のAGC増幅器8の出力と、AGCt!I@器1お
よび2の出力との間の相関値である。第1図の実施例の
受信信号中に広帯域でD/U比(干渉波と希望波の比)
がマイナスとなるような強力な干渉波が存在する場合、
入力1と入力2での希望波と干渉波をそれぞれ81.J
l、S2.J2とし、第2図(a)と(d)のように示
されているとする。ここで、干渉波Jl、J2は任意の
レベルを有する広帯域干渉波とする。tたその発生源は
1つで、この干渉波をJとし、ルート1の干渉波を
Jl=A1exp (Jφ1 ) −J ・
(1)でモデル化する。ここで、AleXp(Jφ1)
はJに対するルート1の伝達関数である。同様にルート
2に対しても干渉波を
J2=A2ex11(jφ2 )−J ・(2
)とおく。In FIG. 1, each diversity input of input 1 and input 2 is normalized to have an amplitude of 1 by AGC amplifiers 1 and 2, respectively, and multipliers 3 and 4 are in-phase combined by an adder 7.
are respectively multiplied by complex tag coefficients. These tag coefficients are the output of the AGC amplifier 8 after diversity synthesis by the correlators 5 and 6, and the AGCt! I@ is the correlation value between the outputs of devices 1 and 2. D/U ratio (ratio of interference wave to desired wave) in the received signal of the embodiment shown in Fig. 1 in a wide band
If there is a strong interference wave that makes
The desired wave and interference wave at input 1 and input 2 are respectively 81. J
l, S2. Let it be assumed that J2 is shown as shown in FIGS. 2(a) and (d). Here, the interference waves Jl and J2 are broadband interference waves having arbitrary levels. There is only one source of t, and this interference wave is J, and the interference wave of route 1 is Jl=A1exp (Jφ1) −J ・
Modeled using (1). Here, AleXp(Jφ1)
is the transfer function of root 1 to J. Similarly, for route 2, the interference wave is J2=A2ex11(jφ2)−J・(2
)far.
この時、乗算器3と乗算器4の出力は、それぞれ(b)
と(e)に示すようになり、AGC増幅器1と2で正規
化された干渉波成分について同相合成されるように制御
される。従って、加算器7の出力は(C)に示すように
干渉波J1+J2が希望波間に比べて支配的なレベルと
なり、希望波については同相合成されないから、そのレ
ベルは余り増大しない、さらに加算器7の出力は、AG
C増幅器8により正規化され、(f)に示すようになる
。ここで、ルート1の干渉波成分が基準になった場合、
AGC増幅器8の出力は
Jr=1・eXll(Jφ1)+a (S1+82)・
・・(3)
で示される。ここでαは干渉波にAGOが掛かったこと
による希望波に対するレベル縮小率である。At this time, the outputs of multiplier 3 and multiplier 4 are (b), respectively.
As shown in (e), the AGC amplifiers 1 and 2 are controlled to perform in-phase synthesis of the normalized interference wave components. Therefore, as shown in (C) in the output of the adder 7, the interference waves J1+J2 have a dominant level compared to the desired waves, and since the desired waves are not combined in phase, their level does not increase much. The output of AG
It is normalized by the C amplifier 8 and becomes as shown in (f). Here, if the interference wave component of route 1 is used as the reference,
The output of the AGC amplifier 8 is Jr=1・eXll(Jφ1)+a (S1+82)・
...(3) It is shown as follows. Here, α is the level reduction rate with respect to the desired wave due to the AGO applied to the interference wave.
相関器11と12はそれぞれ、この正規化干渉波成分J
rとルート1およびルート2の受信信号との相関を取る
。この相関操作はAGC増幅器8の出力の複素共役と各
ダイバーシティ入力との積の平均を取ることにより行わ
れる。なお相関器11と12の相関値をそれぞれWl、
W2とすれば、下記のように示せる。Correlators 11 and 12 each receive this normalized interference wave component J
Correlate r with the received signals of routes 1 and 2. This correlation operation is performed by averaging the products of the complex conjugate of the output of the AGC amplifier 8 and each diversity input. Note that the correlation values of correlators 11 and 12 are Wl, respectively.
If W2 is used, it can be shown as follows.
W1=E目exp(−j φ1)
+α(31°+82°))・(Sl +J1)]=^1
・J+Δ1 ・・・(4)W 2 =
E[(eXE)(−j φ1)+α(81° +S
2” ))・(32+J2)]= A2− exp(
j (φ2−φ1))J+Δ2 ・(5)上式にお
いて、A1とA2はJrに含まれる希望波成分と入力で
の希望波成分との相関値であるが、(3)式の希望波成
分は干渉波に対して小さく、それらの相関成分はきわめ
て小さくなる0乗算器9と10は正規化された干渉波成
分Jrに(4)、(5)式の複素係数W1およびW2を
乗じる。すなわち乗算器9と10の出力はそれぞれ、(
1)、(2)式で示されたJlとJ2に近似される。第
2図(g)と(J)にその様子を示す、このJlとJ2
の推定値J1とJ2をそれぞれルート1とルート2の入
力から減算器13と14により減すること伸より、(h
)と(k)に示すように入力1と入力2の各ダイバーシ
ティルートについて広帯域干渉波を除去できる。ところ
で、(g)と(J)に示すように、乗算器9と10の出
力には(3)式の希望波成分に係数W1とW2がそれぞ
れ乗じられた希望成分W1α(S1+S2)とW2C(
S1十82)とがそれぞれ含まれているから、(h)と
(k)に示すように本来の希望波S1、S2のほかに、
それぞれ−W2C(S1+82)と−W2C(S1+8
2)とが加えられる。これらの成分は干渉となるがレベ
ルが低く、(1)と(1)に示すようにMF15と16
により遅延分散した希望波成分を基準タイミングに最大
比合成される。すなわちSN比の最大化が行なわれ、M
F15と16の出力は加算器17によりダイバーシティ
合成が行なわれる。この加算器17の出力はDFE18
に通され、符号量干渉が除去される。W1=Eth exp(-j φ1) +α(31°+82°))・(Sl +J1)]=^1
・J+Δ1...(4) W 2 =
E[(eXE)(-j φ1)+α(81° +S
2”))・(32+J2)]=A2−exp(
j (φ2-φ1)) J+Δ2 ・(5) In the above equation, A1 and A2 are the correlation values between the desired wave component included in Jr and the desired wave component at the input, but the desired wave component in equation (3) is small with respect to the interference wave, and their correlation components are extremely small. The zero multipliers 9 and 10 multiply the normalized interference wave component Jr by the complex coefficients W1 and W2 of equations (4) and (5). That is, the outputs of multipliers 9 and 10 are respectively (
It is approximated by Jl and J2 shown in equations 1) and (2). This Jl and J2 are shown in Figure 2 (g) and (J).
By subtracting the estimated values J1 and J2 from the inputs of routes 1 and 2, respectively, by subtractors 13 and 14, (h
) and (k), wideband interference waves can be removed for each diversity route of input 1 and input 2. By the way, as shown in (g) and (J), the outputs of multipliers 9 and 10 have desired components W1α(S1+S2) and W2C(
In addition to the original desired waves S1 and S2, as shown in (h) and (k),
−W2C(S1+82) and −W2C(S1+8
2) is added. These components cause interference, but the level is low, and as shown in (1) and (1), MF15 and 16
The desired wave components delayed and dispersed are combined at the maximum ratio at the reference timing. In other words, the S/N ratio is maximized, and M
The outputs of F15 and F16 are subjected to diversity combining by an adder 17. The output of this adder 17 is the DFE18
to remove code amount interference.
以後の動作において干渉波が変動しても、適応的に干渉
波が除去され、マルチパスフェージングによる歪も除去
される。Even if the interference waves fluctuate in subsequent operations, the interference waves are adaptively removed and distortion due to multipath fading is also removed.
(発明の効果)
本発明は、以上説明したように、各ダイバーシティルー
トで受信された干渉波が同相となるようにダイバーシテ
ィ受信信号を合成し、希望波のレベルを抑圧して干渉波
成分を抽出し、この干渉波成分から生成した推定干渉波
を各ダイバーシティルートの受信信号から減することに
より強度な広帯域干渉波を除去し、それぞれの信号のS
/N比を向上させる整合フィルタ(MF)の出力におい
てダイバーシティ合成を行い、その合成信号を判定帰還
形勢化器で等化することにより、ダイバーシティ効果を
損なうことなくマルチパス歪を除去することができる。(Effects of the Invention) As explained above, the present invention combines diversity reception signals so that the interference waves received on each diversity route are in phase, suppresses the level of the desired wave, and extracts the interference wave component. Then, by subtracting the estimated interference wave generated from this interference wave component from the received signal of each diversity route, strong broadband interference waves are removed, and the S of each signal is
By performing diversity synthesis at the output of a matched filter (MF) that improves the /N ratio and equalizing the combined signal with a decision feedback shaper, multipath distortion can be removed without impairing the diversity effect. .
第1図は本発明の干渉波除去装置の一実施例の構成を示
すブロック図、第2図は本実施例の干渉波除去動作を説
明する図、第3図は従来の干渉波除去装置の構成を示す
ブロック図、第4図は従来の干渉波除去装置の干渉波除
去動作を説明する図である。
1.2,8,305,308,309.・・・AGC増
幅器、3,4,9,10,301゜302・・・乗算器
、5,6,11,12,306゜307・・・相関器、
7,17.303・・・加算器、13.14,304・
・・減算器、15.16・・・整合フィルタ(MF)、
18・・・判定帰還型等化器(DFE)、310・・・
切換え器、311・・・適応等化器。FIG. 1 is a block diagram showing the configuration of an embodiment of the interference wave removal device of the present invention, FIG. 2 is a diagram explaining the interference wave removal operation of this embodiment, and FIG. 3 is a diagram of the conventional interference wave removal device. FIG. 4, a block diagram showing the configuration, is a diagram illustrating the interference wave removal operation of the conventional interference wave removal device. 1.2, 8, 305, 308, 309. ... AGC amplifier, 3, 4, 9, 10, 301° 302... Multiplier, 5, 6, 11, 12, 306° 307... Correlator,
7,17.303...adder, 13.14,304...
...Subtractor, 15.16...Matched filter (MF),
18...Decision feedback equalizer (DFE), 310...
Switcher, 311...Adaptive equalizer.
Claims (1)
合成する合成ダイバーシティ方式の干渉波除去装置にお
いて、第1の希望信号と第1の干渉波でなる第1の受信
信号と、第2の希望信号と第2の干渉波でなる第2の受
信信号とを前記第1の干渉波と前記第2の干渉波とが同
相となるように合成する第1の加算器と、該第1の加算
器の出力信号を正規化して正規化信号を得るAGC増幅
器と、前記第1の受信信号と前記正規化信号との相関を
取って第1の相関値を得る第1の相関器と、前記第2の
受信信号と前記正規化信号との相関を取つて第2の相関
値を得る第2の相関器と、前記正規化信号に前記第1の
相関値を乗ずる第1の乗算器と、前記正規化信号に前記
第2の相関値を乗ずる第2の乗算器と、前記第1の受信
信号と前記第1の乗算器の出力信号との差を取つて第1
の差信号を得る第1の減算器と、前記第2の受信信号と
前記第2の乗算器の出力信号との差を取つて第2の差信
号を得る第2の減算器と、前記第1の差信号のS/N比
を向上させる第1の整合フィルタと、前記第2の差信号
のS/N比を向上させる第2の整合フィルタと、前記第
1の整合フィルタの出力信号と前記第2の整合フィルタ
の出力信号とを合成する第2の加算器と、該第2の加算
器の出力信号の等化を行なう判定帰還形等化器とからな
ることを特徴とする干渉波除去装置。In a combining diversity interference wave canceling device that sets two routes and combines the received outputs of the respective routes, a first received signal consisting of a first desired signal and a first interference wave, and a second desired signal are combined. a first adder that combines a signal and a second received signal consisting of a second interference wave such that the first interference wave and the second interference wave are in phase; and the first addition. an AGC amplifier that normalizes an output signal of the amplifier to obtain a normalized signal; a first correlator that obtains a first correlation value by correlating the first received signal and the normalized signal; a second correlator that obtains a second correlation value by correlating the second received signal with the normalized signal; a first multiplier that multiplies the normalized signal by the first correlation value; a second multiplier that multiplies the normalized signal by the second correlation value; and a first multiplier that takes the difference between the first received signal and the output signal of the first multiplier.
a first subtracter for obtaining a difference signal, a second subtractor for obtaining a second difference signal by taking the difference between the second received signal and the output signal of the second multiplier; a first matched filter that improves the S/N ratio of the second difference signal, a second matched filter that improves the S/N ratio of the second difference signal, and an output signal of the first matched filter; An interference wave characterized by comprising: a second adder that combines the output signal of the second matched filter; and a decision feedback equalizer that equalizes the output signal of the second adder. removal device.
Priority Applications (4)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP2142239A JPH073960B2 (en) | 1990-05-31 | 1990-05-31 | Interference wave remover |
US07/707,120 US5335359A (en) | 1990-05-31 | 1991-05-30 | Diversity receiver using matched filter and decision feedback equalizer |
EP96203037A EP0757456B1 (en) | 1990-05-31 | 1991-05-31 | Diversity receivers |
EP91304948A EP0459823B1 (en) | 1990-05-31 | 1991-05-31 | Radio communication system |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP2142239A JPH073960B2 (en) | 1990-05-31 | 1990-05-31 | Interference wave remover |
Publications (2)
Publication Number | Publication Date |
---|---|
JPH0435547A true JPH0435547A (en) | 1992-02-06 |
JPH073960B2 JPH073960B2 (en) | 1995-01-18 |
Family
ID=15310672
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP2142239A Expired - Lifetime JPH073960B2 (en) | 1990-05-31 | 1990-05-31 | Interference wave remover |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPH073960B2 (en) |
Cited By (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5524023A (en) * | 1994-04-28 | 1996-06-04 | Nec Corporation | Interference cancellation using power-inversion adaptive array and LMS adaptive equalizer |
US5659584A (en) * | 1995-01-31 | 1997-08-19 | Matsushita Electric Industrial Co., Ltd. | Data receiving system for receiving data signal faded and delayed |
US5748673A (en) * | 1995-01-31 | 1998-05-05 | Matsushita Electric Industrial Co., Ltd. | Data receiving apparatus |
JP2010507337A (en) * | 2006-10-17 | 2010-03-04 | インターデイジタル テクノロジー コーポレーション | Transmitter / receiver with hybrid adaptive interference canceller to eliminate noise generated by transmitter |
-
1990
- 1990-05-31 JP JP2142239A patent/JPH073960B2/en not_active Expired - Lifetime
Cited By (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5524023A (en) * | 1994-04-28 | 1996-06-04 | Nec Corporation | Interference cancellation using power-inversion adaptive array and LMS adaptive equalizer |
US5659584A (en) * | 1995-01-31 | 1997-08-19 | Matsushita Electric Industrial Co., Ltd. | Data receiving system for receiving data signal faded and delayed |
US5748673A (en) * | 1995-01-31 | 1998-05-05 | Matsushita Electric Industrial Co., Ltd. | Data receiving apparatus |
JP2010507337A (en) * | 2006-10-17 | 2010-03-04 | インターデイジタル テクノロジー コーポレーション | Transmitter / receiver with hybrid adaptive interference canceller to eliminate noise generated by transmitter |
Also Published As
Publication number | Publication date |
---|---|
JPH073960B2 (en) | 1995-01-18 |
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