JP5569862B2 - Xenon lamp lighting device - Google Patents

Xenon lamp lighting device Download PDF

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JP5569862B2
JP5569862B2 JP2010114032A JP2010114032A JP5569862B2 JP 5569862 B2 JP5569862 B2 JP 5569862B2 JP 2010114032 A JP2010114032 A JP 2010114032A JP 2010114032 A JP2010114032 A JP 2010114032A JP 5569862 B2 JP5569862 B2 JP 5569862B2
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charging
xenon lamp
capacitor
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義男 西沢
徹 永瀬
勝明 大久保
信一 鈴木
祐哉 山崎
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Iwasaki Denki KK
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Description

本発明は概略としてキセノンランプ点灯装置に関し、より具体的には、擬似太陽光を照射する擬似太陽光照射装置に用いられるキセノンランプ点灯装置に関する。   The present invention generally relates to a xenon lamp lighting device, and more specifically, to a xenon lamp lighting device used in a pseudo-sunlight irradiation device that emits simulated sunlight.

太陽電池の光電変換特性などの各種太陽エネルギー利用機器の性能測定のために、自然太陽光のスペクトル分布を再現する擬似太陽光を被照射体に照射する擬似太陽光照射装置が知られている。この種の擬似太陽光照射装置においては、キセノンランプからなる光源が箱体内に設置され、光源からの光が光学フィルタを介して照射されることで放射面から擬似太陽光が放射される。   In order to measure the performance of various solar energy utilizing devices such as the photoelectric conversion characteristics of solar cells, a pseudo solar irradiation device that irradiates an object to be irradiated with pseudo sunlight that reproduces the spectral distribution of natural sunlight is known. In this type of simulated sunlight irradiating device, a light source composed of a xenon lamp is installed in a box, and simulated sunlight is emitted from the radiation surface by irradiating light from the light source through an optical filter.

本装置では、例えば、発光長が１０００ｍｍ以上のキセノンランプ（以下、「ランプ」という）が用いられ、直流のランプ電流が通電され、そのランプ電流値を点灯装置によって調整することにより照射面の照度が制御される。一般的には、点灯時のランプ電流は数十アンペア（例えば７０Ａ）、ランプ電圧は数百ボルト（例えば５００Ｖ）程度であり、このランプ電流／電圧が、１回の点灯あたり数十ｍＳｅｃから数百ｍＳｅｃにわたって通電／印加される。この出力状態が定電流又は定電力で制御され、点灯期間中に被照射体の性能が測定される。   In this apparatus, for example, a xenon lamp having a light emission length of 1000 mm or more (hereinafter referred to as “lamp”) is used, a direct-current lamp current is applied, and the lamp current value is adjusted by the lighting device, whereby the illuminance on the irradiated surface Is controlled. Generally, the lamp current at the time of lighting is several tens of amperes (for example, 70 A), the lamp voltage is about several hundred volts (for example, 500 V), and this lamp current / voltage is several tens of mSec per lighting. Energized / applied over 100 mSec. This output state is controlled by constant current or constant power, and the performance of the irradiated object is measured during the lighting period.

上記の場合、ランプ電力が３５ｋＷとなり、瞬時（例えば１００ｍＳｅｃ）とはいえ、この電力を商用電源から直接供給すると、同じ商用電源の系統の周辺機器に障害を及ぼすことや、商用電源と照射装置の間に容量の大きい接点及び配線が必要となることが問題なる。そこで一般には、照射装置内に点灯装置を設け、点灯装置において電力を蓄積し、点灯指令に応じてその蓄積された電力をランプに供給する構成が採用される。   In the above case, the lamp power is 35 kW, and even if it is instantaneous (for example, 100 mSec), if this power is supplied directly from the commercial power supply, it will cause a failure in peripheral devices of the same commercial power system, A problem arises in that a large-capacity contact and wiring are required between them. Therefore, generally, a configuration is adopted in which a lighting device is provided in the irradiation device, electric power is accumulated in the lighting device, and the accumulated power is supplied to the lamp in response to a lighting command.

図４に従来の点灯装置を示す。整流器２及び平滑コンデンサ３で構成される直流電源回路１００で交流電源１が直流電圧に変換され、その直流電圧が充電回路２００に供給される。充電回路２００はトランジスタ４、５、６及び７からなるインバータを含む。制御部４０からの充電指令に応じて、ＰＷＭ制御回路８によってトランジスタ４、７及びトランジスタ５、６の導通時間が制御され、高周波で交互に導通される。これによりトランス９の１次巻線に交流電圧が発生するとともに、トランス９の２次巻線に昇圧比に応じた電圧が発生する。トランス９の２次巻線に発生した電圧は整流器１０で整流され、コイル１１で平滑されて大容量の電解コンデンサ（充電コンデンサ）１３に充電される。ここで、電流検出抵抗１２で検出される充電電流に比例した電圧（即ち、Ｂ−Ｇ間の電圧）と基準電圧１５とが誤差増幅器１４に入力され、両者が等しくなるようにＰＷＭ制御回路８によってトランジスタ４〜７の導通時間がＰＷＭ制御される。これにより、大容量の充電コンデンサ１３は設定された電流値で定電流充電されていく。充電コンデンサ１３がランプ電圧よりも充分に高い電圧（例えば、１０００Ｖ）に充電されると、ＰＷＭ制御回路８はインバータの動作を一旦停止（又は充電電圧を保持）し、スタンバイ状態となる。   FIG. 4 shows a conventional lighting device. The AC power supply 1 is converted into a DC voltage by the DC power supply circuit 100 including the rectifier 2 and the smoothing capacitor 3, and the DC voltage is supplied to the charging circuit 200. Charging circuit 200 includes an inverter composed of transistors 4, 5, 6 and 7. In accordance with the charging command from the control unit 40, the conduction time of the transistors 4, 7 and the transistors 5, 6 is controlled by the PWM control circuit 8 and is alternately conducted at a high frequency. As a result, an AC voltage is generated in the primary winding of the transformer 9 and a voltage corresponding to the boost ratio is generated in the secondary winding of the transformer 9. The voltage generated in the secondary winding of the transformer 9 is rectified by the rectifier 10, smoothed by the coil 11, and charged to a large capacity electrolytic capacitor (charging capacitor) 13. Here, the voltage proportional to the charging current detected by the current detection resistor 12 (that is, the voltage between B and G) and the reference voltage 15 are input to the error amplifier 14, and the PWM control circuit 8 so that they are equal. As a result, the conduction time of the transistors 4 to 7 is PWM-controlled. As a result, the large-capacity charging capacitor 13 is charged with a constant current at the set current value. When the charging capacitor 13 is charged to a voltage sufficiently higher than the lamp voltage (for example, 1000 V), the PWM control circuit 8 temporarily stops the operation of the inverter (or holds the charging voltage) and enters a standby state.

次に、制御部４０からランプ点灯指令が発せられると、電流制御回路３００が動作を開始する。電流制御回路３００は降圧チョッパ回路からなり、降圧チョッパ回路は、ＩＧＢＴ等の半導体スイッチ１６、ダイオード１７、コイル１８、コンデンサ１９、電流検出抵抗２０、半導体スイッチ１６の導通時間を制御するＰＷＭ制御回路２１、誤差増幅器２２、基準電圧２３及び帰還素子２７で構成される。この時点で、ランプ２５の両端に充電コンデンサ１３の電圧とほぼ等しい直流電圧（１０００Ｖ）が直ちに印加される。その後、イグナイタ（不図示）のパルストランス２４によってパルス電圧が上記直流電圧に重畳され、ランプ２５の絶縁破壊が起こる。   Next, when a lamp lighting command is issued from the control unit 40, the current control circuit 300 starts operation. The current control circuit 300 includes a step-down chopper circuit, and the step-down chopper circuit is a PWM control circuit 21 that controls the conduction time of the semiconductor switch 16 such as an IGBT, the diode 17, the coil 18, the capacitor 19, the current detection resistor 20, and the semiconductor switch 16. , An error amplifier 22, a reference voltage 23, and a feedback element 27. At this time, a DC voltage (1000 V) almost equal to the voltage of the charging capacitor 13 is immediately applied across the lamp 25. Thereafter, a pulse voltage is superimposed on the DC voltage by a pulse transformer 24 of an igniter (not shown), and dielectric breakdown of the lamp 25 occurs.

ランプ２５が絶縁破壊を起こすと、コンデンサ１３の充電電圧を電源として電流制御回路３００からの制限された電流がランプ２５に投入される。電流制御回路３００において、電流検知抵抗２０に流れる電流に比例する電圧信号（検出電圧）と基準電圧２３からの電圧信号（基準電圧）が誤差増幅器２２に入力され、両者が等しくなるように、ＰＷＭ制御回路２１によって半導体スイッチ１６の導通時間がＰＷＭ制御される。これにより、コンデンサ１３を電源とするランプ２５の直流点灯が設定電流値で定電流制御される。類似の構成が特許文献１に開示されている。   When the lamp 25 undergoes dielectric breakdown, a limited current from the current control circuit 300 is input to the lamp 25 using the charging voltage of the capacitor 13 as a power source. In the current control circuit 300, a voltage signal (detection voltage) proportional to the current flowing through the current detection resistor 20 and a voltage signal (reference voltage) from the reference voltage 23 are input to the error amplifier 22 so that both are equal. The conduction time of the semiconductor switch 16 is PWM controlled by the control circuit 21. As a result, the DC lighting of the lamp 25 using the capacitor 13 as a power source is controlled at a constant current with the set current value. A similar configuration is disclosed in Patent Document 1.

図２（Ａ）及び（Ｂ）に、点灯指令が発せられてからの充電コンデンサ１３の充電電圧とランプ電流のタイムチャートを示す。図示するように、ｔ０でランプ２５が放電を開始すると充電コンデンサ１３の充電電圧はＶ０から急激に低下し、ランプの定電流点灯に必要な電圧Ｖ１を下回るとランプ電流は低下し始める（ｔ１）。なお、電圧Ｖ１＝（ランプ電圧＋トランス２４の２次巻線端電圧）／ＰＷＭ回路２１の最大デューティ、である。そして、充電電圧がランプ放電に必要な電圧Ｖminを下回るとランプ２５は消灯する（ｔ２）。なお、電圧Ｖmin＝ランプ電圧＋トランス２４の２次巻線端電圧、である。   2A and 2B show time charts of the charging voltage and the lamp current of the charging capacitor 13 after the lighting command is issued. As shown in the figure, when the lamp 25 starts discharging at t0, the charging voltage of the charging capacitor 13 rapidly decreases from V0, and when the voltage falls below the voltage V1 necessary for constant current lighting of the lamp, the lamp current starts to decrease (t1). . The voltage V1 = (lamp voltage + secondary winding end voltage of the transformer 24) / maximum duty of the PWM circuit 21. When the charging voltage falls below the voltage Vmin required for lamp discharge, the lamp 25 is turned off (t2). Note that the voltage Vmin = the lamp voltage + the secondary winding end voltage of the transformer 24.

特開平７−２９９０３０号公報JP-A-7-299030

しかし、従来の構成では、ランプ２５の点灯時間（特に定電流制御できる期間）を長くするためには充電コンデンサ１３の容量を大きくするしかなかった。これにより装置の大型化やコストアップが問題となっていた。特に、充電コンデンサ１３は装置全体に対するスペース及びコストの割合が大きく、充電コンデンサの小型化・低コスト化はキセノンランプ点灯装置において重要な課題である。   However, in the conventional configuration, in order to lengthen the lighting time of the lamp 25 (particularly the period during which constant current control is possible), the capacity of the charging capacitor 13 must be increased. As a result, the increase in size and cost of the apparatus has been a problem. In particular, the charging capacitor 13 has a large space and cost ratio with respect to the entire device, and downsizing and cost reduction of the charging capacitor are important issues in the xenon lamp lighting device.

具体的には、例えば、充電コンデンサ１３の充電電圧が１０００Ｖ、設定ランプ電流が７０Ａ、ランプ電圧が５００Ｖ、このときのトランス２４の２次巻線の電圧降下が２０Ｖ、降圧チョッパ回路３００のＰＷＭ制御回路２１の最大デューティ比が９０％の場合、上記の定電流点灯可能な電圧Ｖ１について、Ｖ１＝（５００Ｖ＋２０Ｖ）／０．９＝５７８Ｖ、となる。上述のように、充電電圧がＶ１（５７８Ｖ）まで低下するとランプ電流が減少し始める。ここで、充電コンデンサ１３の充電電圧は初期の充電電圧に対し、５７．８％の電圧が残っているのに、被照射体へ照射される擬似太陽光出力が低下し始めるため、被照射体の性能測定は時間ｔ１で終了することになってしまう。   Specifically, for example, the charging voltage of the charging capacitor 13 is 1000 V, the set lamp current is 70 A, the lamp voltage is 500 V, the voltage drop of the secondary winding of the transformer 24 at this time is 20 V, and the PWM control of the step-down chopper circuit 300 is performed. When the maximum duty ratio of the circuit 21 is 90%, V1 = (500V + 20V) /0.9=578V for the voltage V1 at which the constant current lighting is possible. As described above, when the charging voltage is reduced to V1 (578V), the lamp current starts to decrease. Here, although the charging voltage of the charging capacitor 13 remains at 57.8% of the initial charging voltage, the simulated solar light output to the irradiated object starts to decrease, and thus the irradiated object This performance measurement ends at time t1.

そこで、本発明は充電コンデンサの容量を大きくすることなく、ランプの定電流点灯期間を長くできる構成を提供することを目的とする。   Therefore, an object of the present invention is to provide a configuration that can extend the constant current lighting period of a lamp without increasing the capacity of a charging capacitor.

本発明の第１の側面は、キセノンランプ点灯装置であって、充電コンデンサ（１３）を有する充電回路（２００）、充電コンデンサの充電電圧を昇圧して平滑する昇圧回路（２５０）、及び昇圧回路の出力を受けて定電流制御されたランプ電流をキセノンランプに投入する電流制御回路（３００）を備え、電流制御回路の入力電圧について、定電流制御に必要な入力電圧が所定値Ｖ１である場合に、昇圧回路が昇圧出力を所定値Ｖ１以上に昇圧するように構成されたキセノンランプ点灯装置。   A first aspect of the present invention is a xenon lamp lighting device, a charging circuit (200) having a charging capacitor (13), a boosting circuit (250) for boosting and smoothing a charging voltage of the charging capacitor, and a boosting circuit. A current control circuit (300) that receives the output of the current and inputs a constant current controlled lamp current to the xenon lamp, and the input voltage required for constant current control is a predetermined value V1 for the input voltage of the current control circuit And a xenon lamp lighting device configured such that the booster circuit boosts the boosted output to a predetermined value V1 or more.

また、昇圧回路（２５０）が充電電圧を検出する検出回路（３５）を備え、充電電圧が所定値Ｖ２（Ｖ１≦Ｖ２）以下となった場合に、昇圧回路が昇圧出力電圧を所定値Ｖ２以上に昇圧するように構成した。
さらに、所定値Ｖ２について、Ｖ２＝Ｖ１としてもよい。 Further, the booster circuit (250) includes a detection circuit (35) for detecting the charging voltage, and when the charging voltage becomes equal to or lower than a predetermined value V2 (V1 ≦ V2), the booster circuit increases the boosted output voltage to a predetermined value V2 or higher. It was configured to boost the pressure.
Further, V2 = V1 may be set for the predetermined value V2.

本発明による第１の実施例のキセノンランプ点灯装置を示す図である。It is a figure which shows the xenon lamp lighting device of 1st Example by this invention. 従来例及び実施例のキセノンランプ点灯装置の動作を説明する図である。It is a figure explaining operation | movement of the xenon lamp lighting device of a prior art example and an Example. 本発明による第２の実施例のキセノンランプ点灯装置の昇圧回路を示す図である。It is a figure which shows the booster circuit of the xenon lamp lighting device of 2nd Example by this invention. 従来のキセノンランプ点灯装置を示す図である。It is a figure which shows the conventional xenon lamp lighting device.

実施例１．
図１に本発明の第１の実施例によるキセノンランプ点灯装置の回路構成を示す。図において、直流電源回路１００、充電回路２００、電流制御回路３００及び不図示のイグナイタ回路は、図４に示す従来例と同様であるので説明を省略する。本発明は充電回路２００と電流制御回路３００の間に昇圧回路２５０を備えた点が従来例と異なる。 Example 1.
FIG. 1 shows a circuit configuration of a xenon lamp lighting device according to a first embodiment of the present invention. In the figure, the DC power supply circuit 100, the charging circuit 200, the current control circuit 300, and the igniter circuit (not shown) are the same as those in the conventional example shown in FIG. The present invention is different from the conventional example in that a booster circuit 250 is provided between the charging circuit 200 and the current control circuit 300.

昇圧回路２５０は、コイル２６、ＩＧＢＴ等の半導体スイッチ２７、ダイオード２８、抵抗２９、３０、出力平滑用の電解コンデンサ（平滑コンデンサ）３１、半導体スイッチ２７の導通時間を制御するＰＷＭ制御回路３２、誤差増幅器３３、基準電圧３４で構成される昇圧チョッパ回路である。   The booster circuit 250 includes a coil 26, a semiconductor switch 27 such as an IGBT, a diode 28, resistors 29 and 30, an output smoothing electrolytic capacitor (smoothing capacitor) 31, a PWM control circuit 32 that controls the conduction time of the semiconductor switch 27, and an error. This is a step-up chopper circuit composed of an amplifier 33 and a reference voltage 34.

昇圧回路２５０の制御において、例えば、平滑コンデンサ３１の電圧に比例した電圧となる抵抗２９、抵抗３０間の電圧信号と基準電圧３４が誤差増幅器３３に入力され、平滑コンデンサ３１の電圧が所定値に維持される。この昇圧回路２５０が動作していないときは充電コンデンサ１３の電圧がそのまま平滑コンデンサ３１に充電される（即ち、充電コンデンサ１３の電圧がそのまま電流制御回路３００の入力となる）。一方、昇圧回路２５０が動作しているときは充電コンデンサ１３の電圧が昇圧されて平滑コンデンサ３１に充電される（即ち、充電コンデンサ１３の電圧より高い平滑コンデンサ３１の電圧が電流制御回路３００の入力となる）。なお、平滑コンデンサ３１の容量は充電コンデンサ１３の容量よりも充分に小さい。   In the control of the booster circuit 250, for example, the voltage signal between the resistor 29 and the resistor 30 and the reference voltage 34, which are voltages proportional to the voltage of the smoothing capacitor 31, are input to the error amplifier 33, and the voltage of the smoothing capacitor 31 is set to a predetermined value. Maintained. When the booster circuit 250 is not operating, the voltage of the charging capacitor 13 is charged as it is into the smoothing capacitor 31 (that is, the voltage of the charging capacitor 13 is directly input to the current control circuit 300). On the other hand, when the booster circuit 250 is operating, the voltage of the charging capacitor 13 is boosted and charged to the smoothing capacitor 31 (that is, the voltage of the smoothing capacitor 31 higher than the voltage of the charging capacitor 13 is input to the current control circuit 300. Becomes). Note that the capacity of the smoothing capacitor 31 is sufficiently smaller than the capacity of the charging capacitor 13.

ランプ２５が絶縁破壊を起こすと、電流制御回路３００は充電コンデンサ１３又は平滑コンデンサ３１の充電エネルギーを電源として、図４で説明したものと同様の定ランプ電流制御が行なわれる。   When the lamp 25 undergoes dielectric breakdown, the current control circuit 300 performs constant lamp current control similar to that described with reference to FIG. 4 using the charging energy of the charging capacitor 13 or the smoothing capacitor 31 as a power source.

図２（Ｃ）及び（Ｄ）に第１の実施例における充電コンデンサ１３の充電電圧とランプ電流のタイムチャートを示す。
本実施例では制御部４０からランプ点灯指令が発せられるのと同時に昇圧回路２５０も動作を開始する。図２（Ｃ）に示すように、ランプ２５がｔ０で放電を開始すると充電コンデンサ１３の電位はＶ０から急激に低下していく。これと並行して昇圧回路２５０は平滑コンデンサ３１の電圧がＶ１以上の設定値（例えば、Ｖ０）を維持するよう動作する。従って、充電コンデンサ１３の電圧が定電流点灯可能な電圧Ｖ１を下回っても、平滑コンデンサ３１には上記設定値が充電されて電流制御回路３００に投入される。 2C and 2D show time charts of the charging voltage and the lamp current of the charging capacitor 13 in the first embodiment.
In this embodiment, the booster circuit 250 also starts to operate simultaneously with the lamp lighting command issued from the control unit 40. As shown in FIG. 2 (C), when the lamp 25 starts discharging at t0, the potential of the charging capacitor 13 rapidly decreases from V0. In parallel with this, the booster circuit 250 operates so that the voltage of the smoothing capacitor 31 maintains a set value (for example, V0) equal to or higher than V1. Therefore, even if the voltage of the charging capacitor 13 is lower than the voltage V1 at which the constant current can be lit, the smoothing capacitor 31 is charged with the set value and is input to the current control circuit 300.

これにより、図２（Ｄ）に示すように、定電流制御維持時間（ｔ０〜ｔ１′）を従来の図２（Ｂ）における時間（ｔ０〜ｔ１）よりも延ばすことが可能となり、擬似太陽光照射装置の性能を向上することができる。   As a result, as shown in FIG. 2D, the constant current control maintaining time (t0 to t1 ′) can be extended from the conventional time (t0 to t1) in FIG. The performance of the irradiation apparatus can be improved.

実施例２．
図３に第２の実施例の回路構成を示す。本実施例では、昇圧回路２５０が充電コンデンサ１３の充電電圧を検出する検出回路３５を備えた点で第１の実施例と異なる。検出回路３５は分圧抵抗３６、３７、基準電圧３８、及びコンパレータ３９からなり、分圧回路で検出される充電電圧が基準電圧３８（後述する電圧Ｖ２に対応）を下回るとコンパレータ出力がローとなり、これを受けてＰＷＭ制御回路３２が動作を開始する。なお、コンパレータのロジックは逆であってもよく、具体的な回路構成は当業者によって適宜設計される。なお、本実施例では、昇圧回路２５０は制御部４０からの点灯指令ではなく、検出回路３５の出力信号によって動作が開始される。 Example 2
FIG. 3 shows a circuit configuration of the second embodiment. This embodiment differs from the first embodiment in that the booster circuit 250 includes a detection circuit 35 that detects the charging voltage of the charging capacitor 13. The detection circuit 35 includes voltage dividing resistors 36 and 37, a reference voltage 38, and a comparator 39. When the charging voltage detected by the voltage dividing circuit falls below the reference voltage 38 (corresponding to a voltage V2 described later), the comparator output becomes low. In response, the PWM control circuit 32 starts operation. The logic of the comparator may be reversed, and the specific circuit configuration is appropriately designed by those skilled in the art. In the present embodiment, the booster circuit 250 is started by the output signal of the detection circuit 35 instead of the lighting command from the control unit 40.

図２（Ｅ）及び（Ｆ）に本実施例における充電コンデンサ１３の充電電圧とランプ電流のタイムチャートを示す。
第１の実施例と異なる点は、昇圧回路２５０の動作開始タイミングである。具体的には、充電電圧が所定値Ｖ２（Ｖ１≦Ｖ２＜Ｖ０）以下になった場合に、昇圧回路２５０は昇圧出力電圧を所定値Ｖ２（又はＶ２以上）に維持する。好ましくは、所定値Ｖ２は、定電流制御可能な電圧Ｖ１（例えば、ランプ電圧５００Ｖ＋トランス２４の２次巻線端電圧２０Ｖ）／ＰＷＭ制御回路２１の最大デューティ０．９＝５７８Ｖ）に等しいかそれよりも若干高い電圧（例えば、６００Ｖ程度）に設定される。 2E and 2F show time charts of the charging voltage and the lamp current of the charging capacitor 13 in this embodiment.
The difference from the first embodiment is the operation start timing of the booster circuit 250. Specifically, when the charging voltage becomes equal to or lower than a predetermined value V2 (V1 ≦ V2 <V0), the booster circuit 250 maintains the boosted output voltage at the predetermined value V2 (or V2 or higher). Preferably, the predetermined value V2 is equal to or equal to the voltage V1 (for example, the lamp voltage 500V + the secondary winding end voltage 20V of the transformer 24) / the maximum duty 0.9 of the PWM control circuit 21 = 578V) capable of constant current control. Is set to a slightly higher voltage (for example, about 600 V).

これにより、図２（Ｃ）の場合と比較して昇圧回路２５０が動作する時間が短くなり、かつ昇圧電圧も低く設定できるため、昇圧回路２５０での消費電力（損失）が少なくなる。また、充電電圧がＶ０〜Ｖ２の間の充電コンデンサ１３の電圧低下速度が遅くなり、図２（Ｆ）に示すように、定電流制御持続時間（ｔ０〜ｔ１″）は図２（Ｄ）の場合と比べて長くなる。従って、擬似太陽光照射装置の性能を更に向上することができる。   As a result, the time during which the booster circuit 250 operates is shortened compared to the case of FIG. 2C, and the boosted voltage can be set low, so that power consumption (loss) in the booster circuit 250 is reduced. In addition, the voltage drop rate of the charging capacitor 13 between the charging voltage V0 and V2 is slowed down, and the constant current control duration (t0 to t1 ″) is as shown in FIG. 2D as shown in FIG. Therefore, the performance of the simulated solar light irradiation device can be further improved.

なお、理想的な回路からなる点灯装置であれば、Ｖ２＝Ｖ１の場合が最も定電流制御持続時間が長くなるが、各素子のインピーダンス又はランプの特性のばらつき等を考慮して、前述したように、Ｖ２はＶ１よりも若干高くしておくことが望ましい。   In the case of a lighting device composed of an ideal circuit, the constant current control duration is the longest when V2 = V1, but as described above in consideration of variations in the impedance of each element or lamp characteristics. In addition, it is desirable that V2 be slightly higher than V1.

本実施例では検出回路３５を用いて昇圧回路２５０の動作期間を決定したが、検出回路３５の替わりに、点灯指令が出てから動作するタイマを制御部４０の外部又は内部に設け、タイマの設定値を図２（Ａ）のｔ１より短くしておき、充電電圧がＶ１以下となる前に昇圧回路２５０が動作するようにしてもよい。   In this embodiment, the operation period of the booster circuit 250 is determined using the detection circuit 35. Instead of the detection circuit 35, a timer that operates after a lighting command is issued is provided outside or inside the control unit 40, and the timer The set value may be shorter than t1 in FIG. 2A, and the booster circuit 250 may operate before the charging voltage becomes V1 or less.

以上より、本発明の点灯装置によると、従来例と比較してランプ電流の定電流制御維持時間を延ばすことが可能となり、擬似太陽光照射装置の性能を向上することができる。   As described above, according to the lighting device of the present invention, it is possible to extend the constant current control maintenance time of the lamp current as compared with the conventional example, and it is possible to improve the performance of the simulated sunlight irradiation device.

以上に本発明の好適な実施例を説明した。各実施例に共通する利点として、最大定電流制御維持時間を従来例と同じ時間とした場合、装置の主要な部分を占める充電コンデンサ１３の容量を低減でき、点灯装置の小型化、コストダウンが可能となる。またさらに、従来回路（図４）に比べて充電回路２００の充電電圧を低くすることができ、充電コンデンサ１３や整流器１０を低耐圧（即ち、小型、低コスト）の部品で構成できる。但し、この場合には、充電コンデンサ１３の容量を更に大きくすることが望ましい。いずれにしても、本発明によると、充電回路２００の設計自由度が大きくなるので好適である。   The preferred embodiments of the present invention have been described above. As an advantage common to each embodiment, when the maximum constant current control maintaining time is the same as that of the conventional example, the capacity of the charging capacitor 13 occupying the main part of the device can be reduced, and the lighting device can be reduced in size and cost. It becomes possible. Furthermore, the charging voltage of the charging circuit 200 can be lowered as compared with the conventional circuit (FIG. 4), and the charging capacitor 13 and the rectifier 10 can be configured with parts having a low withstand voltage (ie, small size and low cost). However, in this case, it is desirable to further increase the capacity of the charging capacitor 13. In any case, according to the present invention, the design freedom of the charging circuit 200 is increased, which is preferable.

２６．コイル
２７．半導体スイッチ
２８．ダイオード
２９、３０、３６、３７．抵抗
３１．電解コンデンサ
３２．ＰＷＭ制御回路
３３．誤差増幅器
３４、３８．基準電圧
３５．検出回路
３９．コンパレータ
４０．制御部
１００．直流電源回路
２００．充電回路
２５０．昇圧回路
３００．電流制御回路 26. Coil 27. Semiconductor switch 28. Diodes 29, 30, 36, 37. Resistance 31. Electrolytic capacitor 32. PWM control circuit 33. Error amplifiers 34, 38. Reference voltage 35. Detection circuit 39. Comparator 40. Control unit 100. DC power supply circuit 200. Charging circuit 250. Booster circuit 300. Current control circuit

Claims (3)

キセノンランプ点灯装置であって、
交流電源を直流電圧に変換する直流電源回路（１００）、
充電コンデンサ（１３）を有し、前記直流電圧を昇圧して前記充電コンデンサに充電し、昇圧動作を停止して前記充電コンデンサの充電電圧を保持するように構成された充電回路（２００）、
前記昇圧動作を停止している充電回路の前記充電コンデンサの充電電圧を昇圧するとともに前記充電コンデンサよりも容量が小さい平滑コンデンサ（３１）によって平滑する昇圧回路（２５０）、及び
前記昇圧回路の出力を受けて、定電流制御されたランプ電流を前記キセノンランプに投入する電流制御回路（３００）
を備え、
前記電流制御回路の入力電圧について、前記定電流制御に必要な入力電圧が所定値Ｖ１である場合に、前記昇圧回路が昇圧出力を該所定値Ｖ１以上に昇圧するように構成されたキセノンランプ点灯装置。 A xenon lamp lighting device,
A DC power supply circuit (100) for converting an AC power supply into a DC voltage;
A charging circuit (200) having a charging capacitor (13) , configured to boost the DC voltage to charge the charging capacitor, and stop the boosting operation to hold the charging voltage of the charging capacitor ;
A boosting circuit (250) that boosts the charging voltage of the charging capacitor of the charging circuit that has stopped the boosting operation and smoothes it by a smoothing capacitor (31) having a smaller capacity than the charging capacitor, and an output of the boosting circuit In response, a current control circuit (300) for supplying a constant current controlled lamp current to the xenon lamp
With
Regarding the input voltage of the current control circuit, when the input voltage required for the constant current control is a predetermined value V1, the xenon lamp is configured so that the booster circuit boosts the boost output to the predetermined value V1 or more. apparatus. 請求項１のキセノンランプ点灯装置において、前記昇圧回路（２５０）が前記充電電圧を検出する検出回路（３５）を備え、
前記充電電圧が所定値Ｖ２（Ｖ１≦Ｖ２）以下となった場合に、該昇圧回路が昇圧出力電圧を該所定値Ｖ２以上に昇圧するように構成されたキセノンランプ点灯装置。 The xenon lamp lighting device according to claim 1, wherein the booster circuit (250) includes a detection circuit (35) for detecting the charging voltage.
A xenon lamp lighting device configured such that, when the charging voltage becomes equal to or lower than a predetermined value V2 (V1 ≦ V2), the booster circuit boosts the boosted output voltage to the predetermined value V2 or higher. 請求項２のキセノンランプ点灯装置において、前記所定値Ｖ２について、Ｖ２＝Ｖ１であることを特徴とするキセノンランプ点灯装置。


3. The xenon lamp lighting device according to claim 2, wherein the predetermined value V2 is V2 = V1.


JP2010114032A 2010-05-18 2010-05-18 Xenon lamp lighting device Expired - Fee Related JP5569862B2 (en)

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