JP4501829B2 - Discharge lamp lighting device, lighting fixture, and lighting system - Google Patents

Discharge lamp lighting device, lighting fixture, and lighting system Download PDF

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JP4501829B2
JP4501829B2 JP2005280948A JP2005280948A JP4501829B2 JP 4501829 B2 JP4501829 B2 JP 4501829B2 JP 2005280948 A JP2005280948 A JP 2005280948A JP 2005280948 A JP2005280948 A JP 2005280948A JP 4501829 B2 JP4501829 B2 JP 4501829B2
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voltage value
discharge lamp
circuit
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control signal
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JP2007095392A (en
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敏也 神舎
勝信 濱本
秀雄 大谷
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Panasonic Corp
Panasonic Electric Works Co Ltd
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Matsushita Electric Works Ltd
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Description

本発明は、放電灯点灯装置及び照明器具及び照明システムに関するものである。   The present invention relates to a discharge lamp lighting device, a lighting fixture, and a lighting system.

従来から、所望の光出力に応じた電圧値の直流信号である調光信号が入力され、調光信号に応じて放電灯の光出力を制御する放電灯点灯装置が提供されている（例えば、特許文献１参照）。
特開１０−１１２３９６号公報 Conventionally, there has been provided a discharge lamp lighting device that receives a dimming signal, which is a DC signal having a voltage value corresponding to a desired light output, and controls the light output of the discharge lamp according to the dimming signal (for example, Patent Document 1).
JP 10-112396 A

しかし、従来の放電灯点灯装置を用いて、１台の制御装置から出力された調光信号が複数個の放電灯点灯装置に入力される照明システムを構成すると、放電灯点灯装置で発生した伝導ノイズが他の放電灯点灯装置や制御装置に影響を与える可能性があった。   However, if a lighting system in which a dimming signal output from one control device is input to a plurality of discharge lamp lighting devices using a conventional discharge lamp lighting device, the conduction generated in the discharge lamp lighting device is formed. Noise may affect other discharge lamp lighting devices and control devices.

本発明は上記事由に鑑みて為されたものであり、その目的は、伝導ノイズの出入りを抑制することができる放電灯点灯装置及びこれを用いた照明器具並びに照明システムを提供することにある。   The present invention has been made in view of the above-described reasons, and an object thereof is to provide a discharge lamp lighting device capable of suppressing the entry and exit of conduction noise, a lighting fixture using the same, and a lighting system.

請求項１の発明は、フォトカプラと、電圧値が時間に対して単調増加する立上りと電圧値が時間に対して単調減少する立下りとを交互に周期的に繰り返す発振信号を生成する発振回路と、所望の光出力に対応する電圧値の直流信号である調光信号が入力されて調光信号の電圧値と発振信号の電圧値との大小関係が入れ替わったときにフォトカプラの発光素子のオンオフを切換えることにより調光信号の電圧値に応じたデューティ比でフォトカプラの発光素子をオンオフするパルス生成回路と、フォトカプラの出力のデューティ比に応じて電圧値が調光信号の電圧値に対して直線的に変化する直流信号である制御信号を生成する制御信号生成回路と、２個のスイッチング素子の直列回路からなり両端間に直流電力が入力されるスイッチング部とスイッチング部の一方のスイッチング素子の両端間に接続され放電灯とともに共振回路を構成する共振部とを有するインバータ回路と、インバータ回路のスイッチング部のスイッチング素子を交互にオンオフするドライブ回路と、放電灯に供給される電力に対応した電圧値を検出するとともに検出された電圧値と制御信号の電圧値との大小関係に応じた出力を生成する比較演算回路と、放電灯の光出力が制御信号の電圧値に対して直線的に変化するようにドライブ回路がスイッチング素子をオンオフする周波数を比較演算回路の出力に応じて制御する制御回路とを備えることを特徴とする。   According to a first aspect of the present invention, there is provided a photocoupler and an oscillation circuit that generates an oscillation signal that alternately and periodically repeats a rising edge whose voltage value monotonously increases with time and a falling edge whose voltage value monotonously decreases with time. When a dimming signal that is a DC signal having a voltage value corresponding to a desired light output is input and the magnitude relationship between the voltage value of the dimming signal and the voltage value of the oscillation signal is switched, the light emitting element of the photocoupler A pulse generation circuit that turns on / off the light emitting element of the photocoupler at a duty ratio according to the voltage value of the dimming signal by switching on and off, and the voltage value to the voltage value of the dimming signal according to the duty ratio of the output of the photocoupler A control signal generation circuit that generates a control signal that is a direct-current signal that changes linearly, and a switching unit that includes a series circuit of two switching elements and receives DC power between both ends. An inverter circuit having a resonance unit that is connected between both ends of one switching element of the switching unit and forms a resonance circuit together with the discharge lamp, a drive circuit that alternately turns on and off the switching element of the switching unit of the inverter circuit, and a discharge lamp A comparison operation circuit that detects a voltage value corresponding to the supplied power and generates an output according to the magnitude relationship between the detected voltage value and the voltage value of the control signal, and the light output of the discharge lamp is the voltage of the control signal And a control circuit that controls the frequency at which the drive circuit turns on and off the switching element so as to change linearly with respect to the value according to the output of the comparison operation circuit.

この発明によれば、調光信号の入力側と制御信号の出力側の間にフォトカプラが介在することにより、伝導ノイズの出入りを抑制することができる。また、放電灯の光出力が制御信号の電圧値に対して直線的に変化し、且つ制御信号の電圧値が調光信号の電圧値に対して直線的に変化することにより、放電灯の光出力は調光信号の電圧値に対して直線的に変化することになるから、放電灯の光出力と調光信号の電圧値との関係が直線的でない場合に比べ、放電灯の光出力の調整が容易となる。   According to this invention, since the photocoupler is interposed between the input side of the dimming signal and the output side of the control signal, it is possible to suppress the entry and exit of conduction noise. In addition, the light output of the discharge lamp changes linearly with respect to the voltage value of the control signal, and the voltage value of the control signal changes linearly with respect to the voltage value of the dimming signal. Since the output changes linearly with respect to the voltage value of the dimming signal, the light output of the discharge lamp is smaller than when the relationship between the light output of the discharge lamp and the voltage value of the dimming signal is not linear. Adjustment is easy.

請求項２の発明は、請求項１の発明において、制御信号生成回路は、２個の抵抗の直列回路からなり両端間に定電圧が入力される分圧部と、分圧部の一方の抵抗の両端間に接続された出力コンデンサと、フォトカプラの出力によってオンオフされるスイッチング素子と抵抗との直列回路からなり出力コンデンサの両端間に接続された入力部とを有し、出力コンデンサの充電電圧を制御信号の電圧値とすることを特徴とする。   According to a second aspect of the present invention, in the first aspect of the present invention, the control signal generating circuit is composed of a series circuit of two resistors, and a voltage dividing unit to which a constant voltage is input between both ends, and one resistance of the voltage dividing unit. The output capacitor is connected between both ends of the output capacitor, and the input capacitor is composed of a series circuit of a switching element and a resistor that are turned on and off by the output of the photocoupler, and is connected between both ends of the output capacitor. Is the voltage value of the control signal.

この発明によれば、分圧部と入力部との計３個の抵抗の抵抗値を適宜選択するだけで、制御信号の電圧値の取り得る範囲を容易に設定することができる。   According to the present invention, the possible range of the voltage value of the control signal can be easily set only by appropriately selecting the resistance values of a total of three resistors of the voltage dividing unit and the input unit.

請求項３の発明は、請求項２の発明において、発振信号の電圧値は立上り時と立下り時との一方では時間に対して直線的に変化し、他方では時間に対して出力コンデンサの放電特性に応じて曲線的に変化することを特徴とする。   According to a third aspect of the present invention, in the second aspect of the invention, the voltage value of the oscillation signal changes linearly with respect to time at one of the rising time and the falling time, and on the other hand, the discharge of the output capacitor with respect to time. It is characterized by changing in a curve according to the characteristics.

請求項４の発明は、請求項３の発明において、発振信号の電圧値の立上り時又は立下り時の曲線は、互いに傾きが異なる複数本の直線で構成された折れ線からなることを特徴とする。   According to a fourth aspect of the present invention, in the third aspect of the present invention, the rising or falling curve of the voltage value of the oscillation signal is composed of a broken line composed of a plurality of straight lines having different inclinations. .

請求項５の発明は、請求項４の発明において、発振信号の電圧値の立上り時又は立下り時の曲線は、互いに傾きが異なる３本以上の直線で構成された折れ線からなることを特徴とする。   According to a fifth aspect of the present invention, in the fourth aspect of the invention, the rising or falling curve of the voltage value of the oscillation signal comprises a broken line composed of three or more straight lines having different inclinations. To do.

この発明によれば、発振信号の電圧値の立上り時又は立下り時の曲線を互いに傾きが異なる２本の直線で構成された折れ線とする場合に比べ、調光信号と制御信号との関係をより直線に近付けることができる。   According to the present invention, the relationship between the dimming signal and the control signal is greater than when the rising or falling curve of the voltage value of the oscillation signal is a broken line composed of two straight lines having different inclinations. It can be closer to a straight line.

請求項６の発明は、請求項１〜５のいずれかの発明において、発振信号の電圧値の最大値及び最小値は、それぞれ、調光信号の電圧値の最大値及び最小値に略等しいことを特徴とする。   The invention of claim 6 is the invention according to any one of claims 1 to 5, wherein the maximum value and the minimum value of the voltage value of the oscillation signal are substantially equal to the maximum value and the minimum value of the voltage value of the dimming signal, respectively. It is characterized by.

この発明によれば、調光信号の電圧値を変更したときには、フォトカプラがオンオフされるデューティ比も必ず変化することになる。   According to the present invention, when the voltage value of the dimming signal is changed, the duty ratio at which the photocoupler is turned on and off always changes.

請求項７の発明は、請求項２の発明において、制御信号生成回路の入力部は、負の温度特性を有してスイッチング素子に直列に接続されたサーミスタを有し、インバータ回路から放電灯に供給される電力は、制御信号の電圧値に対して単調に増加することを特徴とする。   According to a seventh aspect of the present invention, in the second aspect of the present invention, the input part of the control signal generating circuit has a thermistor having a negative temperature characteristic and connected in series with the switching element, and the inverter circuit is changed to the discharge lamp. The supplied power monotonously increases with respect to the voltage value of the control signal.

この発明によれば、低温時には制御信号の電圧値の下限すなわち放電灯に供給される電力の下限値が高くなるから、低温時の放電灯のちらつきや立ち消えの発生を抑えることができる。   According to this invention, since the lower limit of the voltage value of the control signal, that is, the lower limit value of the electric power supplied to the discharge lamp is high at low temperatures, the occurrence of flickering and extinguishing of the discharge lamp at low temperatures can be suppressed.

請求項８の発明は、請求項１〜７のいずれかの発明において、フォトカプラの発光素子がオンオフされるデューティ比が取り得る上限値と下限値との一方が制御信号の上限値に対応し、他方が制御信号の下限値に対応することを特徴とする。   The invention according to claim 8 is the invention according to any one of claims 1 to 7, wherein one of an upper limit value and a lower limit value that can be taken by the duty ratio at which the light emitting element of the photocoupler is turned on and off corresponds to the upper limit value of the control signal. The other corresponds to the lower limit value of the control signal.

この発明によれば、制御信号の範囲を制限するためのクランプ回路が不要となる。   According to the present invention, a clamp circuit for limiting the range of the control signal becomes unnecessary.

請求項９の発明は、請求項１〜８のいずれかの発明において、放電灯の光出力が調光信号の電圧値に対して単調増加することを特徴とする。   The invention of claim 9 is characterized in that, in any one of claims 1 to 8, the light output of the discharge lamp monotonously increases with respect to the voltage value of the dimming signal.

請求項１０の発明は、請求項１〜９のいずれかに記載の放電灯点灯装置と、放電灯点灯装置を収納した器具本体とを備えることを特徴とする。   A tenth aspect of the invention includes the discharge lamp lighting device according to any one of the first to ninth aspects, and a fixture main body that houses the discharge lamp lighting device.

請求項１１の発明は、請求項１０記載の複数個の照明器具と、各照明器具にそれぞれ調光信号を入力する制御装置とを備えることを特徴とする。   The invention of claim 11 is characterized by comprising a plurality of lighting fixtures according to claim 10 and a control device for inputting a dimming signal to each lighting fixture.

本発明は、調光信号の入力側と制御信号の出力側との間にフォトカプラを介在させたので、伝導ノイズの出入りを低減することができる。また、放電灯の光出力が制御信号の電圧値に対して直線的に変化し、且つ制御信号の電圧値が調光信号の電圧値に対して直線的に変化することにより、放電灯の光出力は調光信号の電圧値に対して直線的に変化することになるから、放電灯の光出力と調光信号の電圧値との関係が直線的でない場合に比べ、放電灯の光出力の調整が容易となる。   In the present invention, since the photocoupler is interposed between the input side of the dimming signal and the output side of the control signal, it is possible to reduce the entry and exit of conduction noise. In addition, the light output of the discharge lamp changes linearly with respect to the voltage value of the control signal, and the voltage value of the control signal changes linearly with respect to the voltage value of the dimming signal. Since the output changes linearly with respect to the voltage value of the dimming signal, the light output of the discharge lamp is smaller than when the relationship between the light output of the discharge lamp and the voltage value of the dimming signal is not linear. Adjustment is easy.

以下、本発明を実施するための最良の形態について、図面を参照しながら説明する。   The best mode for carrying out the present invention will be described below with reference to the drawings.

本実施形態は、図１に示すように、直流電源Ｖｄｃが入力され放電灯Ｌａに交流電源を供給して点灯させるインバータ回路１と、所望の光出力に対応する電圧値の直流信号である調光信号ＤＣ１が入力され調光信号ＤＣ１の電圧値に対して直線的に変化する電圧値の直流信号である制御信号を出力する信号変換回路２と、信号変換回路２の出力に応じてインバータ回路１を制御し調光信号ＤＣ１の電圧値に応じた電力を放電灯Ｌａに供給される制御駆動回路３とを備える。また、放電灯Ｌａの各フィラメントには、それぞれ放電灯Ｌａの始動時にフィラメントを予熱する予熱回路４が接続されている。   In the present embodiment, as shown in FIG. 1, an inverter circuit 1 that is supplied with a DC power source Vdc and supplies an AC power source to the discharge lamp La for lighting, and a DC signal having a voltage value corresponding to a desired light output. A signal conversion circuit 2 that receives the optical signal DC1 and outputs a control signal that is a direct current signal having a voltage value that linearly changes with respect to the voltage value of the dimming signal DC1, and an inverter circuit according to the output of the signal conversion circuit 2 1 and a control drive circuit 3 that supplies power corresponding to the voltage value of the dimming signal DC1 to the discharge lamp La. Each filament of the discharge lamp La is connected to a preheating circuit 4 for preheating the filament when the discharge lamp La is started.

インバータ回路１は、２個のスイッチング素子Ｑ１，Ｑ２の直列回路からなり両端間に直流電力Ｖｄｃが入力されるスイッチング部１１と、放電灯Ｌａとともに共振回路を構成する共振部１２とを有する。共振部１２は、放電灯Ｌａとの直列回路がスイッチング部１のローサイドのスイッチング素子Ｑ２の両端間に接続されるインダクタＬ１とコンデンサＣ５との直列回路と、一方の電極がインダクタＬ１とコンデンサＣ５との接続点に接続され他方の電極が接地されたコンデンサＣ４とからなる。すなわち、インバータ回路１は周知のハーフブリッジ形のインバータ回路であって、スイッチング素子Ｑ１，Ｑ２が交互にオンオフされると、交流電力が放電灯Ｌａに供給される。ここで、スイッチング素子Ｑ１，Ｑ２が交互にオンオフされる周波数（以下、「駆動周波数」と呼ぶ。）が、共振部１２と放電灯Ｌａとからなる共振回路の共振周波数に近いほど、放電灯Ｌａに供給される電力は高く、すなわち放電灯Ｌａの光出力は高くなる。なお、直流電力Ｖｄｃは、例えば図２に示すように、商用電源Ｖｉｎから供給された交流電力を全波整流するダイオードブリッジＤＢと、ダイオードブリッジＤＢの出力端間に接続されたインダクタＬ２とダイオードＤ１と平滑コンデンサＣ２１との直列回路と、ダイオードブリッジＤＢの両端間に接続されたコンデンサＣ２０と、ダイオードＤ１とコンデンサＣ２１との直列回路に並列に接続されたスイッチング素子Ｑ４とを備える周知の昇圧チョッパ回路から得られる。スイッチング素子Ｑ４は例えば制御駆動回路３によってオンオフされる。   The inverter circuit 1 includes a switching unit 11 that is composed of a series circuit of two switching elements Q1 and Q2, and into which DC power Vdc is input between both ends, and a resonance unit 12 that forms a resonance circuit together with the discharge lamp La. The resonance unit 12 includes a series circuit of an inductor L1 and a capacitor C5 in which a series circuit with the discharge lamp La is connected between both ends of the switching element Q2 on the low side of the switching unit 1, and one electrode is an inductor L1 and a capacitor C5. The capacitor C4 is connected to the connection point of the other and the other electrode is grounded. That is, the inverter circuit 1 is a well-known half-bridge type inverter circuit, and AC power is supplied to the discharge lamp La when the switching elements Q1, Q2 are alternately turned on and off. Here, as the frequency at which the switching elements Q1 and Q2 are alternately turned on and off (hereinafter referred to as “drive frequency”) is closer to the resonance frequency of the resonance circuit including the resonance unit 12 and the discharge lamp La, the discharge lamp La The electric power supplied to is high, that is, the light output of the discharge lamp La is high. For example, as shown in FIG. 2, the DC power Vdc includes a diode bridge DB for full-wave rectification of AC power supplied from the commercial power source Vin, and an inductor L2 and a diode D1 connected between the output terminals of the diode bridge DB. And a smoothing capacitor C21, a known step-up chopper circuit comprising a capacitor C20 connected between both ends of the diode bridge DB, and a switching element Q4 connected in parallel to the series circuit of the diode D1 and the capacitor C21. Obtained from. The switching element Q4 is turned on / off by the control drive circuit 3, for example.

信号変換回路２は、フォトカプラＰＣ１と、電圧値が時間に対して単調増加する立上りと電圧値が時間に対して単調減少する立下りとを交互に周期的に繰り返す発振信号を生成する発振回路２１と、調光信号ＤＣ１が入力されて調光信号ＤＣ１の電圧値と発振信号の電圧値との大小関係が入れ替わったときにフォトカプラＰＣ１の発光素子のオンオフを切換えることにより調光信号ＤＣ１の電圧値に応じたデューティ比でフォトカプラＰＣ１の発光素子をオンオフするパルス生成回路２２と、フォトカプラＰＣ１の出力のデューティ比に応じて電圧値が調光信号ＤＣ１の電圧値に対して直線的に変化する直流信号である制御信号を生成する制御信号生成回路２３とを備える。   The signal conversion circuit 2 generates a photocoupler PC1 and an oscillation circuit that alternately and periodically repeats a rising edge whose voltage value monotonously increases with time and a falling edge whose voltage value monotonously decreases with time. 21 and when the dimming signal DC1 is input and the magnitude relationship between the voltage value of the dimming signal DC1 and the voltage value of the oscillation signal is switched, the on / off of the light emitting element of the photocoupler PC1 is switched to turn on the dimming signal DC1. A pulse generation circuit 22 for turning on and off the light emitting element of the photocoupler PC1 with a duty ratio according to the voltage value, and a voltage value linearly with respect to the voltage value of the dimming signal DC1 according to the duty ratio of the output of the photocoupler PC1 And a control signal generation circuit 23 that generates a control signal that is a DC signal that changes.

発振回路２１は、定電流源Ｉｓにより充電されるコンデンサＣ４と、負の入力端子にコンデンサＣ４の充電電圧が入力されるとともに正の入力端子に閾値電圧Ｖｔｈが入力されたコンパレータＣＯ２とを備える。閾値電圧Ｖｔｈは、コンパレータＣＯ２の出力がＨレベルのときとＬレベルのときとで切り替わるようになっており、Ｈレベルのときの閾値電圧Ｖｔｈは調光信号の電圧値の最大値Ｖｈと略等しくしてあり、Ｌレベルのときの閾値電圧Ｖｔｈは調光信号の電圧値の最小値Ｖｌと略等しくしてある。また、コンデンサＣ４は、コンパレータＣＯ２の出力がＬレベルである期間にはダイオードＤ３と抵抗Ｒ１０とを介して放電されるようになっている。定電流源Ｉｓは、例えば図３に示すように流れる電流が互いに略等しくなるように構成された２組の入出力端子を有し各入力端子にそれぞれ定電圧Ｖｃｃ２が入力されたカレントミラー回路Ｍ１と、一端がカレントミラー回路Ｍ１の一方の出力端子に接続され他端が接地された抵抗Ｒ１４とで構成することができる。カレントミラー回路Ｍ１は、例えばペアトランジスタからなる。また、２個の抵抗Ｒ１５，Ｒ１６の直列回路の一端を定電圧Ｖｃｃ２に接続して他端を接地するとともに、低電圧側の抵抗Ｒ１６の両端間にコンデンサＣ１５を接続し、さらに抵抗Ｒ１５，１６の接続点を抵抗Ｒ１７を介してコンパレータＣＯ２の出力端子に接続すれば、コンデンサＣ１５の充電電圧を閾値電圧Ｖｔｈとして用いることができる。   The oscillation circuit 21 includes a capacitor C4 that is charged by the constant current source Is, and a comparator CO2 that receives the charging voltage of the capacitor C4 at the negative input terminal and the threshold voltage Vth at the positive input terminal. The threshold voltage Vth is switched between when the output of the comparator CO2 is at the H level and when it is at the L level. The threshold voltage Vth at the H level is substantially equal to the maximum value Vh of the voltage value of the dimming signal. The threshold voltage Vth at the L level is approximately equal to the minimum value Vl of the voltage value of the dimming signal. Further, the capacitor C4 is discharged through the diode D3 and the resistor R10 during the period when the output of the comparator CO2 is at the L level. The constant current source Is has, for example, a current mirror circuit M1 having two sets of input / output terminals configured such that flowing currents are substantially equal to each other as shown in FIG. 3, and a constant voltage Vcc2 is input to each input terminal. And a resistor R14 having one end connected to one output terminal of the current mirror circuit M1 and the other end grounded. The current mirror circuit M1 is composed of, for example, a pair transistor. One end of a series circuit of two resistors R15 and R16 is connected to the constant voltage Vcc2 and the other end is grounded. A capacitor C15 is connected between both ends of the low-voltage side resistor R16, and the resistors R15 and 16 are further connected. Is connected to the output terminal of the comparator CO2 via the resistor R17, the charging voltage of the capacitor C15 can be used as the threshold voltage Vth.

発振回路２１の動作を説明する。コンデンサＣ４が充電されていないときには、コンパレータＣＯ２の出力はＨレベルであって閾値電圧Ｖｔｈは高い側の値Ｖｈをとる。コンデンサＣ４が定電流源Ｉｓにより充電され、充電電圧が直線状に上昇して閾値電圧Ｖｈを超えると、コンパレータＣＯ２の出力はＬレベルとなり、閾値電圧Ｖｔｈは低い側の値Ｖｌに切り替わってコンデンサＣ４の放電が開始され、充電電圧はコンデンサＣ４と抵抗Ｒ１０とによって決まる時定数により曲線状に低下する。やがてコンデンサＣ４の充電電圧が閾値電圧Ｖｌを下回ると、コンパレータＣＯ２の出力がＨレベルとなって閾値電圧Ｖｔｈは高い側の値Ｖｈに切り替わり、コンデンサＣ４の充電が再び開始される。すなわち、コンデンサＣ４の充電電圧は、図４に示すように電圧値Ｖｌと電圧値Ｖｈとの間で直線状の立上りと曲線状の立下りとを一定の周期Ｔで周期的に繰り返すこととなり、この充電電圧が発振信号としてパルス生成回路２２へ出力される。なお、発振信号の波形は、定電流源Ｉｓの出力や抵抗Ｒ１０の抵抗値を適宜選択することにより、図４に示すように立上りの時間と立下りの時間とを同程度としたり、図５に示すように立上りの時間を立下りの時間に対して非常に短くしたりすることができる。   The operation of the oscillation circuit 21 will be described. When the capacitor C4 is not charged, the output of the comparator CO2 is at the H level, and the threshold voltage Vth takes the higher value Vh. When the capacitor C4 is charged by the constant current source Is and the charging voltage rises linearly and exceeds the threshold voltage Vh, the output of the comparator CO2 becomes L level, and the threshold voltage Vth is switched to the lower value Vl, and the capacitor C4 Is started, and the charging voltage decreases in a curved line by a time constant determined by the capacitor C4 and the resistor R10. When the charging voltage of the capacitor C4 eventually falls below the threshold voltage Vl, the output of the comparator CO2 becomes H level, the threshold voltage Vth is switched to the higher value Vh, and charging of the capacitor C4 is started again. That is, as shown in FIG. 4, the charging voltage of the capacitor C4 periodically repeats a linear rise and a curved fall between the voltage value Vl and the voltage value Vh with a constant period T. This charging voltage is output as an oscillation signal to the pulse generation circuit 22. The waveform of the oscillation signal can be set to have the same rise time and fall time as shown in FIG. 4 by appropriately selecting the output of the constant current source Is and the resistance value of the resistor R10, as shown in FIG. As shown in FIG. 4, the rise time can be made very short with respect to the fall time.

パルス生成回路２２は、インピーダンスＺ１を介して調光信号ＤＣ１が入力されて充電されるコンデンサＣ１と、正の入力端子にコンデンサＣ１の充電電圧が入力され負の入力端子に発振信号が入力されるコンパレータＣＯ１とを備える。フォトカプラＰＣ１の発光素子のアノードには抵抗Ｒ５を介して定電圧Ｖｃｃ２が入力されており、コンパレータＣＯ１の出力端子は抵抗Ｒ５とフォトカプラＰＣ１との接続点に接続されている。すなわち、調光信号ＤＣ１の電圧値が発振信号の電圧値を上回っている期間にはコンパレータＣＯ１の出力がＨレベルとなってフォトカプラＰＣ１がオンされ、逆に下回っている期間にはコンパレータＣＯ１の出力がＬレベルとなってフォトカプラＰＣ１がオフされる。つまり、調光信号ＤＣ１の電圧値が高いほど、高いデューティ比でフォトカプラＰＣ１がオンオフされる。   The pulse generation circuit 22 is charged with the dimming signal DC1 input through the impedance Z1, and the charging voltage of the capacitor C1 is input to the positive input terminal and the oscillation signal is input to the negative input terminal. And a comparator CO1. A constant voltage Vcc2 is input to the anode of the light emitting element of the photocoupler PC1 through the resistor R5, and the output terminal of the comparator CO1 is connected to a connection point between the resistor R5 and the photocoupler PC1. That is, when the voltage value of the dimming signal DC1 is higher than the voltage value of the oscillation signal, the output of the comparator CO1 becomes H level and the photocoupler PC1 is turned on, and conversely, the output of the comparator CO1 is lower. The output becomes L level and the photocoupler PC1 is turned off. That is, as the voltage value of the dimming signal DC1 is higher, the photocoupler PC1 is turned on / off with a higher duty ratio.

制御信号生成回路２３は、一端が定電圧Ｅ１に接続され他端がフォトカプラＰＣ１の出力側を介して接地された抵抗Ｒ６と、２個の抵抗Ｒ７，Ｒ８からなり一端が定電圧Ｅ１に接続されて他端が接地された分圧部と、分圧部の低電圧側の抵抗Ｒ８の両端間に接続された出力コンデンサＣ２と、スイッチング素子としてのトランジスタＱ３と抵抗Ｒ９との直列回路からなり出力コンデンサＣ２の両端間に接続された入力部とを備える。トランジスタＱ３のベースは、抵抗Ｒ６とフォトカプラＰＣ１との接続点に接続されている。フォトカプラＰＣ１がオフされている期間にはトランジスタＱ３がオンされて出力コンデンサＣ２の両端電圧が低くなり、フォトカプラＰＣ１がオンされている期間にはトランジスタＱ３がオフされて出力コンデンサＣ２の両端電圧が高くなるから、フォトカプラＰＣ１がオンオフされるデューティ比（以下、単に「デューティ比」と呼ぶ。）が高いほど出力コンデンサＣ２の充電電圧は高くなる。この出力コンデンサＣ２の充電電圧が制御信号として制御駆動回路３に出力される。ここで、調光信号ＤＣ１の電圧値を横軸にとりデューティ比を縦軸にとったグラフは図６（ａ）に示すように上に凸の対数関数的な曲線となり、デューティ比を横軸にとり制御信号の電圧値を縦軸にとったグラフは図６（ｂ）に示すように下に凸の指数関数的な曲線となる。これらの曲線の曲率は組合わせにより互いに相殺され、制御信号の電圧値と調光信号ＤＣ１の電圧値との関係は調光信号ＤＣ１の電圧値が取り得る値の全体にわたって直線状となる。   The control signal generation circuit 23 includes a resistor R6 having one end connected to the constant voltage E1 and the other end grounded via the output side of the photocoupler PC1, and two resistors R7 and R8, and one end connected to the constant voltage E1. And a series circuit of a voltage dividing section whose other end is grounded, an output capacitor C2 connected between both ends of the low voltage side resistor R8 of the voltage dividing section, a transistor Q3 as a switching element, and a resistor R9. And an input section connected between both ends of the output capacitor C2. The base of the transistor Q3 is connected to a connection point between the resistor R6 and the photocoupler PC1. During the period when the photocoupler PC1 is turned off, the transistor Q3 is turned on and the voltage across the output capacitor C2 becomes low. When the photocoupler PC1 is turned on, the transistor Q3 is turned off and the voltage across the output capacitor C2 is turned off. Therefore, the higher the duty ratio at which the photocoupler PC1 is turned on and off (hereinafter simply referred to as “duty ratio”), the higher the charging voltage of the output capacitor C2. The charging voltage of the output capacitor C2 is output to the control drive circuit 3 as a control signal. Here, a graph in which the voltage value of the dimming signal DC1 is plotted on the horizontal axis and the duty ratio is plotted on the vertical axis is a logarithmic curve convex upward as shown in FIG. 6A, and the duty ratio is plotted on the horizontal axis. A graph in which the voltage value of the control signal is plotted on the vertical axis is an exponential curve convex downward as shown in FIG. The curvatures of these curves cancel each other out by the combination, and the relationship between the voltage value of the control signal and the voltage value of the dimming signal DC1 is linear throughout the possible values of the voltage value of the dimming signal DC1.

制御駆動回路３は、インバータ回路１のスイッチング部１１のスイッチング素子Ｑ１，Ｑ２を交互にオンオフするドライブ回路３１と、制御信号が入力されスイッチング部１１のローサイドのスイッチング素子Ｑ２に流れる電流に応じた電圧値（以下、「検出電圧値」と呼ぶ。）を検出して検出電圧値と制御信号の電圧値との大小関係に基いた電圧信号を出力する比較演算回路３２と、比較演算回路３２から出力された電圧信号に基いてドライブ回路３１の駆動周波数を制御する制御回路３３とを有する。比較演算回路３２は、正の入力端子に制御信号が入力されるオペアンプＥＡ１を有する。ここで、スイッチング部１１のローサイドのスイッチング素子Ｑ２は抵抗Ｒ１を介して接地されており、この抵抗Ｒ１とスイッチング素子Ｑ２との接続点は抵抗Ｒ２を介してオペアンプＥＡ１の負の入力端子に接続されている。また、オペアンプＥＡ１の負の入力端子と出力端子との間にはコンデンサＣ３が接続されている。つまり、放電灯Ｌａに供給される電力すなわち放電灯Ｌａの光出力が、制御信号の電圧値に応じた一定値に維持されるように、制御回路３３は駆動周波数をフィードバック制御する。   The control drive circuit 3 includes a drive circuit 31 that alternately turns on and off the switching elements Q1 and Q2 of the switching unit 11 of the inverter circuit 1 and a voltage corresponding to a current that flows through the low-side switching element Q2 when the control signal is input. A comparison operation circuit 32 that detects a value (hereinafter referred to as a “detection voltage value”) and outputs a voltage signal based on the magnitude relationship between the detection voltage value and the voltage value of the control signal; And a control circuit 33 for controlling the drive frequency of the drive circuit 31 based on the voltage signal. The comparison operation circuit 32 includes an operational amplifier EA1 in which a control signal is input to a positive input terminal. Here, the switching element Q2 on the low side of the switching unit 11 is grounded via the resistor R1, and the connection point between the resistor R1 and the switching element Q2 is connected to the negative input terminal of the operational amplifier EA1 via the resistor R2. ing. A capacitor C3 is connected between the negative input terminal and the output terminal of the operational amplifier EA1. That is, the control circuit 33 feedback-controls the drive frequency so that the power supplied to the discharge lamp La, that is, the light output of the discharge lamp La is maintained at a constant value according to the voltage value of the control signal.

ここで、制御信号の電圧値と駆動周波数との関係は、制御信号の電圧値と放電灯Ｌａの光出力との関係が図６（ｃ）に示すように直線状となるようにしてある。既に述べたように制御信号の電圧値と調光信号ＤＣ１の電圧値との関係は直線状となっているから、調光信号ＤＣ１の電圧値と放電灯Ｌａの光出力との関係は図６（ｄ）に示すように直線状となる。従って、調光信号ＤＣ１の調整による放電灯Ｌａの光出力の調整が容易となっている。また、調光信号ＤＣ１の電圧値が取り得る範囲の全体にわたって制御信号の電圧値は調光信号ＤＣ１の電圧値に対して直線状に変化し、且つ制御信号の電圧値が変化すれば必ず放電灯Ｌａの光出力が変化するから、調光信号ＤＣ１の電圧値が変化すれば必ず放電灯Ｌａの光出力が変化することになる。つまり、例えば調光信号ＤＣ１が使用者によって回動操作又はスライド操作されるハンドルを有しハンドルの位置に応じた電圧値の調光信号を出力する制御装置（図示せず）から出力されるものである場合、ハンドルの可動範囲の全体にわたって放電灯Ｌａの光出力の変化幅がハンドルの操作量に比例することになり、良好な操作性が得られる。なお、調光信号ＤＣ１の電圧値とデューティ比との関係と、デューティ比と制御信号の電圧値との関係とをともに直線状としても、同様の効果が得られる。   Here, the relationship between the voltage value of the control signal and the drive frequency is such that the relationship between the voltage value of the control signal and the light output of the discharge lamp La is linear as shown in FIG. Since the relationship between the voltage value of the control signal and the voltage value of the dimming signal DC1 is linear as already described, the relationship between the voltage value of the dimming signal DC1 and the light output of the discharge lamp La is shown in FIG. As shown in FIG. Therefore, the light output of the discharge lamp La can be easily adjusted by adjusting the dimming signal DC1. Further, the voltage value of the control signal changes linearly with respect to the voltage value of the dimming signal DC1 over the entire range that the voltage value of the dimming signal DC1 can take, and is always released if the voltage value of the control signal changes. Since the light output of the electric lamp La changes, the light output of the discharge lamp La always changes whenever the voltage value of the dimming signal DC1 changes. That is, for example, the dimming signal DC1 is output from a control device (not shown) that has a handle that is rotated or slid by a user and that outputs a dimming signal having a voltage value corresponding to the position of the handle. In this case, the change width of the light output of the discharge lamp La is proportional to the operation amount of the handle over the entire movable range of the handle, and good operability can be obtained. The same effect can be obtained even if the relationship between the voltage value of the dimming signal DC1 and the duty ratio and the relationship between the duty ratio and the voltage value of the control signal are both linear.

上記構成によれば、パルス生成回路２２と制御信号生成回路２３との間をフォトカプラＰＣ１によって電気的に絶縁しているから、調光信号ＤＣ１を直接制御信号として用いる場合に比べて伝導ノイズが出入りしにくくなっている。   According to the above configuration, since the pulse generation circuit 22 and the control signal generation circuit 23 are electrically insulated by the photocoupler PC1, the conduction noise is smaller than when the dimming signal DC1 is directly used as the control signal. It is difficult to get in and out.

また、デューティ比が０〜１という限られた値しか取り得ないことにより、制御信号の電圧値が取り得る範囲は制限されるから、仮に調光信号ＤＣ１として過大な電圧値や過小な電圧値の直流信号が入力されても、制御信号の電圧値が過大な値や過小な値となることがない。従って、制御信号の電圧値の範囲を制限するためのクランプ回路が不要である。   Moreover, since the range in which the voltage value of the control signal can be taken is limited because the duty ratio can take only a limited value of 0 to 1, it is assumed that the dimming signal DC1 has an excessive voltage value or an excessive voltage value. Even if a DC signal is input, the voltage value of the control signal does not become an excessive value or an excessive value. Therefore, a clamp circuit for limiting the voltage value range of the control signal is not necessary.

さらに、制御信号の電圧値が取り得る範囲は制御信号生成部の抵抗Ｒ７〜Ｒ９の抵抗値によってのみ決定されるので、制御信号の電圧値の範囲の下限を放電灯Ｌａを点灯可能な値とし、且つ制御信号の電圧値の範囲の上限を回路部品に過大な負荷がかからない程度とするには、抵抗Ｒ７〜Ｒ９の抵抗値を選択するだけでよいから設計が容易である。   Furthermore, since the range that the voltage value of the control signal can take is determined only by the resistance values of the resistors R7 to R9 of the control signal generator, the lower limit of the range of the voltage value of the control signal is a value that can light the discharge lamp La. In order to set the upper limit of the voltage value range of the control signal to such an extent that an excessive load is not applied to the circuit components, the design is easy because it is only necessary to select the resistance values of the resistors R7 to R9.

なお、図７に示すように、発振回路２１においてコンデンサＣ４と定電流源Ｉｓとの間に、コンパレータＣＯ２の出力がＨレベルのときにオンされＬレベルのときにオフされるスイッチＳＷを追加してもよい。この構成を採用すれば、発振信号の立下りがより急峻になる。   As shown in FIG. 7, a switch SW that is turned on when the output of the comparator CO2 is at the H level and turned off when the output is at the L level is added between the capacitor C4 and the constant current source Is in the oscillation circuit 21. May be. By adopting this configuration, the fall of the oscillation signal becomes steeper.

また、図８に示すように、制御信号生成回路２３において入力部を構成する抵抗Ｒ９に、負の温度特性を有するサーミスタＮＴＣ１を直列に接続してもよい。この場合、横軸にフォトカプラＰＣ１のデューティ比をとり縦軸に制御信号の電圧値をとったグラフは常温時には図９に曲線Ｌｎで示すグラフとなるのに対し、温度がより高い高温時には曲線Ｌｈで示すグラフとなり、温度がより低い低温時には曲線Ｌｌで示すグラフとなる。すなわち、制御信号の電圧値の上限Ｖｕは温度に関わらず略一定となるのに対し、下限Ｖｂｌ，Ｖｂｎ，Ｖｂｈは温度の低下に伴って高くなる。この構成によれば、低温時には放電灯Ｌａに供給される電力の最低値が高温時よりも高い値に確保されることになるから、低温時の放電灯Ｌａのちらつきや立ち消えの発生を抑えることができる。   Further, as shown in FIG. 8, a thermistor NTC1 having negative temperature characteristics may be connected in series to a resistor R9 that constitutes an input unit in the control signal generation circuit 23. In this case, the graph in which the horizontal axis represents the duty ratio of the photocoupler PC1 and the vertical axis represents the voltage value of the control signal is a graph indicated by a curve Ln in FIG. The graph is indicated by Lh, and the graph is indicated by the curve L1 when the temperature is lower. That is, the upper limit Vu of the voltage value of the control signal is substantially constant regardless of the temperature, whereas the lower limits Vbl, Vbn, Vbh increase with a decrease in temperature. According to this configuration, since the minimum value of the electric power supplied to the discharge lamp La is ensured at a higher value at a low temperature than at a high temperature, the occurrence of flickering or extinction of the discharge lamp La at a low temperature is suppressed. Can do.

さらに、発振回路２１として、図１０に示すように立上りが複数の直線からなる折れ線である発振信号を出力するものを用いてもよい。このような発振信号は、例えば破線で示すようなそれぞれ立上りの傾きが異なるのこぎり波を生成する複数個の発振回路を、それぞれ出力端にダイオードを接続した上で互いに並列に接続するなど、複数個の発振回路の出力のうち最も出力電圧が高いものが出力されるように構成することにより得ることができる。この場合、発振回路２１として図１１に示すように発振信号の立ち上がりの曲線がより多くの直線で構成されるものを用いれば、発振信号の波形を制御信号生成回路２３の特性により合致させ、調光信号ＤＣ１と制御信号との関係すなわち調光信号ＤＣ１と放電灯Ｌａの光出力との関係をより直線的として、放電灯Ｌａの光出力の調整をより容易とすることができる。   Further, as the oscillation circuit 21, a circuit that outputs an oscillation signal whose rising edge is a broken line composed of a plurality of straight lines as shown in FIG. 10 may be used. Such oscillating signals include a plurality of oscillating circuits that generate sawtooth waves having different rising slopes as indicated by broken lines, for example, by connecting diodes at their output ends and connecting them in parallel to each other. It is possible to obtain the output circuit having the highest output voltage. In this case, if an oscillation circuit 21 having a rising curve of the oscillation signal composed of more straight lines as shown in FIG. 11 is used, the waveform of the oscillation signal is matched with the characteristics of the control signal generation circuit 23 and adjusted. The relationship between the light signal DC1 and the control signal, that is, the relationship between the light control signal DC1 and the light output of the discharge lamp La can be made more linear, and the light output of the discharge lamp La can be adjusted more easily.

また、制御信号生成回路２３において、図１２に示すように、トランジスタＱ３を設ける代わりに、抵抗Ｒ６とフォトカプラＰＣ１との接続点をバッファＶｓと抵抗Ｒ９とを介して入力コンデンサＣ２に接続し、分圧部を設ける代わりに、制御信号の電圧値が所定の値を下回ることを防止するクランプ回路２３ａを設けてもよい。   In the control signal generation circuit 23, as shown in FIG. 12, instead of providing the transistor Q3, the connection point between the resistor R6 and the photocoupler PC1 is connected to the input capacitor C2 via the buffer Vs and the resistor R9. Instead of providing the voltage divider, a clamp circuit 23a that prevents the voltage value of the control signal from falling below a predetermined value may be provided.

さらに、図１３に示すように、調光信号ＤＣ１に一定の電圧Ｖｒｅｆを加えたものをパルス生成回路のコンパレータＣＯ１に入力するようにしてもよい。   Furthermore, as shown in FIG. 13, a signal obtained by adding a constant voltage Vref to the dimming signal DC1 may be input to the comparator CO1 of the pulse generation circuit.

また、図１４に示すように、パルス生成回路２２において、正の入力端子に一定の電圧Ｖｒｅｆ２が入力され負の入力端子に抵抗Ｒ２１を介して調光信号ＤＣ１が入力されるオペアンプＥＡ２と、オペアンプＥＡ２の負の入力端子と出力端子との間に接続された抵抗Ｒ２２とからなる反転増幅器により、調光信号ＤＣ１を反転増幅してコンパレータＣＯ１の負の入力端子に入力し、発振信号をコンパレータＣＯ１の正の入力端子に入力するようにしてもよい。   As shown in FIG. 14, in the pulse generation circuit 22, an operational amplifier EA2 in which a constant voltage Vref2 is input to a positive input terminal and a dimming signal DC1 is input to a negative input terminal via a resistor R21, and an operational amplifier The dimming signal DC1 is inverted and amplified by an inverting amplifier including a resistor R22 connected between the negative input terminal and the output terminal of the EA2, and is input to the negative input terminal of the comparator CO1, and the oscillation signal is input to the comparator CO1. You may make it input into the positive input terminal.

ここで、デューティ比が０であるときに制御信号の電圧値が０Ｖとなる図１２〜図１４の例において制御信号の電圧値として０Ｖが適切な値でない場合のように、デューティ比によっては制御信号の電圧値が適切でない値を取り得る場合には、調光信号ＤＣ１の電圧値が取り得る範囲に対して発振信号の波形や振幅を適宜選択することによりデューティ比が取り得る範囲を制限すればよいが、図１２〜図１４の例では、クランプ回路２３ａを設けたことにより、制御信号の電圧値が過小な値となることを確実に防止している。   Here, when the duty ratio is 0, the voltage value of the control signal is 0 V. In the examples of FIGS. 12 to 14, as in the case where 0 V is not an appropriate value as the voltage value of the control signal, control is performed depending on the duty ratio. When the voltage value of the signal can take an inappropriate value, the range in which the duty ratio can be taken is limited by appropriately selecting the waveform and amplitude of the oscillation signal with respect to the range in which the voltage value of the dimming signal DC1 can take. However, in the examples of FIGS. 12 to 14, the provision of the clamp circuit 23a reliably prevents the voltage value of the control signal from becoming an excessively small value.

上記の放電灯点灯装置は、図１５に示すように、放電灯Ｌａが取付けられるソケット５１を有し放電灯点灯装置を収納して天井面などの造営面に取付けられる器具本体５を備える照明器具に用いることができる。本実施形態の放電灯点灯装置では伝導ノイズの出入りが抑制されるから、上記の照明器具は、１個の制御装置（図示せず）から出力された調光信号ＤＣ１を複数個の放電灯点灯装置に入力するような照明システムでの使用に適する。   As shown in FIG. 15, the discharge lamp lighting device includes a socket 51 to which the discharge lamp La is attached, and includes a fixture body 5 that houses the discharge lamp lighting device and is attached to a construction surface such as a ceiling surface. Can be used. Since the discharge lamp lighting device according to the present embodiment suppresses the entry and exit of conduction noise, the above-mentioned lighting fixture uses a dimming signal DC1 output from one control device (not shown) to light a plurality of discharge lamps. Suitable for use in lighting systems that input to the device.

本発明の実施形態を示す回路ブロック図である。It is a circuit block diagram showing an embodiment of the present invention. 同上のインバータ回路に入力される直流電力を生成する回路の一例を示す回路図である。It is a circuit diagram which shows an example of the circuit which produces | generates the direct-current power input into an inverter circuit same as the above. 同上の信号変換回路の例を示す回路図である。It is a circuit diagram which shows the example of a signal conversion circuit same as the above. 同上の発振回路の動作の一例を示す説明図である。It is explanatory drawing which shows an example of operation | movement of an oscillation circuit same as the above. 同上の発振回路の動作の別の例を示す説明図である。It is explanatory drawing which shows another example of operation | movement of an oscillation circuit same as the above. 同上の動作を示す説明図であり、（ａ）は調光信号の電圧値とフォトカプラがオンオフされるデューティ比との関係を示し、（ｂ）はフォトカプラがオンオフされるデューティ比と制御信号の電圧値との関係を示し、（ｃ）は制御信号の電圧値と放電灯の光出力との関係を示し、（ｄ）は調光信号の電圧値と放電灯の光出力との関係を示す。It is explanatory drawing which shows operation | movement same as the above, (a) shows the relationship between the voltage value of a light control signal, and the duty ratio by which a photocoupler is turned on-off, (b) is the duty ratio by which a photocoupler is turned on-off, and a control signal (C) shows the relationship between the voltage value of the control signal and the light output of the discharge lamp, and (d) shows the relationship between the voltage value of the dimming signal and the light output of the discharge lamp. Show. 同上の信号変換回路の別の例を示す回路図である。It is a circuit diagram which shows another example of a signal conversion circuit same as the above. 同上の信号変換回路の更に別の例を示す回路図である。It is a circuit diagram which shows another example of a signal conversion circuit same as the above. 図８の例の信号変換回路においてフォトカプラがオンオフされるデューティ比と制御信号の電圧値との関係を示す説明図である。FIG. 9 is an explanatory diagram illustrating a relationship between a duty ratio at which a photocoupler is turned on / off and a voltage value of a control signal in the signal conversion circuit in the example of FIG. 8. 同上の別の形態における発振回路の動作を示す説明図である。It is explanatory drawing which shows operation | movement of the oscillation circuit in another form same as the above. 同上の更に別の形態における発振回路の動作を示す説明図である。It is explanatory drawing which shows operation | movement of the oscillation circuit in another form same as the above. 同上の信号変換回路の別の例を示す回路ブロック図である。It is a circuit block diagram which shows another example of a signal conversion circuit same as the above. 同上の信号変換回路の更に別の例を示す回路ブロック図である。It is a circuit block diagram which shows another example of a signal conversion circuit same as the above. 同上の信号変換回路の別の例を示す回路ブロック図である。It is a circuit block diagram which shows another example of a signal conversion circuit same as the above. 同上を用いた照明器具の一例を示す斜視図である。It is a perspective view which shows an example of the lighting fixture using the same.

符号の説明Explanation of symbols

１ インバータ回路
１１ スイッチング部
１２ 共振部
２１ 発振回路
２２ パルス生成回路
２３ 制御信号生成回路
３１ ドライブ回路
３２ 比較演算回路
３３ 制御回路
Ｌａ 放電灯
ＰＣ１ フォトカプラ DESCRIPTION OF SYMBOLS 1 Inverter circuit 11 Switching part 12 Resonant part 21 Oscillation circuit 22 Pulse generation circuit 23 Control signal generation circuit 31 Drive circuit 32 Comparison operation circuit 33 Control circuit La Discharge lamp PC1 Photocoupler

Claims (11)

フォトカプラと、電圧値が時間に対して単調増加する立上りと電圧値が時間に対して単調減少する立下りとを交互に周期的に繰り返す発振信号を生成する発振回路と、所望の光出力に対応する電圧値の直流信号である調光信号が入力されて調光信号の電圧値と発振信号の電圧値との大小関係が入れ替わったときにフォトカプラの発光素子のオンオフを切換えることにより調光信号の電圧値に応じたデューティ比でフォトカプラの発光素子をオンオフするパルス生成回路と、フォトカプラの出力のデューティ比に応じて電圧値が調光信号の電圧値に対して直線的に変化する直流信号である制御信号を生成する制御信号生成回路と、２個のスイッチング素子の直列回路からなり両端間に直流電力が入力されるスイッチング部とスイッチング部の一方のスイッチング素子の両端間に接続され放電灯とともに共振回路を構成する共振部とを有するインバータ回路と、インバータ回路のスイッチング部のスイッチング素子を交互にオンオフするドライブ回路と、放電灯に供給される電力に対応した電圧値を検出するとともに検出された電圧値と制御信号の電圧値との大小関係に応じた出力を生成する比較演算回路と、放電灯の光出力が制御信号の電圧値に対して直線的に変化するようにドライブ回路がスイッチング素子をオンオフする周波数を比較演算回路の出力に応じて制御する制御回路とを備えることを特徴とする放電灯点灯装置。   A photocoupler, an oscillation circuit that generates an oscillation signal that alternately and periodically repeats a rise in which the voltage value monotonously increases with time and a fall in which the voltage value monotonously decreases with time, and a desired optical output When a dimming signal, which is a DC signal with a corresponding voltage value, is input and the magnitude relationship between the voltage value of the dimming signal and the voltage value of the oscillation signal is switched, dimming is performed by switching on and off the light emitting element of the photocoupler. A pulse generation circuit for turning on and off the light emitting element of the photocoupler with a duty ratio according to the voltage value of the signal, and the voltage value linearly changes with respect to the voltage value of the dimming signal according to the duty ratio of the output of the photocoupler A control signal generation circuit that generates a control signal that is a DC signal, and a switching unit that includes a series circuit of two switching elements and receives DC power between both ends. An inverter circuit having a resonance unit that is connected between both ends of the switching element and constitutes a resonance circuit together with the discharge lamp, a drive circuit that alternately turns on and off the switching element of the switching unit of the inverter circuit, and power supplied to the discharge lamp And a comparison operation circuit that generates an output corresponding to the magnitude relationship between the detected voltage value and the voltage value of the control signal, and the light output of the discharge lamp with respect to the voltage value of the control signal A discharge lamp lighting device comprising: a control circuit that controls a frequency at which the drive circuit turns on and off the switching element so as to change linearly according to an output of the comparison operation circuit. 制御信号生成回路は、２個の抵抗の直列回路からなり両端間に定電圧が入力される分圧部と、分圧部の一方の抵抗の両端間に接続された出力コンデンサと、フォトカプラの出力によってオンオフされるスイッチング素子と抵抗との直列回路からなり出力コンデンサの両端間に接続された入力部とを有し、出力コンデンサの充電電圧を制御信号の電圧値とすることを特徴とする請求項１記載の放電灯点灯装置。   The control signal generation circuit is composed of a series circuit of two resistors, a voltage dividing unit to which a constant voltage is input between both ends, an output capacitor connected between both ends of one resistance of the voltage dividing unit, and a photocoupler An input unit comprising a series circuit of a switching element that is turned on and off by an output and a resistor and connected between both ends of the output capacitor, wherein the charging voltage of the output capacitor is used as the voltage value of the control signal. Item 2. A discharge lamp lighting device according to Item 1. 発振信号の電圧値は立上り時と立下り時との一方では時間に対して直線的に変化し、他方では時間に対して出力コンデンサの放電特性に応じて曲線的に変化することを特徴とする請求項２記載の放電灯点灯装置。   The voltage value of the oscillation signal changes linearly with respect to time at one of the rising and falling times, and changes with a curve according to the discharge characteristics of the output capacitor with respect to time. The discharge lamp lighting device according to claim 2. 発振信号の電圧値の立上り時又は立下り時の曲線は、互いに傾きが異なる複数本の直線で構成された折れ線からなることを特徴とする請求項３記載の放電灯点灯装置。   4. The discharge lamp lighting device according to claim 3, wherein the rising or falling curve of the voltage value of the oscillation signal comprises a broken line composed of a plurality of straight lines having different inclinations. 発振信号の電圧値の立上り時又は立下り時の曲線は、互いに傾きが異なる３本以上の直線で構成された折れ線からなることを特徴とする請求項４記載の放電灯点灯装置。   5. The discharge lamp lighting device according to claim 4, wherein the rising or falling curve of the voltage value of the oscillation signal is formed by a broken line composed of three or more straight lines having different inclinations. 発振信号の電圧値の最大値及び最小値は、それぞれ、調光信号の電圧値の最大値及び最小値に略等しいことを特徴とする請求項１〜５のいずれか記載の放電灯点灯装置。   6. The discharge lamp lighting device according to claim 1, wherein the maximum value and the minimum value of the voltage value of the oscillation signal are substantially equal to the maximum value and the minimum value of the voltage value of the dimming signal, respectively. 制御信号生成回路の入力部は、負の温度特性を有してスイッチング素子に直列に接続されたサーミスタを有し、インバータ回路から放電灯に供給される電力は、制御信号の電圧値に対して単調に増加することを特徴とする請求項２記載の放電灯点灯装置。   The input part of the control signal generation circuit has a thermistor having a negative temperature characteristic and connected in series to the switching element, and the power supplied from the inverter circuit to the discharge lamp is relative to the voltage value of the control signal. The discharge lamp lighting device according to claim 2, which monotonously increases. フォトカプラの発光素子がオンオフされるデューティ比が取り得る上限値と下限値との一方が制御信号の上限値に対応し、他方が制御信号の下限値に対応することを特徴とする請求項１〜７のいずれか記載の放電灯点灯装置。   2. One of an upper limit value and a lower limit value that can be taken by a duty ratio at which a light emitting element of a photocoupler is turned on / off corresponds to an upper limit value of a control signal, and the other corresponds to a lower limit value of the control signal. The discharge lamp lighting device according to any one of? 放電灯の光出力が調光信号の電圧値に対して単調増加することを特徴とする請求項１〜８のいずれか記載の放電灯点灯装置。   9. The discharge lamp lighting device according to claim 1, wherein the light output of the discharge lamp monotonously increases with respect to the voltage value of the dimming signal. 請求項１〜９のいずれかに記載の放電灯点灯装置と、放電灯点灯装置を収納した器具本体とを備えることを特徴とする照明器具。   A lighting fixture comprising: the discharge lamp lighting device according to any one of claims 1 to 9; and a fixture main body housing the discharge lamp lighting device. 請求項１０記載の複数個の照明器具と、各照明器具にそれぞれ調光信号を入力する制御装置とを備えることを特徴とする照明システム。   11. A lighting system comprising: the plurality of lighting fixtures according to claim 10; and a control device that inputs a dimming signal to each lighting fixture.
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JPS5615600U (en) * 1979-07-17 1981-02-10
JPH0289799U (en) * 1988-12-28 1990-07-17
JPH02284390A (en) * 1989-04-25 1990-11-21 Matsushita Electric Works Ltd Lighting load controlling device
JPH02284391A (en) * 1989-04-25 1990-11-21 Matsushita Electric Works Ltd Lighting load controlling device
JPH07106090A (en) * 1993-09-30 1995-04-21 Toshiba Lighting & Technol Corp Discharge lamp lighting device and lighting system
JP2003317993A (en) * 2003-04-23 2003-11-07 Mitsubishi Electric Corp Lighting system

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS5539690U (en) * 1978-09-08 1980-03-14
JPS5615600U (en) * 1979-07-17 1981-02-10
JPH0289799U (en) * 1988-12-28 1990-07-17
JPH02284390A (en) * 1989-04-25 1990-11-21 Matsushita Electric Works Ltd Lighting load controlling device
JPH02284391A (en) * 1989-04-25 1990-11-21 Matsushita Electric Works Ltd Lighting load controlling device
JPH07106090A (en) * 1993-09-30 1995-04-21 Toshiba Lighting & Technol Corp Discharge lamp lighting device and lighting system
JP2003317993A (en) * 2003-04-23 2003-11-07 Mitsubishi Electric Corp Lighting system

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